CN103312151A - 直流连接电路 - Google Patents

直流连接电路 Download PDF

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CN103312151A
CN103312151A CN2013100668884A CN201310066888A CN103312151A CN 103312151 A CN103312151 A CN 103312151A CN 2013100668884 A CN2013100668884 A CN 2013100668884A CN 201310066888 A CN201310066888 A CN 201310066888A CN 103312151 A CN103312151 A CN 103312151A
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CN103312151B (zh
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M·盖兹特
瓦迪姆·卢博米尔斯基
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SolarEdge Technologies Ltd
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    • G—PHYSICS
    • G05—CONTROLLING; REGULATING
    • G05F—SYSTEMS FOR REGULATING ELECTRIC OR MAGNETIC VARIABLES
    • G05F3/00—Non-retroactive systems for regulating electric variables by using an uncontrolled element, or an uncontrolled combination of elements, such element or such combination having self-regulating properties
    • G05F3/02—Regulating voltage or current
    • G05F3/08—Regulating voltage or current wherein the variable is dc
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02S—GENERATION OF ELECTRIC POWER BY CONVERSION OF INFRARED RADIATION, VISIBLE LIGHT OR ULTRAVIOLET LIGHT, e.g. USING PHOTOVOLTAIC [PV] MODULES
    • H02S40/00—Components or accessories in combination with PV modules, not provided for in groups H02S10/00 - H02S30/00
    • H02S40/30—Electrical components
    • H02S40/32—Electrical components comprising DC/AC inverter means associated with the PV module itself, e.g. AC modules
    • H02J3/383—
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
    • H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
    • H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
    • H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
    • H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
    • H02M3/158—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
    • H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
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    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02E—REDUCTION OF GREENHOUSE GAS [GHG] EMISSIONS, RELATED TO ENERGY GENERATION, TRANSMISSION OR DISTRIBUTION
    • Y02E10/00—Energy generation through renewable energy sources
    • Y02E10/50—Photovoltaic [PV] energy
    • Y02E10/56—Power conversion systems, e.g. maximum power point trackers

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  • Electromagnetism (AREA)
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Abstract

本发明涉及直流连接电路。根据本发明的特征，公开了用于将来自浮动DC电力源的电力转换成双直流（DC）输出的电子电路。该电子电路可包括正输入端子和负输入端子，其可连接到浮动DC电力源。双DC输出可以连接到DC/AC逆变器的输入端。正输出端子连接到DC/AC逆变器的正输入端子，而负输出端子和接地端子可被连接到DC/AC逆变器的输入端。第一电力开关和第二电力开关的串联连接是横跨正输入端子和负输入端子连接的。负回路可以包括连接在负输入端子和负输出端子之间的第一二极管和第二二极管。谐振电路可以连接在所述串联连接和所述负回路之间。

Description

直流连接电路
技术领域
本公开的方面涉及分布式电力系统，特别涉及光伏电力收集系统，且更特别地，涉及连接在光伏阵列和三相逆变器电路之间的直流电路。
背景技术
在配置为给单相或三相交流（AC）电力网馈电的常规光伏电力收集系统中，双（正和负）直流（DC）电力可以首先从太阳能板产生。由双（正和负）直流（DC）电力供电的三相逆变器产生在三相逆变器输出端处的三相AC电力。通常，通过串联连接太阳能板，足够高的DC电压可被提供至三相逆变器的输入端。然而，为了增加总的电力转换效率，逆变器所需要的正和负DC轨的总和可能超过600伏。
在北美，超过600伏的电压输入可引起安全机构认证的问题。避免安全问题的方法可包括将小于600伏的电压输入到增压电路或变压器隔离电路，以内部地产生用于逆变器输入端的双DC轨。额外的增压电路或变压器隔离电路格外地增加费用和复杂性，因为额外的电力转换器模块通常要求专设的控制和保护功能。此外，增压电路或变压器隔离电路还可以产生电磁干扰（EMI），并可以引起DC电力到三相AC电力的转换的总的效率的下降。
因此，存在一种需求，即，具有带有低电压输入的DC连接电路，并且其会是有利的，所述带有低电压输入的DC连接电路不引起DC电力到三相AC电力的转换的总的效率的显著下降，并提供到AC逆变器的足够高的DC输入电压，以产生逆变器的所需要的幅度的AC输出。
发明内容
实施方式包括一种电子电路，用于将来自浮动DC电力源的电力转换为双直流（DC）输出。电子电路可包括正输入端子和负输入端子，其可连接到浮动DC电力源。正输出端子和负输出端子以及接地端子可连接到双DC输出。正输出端子可连接到正输入端子。正输出端子、负输出端子和接地端子可以给三相逆变器馈电。电荷存储器件可以并联连接到正输入端子和负输入端子。电荷存储器件可以从正输入端子和负输入端子充电。
第一电力开关和第二电力开关的串联连接是横跨正输入端子和负输入端子连接的。串联连接可提供在第一电力开关和第二电力开关之间的电力输出端子和在负输出端子和负输入端子之间的负电流回路。串联连接还可包括第一电力开关的第一电力端子，其连接到正输出端子和正输入端子。第一电力开关的第二电力端子连接到第二电力开关的第三电力端子，以提供电力输出端子。第二电力开关的第四电力端子连接到负输入端子。
负回路可包括第一二极管和第二二极管。第一二极管的阴极连接到负输入端子，且第二二极管的阴极连接到第一二极管的阳极，以提供二极管端子。第二二极管的阳极连接到负输出端子，且谐振电路可以连接在电力输出端子和二极管端子之间。
谐振电路可适于通过施加到第一电力开关和第二电力开关的各自的驱动端子的交替切换信号，交替地给谐振电路充电和将谐振电路放电到负输出端子。交替切换信号导致第一电力开关和第二电力开关以实质上零电流开启和关闭。
另外的实施方式包括第三电力开关和第四电力开关的第二串联连接。该第二串联连接可包括第三电力开关的第五电力端子，其连接到正输出端子和正输入端子。第三电力开关的第六电力端子连接到第四电力开关的第七电力端子，以给出第二电力输出端子。第四电力开关的第八电力端子连接到负输入端子。第三二极管和第四二极管串联连接在负输出端子和负输入端子之间。第三二极管的阴极连接到负输入端子。第四二极管的阴极连接到第三二极管的阳极，以给出第二二极管端子。第四二极管的阳极连接到负输出端子。第二谐振电路连接在第二电力输出端子和第二二极管端子之间。通过施加到第三电力开关和第四电力开关的各自的驱动端子的交替切换信号，第二谐振电路可适于交替地给第二谐振电路充电和将第二谐振电路放电到负输出端子。交替切换信号导致第三电力开关和第四电力开关以实质上零电流开启和关闭。
实施方式包括一种方法，用于将来自浮动DC电力源的电力转换成关于地面接地的双直流（DC）输出。浮动DC电力源可以包括正输入端子和负输入端子。双DC输出可以包括正输出端子、负输出端子和接地端子。正输入端子连接到正输出端子。第二二极管的阴极和第一二极管的阳极可以被连接在一起。第二二极管的阳极连接到负输出端子，且第一二极管的阴极连接到负输入端子。所述方法在施加到第一电力开关的第一切换周期给谐振电路充电。第一切换周期通过第一二极管将谐振电路横跨正输入端子和负输入端子连接。谐振电路在施加到第二电力开关的第二切换周期中放电。第二切换周期通过第二二极管将谐振电路串联连接在负输入端子和负输出端子之间。
实施方式包括一种电子电路，用于将来自浮动DC电力源的电力转换到双直流(DC)输出。电子电路可包括正输入端子和负输入端子，其能够被连接到浮动DC电力源。正输出端子和负输出端子以及接地端子可被连接到双DC输出。负输出端子可连接到负输入端子。正输出端子、负输出端子和接地端子可以给三相逆变器馈电。电荷存储器件可以并联连接到正输入端子和负输入端子。电荷存储器件可以从正输入端子和负输入端子被充电。
第一电力开关和第二电力开关的串联连接是横跨正输入端子和负输入端子连接的。该串联连接可以提供在第一电力开关和第二电力开关之间的电力输出端子以及在正输出端子和正输入端子之间的正电流回路。串联连接还可包括第一电力开关的第一电力端子，其连接到正输出端子和正输入端子。第一电力开关的第二电力端子连接到第二电力开关的第三电力端子，以提供电力输出端子。第二电力开关的第四电力端子连接到负输入端子。
正回路可以第一二极管和第二二极管。第一二极管的阴极连接到正输出端子，且第二二极管的阴极连接到第一二极管的阳极，以提供二极管端子。第二二极管的阳极连接到正输入端子，且谐振电路可以连接在电力输出端子和二极管端子之间。
通过施加到第一电力开关和第二电力开关的各自的驱动端子的交替切换信号，谐振电路可适于交替地给谐振电路充电和将谐振电路放电到正输出端子。交替切换信号导致第一电力开关和第二电力开关以实质上零电流开启和关闭。
另外的实施方式包括第三电力开关和第四电力开关的第二串联连接。该第二串联连接可包括第三电力开关的第五电力端子，其连接到正输出端子和正输入端子。第三电力开关的第六电力端子连接到第四电力开关的第七电力端子，以给出第二电力输出端子。第四电力开关的第八电力端子连接到负输入端子。第三二极管和第四二极管串联连接在正输出端子和正输入端子之间。第三二极管的阴极连接到正输出端子。第四二极管的阴极连接到第三二极管的阳极，以给出第二二极管端子。第四二极管的阳极连接到正输入端子。第二谐振电路连接在第二电力输出端子和第二二极管端子之间。通过施加到第三电力开关和第四电力开关的各自的驱动端子的交替切换信号，第二谐振电路可适于交替地给第二谐振电路充电和将第二谐振电路放电到正输出端子。交替切换信号导致第三电力开关和第四电力开关以实质上零电流开启和关闭。
附图说明
作为例子而非限制，在附图中示出某些实施方式，其中在全文中相同的参考数字指相同的元件：
图1示出了根据常规技术的光伏电力收集系统。
图2示出了根据本文所描述的一个或更多实施方式的电力收集系统。
图3示出了根据本文所描述的一个或更多实施方式的用于图2中所示的电力收集系统的方法。
图4a示出了根据本文所描述的一个或更多实施方式的电路。
图4b示出了根据本文所描述的一个或更多实施方式的、可以是在图4a中示出的电路的交织拓扑结构形式的电路。
图4c示出了根据本文所描述的一个或更多实施方式的方法。
具体实施方式
现在详细参考本发明的特征，本发明的例子在附图中示出。下面描述特征以通过参考附图来解释本发明。
在详细解释本发明的特征之前，应理解，本发明在其应用中不限于在下面的描述中阐述的或在附图中示出的部件的设计和布置的细节。本发明能够有其它特征或能够以各种方式被实践或实现。此外，应理解，本文所使用的措辞和术语是为了描述的目的，且不应被视为限制性的。例如，这里使用的不定冠词“a”和“an”，例如在“开关（a switch）”“DC输出（aDC output）”具有“一个或更多”的意思，例如“一个或更多开关”和“一个或更多DC输出”。
应注意，虽然本文的讨论主要涉及光伏系统，本发明可作为非限制性的例子可选地使用其它分布式电力系统包括（但不限于）风力涡轮机、水力涡轮机、燃料电池、存储系统（例如电池、超导飞轮和电容器）和机械设备（包括常规和可变速度柴油发动机、斯特林发动机、气体涡轮机和微型涡轮机）来配置。
如本文使用的术语“开关”指以下项中的任一个：可控硅整流器(SCR)、绝缘栅双极型晶体管(IGBT)、双极结晶体管(BJT)、场效应管(FET)、结型场效应管(JFET)、机械操作的单刀双掷开关(SPDT)、SPDT电气继电器、SPDT簧片继电器、SPDT固态继电器、绝缘栅场效应晶体管(IGFET)、双向触发二极管(DIAC)和三端双向可控硅开关元件(TRIAC)。
在本文中使用的术语“开关”指三端子器件。三个端子中的两个在这里指“电力端子”，并等同于例如BJT的集电极和发射极、或FET的源极或漏极。三端子器件中的剩余的“驱动端子”等同于例如BJT的基极或FET的栅极。
本文使用的术语“正电流”指从电路中的较高电势点到电路中的较低电势不同点的电流流动方向。本文使用的术语“负电流”指从负DC输出到负输入端子的返回电流流动。
本文使用的术语“零电流切换”（或“ZCS”）是在开关被打开或闭合之前通过开关的电流降低至实质上零安培。
本文使用的术语“电力转换器”适用于DC到DC转换器、AC到DC转换器、DC到AC逆变器、降压转换器、升压转换器、降压-升压转换器、全桥式转换器和半桥式转换器或本领域已知的任何其它类型的电力转换/反转。
本文使用的术语“电力网”和“主电网”是可互换的，并且指由供电公司提供的交流（AC）电力源和/或从分布式电力系统提供的AC电力源。
术语“谐振电路的周期”指由谐振电路产生的实质上周期性的波形的时间周期。该时间周期等于谐振电路的谐振频率的倒数。
本文使用的术语“低输入电压”指小于600伏的、横跨两个端子的浮动(即，未参照接地电势)DC电压输入，或由安全规则限定的其它电压。
术语“双DC”输入或输出指正端子和负端子，其可以参照第三端子，例如接地电势、电接地、或交流（AC）供电的中性点，其可以被连接到某点处的电接地。
本文使用的术语“二级逆变器”可以指其输出。二级逆变器的AC相输出关于负端子具有两个电压水平。负端子对于二级逆变器的直流(DC)输入和AC相输出是共有的。二级逆变器的交流（AC）相输出可以是单相输出、两相输出、或三相输出。因此，单相输出关于负端子具有两个电压水平。两相输出关于负端子对于两个相位中的每一个具有两个电压水平。三相输出关于负端子对于三个相位中的每一个具有两个电压水平。
类似地，本文使用的术语“三级逆变器”可以指三级逆变器的交流（AC）相输出。AC相输出关于负端子具有三个电压水平。负端子对于三级逆变器的直流(DC)输入和AC相输出是共有的。三级逆变器的交流（AC）相输出可以是单相输出、两相输出、或三相输出。因此，单相输出关于负端子具有三个电压水平。两相输出关于负端子对于两个相位的每一个具有三个电压水平。三相输出关于负端子对于三个相位的每一个具有三个电压水平。
三级逆变器与二级逆变器相比，可具有更清楚的AC输出波形，可使用大小更小的磁部件并可具有电力开关中的更低的损耗，因为可以使用更有效的更低的电压的设备。三级逆变器电路可以具有双(正和负)直流(DC)输入。
参照图1，其示出了根据常规技术的光伏电力收集系统10。光伏串109包括串联连接的光伏板101。光伏串109可以与互联阵列111并联连接在一起，其提供在DC电力线X和Y处的并行直流(DC)电力输出。并行DC电力输出供给DC电力线X和Y上的直流-交流（DC-AC）三相逆变器103的电力输入。逆变器103的三相AC电力输出（相位W、U和V）跨接在AC负载105两端。作为例子，AC负载105可以是三相AC电机或三相电力网络。
现在参照图2，其示出了根据本发明的特征的电力收集系统20。系统20包括互联的光伏阵列111，其可包括在正输入端子A和负输入端子B上的浮动直流电压(DC)。浮动DC电压还可从例如DC电压生成器的其它分布式电力系统提供。横跨正输入端子A和负输入端子B连接的是电荷存储器件C1，其可以是电容器。连接到正输入端子A的是绝缘栅双极型晶体管(IGBT)IGBT1的集电极。IGBT1的发射极连接到节点C。IGBT1可以包括集成二极管，其阳极连接到发射极而阴极连接到集电极。连接到负输入端子B的是绝缘栅双极型晶体管(IGBT)IGBT2的发射极。IGBT2的集电极连接到节点C。IGBT2可以包括集成二极管，其阳极连接到发射极而阴极连接到集电极。驱动电路G1和G2分别连接到IGBT1的基极和IGBT2的基极，并可以参照到接地。感应器L1连接在节点C和节点D之间，其中节点D可以连接到接地和逆变器103a的接地输入。二极管CR1具有连接到正输入端子A的阳极和连接到节点V+的阴极。二极管CR1提供在节点V+和正输入端子A之间的正电流路径。电容器C2连接在节点D和节点V+之间。节点V+提供DC正电压到逆变器103a的输入端。二极管CR2具有连接到负输入端子B的阴极和连接到节点V-的阳极。二极管CR2提供在节点V-和节点B之间的负电流回路。电容器C3连接在节点D和节点V-之间。节点V-提供DC负电压到逆变器103a的输入端。电容器C2和C3可以具有实质相等的电容值。逆变器103a可以具有三级逆变器拓扑结构，其中双DC输入来自节点V+、V-和节点D，其可以被转换为单相或三相AC电压输出，其给负载105供电，负载105可以是单相或三相负载。
现在参照图3，其示出根据本发明的特征的适用于图2所示的电力收集系统20的方法301。在步骤303中，由于电容器C1在正输入端子A和负输入端子B处直接跨接在阵列111两端，电容器C1可以由阵列111的浮动DC电压充电。
分别通过驱动电路G1和G2，IGBT1和IGBT2可以被交替地选通，使得在IGBT1被开启时，IGBT2被关闭，反之亦然。IGBT1和IGBT2可以被交替地选通，其中占空比小于50%，从而避免在IGBT1和IGBT2之间的交叉导通(即，避免IGBT1和IGBT2同时被开启)。阵列111提供的浮动电压实质上关于接地提供了节点V+上的正电压和节点V-上的负电压。节点V+和节点V-上的电压可以实质上等于浮动电压的幅度。为电容器C1充电的步骤303可以在开关IGBT1和IGBT2的交替选通期间继续。
当开关IGBT1被开启(且IGBT2被关闭)时，来自阵列111的电流和来自存储电容器C1的放电电流（步骤305a）通过IGBT1的集电极和发射极、通过感应器L1，流入在接地(节点D)和节点V-之间的电容器C3和逆变器103a的输入负载。感应器L1和电容器C3形成串联谐振电路。横跨IGBT1的二极管关于在正输入端A处的电压被反向偏置。逆变器103a的关于接地(节点D)和节点V-的输入电压可以横跨电容器C3被得到。感应器L1和电容器C3的谐振频率由等式1给出，而相应的谐振时间周期T在等式2中给出。
fo=1/2π(L1×C3)1/2     等式1
T=1/fo            等式2
在IGBT1起初开启时，存在通过感应器L1和通过IGBT1的集电极和发射极的零电流。在IGBT1起初开启时，通过L1的电流和通过IGBT1的集电极和发射极的电流可以正弦地增加且然后下降。当IGBT1关闭时(开关开启时段对应于谐振时间周期T的一半)，可以接近于通过感应器L1和通过IGBT1的集电极和发射极的零电流。
节点V-和负输入端子B之间的负电流路径可以对应于谐振时间周期T的一半通过二极管CR2接通。
步骤303继续，这是因为，由于电容器C1在正输入端子A和负输入端子B处直接跨接在阵列111两端，电容器C1仍然由阵列111的浮动DC电压充电。当开关IGBT2被开启(且IGBT1被关闭)时，来自阵列111的电流和来自存储电容器C1的放电电流（步骤305b）通过二极管CR1、通过接地(节点D)和节点V-之间的逆变器103a的输入负载、通过C2、通过感应器L1、和通过IGBT2的集电极和发射极。感应器L1和电容器C2形成串联谐振电路。横跨IGBT2的二极管关于在负输入端子B处的电压被反向偏置。逆变器103a的关于接地(节点D)和节点V+的输入电压可以横跨电容器C2被得到。电容器C2可以具有与电容器C3相同的值；因此，感应器L1和电容器C2的谐振频率以及相应的谐振时间周期T可以实质上相同。当IGBT2起初开启时，通过感应器L1和通过IGBT2的集电极和发射极的均为零电流，且在IGBT2开启时可以为实质上零电力损耗。在IGBT2起初开启之后，通过L1的电流和通过IGBT2的集电极和发射极的电流可以正弦地增加且然后下降。当IGBT2关闭时(开关开启时段对应于谐振时间周期T的一半)，可以接近于感应器L1中的零电流和接近于通过IGBT2的集电极和发射极的零电流。因此，在IGBT2关闭时可以为实质上零电力损耗。节点V+和正输入端子A之间的正电流路径可以对应于谐振时间周期T的一半通过二极管CR1接通。因此，可以提供零电流切换(ZCS)，用于开关IGBT1和IGBT2两者的开启和关闭。
零电流切换(ZCS)可以允许使用和实现用于IGBT1和IGBT2的较慢速率的晶体管，其可以具有在集电极和发射极之间的较低的电压降。因此，切换损耗和传导损耗两者可以被降低。类似地，具有较低的电压降的IGBT1和IGBT2的较慢的集成二极管可以被使用。较慢的二极管CR1和CR2也可以被使用。通过IGBT1和IGBT2的集电极和发射极的谐振电流形状也可以降低二极管CR1和CR2中的开启损耗，并降低所生成的电磁干扰(EMI)。
根据常规技术，生成双DC轨的另一种方法可以是使用升压电路或隔离变压器电路。如果使用升压电路，升压电路传导和切换损耗可能非常高。升压感应器可能是大的且有损耗，升压电路的输出二极管的逆向恢复问题也可能很显著。使用碳化硅二极管用于升压电路输出可以除去逆向恢复问题，但可能增加传导损耗。如果大量的昂贵的碳二极管并联在一起以适应高功率水平，则升压电路的总的费用可能很高。此外，用于从太阳能板产生双DC轨的一些电路拓扑结构可能使太阳能板电压关于接地而变化。如果太阳能板电压快速变化，则可能产生接地循环电流，且可能超出由安全机构设置的电流水平。以下以各种特征和方面描述的电路拓扑结构可能解决电路拓扑结构的上述设计考虑，以从太阳能板产生双DC轨。
现在参照图4a，其示出了根据本发明的方面的电路40a。互联的光伏阵列111在节点A和B处横跨电容器C1被连接。连接到节点A的是晶体管IGBT1的集电极。IGBT1的发射极在节点C处连接到晶体管IGBT2的集电极。晶体管IGBT1和IGBT2两者都具有整体二极管，分别地，其阳极连接到每个晶体管的发射极且阴极连接到每个晶体管的集电极。驱动电路G1和G2分别连接到IGBT1和IGBT2的基极。IGBT2的发射极连接到节点B和二极管CR1的阴极。二极管CR1的阳极在节点F连接到二极管CR2的阴极。感应器L1的一端连接到节点C且感应器L1的另一端连接到电容器C4的一端。电容器C4的另一端连接到节点F。二极管CR2的阳极连接到DC到交流(AC)逆变器103a的负直流(DC)输入V-。二极管CR2的阳极还连接到电容器C3的一端，C3的另一端连接到接地或中性中心点节点D。节点D连接到对逆变器103a的接地输入。电容器C2的一端连接到节点D，电容器C2的另一端连接到节点A和DC到AC逆变器103a的正直流(DC)输入V+。逆变器103a可以具有三级逆变器拓扑，其中双DC输入来自节点V+、V-和节点D，其可以被转换为单相或三相AC电压输出，这为可以是单相或三相的负载105供电。
可选择地，在电路40a中，二极管CR1和CR2可以以串联连接的形式被放置在节点A和节点V+之间。该串联连接具有连接到节点A的二极管CR2的阳极和IGBT1的集电极。CR2的阴极连接到二极管CR1的阳极。二极管CR1的阴极连接到节点V+和电容器C2的一端。谐振回路T1中，L1的一个端部连接到节点C而L1的另一个端部连接到电容器C4的一个端部。C4的另一个端部连接到二极管CR2的阴极。IGBT2的发射极和节点B此时连接到节点V-和电容器C3的一个端部。
现在参照图4c，其示出了根据本发明的特征的方法401。电路40a中的IGBT1和IGBT2由驱动电路G1和G2利用脉宽调制（PWM）被交替选通。电路40a中的IGBT1和IGBT2以最多几乎50%的占空比被交替选通，从而避免IGBT1和IGBT2之间的交叉导通。在由驱动电路G1应用的PWM周期的第一半周期间，IGBT1以零电流被开启(无损耗开启)。电流然后在IGBT1的集电极和发射极之间流动进入由感应器L1和电容器C4形成的串联连接的谐振回路T1，经过二极管CR1，并被返回至板111的负输入端子(节点B)。全部太阳能板111电压Vin(横跨节点A和节点B)被施加到谐振回路T1。在通过谐振回路T1的电流升高时，电容器C4充电(步骤403)。当电容器C4的电压达到输入电压Vin(横跨节点A和节点B)，谐振回路T1中的电流下降至实质上为零。到IGBT1关闭时，通过IGBT1和谐振回路T1的电流已经实质上为零，且IGBT1的关闭也实质上是无损耗的。
在PWM周期的第二半周期间，IGBT1关闭且IGBT2以零电流开启。由L1缓冲的被充电的电容器C4与输入电压Vin（横跨节点A和节点B)串联连接。二极管CR2的阴极处的电压变为负，使得二极管CR2开始传导。形成了从正输入端子(节点A)、通过由C2、C3和逆变器103a提供的输出滤波器电容和负载、通过CR2、通过电容器C4和感应器L1、通过IGBT2并到达负输入端子(节点B)的电流路径。流经谐振回路T1的该电流路径对电容器C4放电（步骤405）。就象对于IGBT1一样，由于谐振回路T1中的正弦电流，IGBT2的开启和关闭以零电流发生。
谐振回路T1的谐振行为因此可允许使用较慢的费用较低的硅输出二极管CR1和CR2，且可能没有常规拓扑结构中所使用的二极管的逆向恢复问题，以从单个DC源产生双DC轨。类似地，IGBT1和IGBT2可以是较慢的，具有较低的电压降并因此可以是不太昂贵的。横跨端子V+和端子V-的输出电压实质上等于输入电压Vin的两倍。利用电路40a，不需要电压反馈来调节两个DC输出V+和V-。
现在参照图4b，其示出了根据本发明的特征的电路40b，其是图4a中所示的电路40a的交织拓扑结构形式。该交织拓扑结构形式具有额外的晶体管IGBT3和IGBT4、感应器L2、电容器C5、二极管CR3和CR4。晶体管IGBT3和IGBT4两者都具有整体二极管，分别地，其阳极连接到每个晶体管的发射极且阴极连接到每个晶体管的集电极。连接到节点A的是晶体管IGBT3的集电极。IGBT3的发射极在节点E连接到晶体管IGBT4的集电极。驱动电路G1和G2也分别连接到IGBT4的基极和IGBT3的基极。IGBT4的发射极连接到节点B和二极管CR3的阴极。二极管CR3的阳极在节点G连接到二极管CR4的阴极。感应器L2的一个端部连接到节点E且感应器L2的另一个端部连接到电容器C5的一个端部。感应器L2和电容器C5的串联连接形成了谐振回路T2。电容器C5的另一个端部连接到节点G。二极管CR4的阳极连接到DC到交流(AC)逆变器103a的负直流(DC)输入V-。
可选择地，在电路40b中，二极管CR1、CR2、CR3和CR4可以以串联连接的形式被放置在节点A和节点V+之间。在CR1和CR2之间的串联连接中，二极管CR2的阳极连接到节点A和IGBT1和IGBT3的集电极。CR2的阴极连接到二极管CR1的阳极。二极管CR1的阴极连接到节点V+和电容器C2的一个端部。类似地，在CR3和CR4之间的串联连接中，二极管CR4的阳极连接到节点A和IGBT1和IGBT3的集电极。CR4的阴极连接到二极管CR3的阳极。二极管CR3的阴极连接到节点V+和电容器C2的一个端部。在谐振回路T1中，L1的一个端部连接到节点C而L1的另一个端部连接到电容器C4的一个端部。C4的另一个端部连接到二极管CR2的阴极。IGBT2、IGBT4的发射极和节点B此时连接到节点V-和电容器C3的一个端部。类似地，在谐振回路T2中，L2的一个端部连接到节点E而L2的另一个端部连接到电容器C5的一个端部。C5的另一个端部连接到二极管CR4的阴极。
以高功率，在常规电路拓扑结构中，半导体开关和输出二极管通常可以是并行在一起的。实际上，直接并行硅二极管可能是不可行的。同样，也并非所有类型的IGBT可以被直接并行。相反，就电路40b而言，相同数量的开关和二极管可以被重新布置成交织的拓扑结构，如图4b中所示。由于其中纹波电流的部分消除，C1、C2和C3电容器的额定纹波电流可以被大大降低(连同费用和大小)。二极管CR1、CR2、CR3、CR4和IGBT1、IGBT2、IGBT3和IGBT4共享负载(到逆变器103a的输入)，而不必被直接并行，因此将被递送到负载的电力的共享可以不再成为一个问题。
虽然示出和描述了本发明的选定特征，但应理解，本发明不限于所述特征。相反，应认识到，可对这些特征做出改变，而不偏离本发明的原理和精神，本发明的范围由权利要求及其等效形式限定。

Claims (15)

1.一种电子电路，包括：
正输入端子和负输入端子，所述正输入端子和所述负输入端子适于横跨浮动直流（DC）电力源连接；
正输出端子和负输出端子；
横跨所述正输入端子和所述负输入端子被串联连接的第一开关和第二开关，其中在所述第一开关和所述第二开关之间的连接点形成第一节点；
串联连接的第一二极管和第二二极管，其中所述第一二极管和所述第二二极管之间的连接点形成第二节点；以及
串联连接在所述第一节点和所述第二节点之间的谐振电路，其中，当所述第一开关闭合且所述第二开关打开时，所述谐振电路跨接于所述正输入端子并然后通过所述第一二极管跨接于所述负输入端子，且其中，所述第一开关打开且所述第二开关闭合时，所述正输出端子、所述负输出端子和所述谐振电路通过所述第二二极管横跨所述正输入端子和所述负输入端子被串联连接。
2.如权利要求1所述的电子电路，其中所述第一二极管的阴极连接到所述负输入端子，且所述第二二极管的阳极连接到所述负输出端子，且所述第一二极管的阳极和所述第二二极管的阴极连接到所述第二节点。
3.如权利要求1所述的电子电路，其中所述第一二极管的阳极连接到所述正输入端子，且所述第二二极管的阴极连接到所述正输出端子，且所述第一二极管的阴极和所述第二二极管的阳极连接到所述第二节点。
4.如权利要求1所述的电子电路，还包括横跨所述正输入端子和所述负输入端子被连接的电荷存储器件。
5.如权利要求1所述的电子电路，其中所述谐振电路包括串联连接在所述第一节点和所述第二节点之间的感应器和电容器。
6.如权利要求1所述的电子电路，还包括：
接地输出端子；
连接在所述正输出端子和所述接地输出端子之间的第一电容器；
连接在所述负输出端子和所述接地输出端子之间的第二电容器；以及
逆变器，其具有连接到所述正输出端子的正逆变器输入端子、连接到所述负输出端子的负逆变器输入端子、和连接到所述接地输出端子的接地逆变器端子。
7.如权利要求1所述的电子电路，还包括第一驱动电路和第二驱动电路，该第一驱动电路和第二驱动电路适于利用脉宽调制PWM周期交替地选通所述第一开关和所述第二开关，使得在所述PWM周期的第一半期间，所述第一开关闭合而所述第二开关打开，且在所述PWM周期的第二半期间，所述第二开关闭合而所述第一开关打开。
8.如权利要求7所述的电子电路，其中所述第一驱动电路和所述第二驱动电路适于以小于50%的占空比交替地选通所述第一开关和所述第二开关，从而避免在所述第一开关和所述第二开关之间的交叉导通。
9.如权利要求7所述的电子电路，其中所述第一驱动电路和所述第二驱动电路配置成以实质上为零的通过所述第一开关和所述第二开关的电流打开和闭合所述第一开关和所述第二开关。
10.如权利要求1所述的电子电路，还包括：
横跨所述正输入端子和所述负输入端子被串联连接的第三开关和第四开关，其中在所述第三开关和所述第四开关之间的连接点形成第三节点；
串联连接的第三二极管和第四二极管，其中所述第三二极管和所述第四二极管之间的连接点形成第四节点；以及
串联连接在所述第三节点和所述第四节点之间的第二谐振电路，其中，当所述第三开关闭合且所述第四开关打开时，所述第二谐振电路跨接于所述正输入端子且然后通过所述第三二极管跨接于所述负输入端子，且其中，所述第三开关打开且所述第四开关闭合时，所述正输出端子和所述负输出端子以及所述第二谐振电路通过所述第四二极管横跨所述正输入端子和所述负输入端子被串联连接，其中所述第一开关和所述第四开关配置为一起打开和闭合，且所述第二开关和所述第三开关配置为一起打开和闭合。
11.一种转换电力的方法，用于将来自浮动直流（DC）电力源的电力转换到双DC输出端，所述双DC输出端具有参照接地输出端子的正输出端子和负输出端子，所述方法包括：
横跨一电路的正输入端子和负输入端子连接所述浮动DC电力源，所述电路包括：
横跨所述正输入端子和所述负输入端子串联连接的第一开关和第二开关，其中所述第一开关和所述第二开关之间的连接点形成第一节点；
串联连接的第一二极管和第二二极管，其中所述第一二极管和所述第二二极管之间的连接点形成第二节点；以及
串联连接在所述第一节点和所述第二节点之间的谐振电路，其中，当所述第一开关闭合且所述第二开关打开时，所述谐振电路跨接于所述正输入端子且然后通过所述第一二极管跨接于所述负输入端子，且其中，所述第一开关打开且所述第二开关闭合时，所述正输出端子、所述负输出端子和所述谐振电路通过所述第二二极管横跨所述正输入端子和所述负输入端子被串联连接；
交替地选通所述第一开关和所述第二开关，使得在脉宽调制PWM周期的第一阶段期间，所述第一开关闭合而所述第二开关打开，从而用所述浮动DC电力源的电力为所述谐振电路充电，并使得在所述PWM周期的第二阶段期间，所述第一开关打开而所述第二开关闭合，从而将所述谐振电路放电，以将转换的电力提供给连接到所述正输出端子、所述负输出端子和所述接地输出端子的负载。
12.如权利要求11所述的方法，其中所述第一二极管和所述第二二极管以如下方式之一被连接：
所述第一二极管的阴极连接到所述负输入端子，所述第二二极管的阳极连接到所述负输出端子，且所述第一二极管的阳极和所述第二二极管的阴极连接到所述第二节点；和
所述第一二极管的阳极连接到所述正输入端子，所述第二二极管的阴极连接到所述正输出端子，且所述第一二极管的阴极和所述第二二极管的阳极连接到所述第二节点。
13.如权利要求1所述的电子电路，其中，所述负载包括逆变器，所述方法还包括：
利用所述逆变器来逆变所转换的电力。
14.如权利要求11所述的方法，还包括：
以小于50%的脉宽调制占空比交替地选通所述第一开关和所述第二开关，从而避免在所述第一开关和所述第二开关之间的交叉导通。
15.如权利要求11所述的方法，还包括：
交替地选通所述第一开关和所述第二开关，使得所述第一开关和所述第二开关以实质上为零的通过所述第一开关和所述第二开关的电流打开和闭合。
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