US20150080063A1 - Method, apparatus and system for rendering an information bearing function of time - Google Patents

Method, apparatus and system for rendering an information bearing function of time Download PDF

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Publication number
US20150080063A1
US20150080063A1 US14/489,121 US201414489121A US2015080063A1 US 20150080063 A1 US20150080063 A1 US 20150080063A1 US 201414489121 A US201414489121 A US 201414489121A US 2015080063 A1 US2015080063 A1 US 2015080063A1
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Prior art keywords
function
time
information bearing
freedom
degrees
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David F. Sorrells
Gregory S. Rawlins
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ParkerVision Inc
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ParkerVision Inc
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Priority to US14/489,121 priority Critical patent/US20150080063A1/en
Assigned to PARKERVISION, INC. reassignment PARKERVISION, INC. ASSIGNMENT OF ASSIGNORS INTEREST (SEE DOCUMENT FOR DETAILS). Assignors: SORRELLS, DAVID F, RAWLINS, GREGORY S
Publication of US20150080063A1 publication Critical patent/US20150080063A1/en
Priority to US15/401,066 priority patent/US20170118717A1/en
Priority to US15/401,064 priority patent/US10278131B2/en
Priority to US15/401,071 priority patent/US10206167B2/en
Priority to US15/411,758 priority patent/US20170201949A1/en
Priority to US15/411,723 priority patent/US10264530B2/en
Abandoned legal-status Critical Current

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    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04W—WIRELESS COMMUNICATION NETWORKS
    • H04W52/00—Power management, e.g. TPC [Transmission Power Control], power saving or power classes
    • H04W52/02—Power saving arrangements
    • H04W52/0209—Power saving arrangements in terminal devices
    • H04W52/0261—Power saving arrangements in terminal devices managing power supply demand, e.g. depending on battery level
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04W—WIRELESS COMMUNICATION NETWORKS
    • H04W52/00—Power management, e.g. TPC [Transmission Power Control], power saving or power classes
    • H04W52/02—Power saving arrangements
    • H04W52/0209—Power saving arrangements in terminal devices
    • G—PHYSICS
    • G06—COMPUTING; CALCULATING OR COUNTING
    • G06F—ELECTRIC DIGITAL DATA PROCESSING
    • G06F1/00—Details not covered by groups G06F3/00 - G06F13/00 and G06F21/00
    • G06F1/26—Power supply means, e.g. regulation thereof
    • G06F1/32—Means for saving power
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04M—TELEPHONIC COMMUNICATION
    • H04M1/00—Substation equipment, e.g. for use by subscribers
    • H04M1/72—Mobile telephones; Cordless telephones, i.e. devices for establishing wireless links to base stations without route selection
    • H04M1/725—Cordless telephones
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02D—CLIMATE CHANGE MITIGATION TECHNOLOGIES IN INFORMATION AND COMMUNICATION TECHNOLOGIES [ICT], I.E. INFORMATION AND COMMUNICATION TECHNOLOGIES AIMING AT THE REDUCTION OF THEIR OWN ENERGY USE
    • Y02D30/00—Reducing energy consumption in communication networks
    • Y02D30/70—Reducing energy consumption in communication networks in wireless communication networks

Definitions

  • Embodiments of the present invention relate generally to a method, apparatus and system for rendering an information bearing function of time based on input signals.
  • Embodiments of the present invention present a novel solution to increasing operational battery life and reduced thermal footprint of a cell phone or other communications device, apparatus, module, subsystem or component by using enhanced information distribution and power supply control techniques. More particularly, embodiments of the present invention are directed to rendering the information bearing function of time based on efficient information distribution and without requiring feedback loops or pre-distortion techniques.
  • the cell phone transmitter and particularly the power amplifier (PA) consumes a significant amount of battery power and generates the most heat when compared with other phone functions.
  • the relative battery power demand of the PA is driven by the RF link budget and PA efficiency.
  • the PA is not efficient because it transmits signals while operating in a substantially linear mode of operation. Both high power output and linearity are required to ensure that the transmissions from the cell phone conform to currently defined industry standards, and to overcome communication link budget deficits. Unwanted heat is generated by the PA because of inefficiencies in PA operation.
  • PAs operating in a linear mode are not particularly efficient, and so, currently, a compromise must be made between battery life and conformance to the defined industry standards. Since the defined industry standards are mandatory and inflexible, the reduced battery life due to the PAs higher power consumption has been expected as a necessary impact.
  • An objective of envelope tracking is to improve the efficiency of power amplifiers (PA) carrying high peak- to average-power-ratio (PAPR) signals.
  • PA power amplifiers
  • PAPR peak- to average-power-ratio
  • the need to achieve high data throughput within limited spectrum resources requires the use of linear modulation with high peak to average power.
  • traditional fixed-supply power amplifiers operating under these conditions have low efficiency.
  • One approach to improve the efficiency of a power amplifier is to vary the amplifier's supply voltage in synchronism with the amplitude envelope of the RF signal. This is known as envelope tracking.
  • envelope tracking may include: using direct current (DC) to direct current (DC) converters; power DAC (digital analog converter); and Class “AB” push pull video amplifiers. These are some of the methods used to amplify the amplitude signal. A single amplifier could also be used with Class “A” operation to transfer amplitude information to the carrier envelope. Unfortunately, this is a very inefficient method to transfer envelope energy to the radio frequency (RF) amplifier. Often envelope tracking is used to make slow adjustments to the DC supply only when envelope fluctuations are of relatively low bandwidth. Such an apparatus is not stable or competitively efficient if modulated at a higher rate as needed in present-day cell phones.
  • Another approach is envelope tracking through adjustment of an amplifier power supply using DC to DC converters.
  • the DC to DC converter output is varied by its output duty cycle in proportion to a desired energy so that the resultant filtered voltage level reproduces an amplitude modulation signal.
  • a drawback to this approach is that a high modulation rate may not be achieved without distortion and/or stability problems.
  • pre-distortion techniques apply a pre-distorted power amplifier (PA) input signal to a PA.
  • PA power amplifier
  • This pre-distorted PA input signal is used to cancel or compensate for inherent distortion of the PA and attempts to improve linearization of the PA.
  • DSP digital signal processing
  • most digital implementations of pre-distortion utilize digital signal processing (DSP) and software, which can cause resource challenges and consume significant power associated with the management of current PAs, which follow rapid changes in power levels.
  • DSP digital signal processing
  • digital implementations of pre-distortion require significant investment of integrated circuit silicon area.
  • pre-distortion techniques are the need to insert a nonlinear module (typically known as a “pre-distorter” module) before the RF power amplifier.
  • This pre-distorter module counters the nonlinear portion of the PA transfer characteristic.
  • the overall system response from input to the output of the PA is linear when compensated by the pre-distortion module.
  • the philosophy of this approach identifies the PA nonlinearity as an undesirable design limitation or weakness which must be removed. Efficiency is not a primary optimization parameter for such schemes.
  • Adaptive digital pre-distortion is a technique that involves digital implementation of the pre-distorter module and a feedback loop that adapts to changes in the response of the PA due to varying operating conditions.
  • the major drawbacks to this technique are increased power consumption, complexity, size and cost of the system due to the adaptive feedback architecture.
  • a feedback loop is a circuit configuration that adapts to changes in the response of the PA due to varying operating conditions.
  • a regenerative feedback loop there is a specific type of feedback loop known as a “regenerative feedback loop”.
  • any RF (radio frequency, which possesses a rate of oscillation in the range of about 3 kHz to 300 GHz, which corresponds to the frequency of radio waves, and the alternating currents, which carry radio signals) feedback oscillator can be operated as a regenerative receiver if modified to provide a controllable reduction in the feedback loop. It also requires coupling the feedback loop to an incoming signal source, and coupling audio frequencies out of the feedback loop to a subsequent audio amplification stage.
  • feedback loops including regenerative feedback loops, require additional components and therefore, increase the power consumption, complexity, size and cost of the circuit.
  • feedback loops introduce a number of waveform distortions that must be addressed.
  • the feedback loops can actually introduce additional noise and errors into the system.
  • Polar modulation is a modulation technique that uses a modulated signal that is both phase modulated (PM) and amplitude modulated (AM).
  • the low power modulated signal is split into two components: a phase component; and a magnitude component.
  • the phase and increased magnitude components are then combined using an amplifier.
  • polar modulation is an inadequate solution because it requires a relatively large sample rate compared to the signal Nyquist bandwidth and often requires the use of pre-distortion in the phase and magnitude.
  • Feedback loops are often employed further complicating solutions at a significant cost in efficiency.
  • the field of power amplification also includes the use of amplifiers such as: Class “AB” Power Amplifiers; Stage Switching and Doherty Amplifiers; Envelope Elimination and Restoration (EER) Amplifiers; and Outphasing and Linear Amplification with Nonlinear Components (LINC) Amplifiers.
  • Class “AB” Power Amplifiers Stage Switching and Doherty Amplifiers
  • EER Envelope Elimination and Restoration
  • LINC Nonlinear Components
  • Class “AB” Power Amplifiers are a mature and popular technology for high production volume RF amplification circuits, such amplifiers suffer numerous drawbacks. For instance, Class “AB” amplifiers achieve only incremental efficiency gains by adaptive bias control, envelope tracking control, and power supply control. There is a detrimental tradeoff between linearity and efficiency. “Over-the-Air” specifications impose minimum linearity requirements such that precise input power backoff is required to balance linearity and efficiency. (“Input power backoff” is a reduction of the output power when reducing the input power.
  • the efficiency of the power amplifier is reduced due to backoff of the output power, because the amplifier operates in a linear region.) Since input power backoff is waveform dependent, the input power backoff must be increased for higher peak to average waveforms, which reduces efficiency making Class “AB” amplifiers less than ideal for many applications.
  • Stage switching amplifiers are typically implemented with switches or staggered bias control, which can be optimized for efficiency at multiple operating points. Stage switching amplifiers have higher average efficiencies than traditional class “AB” power amplifiers when the output power range traverses the operating points and such amplifiers can also be integrated in various semiconductor processes.
  • Stage switching amplifiers have a number of undesirable drawbacks.
  • stage switching amplifiers are normally constructed using Class “AB” stages and therefore, have all of the limitations of Class “AB” power amplifiers, some of which were described above. These drawbacks include a tradeoff of linearity versus efficiency and heat dissipation.
  • Doherty amplifiers are another conventional technique. These amplifiers have increased efficiency for higher peak to average ratio waveforms and the carrier power amplifier PA is biased Class “B” amplification. Typically, with Doherty amplifiers, the carrier PA alone supplies the output power over most of the output power dynamic range. The peaking PA is biased as Class “C” amplification and the peaking PA is “off” during most of the output power dynamic range. The peaking PA and carrier PA of Doherty amplifiers both supply output power during waveform peaks.
  • Doherty amplifiers suffer numerous undesirable performance drawbacks. For example, they require precise control of the input drive and bias of the carrier and peaking PAs (power amplifiers). They also require precise impedance values to ensure minimum distortion crossover performance as well as having all of the limitations of linear Class “B” power amplifiers. As with the case of stage switching amplifiers, Doherty amplifiers also suffer from linearity versus efficiency tradeoff problems. Additionally, Doherty amplifiers have inadequacies due to input backoff considerations, heat dissipation versus linearity tradeoff.
  • EER amplifiers separate the phase and amplitude components from a modulated signal. This type of nonlinear power amplifier technology is employed in the phase signal path, which has no amplitude component. The amplitude signal path has no phase component. EER amplifiers can utilize Class “C”, “D”, “E”, “F” and other nonlinear amplifiers.
  • EER amplifiers are also referred to as Kahn and/or polar amplifiers and are more efficient than Class “AB” power amplifiers at lower output power levels.
  • the EER amplifier permits the bias and power supply voltages to be controlled so as to optimize power consumption at different power levels. Theses amplifiers can be largely integrated in various semiconductor technologies.
  • EER amplifiers Kahn and/or polar amplifiers
  • EER amplifiers have numerous undesirable characteristics. For example, EER amplifiers have extreme difficulty maintaining phase signal path and amplitude signal path alignment. Furthermore, small alignment errors will result in the failure to pass most ACPR/ACLR requirements.
  • EER amplifiers generally require feedback to achieve linearity requirements. These feedback mechanisms typically involve polar feedback with separate amplitude correction and phase correction loops or Cartesian feedback loops. As discussed above herein, feedback loops greatly reduce amplifier efficiency.
  • the EER amplifiers which utilize DC to DC converter also require the DC/DC converter bandwidth to be greater than the signal bandwidth and are dependent on input waveform linearity. This is a serious drawback since input waveforms must significantly exceed the output linearity requirements.
  • Another conventional approach has been to use polar amplifiers with Cartesian feedback. It requires a complex demodulator (I/Q (In-Phase/Quadrature) Receiver) for the feedback path. Furthermore, using this approach can cause errors in the complex demodulator such as Quadrature and Amplitude imbalance that will be present on the output signal.
  • Other drawbacks of this approach include: difficulty maintaining feedback loop stability due to path delays from the baseband to the RF output; the complex demodulator reduces the efficiency; and the requirement that the amplitude envelope reconstruction bandwidth must be much greater than the desired output signal bandwidth.
  • Outphasing was first proposed by H. Chireix, (“High Power Outphasing Modulation,” Proc. IRE, Vol. 23, No. 11, November 1935, pp. 1370-1392 as a method of Generating High Power/High Quality AM Signals with vacuum tubes.
  • the term “Outphasing” was supplemented with LINC (Linear Amplification with Nonlinear Components) as the technology was adopted for use in microwave applications.
  • Outphasing, or LINC is a technique that provides In-Phase and Quadrature Phase Baseband Inputs and incorporates transmitter function. It eliminates the traditional RF transmitter to PA (power amplifier) input interface impedance match, filter, and backoff requirements.
  • LINC is able to utilize multiple nonlinear amplifiers in an attempt to increase amplifier efficiency, favorable thermal characteristics and higher available output power. Indeed LINC does not have any amplitude and phase alignment issues that EER architectures do and LINC also has a simple transfer function. Another advantage of LINC techniques is that In-Phase and Quadrature inputs are transformed into two or more constant envelope signal components.
  • LINC has some advantages, as discussed above, the technique suffers serious drawbacks.
  • LINC requires power combiner technology with the accompanying large physical size (quarter wave elements are 3.75 cm (1.5 inches) at 2 GHz and 7.5 cm (3.0 inches) at 1 GHz).
  • LINC cannot be integrated without large losses, which causes it to be impractical due to semiconductor die size.
  • LINC also suffers from a relatively narrow practical application bandwidth.
  • parametric and temperature variations adversely affect performance.
  • LINC has a limited operational temperature range for optimal performance.
  • phase accuracy requirements and physical size are significant drawbacks.
  • 40 dB of output power dynamic range is desirable. Therefore, two sinusoids with perfect amplitude and phase balance need to vary between 0 degrees phase and 178.86 degrees phase to achieve a 40 dB dynamic power output range.
  • the accuracy required to achieve 40 dB challenges the tolerance of practical circuits in a high volume application. Thus, this technique is not desirable for current cell phone applications.
  • quarter wave elements are 3.75 cm ( ⁇ 1.5 inches) at 2 GHz and 7.5 cm ( ⁇ 3.0 inches) at 1 GHz. With such large size requirements, this approach currently cannot be integrated without large losses, whenever quarter wave combiner techniques are used even on a silicon based substrate. Furthermore, it is impractical due to semiconductor die size.
  • Other drawbacks, similar to those mentioned above include: narrow bandwidth; having real losses that adversely affect efficiency; parametric and temperature variations that adversely affect performance; unit-to-unit performance variations that unexpectedly vary loss, isolation, and center frequency. Additionally, outphasing has a limited temperature range for optimal performance and requires isolation between power amplifiers. Similar to LINC described above, lossless combiners (reactive elements only) have been used and create undesired output waveform distortions. Yet another drawback is that outphasing requires significant branch phase accuracy and branch amplitude accuracy to generate waveforms of acceptable quality.
  • Embodiments of the present invention are directed to methods, apparatus and systems, as well as components of the methods, apparatus and systems that provide blended control, (also known as BLENDED CONTROL BY PARKERVISIONTM, BLENDED CONTROL BY PARKERVISIONTM is a registered trademark of ParkerVision, Inc., Jacksonville, Fla.) that enhances power efficiency or energy efficiency or thermodynamic efficiency (hereafter simply efficiency unless otherwise stated) for base band and RF modulation processes.
  • This BLENDED CONTROL BY PARKERVISIONTM utilizes a process of distributing domains of information to various apparatus modulation and encoding functions as well as one or more than one energy source to improve efficiency of communications systems, devices, and components including transmitters. This involves the process of information and energy partitioning, associated with a FLUTTERTM algorithm, (FLUTTERTM is a registered trademark of ParkerVision, Inc., Jacksonville, Fla.).
  • FLUTTERTM organizes input control signals, derived from the information source, into domains, which when processed and reintegrated, efficiently reconstitute a desired modulation and/or encoding.
  • FLUTTERTM dynamically manipulates multiple degrees of freedom (v+i) in hardware and/or software, which control the magnitudes and phases of partitions, whilst allocating quantities of information per partition.
  • One novel embodiment of the present invention includes utilizing FLUTTERTM to render an information bearing function of time, which includes waveforms and/or signals and/or a combination of waveforms and signals, an RF modulated waveform, and/or an RF modulated carrier signal.
  • the FLUTTERTM process includes compositing multiple signals, for example, three or more signals, to render the information bearing function of time, or a representation, or facsimile thereof, such as electronic data representing the information bearing function of time. These signals may include one or more phase functions and two or more amplitude functions.
  • the compositing process includes processing constituent signals substantially simultaneously (or concurrently or in parallel), with each constituent signal assigned a weighting factor dependent on the information distributed by the constituent signal, the efficiency associated with the constituent signal statistical distribution and the efficiency for reintegrating constituent signals to form a desired information bearing function of time.
  • Compositing may also include mapping of one or more signals or portions of one or more signals to ranges or domains of functions and their subordinate values according to a dynamic co-variance or cross-correlation of the functions distributed within blended controls to an apparatus that generates a desired output signal or signals.
  • the composite statistic of the blended controls is determined by at least one information source with information entropy of H(x), the number of the available degrees of freedom for the apparatus, the efficiency of each degree of freedom, and the corresponding potential to reliably distribute a specific signal rate and information in each degree of freedom.
  • Compositing includes a dynamically and statistically weighted calculation of a desired complex signal in terms of the encoded information, complex cross-correlations of subordinate functions, compositing signals and minimized waste energy per unit time. Furthermore, the compositing signals may have different bandwidths, and spectral distributions.
  • the desired output composited signal may be an RF carrier signal or a base band signal.
  • the desired output RF carrier or baseband signal may also exist at variable power levels.
  • a communications platform transmitter based on FLUTTERTM and BLENDED CONTROL BY PARKERVISIONTM generates a desired communications signal at the proper signal level and frequency.
  • the results of employing FLUTTERTM and BLENDED CONTROL BY PARKERVISIONTM algorithms and architectures are increased efficiency, lower thermal footprint and universal signal construction. For example, using these algorithms and architectures, mobile communications devices can operate longer per battery charge cycle while running cooler. In addition, modern digital communications standards as well as Legacy modulation standards are accommodated.
  • FLUTTERTM significantly reduces the effective sampling rates and/or bandwidths as well as agile power source resolution critical to certain aspects of signal envelope reconstruction when compared to Legacy technologies.
  • FLUTTERTM greatly relieves the specification of agile power supply design used in complex signal envelope construction. While current technology approaches seek to increase sample rates and resolution of switched power supplies to increase envelope reconstruction bandwidths and quality, FLUTTERTM enables the minimum information distributed to one or more agile power sources utilized as part of a desired complex signal reconstruction process. Unlike legacy technologies, average complex envelope sample rates in the power source path may be tailored to fall below the Nyquist reconstruction sample rate using FLUTTERTM, if so desired.
  • Compliant signals may be created by the composite of sparsely sampled power sources with (i) degrees of freedom and additional (v) degrees of freedom within various encoding and modulation functions of the transmitter.
  • FLUTTERTM is the most efficient approach.
  • the FLUTTERTM algorithm selects from a minimum number of specifically tailored power source metrics, distributed at irregular sample intervals of time dependent on envelope statistics, whilst assisting the other degrees of freedom in the transmitter in the process of signal envelope construction.
  • This can be accomplished with an open loop feed forward (OLFF) algorithm if so desired.
  • OLFF open loop feed forward
  • the feed forward approach can also be accompanied by a maximum pursuit of nonlinearity in a plurality of parallel algorithm paths to further enhance efficiency whilst preserving ultimate output signal integrity.
  • Legacy approaches such as envelope tracking, Kahn's technique and envelope restoration, utilize Nyquist or greater sampling rates, distributing samples at regular intervals of time, in the power supply path to construct signal envelopes. Often these techniques utilize feedback algorithms to enhance quality and compensate for nonlinearities, in contrast to FLUTTERTM.
  • the sampled power supply values are not optimal, like values determined through FLUTTERTM. Rather, they are determined through standard sampling approaches to follow the magnitude of a desired envelope at specific regular sample instants (sample instants are independent of signal envelope statistics) while interpolating between these sampled values, primarily using filtering technologies.
  • FLUTTERTM provides the maximum practical efficiency for signal envelope construction given finite energy or power supply resources and the desire to minimize energy or power supply resource performance requirements when those resources are dynamic.
  • One embodiment of the present invention is directed to a method for partitioning an energy or power source.
  • the energy source may be, for example, a battery or batteries or other power supply or power supplies for an electronic device, such as a cell phone, or mobile device.
  • the energy source (battery for example), or power supply, provides power to a cell phone, or mobile device or any other load or power consuming device. Partitioning this energy source is a technique for controlling its operation so that power is provided to the power consuming device, such as a cell phone more efficiently, thereby extending the length of time the phone can be used between re-charging.
  • Each energy partition has one or more associated sample regions.
  • a sample region corresponds to a range of voltage and current, from which metered quantities may be extracted, acquired, generated or sampled and allocated to power the electronic device, including circuits used for transmission and reception of information bearing functions of time.
  • a sample region includes one or more samples that can be used to render a representation of a signal (information bearing function of time). This representation may be a reconstruction or rendering. The number of partitions and their associated metrics are a function of a desired efficiency to render the desired signal.
  • the number of partitions is bounded by a desired resolution i ⁇ 2 K where;
  • the number of partitions (i) is less than or equal to 2 raised to the K th power.
  • a desired signal typically includes information, such as data that is encoded on a waveform.
  • the signal (information bearing function of time) that is rendered, using the partitioning method described herein, can have an information entropy value from zero to a maximum value determined by the dynamic range and ability to access or create resolution of the signal.
  • the entropy value represents the degree of signal uncertainty; the greater the entropy the greater the uncertainty and information content.
  • the partitioning method described above can also utilize auxiliary degrees of freedom to determine one or more rendering parameters of a particular partition.
  • the auxiliary degrees of freedom possess the quality of, for example, a dimension, or dimensions, or subset of a dimension, associated with a conceptual mathematical space known as phase space into which energy and/or information can individually or jointly be imparted and represented.
  • phase space may be multi-dimensional and sponsor multiple degrees of freedom.
  • a single dimension may also support multiple degrees of freedom.
  • the v degrees of freedom are associated with other aspects of information encoding functions.
  • v,i and auxiliary degrees of freedom will be referred to as desired degrees of freedom unless otherwise stated.
  • the partitioning method has parameters for rendering (i.e. rendering parameters) the signal (i.e., the information bearing function of time).
  • the rendering parameters or rendering functions may be expressed as, for example, an amplitude function, a phase function, a frequency function, or combinations and permutations of amplitude functions, phase functions and frequency functions.
  • the amplitude function may be, for example, a voltage or current versus time or a discrete set of sample values versus sample number or discrete time increment.
  • the phase function may be for example a phase angle versus time or a discrete set of sample values versus sample number or discrete time increment.
  • the frequency function may be, for example, a frequency versus time or a discrete set of sample values versus sample number or discrete time increment.
  • amplitude, phase, and frequency may be interrelated by functions.
  • rendering parameters may also consist of operational constants along with some number of rendering functions. Rendering parameters can be obtained and assigned from knowledge of the signal and characterization of the apparatus used for signal construction. Rendering parameters are coordinated by and distributed by blended controls, which manipulate one or more degrees of freedom within the apparatus.
  • Yet another embodiment of the present invention is directed to the partitioning method described above in which the energy source (for example, one or more batteries) may be associated with a plurality of domains.
  • Domains include a range of values or functions of values relevant to mathematical and/or logical operation or calculation within the FLUTTERTM algorithm. Domains may apply to multiple dimensions and therefore bound hyper-geometric quantities or objects and they may include real and imaginary numbers or sets of mathematical and/or logical functions or objects. Domains may be identified using subsets of the values from (v,i) indices the desirable degrees of freedom for the system or apparatus. (v,i) may be used to specify blended controls and associated functions. Domains may be associated with sub spaces of the phase space.
  • Yet another embodiment of the present invention is directed to the partitioning method described above and also utilizes current differentials. These current differentials provide energy to each partition in charge increments.
  • differential refers to a difference between some desired value and some preferred reference value.
  • Yet another embodiment of the present invention is directed to the partitioning method described above and also utilizes electromagnetic (EM) field differentials.
  • EM field differentials provide energy to each partition.
  • differential refers to a difference between some desired value and some preferred reference value.
  • Yet another embodiment of the present invention is directed toward the partitioning method described above wherein the energy source is either a fixed energy source or a variable energy source.
  • a fixed energy source provides access to a fixed potential or rate of charge from one or more sources.
  • a variable energy source provides access to a variable potential or rate of charge from one or more sources.
  • the voltage domain may be fixed or adjustable. A fixed voltage domain does not change.
  • An adjustable voltage domain is adjustable over a range of ⁇ V i , or a multiplicity thereof. The adjustment may also be based on H(x) v,i or H(x) v i , a set of entropy functions dependent on a number of transmitter degrees of freedom and power source degrees of freedom.
  • v i is an index for blended controls for one or more degrees of freedom within a regulator apparatus, where v is a number of degrees of freedom and ti is a power source partition number.
  • Yet another embodiment of the present invention is directed to the partitioning method described above and includes using at least a portion of prior knowledge to construct a complex signal envelope.
  • the prior knowledge is information about the desired signal (information bearing function of time) that is known prior to the rendering of the signal. This prior knowledge is used in the partitioning procedure to determine partition metrics, and may include statistical characterization.
  • Yet another embodiment of the present invention is directed to the partitioning method described above and also includes parsing the system input information H(x) into constituent information functions H(x) v,i and/or H(x) v i to form domains. Domains may possess jointly-statistically dependent functions of the constituent entropy sets H(x) v,i , H(x) v i .
  • Yet another embodiment of the present invention is directed to the partitioning method described above and also includes adjusting v,i and/or v i based on, signal statistics and apparatus characterization, where v is an index for blended controls for one or more degrees of freedom.
  • Yet another embodiment of the present invention is directed to the partitioning method described above, wherein the partitioning step described above also includes generating a blended control function.
  • the blended control function is used to construct signals via the control of apparatus degrees of freedom.
  • the blended control function may use a plurality of paths, including parallel paths, and may also include at least a partial cross-correlation between related domains.
  • Yet another embodiment of the present invention is directed to the partitioning method described above, wherein the blended control function excludes cross-correlation between domains.
  • the blended control function operates independent of cross-correlation.
  • Yet another embodiment of the present invention is directed to the partitioning method described above and also includes calculating and/or approximating a statistical dependence for the correlations and creating a composite statistic from the blended controls.
  • Yet another embodiment of the present invention is directed to the partitioning method described above and also includes establishing one or more paths for the partitioning procedure.
  • FLUTTERTM can manipulate partitions which are based on any relevant dynamic operational parameter.
  • FLUTTERTM can manipulate energy, momentum, voltage, current, and entropy partitions. Manipulations of these quantities contain portions of the information of a desired signal distributed in blended controls to parallel segments of a transmitter apparatus. Information may be encoded in complex values (magnitude and phase) for each blended control path.
  • Yet another embodiment of the present invention is directed to the partitioning method described above and also includes switching a power source or other partition resource at a rate less than a sampling rate. This may also include switching the power source or other partition resource at a rate less than or equal to the Nyquist rate associated with a rendered output signal. This may also include switching a power supply or other energy partition resource at a rate greater than the Nyquist rate. This may include switching a power supply at irregular intervals. This may also include switching a power supply or other partition resource at a rate different than the rate used to reconstruct an output signal.
  • Yet another embodiment of the present invention is directed to the partitioning method described above and also includes establishing sampling rates related to domains.
  • information entropy and entropy rate within the domain may be used to determine the domain sampling rate.
  • Yet another embodiment of the present invention is directed to the partitioning method described above and also includes establishing domain bandwidths. Bandwidths associated with processing domains may be less than a rendering bandwidth for a desired output signal.
  • Yet another embodiment of the present invention is directed to the partitioning method described above wherein one or more blended control paths manipulate energy partitions.
  • the blended control paths can adjust the relative weight and access to degrees of freedom of any partition.
  • the blended control paths being dynamic, can vary as the information bearing function of time evolves.
  • Yet another embodiment of the present invention is directed to the partitioning method described above and also includes coordinating at least two partition paths based on one or more parameters of the information bearing function of time.
  • partition paths may be structured depending on parameter(s) of the information bearing function of time (signal).
  • the parameters of the information bearing function of time include, for example, functions of phase, and/or functions of amplitude, entropy, and efficiency.
  • Yet another embodiment of the present invention is directed to the partitioning method described above and also includes utilizing one or more partitions based on one or more energy sources.
  • Yet another embodiment of the present invention is directed to the partitioning method described above and also utilizes a prior characterization of a system response.
  • the prior characterization can be used to determine the number of partitions, their associated metrics and associated sample rates.
  • the prior characterization of the system response is information about the signal that is known prior to the rendering of the signal.
  • Yet another embodiment of the present invention is directed to the partitioning method described above and also includes coordinating one or more FLUTTERTM algorithm parameters.
  • FLUTTERTM algorithm parameters may include, for example, statistics, ranges, domains, logic functions and/or metrics.
  • the coordinating is a function of one or more transmitter parameters.
  • the transmitter parameters may include, for example, power control states, temperature, power supply levels, antenna interface circuit impedance, waveform statistics, data rate, channel frequency, GPS coordinates, accelerometer data, compass information, and spatial orientation.
  • Yet another embodiment of the present invention is directed to the partitioning method described above, wherein one or more of the energy partitions are statistically allocated.
  • the one or more of the energy partitions are allocated to transition between constellation points within a phase space.
  • the energy partitions are allocated based on a radial difference of an average of a particular portion of phase space relative to the phase space center, where a radial value of zero is designated as the center position of the phase space. Different energy partitions possess different radial values.
  • Yet another embodiment of the present invention is directed to the partitioning method described above, wherein one or more of the energy partitions are allocated based on Peak to Average Power Ratio (PAPR) statistics of the rendered information bearing function of time.
  • PAPR Peak to Average Power Ratio
  • Yet another embodiment of the present invention is directed to the partitioning method described above and also includes imparting information embedded within the functions ⁇ tilde over (I) ⁇ H(x) v,i ⁇ and/or ⁇ tilde over (I) ⁇ H(x) v,i ⁇ to one or more information domains from one or more information sources to interface to an RF signal modulation architecture.
  • This information includes any data suitable for application.
  • Yet another embodiment of the present invention is directed to the partitioning method described above and also includes modifying an operational state of a power supply during the partitioning procedure.
  • This modification may be for example, turning the power supply “on” or “off”.
  • This modification may also include switching between two or more power sources during the partitioning procedure.
  • This modification may also include adjustment of two or more power sources during the partitioning procedure.
  • Yet another embodiment of the present invention is directed to the partitioning method described above in which one or more partitions are allocated based on efficiency of operation.
  • Efficiency of operation may be determined by apparatus characterization, rendered signal statistics (such as PAPR), by a process of associating volumes of phase space with associated domain functions, in part based on rendered parameters. This process is used to develop blended controls.
  • the blended controls can be used to coordinate partitions.
  • Yet another embodiment of the present invention is directed to a method to generate an information bearing function of time.
  • the information bearing function of time may be, for example, a signal or waveform, RF modulated signal, representation of a signal, such as electronic data stored on a computer-readable medium, an information bearing energetic function of time and space that enables communication, or a modulated RF carrier waveform, having a dynamic range of approximately between 20 dB to 174 dB.
  • the modulated RF carrier waveform may have one or more power levels.
  • This method may be facilitated by storage on a computer-readable medium, such as software, or RAM (Random Access Memory) ROM (Read Only Memory), PROM (Programmable Read Only Memory), EEPROM (Electrically Erasable Programmable Read Only Memory), non-volatile memory, flash memory, memory stick, or other suitable electronic storage medium.
  • a computer-readable medium such as software, or RAM (Random Access Memory) ROM (Read Only Memory), PROM (Programmable Read Only Memory), EEPROM (Electrically Erasable Programmable Read Only Memory), non-volatile memory, flash memory, memory stick, or other suitable electronic storage medium.
  • This method includes utilizing a mathematical description of modulation and characterization of apparatus based on prior knowledge of the apparatus.
  • This mathematical description or substantially equivalent functional representation provides a model suitable for describing the modulation and/or information encoding process of the apparatus.
  • a functional description of an original data set is generated and an estimation is also generated.
  • the estimation function represents an approximation of a deviation from an expected, or desired, function of a signal compared to a signal at the output of the apparatus model.
  • One or more values for the output information bearing function of time (signal) are calculated based on real-time input samples, apparatus characterization and/or real time measurements, and used to develop the estimation function.
  • the real-time input samples are signals or other inputs received by the system.
  • Yet another embodiment of the present invention is directed to the method to generate an information bearing function of time in which the mathematical description of modulation includes real and imaginary components.
  • the mathematical description includes digital I and Q components.
  • the I-components include “In-phase” and the Q-components include “Quadrature-phase”.
  • Yet another embodiment of the present invention is directed to a method for rendering a representation of an information bearing function of time.
  • the information bearing function of time may be a signal or a waveform, or an RF carrier signal or a modulated RF carrier waveform.
  • the method includes accessing parameters of a desired information bearing function of time. These parameters include, for example, amplitude, phase, frequency or functions thereof and may be based on prior system knowledge. Multiple signals are composited to form a desired output signal. Compositing includes, for example, mapping one or more signals or portions of one or more signals to ranges or domains of functions and their subordinate values. Mapping is accomplished according to the FLUTTERTM algorithm. FLUTTERTM manages the apparatus functions which generate the constituent signals of the blended controls. The composite statistic of the blended controls is determined by an information source with source entropy of H(x), the number of the available degrees of freedom for the apparatus, the efficiency of each degree of freedom, and the corresponding potential to distribute a specific signal rate as well as information rate in each degree of freedom. A representation of the desired information bearing function of time is rendered based on the compositing step. The rendering may be an output signal or waveform, or an electronic representation stored on an electronic medium, such as a computer-readable medium.
  • Yet another embodiment of the present invention is directed to the method for rendering a representation of an information bearing function of time, as described above, wherein the compositing step includes managing a covariance of statistical parameters of constituent signals. Functions of the constituent signals are reintegrated in the compositing process to form a desired output signal.
  • Yet another embodiment of the present invention is directed to the method for rendering a representation of an information bearing function of time, as described above, wherein the compositing step includes cross-correlations.
  • the cross-correlations are measurements or calculations of similarity between two or more waveforms and/or signals.
  • Yet another embodiment of the present invention is directed to the method for rendering a representation of an information bearing function of time, as described above, wherein the compositing step includes calculations or measurements of statistical dependencies.
  • the statistical dependencies include, for example, a condition in which two or more random variables are not statistically independent.
  • Yet another embodiment of the present invention is directed to the method for rendering a representation of an information bearing function of time, as described above, wherein the composited signals include one or more subsets of signals.
  • Yet another embodiment of the present invention is directed to the method for rendering a representation of an information bearing function of time, as described above, wherein compositing consists of a function of three or more signals.
  • This set of signals may include, for example, two or more amplitude functions and one or more phase functions.
  • each of the two or more amplitude functions may have an associated spectral distribution and respective bandwidths.
  • the first amplitude function has a first spectral distribution and the second amplitude function has a second spectral distribution; the first spectral distribution and bandwidth being different than the second spectral distribution and bandwidth.
  • the multiplicity of phase functions may possess unique spectral distributions and bandwidths.
  • Yet another embodiment of the present invention is directed to the method for rendering a representation of an information bearing function of time, as described above, wherein two or more functions (amplitude and/or phase) have an associated spectral density.
  • a first function has a first spectral density and a second function has a second spectral density; these first and second spectral densities being at least partially statistically independent of one another or partially uncorrelated.
  • Yet another embodiment of the present is directed to the method for rendering a representation of an information bearing function of time, as described above, wherein the parameters of a desired information bearing function of time are based, at least in part, on prior knowledge obtained by apparatus characterization.
  • Yet another embodiment of the present invention is directed to a method for generating an information bearing function of time, or a representation thereof, that includes identifying one or more characteristics of an information bearing function of time.
  • the information bearing function of time may be, for example, a signal, waveform, RF modulated signal, an RF carrier signal, or wave representation or composite waveforms.
  • a representation, such as a waveform, signal, data set, electronic rendering or other manifestation, of the information bearing function of time may be synthesized based upon a composition or compositing of multiple signals.
  • the composition or compositing includes mapping of one or more signals or portions of one or more signals to ranges or domains of functions and their subordinate values according to a dynamic co-variance or cross-correlation of the functions that distribute blended controls to an apparatus which generates signals.
  • a composite statistic of the blended controls can be determined by an information source with source entropy of H(x), the number of the available degrees of freedom for the apparatus, the efficiency of each degree of freedom, and the corresponding potential to distribute a specific signal rate in and information each degree of freedom.
  • the composition may include, for example: examining covariance of statistical parameters of a signal of interest; and cross-correlations and/or calculated and/or measured dependencies.
  • Yet another embodiment of the present invention is directed toward the method for generating an information bearing function of time, described above wherein the multiple signals include three or more signals.
  • the three or more signals include two or more amplitude functions and one or more phase functions.
  • each of the two or more amplitude functions has a spectral distribution.
  • a first amplitude function has a first spectral distribution and bandwidth and a second amplitude function has a second spectral distribution and bandwidth; the first spectral distribution does not necessarily equal the second spectral distribution, or the two spectral distributions may be at least partially correlated.
  • Yet another embodiment of the present invention is directed to the method for generating an information bearing function of time, described above wherein parameters of a desired information bearing function of time are based, at least in part, on prior characterization (prior knowledge) of the apparatus.
  • the prior knowledge may include, for example, prior known information about the desired information bearing function of time, as well as characteristics of an apparatus such as modulator, encoder or transmitter.
  • Yet another embodiment of the present invention is directed to a method for generating an information bearing function of time.
  • This method includes accessing parameters of a desired information bearing function of time. These parameters include, for example, amplitude, phase, frequency, or functions thereof.
  • a first subset representation of the desired information bearing function of time is generated based on one or more input signals and a first function.
  • the first subset representation of the desired information bearing function of time is compared to the parameters of a desired information bearing function of time and a differential quantity is identified based on the comparison.
  • the input signals are composited with additional one or more input signals when the differential quantity exceeds a predetermined threshold and a second subset representation of the desired information bearing function of time is generated based on the compositing step.
  • differential refers to a difference between some desired value and some preferred reference value.
  • Yet another embodiment of the present invention is directed to the method described above, wherein the differential quantity is a function of desirable characteristics of the information bearing function of time.
  • the desirable characteristics of the information bearing function of time include one or more of function of amplitude, function of frequency and/or function of phase.
  • Yet another embodiment of the present invention is directed to the method described above and also includes identifying one or more statistics of amplitude, frequency and/or phase.
  • Yet another embodiment of the present invention is directed to the method described above, wherein the parameters of a desired information bearing function of time are based on prior characterization (prior knowledge) of the apparatus.
  • This apriori or a priori or prior knowledge includes information that was known, or identified, prior to the rendering of the information bearing function of time.
  • Yet another embodiment of the present invention is directed to the method described above, wherein the first subset representation and the second subset representation are based on nonlinear functions. Thus, the subset representations are not linear.
  • Yet another embodiment of the present invention is directed to the method described above, wherein the parameters of a desired information bearing function of time include real and imaginary components that are established prior to generating a first subset representation of the desired information bearing function of time.
  • Yet another embodiment of the present invention is directed to a method for optimizing the relevant metrics of one or more power sources.
  • This method includes accessing characterizations of an information bearing function of time.
  • the information bearing function of time may be, for example, a signal, waveform, RF modulated signal, an RF carrier signal, or representation or composite waveforms or electronic replication thereof.
  • a plurality of input sources providing power are accessed. These input power sources also serve as constituent input signals, which may be nonlinear and/or switched. Two or more of the input signals are composited to generate a representation of the desired output information bearing function of time.
  • This representation may be a waveform, signal, or electronic representation.
  • An operational state of at least one of the power sources is controlled based on the compositing step.
  • Yet another embodiment of the present invention is directed to an apparatus to control one or more energy sources.
  • the apparatus includes a storage module adapted to store one or more functions of the characteristics of a desired information bearing function of time. These functions may include, for example, one or more of function of amplitude, function of frequency and/or function of phase.
  • the information bearing function of time may be, for example, a signal, waveform, RF modulated signal, an RF carrier signal, or representation of composite waveforms.
  • the apparatus also includes a first module adapted to receive one or more input signals and provide a first subset of output signals.
  • a second module which is operatively coupled to the first module, is adapted to receive one or more input signals and provide a second subset of output signals.
  • the first subset of output signals are composited with the second subset of output signals to generate a representation of the desired information bearing function of time.
  • the compositing includes mapping of one or more signals or portions of one or more signals to ranges or domains of functions and their subordinate values according to a dynamic co-variance or cross-correlation of the functions that distribute blended controls to an apparatus which generates signals.
  • the composite statistic of the blended controls is determined by an information source with source entropy of H(x), the number of the available degrees of freedom for the apparatus, the efficiency of each degree of freedom, and the corresponding potential to distribute a specific signal rate as well as information in each degree of freedom.
  • the compositing process may include, for example: examining covariance of statistical parameters of a signal of interest; and cross-correlations and/or calculated dependencies.
  • Yet another embodiment of the present invention is directed to the apparatus described above, wherein the first module and the second module are nonlinear modules. That is, the first and second modules obtain nonlinear input signals.
  • Yet another embodiment of the present invention is directed to the apparatus described above and also includes a node, operatively coupled to the second module, adapted to receive the representation of the desired information bearing function of time and provide a linear representation of the desired information bearing function of time.
  • Yet another embodiment of the present invention is directed to the apparatus described above, wherein the signal is reconstituted during compositing of the one or more first subset of input signals, which are derived from blended controls, and one or more of the second subset of input signals, which are derived from blended controls.
  • the reconstitution is a desired information bearing function of time which is compliant to a quality metric, often a standard, for example.
  • Yet another embodiment of the present invention is directed to a method for rendering a representation of an information bearing function of time.
  • the information bearing function of time may be, for example, a signal, waveform, RF modulated signal, an RF carrier signal, or wave representation or composite waveforms or electronic representation thereof.
  • the method includes utilizing one or more energy sources.
  • These energy sources may be, for example, one or more batteries, one or more power supplies, other power source or sources, or combinations of these energy sources.
  • the one or more energy sources are partitioned within selected domains to efficiently generate signals used to form a rendered information bearing function of time. Domains, for example, include a range of values or functions of values relevant to mathematical and/or logical operations or calculations within the FLUTTERTM algorithm. Domains may apply to multiple dimensions and therefore bound hyper-geometric quantities and they may include real and imaginary numbers or any suitable mathematical and/or logical function.
  • the signals, which have been generated, are allocated to render the representation of the information bearing function of time, such that the allocation associates with the change of an operational state of at least one or more than one of the energy sources.
  • the allocation may be coordinated by a blended control or blended controls, such as BLENDED CONTROL FUNCTION BY PARKERVISIONTM according to a FLUTTERTM algorithm.
  • Yet another embodiment of the present invention is directed to the rendering method described above and also includes iteratively optimizing a blending function for the allocation of the input signals.
  • This optimization includes characterization of the implementing apparatus and the information bearing function of time that it renders and constructing a blended control, such as BLENDED CONTROL FUNCTION BY PARKERVISIONTM according to a FLUTTERTM algorithm.
  • Yet another embodiment of the present invention is directed to the rendering method described above, wherein the information bearing function of time is a waveform.
  • This waveform is based on a stimulus function, which may include the stimulus of some or all of the degrees of freedom, dimensions and domains of the apparatus.
  • Yet another embodiment of the present invention is directed to a method for rendering a representation of an information bearing function of time.
  • the method includes accessing parameters of a plurality of desired information bearing functions of time, such as signals, waveforms, RF modulated signals, and RF carrier signals, or wave representations or composite waveforms.
  • the plurality of desired information bearing functions of time may be rendered substantially simultaneously (or concurrently or in parallel).
  • Multiple signals (signal subsets) associated with each of the plurality of desired information bearing functions of time are composited.
  • This composition includes, for example, mapping of one or more signals or portions of one or more signals to ranges or domains of functions and their subordinate values according to a dynamic co-variance or cross-correlation of said functions that distribute blended controls to an apparatus which generates signals.
  • the composite statistic of the blended controls is determined by an information source with source entropy of H(x), the number of the available degrees of freedom for the apparatus, the efficiency of each degree of freedom, and the corresponding potential to distribute a specific signal rate as well as information in each degree of freedom.
  • a representation of each of the plurality of the desired information bearing functions of time is generated as a part of the compositing step. This representation may be, for example, a waveform, a signal, an RF modulated signal or electronic data that may be stored on an electronic storage medium, computer-readable medium and/or transmitted to a remote location via a communication medium, such as a network, wireless medium or wired medium.
  • Yet another embodiment of the present invention is directed to a method that includes accounting for a number and/or impact of desired degrees of freedom in a system and accounting for a number and/or impact of undesired degrees of freedom in the system.
  • One or more of the desired degrees of freedom are excited with energetic waveforms and/or signals and/or other excitation source.
  • a response by one or more of the undesired degrees of freedom is assessed.
  • This embodiment is used in a system that has desired degrees of freedom and undesired degrees of freedom.
  • Energy may be applied to the system to excite one or more of the desired degrees of freedom.
  • Undesired degrees of freedom will be excited by the applied energy and a response to the applied energy by the undesired degrees of freedom can be assessed.
  • desired degrees of freedom may be monitored and assessed for corresponding excitations.
  • Yet another embodiment of the present invention is directed to the method described above and also includes utilizing prior characterization (prior knowledge) of the apparatus and desired signal, apriori information, to identify and/or characterize the desired degrees of freedom.
  • This prior knowledge is previously obtained, or previously acquired data about the apparatus and desired information bearing function of time prior to final rendering.
  • the desired information bearing function of time may be, for example, a signal, waveform, RF modulated signal, an RF carrier signal, or wave representation or composite waveforms.
  • Yet another embodiment of the present invention is directed to the method described above and also includes characterizing the desired degrees of freedom for the system. This includes, for example, degrees of freedom that are purposefully designed into the system.
  • Yet another embodiment of the present invention is directed to the method described above, wherein the undesired degrees of freedom include undesirable phenomena scavenging energy. This may include, for example, rotational, translational vibrational, as well as other forms of energy, including apparatus modes which generate heat or any undesirable spurious phenomena.
  • the undesired degrees of freedom include degrees of freedom that are not purposefully designed into the system.
  • Yet another embodiment of the present invention is directed to the method described above and also includes identifying and/or characterizing a total number of degrees of freedom.
  • Yet another embodiment of the present invention is directed to the method described above and also includes estimating a probability or probabilities that one or more of the undesired degrees of freedom will be in an excited state or an relatively unexcited state as well as the probability vs. energy distributed in those states.
  • the effect(s) of one or more of the undesired degrees of freedom are controlled, or moderated, utilizing the estimated probability or probabilities.
  • the probability or probabilities is/are estimated based on prior, or apriori, apparatus characterization and the statistics of the desired information bearing function of time.
  • Yet another embodiment of the present invention is directed to the method described above and also includes identifying one or more thermal characteristics to calculate the probability that one or more of the undesired degrees of freedom will be in an excited or unexcited state as well as the probability vs. energy level distributed in those states.
  • Yet another embodiment of the present invention is directed to a method that includes processing one or more information source inputs, H 1 (x), H 2 (x) . . . H m (x), where m is any suitable integer using FLUTTERTM and blended control algorithms to produce one or more information bearing functions of time.
  • Such information bearing functions of time known also as output signals are enumerated 1, 2 . . . n where n is a suitable integer, are rendered from any number m information sources and FLUTTERTM algorithms via blended controls.
  • any number of m inputs may be mapped to any number of n outputs where m may or may not equal n.
  • Each of the n output signals or alternatively output channels may be a result of independent or dependent compositing.
  • each of the n outputs may share information to any extent required or desired.
  • This algorithm may be used in applications such as multiple input multiple output (MIMO) and diversity processing.
  • n may be less than m, thus mapping m input information sources to fewer output signals.
  • embodiments of the present invention are desired to not encompass any previously known product, process of making the product, or method of using the product such that Applicants reserve the right and hereby disclose a disclaimer of any previously known product, process, or method. It is further noted that embodiments of the present invention do not intend to encompass within the scope of the invention any product, process, or making of the product or method of using the product, which does not meet the written description and enablement requirements of the USPTO (35 U.S.C. ⁇ 112, first paragraph) or the EPO (Article 83 of the EPC), such that Applicants reserve the right and hereby disclose a disclaimer of any previously described product, process of making the product, or method of using the product.
  • FIG. 1 shows a block diagram of inter connect and relation between FLUTTERTM, blended control and compositing.
  • FIG. 2 shows a block diagram of a modulator apparatus with blended controls.
  • FIG. 3 shows a diagram of energy transformation and entropy processing with blended controls.
  • FIG. 5 shows a block diagram illustrating modification of H(x) by channel.
  • FIG. 6 shows a graphical representation of an approximate Gaussian Probability Density Function (pdf) with 0.5 mean.
  • FIG. 7 shows a graphical representation of an approximate truncated Gaussian Probability Density Function (pdf).
  • FIG. 8 shows a schematic of a summing node with two input signals and/or waveforms and one output signal.
  • FIGS. 9A and 9B show representations of a differential and single ended Type I series modulator, respectively, that may be used with embodiments of the present invention.
  • FIGS. 10A and 10B show representations of a differential and single ended Type I shunt modulator, respectively, that may be used with embodiments of the present invention.
  • FIG. 11 shows a graphical representation of an approximately Gaussian Probability Density Function (pdf) for output voltage at particular parameters.
  • pdf Probability Density Function
  • FIG. 12 shows a graphical representation of a Probability Density Function (pdf) for the instantaneous efficiency of a particular Type I modulator.
  • pdf Probability Density Function
  • FIG. 13 illustrates a method, using a block diagram, for generating an information bearing function of time using blended controls and compositing.
  • FIG. 14 illustrates a method, using a block diagram, of generating an information bearing function of time using blended controls and compositing.
  • FIG. 15 shows an example of a parallel channel configuration to reduce Peak Average Power Ratio (PAPR) per branch.
  • PAPR Peak Average Power Ratio
  • FIG. 16 shows an example of pseudo-phase space samples with three possible energy partitions.
  • FIG. 17 shows a graphical representation of an approximate Gaussian Probability Density Function (pdf) for output voltage at certain parameters, illustrating an example associated with three energy partitions.
  • pdf Gaussian Probability Density Function
  • FIG. 18 shows a block diagram of a circuit that transitions as a statistically influenced boundary is traversed.
  • FIG. 19 shows a graphical representation of instantaneous waveform efficiency as a function of energy partition number for a modulator.
  • FIG. 20 shows an example of a series Type II modulator.
  • FIG. 21 shows an example of a shunt Type II modulator.
  • FIG. 22 illustrates an information and energy partition organization in terms of topological signal flow.
  • FIGS. 23A and 23B show a particular graphical illustration of differential magnitude and differential phase entropy surfaces, respectively.
  • FIGS. 24A and 24B show a particular graphical illustration of reduced differential magnitude and differential phase entropy surfaces, respectively.
  • FIG. 25 shows an example of a composite statistic of the information bearing function of time and statistics of domains of signals plotted on voltage and probability axes.
  • FIG. 26 shows a flowchart for synthesizing FLUTTERTM and blended controls.
  • FIG. 27 shows an example of a circuit using FLUTTERTM with (i) fixed power source partitions and v auxiliary degrees of freedom.
  • FIG. 28 shows an example of a Thévenized equivalent of FIG. 27 .
  • FIG. 29 shows an example of a circuit using FLUTTERTM with switching or variable power supplies for one or more of the energy partitions.
  • FIG. 30 shows of a series equivalent of FIG. 29 .
  • FIG. 31 shows an example of a modulator architecture which may be used with the FLUTTERTM algorithm.
  • FIG. 32 shows an example of a modulator architecture which may be used with the FLUTTERTM algorithm.
  • FIG. 33 shows an example of some signals associated with application of blended controls as part of the FLUTTERTM algorithm.
  • FIG. 34 shows an example of some signals associated with application of blended controls as part of the FLUTTERTM algorithm.
  • FIG. 35 shows a cascaded switch structure
  • FIG. 36 shows a parallel switch topology
  • FIG. 37 shows an example of one or more composite information bearing functions of time, constructed from one or more information sources, using a FLUTTERTM or blended control based architecture.
  • FIG. 38 shows an example of two dimensional geometrical structures for forming differential surfaces.
  • FIG. 39 shows an example of thermodynamic efficiency enhancement performance plot associated with applications of a FLUTTERTM algorithm to a Type 1 modulator.
  • the first law is often formulated by stating that the change in the internal energy of a closed system is equal to the amount of heat supplied to the system, minus the amount of work done by the system on its surroundings. Other forms of energy (including electrical) may be substituted for heat energy in an extension of the first law formulation.
  • the first law of thermodynamics is an energy conservation law with an implication that energy cannot be created or destroyed. Energy may be transformed or transported but a numerical calculation of the sum total of energy inputs to an isolated process or system will equal the total of the energy stored in the process or system plus the energy output from the process or system.
  • the law of conservation of energy states that the total energy of an isolated system is constant.
  • the first law of thermodynamics is referenced occasionally as simply the first law.
  • thermodynamic entropy is a basic postulate defining the concept of thermodynamic entropy, applicable to any system involving measurable energy transfer (classically heat energy transfer).
  • information entropy is defined from information theory using Shannon's entropy.
  • entropy is a measure of the number of alternative microscopic configurations or states of a system corresponding to a single macroscopic state of the system.
  • One consequence of the second law is that practical physical systems may never achieve 100% thermodynamic efficiency. Also, the entropy of an isolated system will always possess an ever increasing entropy up to the point equilibrium is achieved.
  • the second law of thermodynamics is referred to as simply the second law.
  • ACPR Adjacent Channel Power Ratio usually measured in decibels (dB) as the ratio of an “out of band” power per unit bandwidth to an “in band” signal power per unit bandwidth. This measurement is usually accomplished in the frequency domain. Out of band power is typically unwanted.
  • A.C. An alternating current which corresponds to a change in the direction of charge transport and/or the electromagnetic fields associated with moving charge through a circuit.
  • One direction of current flow is usually labeled as positive and the opposite direction of current flow is labeled as negative and direction of current flow will change back and forth between positive and negative over time.
  • Access Obtain examine or retrieve; ability to use; freedom or ability to obtain or make use of something.
  • Account Record, summarize; keeping a record of; reporting or describing an existence of.
  • a circuit or system/module is A.C. coupled at is interfaced to another circuit or system/module if D.C. current cannot pass through the interface but A.C. current or signal or waveform can pass through the interface.
  • Adjacent channel leakage ratio is a measure of how much signal from a specific channel allocation leaks to an adjacent channel.
  • channel refers to a band of frequencies. Leakage from one band or one channel to another band or channel occurs when signals are processed by nonlinear systems.
  • A/D Analog to digital conversion.
  • Adapt Modify or adjust or reconstruct for utilization.
  • Adjust Alter or change or arrange for a desired result or outcome.
  • Algorithm A set of steps that are followed in some sequence to solve a mathematical problem or to complete a process or operation such as (for example) generating signals according to FLUTTERTM.
  • Align Arrange in a desired formation; adjust a position relative to another object, article or item, or adjust a quality/characteristic of objects, articles or items in a relative sense.
  • Allocate Assign, distribute, designate or apportion.
  • Amplitude A scalar value which may vary with time. Amplitude can be associated as a value of a function according to its argument relative to the value zero. Amplitude may be used to increase or attenuate the value of a signal by multiplying a constant by the function. A larger constant multiplier increases amplitude while a smaller relative constant decreases amplitude. Amplitude may assume both positive and negative values.
  • Annihilation of Information Transfer of information entropy into non-information bearing degrees of freedom no longer accessible to the information bearing degrees of freedom of the system and therefore lost in a practical sense even if an imprint is transferred to the environment through a corresponding increase in thermodynamic entropy.
  • Apparatus Any system or systematic organization of activities, algorithms, functions, modules, processes, collectively directed toward a set of goals and/or requirements:
  • An electronic apparatus consists of algorithms, software, functions, modules, and circuits in a suitable combination depending on application which collectively fulfill a requirement.
  • Application phase space is a higher level of abstraction than phase space.
  • Application phase space consists of one or more of the attributes of phase space organized at a macroscopic level with modules and functions within the apparatus.
  • Phase space may account for the state of matter at the microscopic (molecular) level but application phase space includes consideration of bulk statistics for the state of matter where the bulks are associated with a module function, or degree of freedom for the apparatus.
  • Approximate Approximate: almost correct or exact; close in value or amount but not completely precise; nearly correct or exact.
  • apriori What can be known based on inference from common knowledge derived through prior experience, observation, characterization and/or measurement. Formed or conceived beforehand; relating to what can be known through an understanding of how certain things work rather than by observation; presupposed by experience. Sometimes separated as a priori.
  • Time Auto Correlation Method of comparing a signal with or waveform itself. For example, Time Auto Correlation function compares a time shifted version of a signal or waveform with itself. The comparison is by means of correlation.
  • Auto Covariance Method of comparing a signal or waveform with itself once the average value of the signal/or waveform is removed. For example, a time auto covariance function compares a signal or waveform with a time shifted version of said signal or waveform.
  • Bandwidth Frequency span over which a substantial portion of a signal is restricted or distributed according to some desired performance metric. Often a 3 dB power metric is allocated for the upper and lower band (span) edge to facilitate the definition. However, sometimes a differing frequency span vs. power metric, or frequency span vs. phase metric, or frequency span vs. time metric, is allocated/specified. Frequency span may also be referred to on occasion as band, or bandwidth depending on context.
  • Baseband Range of frequencies near to zero Hz. and including zero Hz.
  • Bin A subset of values or span of values within some range or domain.
  • Bit Unit of information measure (binary digit) calculated using numbers with a base 2.
  • Blended Controls A set of dynamic distributed control signals generated as part of the FLUTTERTM algorithm, used to program, configure, and dynamically manipulate the information encoding and modulation facilities of a communications apparatus.
  • Blended Control Function Set of dynamic and configurable controls which are distributed to an apparatus according to an optimization algorithm which accounts for H(x), the input information entropy, the waveform standard, significant hardware variables and operational parameters. Blended control functions are represented by ⁇ tilde over (I) ⁇ H(x) v,i ⁇ where v+i is the total number of degrees of freedom for the apparatus which is being controlled.
  • BLENDED CONTROL BY PARKERVISIONTM is a registered trademark of ParkerVision, Inc., Jacksonville, Fla.
  • Branch A path within a circuit or algorithm or architecture.
  • Bus One or more than one interconnecting structure such as wires or signal lines which may interface between circuits or modules and transport digital or analog information or both.
  • Capacity The maximum possible rate for information transfer through a communications channel, while maintaining a specified quality metric. Capacity may also be designated (abbreviated) as C, or C with possibly a subscript, depending on context. It should not be confused with Coulomb, a quantity of charge. On occasion capacity is qualified by some restrictive characteristics of the channel.
  • Cascading Transferring or representing a quantity or multiple quantities sequentially. Transferring a quantity or multiple quantities sequentially.
  • Cascoding Using a power source connection configuration to increase potential energy.
  • a causal system means that a system's output response (as a function of time) cannot precede its input stimulus.
  • CDF or cdf Cumulative Distribution Function in probability theory and statistics, the cumulative distribution function (CDF), describes the probability that a real-valued random variable X with a given probability distribution will be found at a value less than or equal to x. Cumulative distribution functions are also used to specify the distribution of multivariate random variables. A cdf may be obtained through an integration or accumulation over a relevant pdf domain.
  • Characterization Describing the qualities or attributes of something. The process of determining the qualities or attributes of an object, or system.
  • Channel Frequency The center frequency for a channel.
  • the center frequency for a range or span of frequencies allocated to a channel.
  • Charge Fundamental unit in coulombs associated with an electron or proton, ⁇ 1.602 ⁇ 10 ⁇ 19 C, or an integral multiplicity thereof.
  • Code A combination of symbols which collectively possess an information entropy.
  • Communications Channel Any path possessing a material and/or spatial quality that facilitates the transport of a signal.
  • Communications Sink Targeted load for a communications signal or an apparatus that utilizes a communication signal. Load in this circumstance refers to a termination which consumes the application signal and dissipates energy.
  • Complex Number A number which has two components; a real part and an imaginary part.
  • the imaginary part is usually associated with a multiplicative symbol i) or j) which has a value ⁇ square root over ( ⁇ 1) ⁇ .
  • the numbers are used to represent values on two different number lines and operations or calculations with these numbers require the use of complex arithmetic.
  • Complex arithmetic and the associated numbers are used often in the study signals, mathematical spaces, physics and many branches of science and engineering.
  • Complex Signal Envelope A mathematical description of a signal, x(t), suitable for RF as well as other applications.
  • the various quantities and relationships that follow may be derived from one another using vector analysis and trigonometry as well as complex arithmetic.
  • ⁇ ⁇ ( t ) arc ⁇ ⁇ tan ⁇ [ a Q ⁇ ( t ) a I ⁇ ( t ) ] ⁇ [ sign ]
  • [sign] ⁇ A function which accounts for the quadrant of ⁇ (t) in the complex signal/waveform plane
  • complex envelope which accounts for the quadrant of ⁇ (t) in the complex signal/waveform plane
  • Compositing The mapping of one or more constituent signals or portions of one or more constituent signals to domains and their subordinate functions and arguments according to a FLUTTERTM algorithm. Blended controls developed in the FLUTTERTM algorithm, regulate the distribution of information to each constituent signal. The composite statistic of the blended controls is determined by an information source with source entropy of H(x), the number of the available degrees of freedom for the apparatus, the efficiency of each degree of freedom, and the corresponding potential to distribute a specific signal rate, as well as information, in each degree of freedom.
  • Constellation Set of coordinates in some coordinate system with an associated pattern.
  • Constellation Point A single coordinate from a constellation.
  • Constituent Signal A signal which is part of a parallel processing path in FLUTTERTM and used to form more complex signals through compositing or other operations.
  • Coordinate A value which qualifies and/or quantifies position within a mathematical space. Also may possess the meaning; to manage a process.
  • Correlation The measure by which the similarity of two or more variables may be compared.
  • a measure of 1 implies they are equivalent and a measure of 0 implies the variables are completely dissimilar.
  • a measure of ( ⁇ 1) implies the variables are opposite or inverse. Values between ( ⁇ 1) and (+1) other than zero also provide a relative similarity metric.
  • Covariance This is a correlation operation between two different random variables for which the random variables have their expected values or average values extracted prior to performing correlation.
  • Cross-Covariance Covariance between two different random variables.
  • d2pTM Direct to Power (Direct2PowerTM) a registered trademark of ParkerVision Inc., corresponding to a proprietary RF modulator and transmitter architecture and modulator device.
  • Direct2PowerTM Direct to Power
  • Data Rates A rate of information flow per unit time.
  • D.C. Direct Current referring to the average transfer of charge per unit time in a specific path through a circuit. This is juxtaposed to an AC current which may alternate directions along the circuit path over time. Generally a specific direction is assigned as being a positive direct current and the opposite direction of current flow through the circuit is negative.
  • a circuit or system/module is D.C. coupled at its interface to another circuit or system/module if D.C. current or a constant waveform value may pass through the interface.
  • DCPS Digitally Controlled Power or Energy Source
  • Decoding Process of extracting information from an encoded signal.
  • Decoding Time The time interval to accomplish a portion or all of decoding.
  • Degrees of Freedom A subset of some space (for instance phase space) into which energy and/or information can individually or jointly be imparted and extracted according to qualified rules which may determine codependences. Such a space may be multi-dimensional and sponsor multiple degrees of freedom. A single dimension may also support multiple degrees of freedom. Degrees of freedom may possess any dependent relation to one another but are considered to be at least partially independent if they are partially or completely uncorrelated. Degrees of freedom also possess a corresponding realization in the information encoding and modulation functions of a communications apparatus. Different mechanisms for encoding information in the apparatus may be considered as degrees of freedom.
  • Dirac delta function In mathematics, the Dirac delta function, or ⁇ function, is a generalized function, or distribution, on the real number line that is zero everywhere except at the specified argument of the function, with an integral equal to the value one when integrated over the entire real line.
  • a weighted delta function is a delta function multiplied by a constant or variable.
  • Density of States for Phase Space Function of a set of relevant coordinates of some mathematical, geometrical space such as phase space which may be assigned a unique time and/or probability, and/or probability density.
  • the probability densities may statistically characterize meaningful physical quantities that can be further represented by scalars, vectors and tensors.
  • Derived Originating from a source in a manner which may be confirmed by measure, analysis, or inference.
  • Desired Degree of Freedom A degree of freedom that is efficiently encoded with information. These degrees of freedom enhance information conservation and are energetically conservative to the greatest practical extent. They are also known as information bearing degrees of freedom. These degrees of freedom may be deliberately controlled or manipulated to affect the causal response of a system through, and application of, algorithm or function such as a blended control function enabled by a FLUTTERTM algorithm.
  • Dimension A metric of a mathematical space.
  • a single space may have one or more than one dimension. Often, dimensions are orthogonal. Ordinary space has 3-dimensions; length, width and depth. However, dimensions may include time metrics, code metrics, frequency metrics, phase metrics, space metrics and abstract metrics as well, in any suitable quantity or combination.
  • Domain A range of values or functions of values relevant to mathematical or logical operations or calculations. Domains may encompass processes associated with one or more degrees of freedom and one or more dimensions and therefore bound hyper-geometric quantities. Domains may include real and imaginary numbers, and/or any set of logical and mathematical functions and their arguments.
  • Encoding Process of imprinting information onto a waveform to create an information bearing function of time.
  • Encoding Time Time interval to accomplish, a portion or all, encoding.
  • Energy Capacity to accomplish work where work is defined as the amount of energy required to move an object or associated physical field (material or virtual) through space and time. Energy may be measured in units of Joules.
  • Energy Function Any function that may be evaluated over its arguments to calculate the capacity to accomplish work, based on the function arguments. For instance, energy may be a function of time, frequency, phase, samples, etc. When energy is a function of time it may be referred to as instantaneous power or averaged power depending on the context and distribution of energy vs. some reference time interval. One may interchange the use of the term power and energy given implied or explicit knowledge of some reference interval of time over which the energy is distributed. Energy may be quantified in units of Joules.
  • Energy Partition A function of a distinguishable gradient field, with the capacity to accomplish work. Partitions may be specified in terms of functions of energy, functions of power, functions of current, functions of voltage, or some combination of this list.
  • Energy partitions are distinguished by distinct ranges of variables which define them. For instance, out of i possible energy domains the k th energy domain may associate with a specific voltage range or current range or energy range or momentum range . . . etc.
  • Energy Source or Sources A device or devices which supplies or supply energy from one or more access nodes of the source or sources to one or more apparatuses.
  • One or more energy sources may supply a single apparatus.
  • One or more energy sources may supply more than one apparatus.
  • Entropy is an uncertainty metric proportional to the logarithm of the number of possible states in which a system may be found according to the probability weight of each state.
  • Information entropy is the uncertainty of an information source based on all the possible symbols from the source and their respective probabilities.
  • Physical entropy is the uncertainty of the states for a physical system with a number of degrees of freedom. Each degree of freedom may have some probability of energetic excitation.
  • Equilibrium is a state for a system in which entropy is stable, i.e., no longer changing.
  • Ergodic Stochastic processes for which statistics derived from time samples of process variables correspond to the statistics of independent ensembles selected from the process. For ergodic ensemble, the average of a function of the random variables over the ensemble is equal with probability unity to the average over one or more possible time translations of a particular member function of the ensemble, except for a subset of representations of measure zero. Although processes may not be perfectly ergodic they may be suitably approximated as so under a variety of practical circumstances.
  • Electromagnetic transmission medium usually ideal free space unless otherwise implied. It may be considered as an example of a physical channel.
  • EVM Error Vector Magnitude applies to a sampled signal that is described in vector space. The ratio of power in the unwanted variance (or approximated variance) of the signal at the sample time to the root mean squared power expected for a proper signal.
  • CFF closed loop feed forward
  • Feed forward The direction of signal flow from input to output of a circuit or module or apparatus. Present output values of such architectures or topologies are not returned or “fed back” to portions of the circuit or module in a manner to influence future outputs using control loops. Sometimes this may be referred to as open loop feed forward (OLFF) to indicate the absence of a control loop in the architecture.
  • OLFF open loop feed forward
  • FLUTTERTM Algorithm which manages one or more of the degrees of freedom of a system to efficiently distribute energy via blended control functions to functions/modules within a communications apparatus.
  • FLUTTERTM is a registered trademark of ParkerVision, Inc. Jacksonville, Fla.
  • Frequency (a) Number of regularly occurring particular distinguishable events per unit time, usually normalized to a per second basis. Number of cycles or completed alternations per unit time of a wave or oscillation, also given in Hertz (Hz) or radians per second (in this case cycles or alternations are considered events). The events may also be samples per unit time, pulses per unit time, etc. An average rate of events per unit time.
  • frequency relates to how often or how likely the occurrence of an event is relative to some total number of possible occurrences. The number of occurrences of a particular value or quality may be counted and compared to some total number to obtain a frequency.
  • Frequency Span Range of frequency values. Band of frequency values. Channel.
  • I ⁇ ⁇ or ⁇ tilde over (I) ⁇ ⁇ are used to indicate a “function of” the quantity or expression (also known as argument) in the bracket ⁇ ⁇ .
  • the function may be a combination of mathematical and/or logical operation.
  • Harmonic Possessing a repetitive or rhythmic quality, rhythm or frequency which may be assigned units of Hertz (Hz) or radians per second (rad/s) or integral multiples thereof. For instance a signal with a frequency of ⁇ c possesses a first harmonic of 1 ⁇ c Hz, a second harmonic of 2 ⁇ c Hz, a third harmonic of 3 ⁇ c Hz, so on and so forth.
  • the frequency 1 ⁇ c Hz or simply ⁇ c Hz is known as the fundamental frequency.
  • Hyper-Geometric Manifold Mathematical surface described in a space with 4 or more dimensions. Each dimension may also consist of complex quantities.
  • Impedance A measure to the opposition of time varying current flow in a circuit.
  • the impedance is represented by a complex number with a real part or component also called resistance and an imaginary part or component also called a reactance.
  • the unit of measure is ohms.
  • Imprint The process of replicating information, signals, patterns, or set of objects. A replication of information, signals, patterns, or set of objects.
  • a message contains a quantity of information determined by the accumulation of the following; the logarithm of a symbol probability multiplied by the negative of the symbol probability, for one or more symbols of the message.
  • symbol refers to some character or representation from a source alphabet which is individually distinguishable and occurs with some probability in the context of the message.
  • Information is therefore a measure of uncertainty in data, a message or the symbols composing the message.
  • the calculation described above is an information entropy measure. The greater the entropy the greater the information content.
  • Information can be assigned the units of bits or nats depending on the base of the logarithm.
  • An event is a physical action or reaction which is instructed or controlled by the symbols from a message.
  • information bearing degrees of freedom are degrees of freedom which may be encoded with information.
  • H(p(x)) is also given the abbreviated notation H(x) and refers to the entropy of a source alphabet with probability density p(x), or the uncertainty associated with the occurrence of symbols (x) from a source alphabet.
  • the metric H(x) may have units of bits or bits/per second depending on context but is defined by
  • H ⁇ ( x ) - ⁇ p ⁇ ( x ) ⁇ log b ⁇ p ⁇ ( x ) ⁇ ⁇ x m ⁇ ( x )
  • Information Stream A sequence of symbols or samples possessing an information metric. For instance, a code is an example of an information stream. A message is an example of an information stream.
  • Input Sample An acquired quantity or value of a signal, waveform or data stream at the input to a function, module, apparatus, or system.
  • Instantaneous Efficiency This is a time variant efficiency obtained from the ratio of the instantaneous output power divided by the instantaneous input power of an apparatus, accounting for statistical correlations between input and output. The ratio of output to input powers may be averaged.
  • Integrate This term can mean to perform the mathematical operation of integration or to put together some number of constituents or parts to form a whole.
  • Interface A place or area where different objects or modules or circuits, meet and communicate or interact with each other or values or attributes or quantities are exchanged.
  • Intermodulation Distortion Distortion arising from nonlinearities of a system. These distortions may corrupt a particular desired signal as it is processed through the system.
  • Line A geometrical object which exists in two or more dimensions of a referenced coordinate system.
  • a line possesses a continuous specific sequence of coordinates within the reference coordinate system and also possesses a finite derivative at every coordinate (point) along its length.
  • a line may be partially described by its arc length and radius of curvature. The radius of curvature is greater than zero at all points along its length.
  • a curved line may also be described by the tip of a position vector which accesses each point along the line for a prescribed continuous phase function and prescribed continuous magnitude function describing the vector in a desired coordinate system.
  • Line Segment A portion of a line with a starting coordinate and an ending coordinate.
  • Linear Pertaining to a quality of a system to convey inputs of a system to the output of the system.
  • a linear system obeys the principle of superposition.
  • Linear Operation Any operation of a module system or apparatus which obeys the principle of superposition.
  • Logic A particular mode of reasoning viewed as valid or faulty, a system of rules which are predictable and consistent.
  • Logic Function A circuit, module, system or processor which applies some rules of logic to produce an output from one or more inputs.
  • Macroscopic Degrees of Freedom The unique portions of application phase space possessing separable probability densities that may be manipulated by unique physical controls derivable from the function ⁇ tilde over (I) ⁇ H(x) v i ⁇ and/or ⁇ tilde over (I) ⁇ H(x) v,i ⁇ sometimes referred to as blended controls or blended control signals.
  • This function takes into consideration, or accounts for, desired degrees of freedom and undesired degrees of freedom for the system.
  • These degrees of freedom can be a function of system variables and may be characterized by prior knowledge of the apparatus a priori information.
  • Magnitude A numerical quantitative measurement or value proportional to the square root of a squared vector amplitude.
  • Manifold A surface in 3 or more dimensions which may be closed.
  • Manipulate To move or control; to process using a processing device or algorithm:
  • Mathematical Description Set of equations, functions and rules based on principles of mathematics characterizing the object being described.
  • Metrics A standard of measurement; a quantitative standard or representation; a basis for comparing two or more quantities. For example, a quantity or value may be compared to some reference quantity or value.
  • Microscopic degrees of freedom are spontaneously excited due to undesirable modes within the degrees of freedom. These may include, for example, unwanted Joule heating, microphonics, photon emission, electromagnetic (EM) field emission and a variety of correlated and uncorrelated signal degradations.
  • undesirable modes within the degrees of freedom may include, for example, unwanted Joule heating, microphonics, photon emission, electromagnetic (EM) field emission and a variety of correlated and uncorrelated signal degradations.
  • MIMO Multiple input multiple output system architecture.
  • MISO Multiple input single output operator.
  • Mixture A combination of two or more elements; a portion formed by two or more components or constituents in varying proportions.
  • the mixture may cause the components or constituents to retain their individual properties or change the individual properties of the components or constituents.
  • Partition consisting of scalars, vectors tensors with real or imaginary number representation in any combination.
  • MMSE Minimum Mean Square Error. Minimizing the quantity ( ⁇ tilde over (X) ⁇ X) 2 where ⁇ tilde over (X) ⁇ is the estimate of X, a random variable. ⁇ tilde over (X) ⁇ is usually an observable from measurement or may be derived from an observable measurement, or implied by the assumption of one or more statistics.
  • Modes The manner in which energy distributes into degrees of freedom. For instance, kinetic energy may be found in vibrational, rotational and translation forms or modes. Within each of these modes may exist one or more than one degree of freedom. In the case of signals for example, the mode may be frequency, or phase or amplitude, etc., Within each of these signal manifestations or modes may exist one or more than one degree of freedom.
  • Modulation A change in a waveform, encoded according to information, transforming the waveform to a signal.
  • Modulation Architecture A system topology consisting of modules and/or functions which enable modulation.
  • Modulated Carrier Signal A sine wave waveform of some physical quantity (such as current or voltage) with changing phase and/or changing amplitude and/or changing frequency where the change in phase and amplitude are in proportion to some information encoded onto the phase and amplitude.
  • the frequency may also be encoded with information and therefore change as a consequence of modulation.
  • Module A processing related entity, either hardware, software, or a combination of hardware and software, or software in execution.
  • a module may be, but is not limited to being, a process running on a processor or microprocessor, an object, an executable, a thread of execution, a program, and/or a computer.
  • One or more modules may reside within a process and/or thread of execution and a module may be localized on one chip or processor and/or distributed between two or more chips or processors.
  • the term “module” also means software code, machine language or assembly language, an electronic medium that may store an algorithm or algorithms or a processing unit that is adapted to execute program code or other stored instructions.
  • a module may also consist of analog, or digital and/or software functions in some combination or separately. For example an operational amplifier may be considered as an analog module.
  • Multiplicity The quality or state of being plural or various.
  • Node A point of analysis, calculation, measure, reference, input or output, related to procedure, algorithm, schematic, block diagram or other hierarchical object. Objects, functions, circuits or modules attached to a node of a schematic or block diagram access the same signal and/or function of signal common to that that node.
  • Non Central As pertains to signals or statistical quantities; the signals or statistical quantities are characterized by nonzero mean random processes or random variables.
  • Non-Excited The antithesis of excited. (see unexcited)
  • Non-Linear Not obeying the principle of super position. A system or function which does not obey the superposition principle.
  • Non-Linear Operation Function of an apparatus, module, or system which does not obey superposition principles for inputs conveyed through the system to the output.
  • Nyquist Rate A rate which is 2 times the maximum frequency of a signal to be reproduced by sampling.
  • Nyquist Shannon Criteria also called the Nyquist-Shannon sampling criteria; requires that the sample rate for reconstructing a signal or acquiring/sampling a signal be at least twice the bandwidth of the signal (usually associated as an implication of Shannon's work). Under certain conditions the requirement may become more restrictive in that the required sample rate may be defined to be twice the frequency of the greatest frequency of the signal being sampled, acquired or reconstructed (usually attributed to Nyquist). At baseband, both interpretations apply equivalently. At pass band it is theoretically conceivable to use the first interpretation, which affords the lowest sample rate.
  • An object may be abstract or material, of mathematical nature, an item or a representation depending on the context of use.
  • “on the fly” This term refers to a substantially real time operation which implements an operation or process with minimal delay maintaining a continuous time line for the process or operation.
  • the response to each step of the operation, or procedure organizing the operation responds in a manner substantially unperceived by an observer compared to some acceptable norm.
  • Optimize Maximize or Minimize one or more quantities and/or metrics of features subject to a set of constraints.
  • PAER Peak to Average Energy Ratio which can be measured in dB if desired. It may also be considered as a statistic or statistical quantity for the purpose of this disclosure. It is obtained by dividing the peak energy for a signal or waveform by its average energy.
  • PAPR Peak to Average Power Ratio which can be measured in dB if desired.
  • PAPR is the peak to average power of a signal or waveform determined by dividing the instantaneous peak power excursion for the signal or waveform by its average power value. It may also be considered as a statistic or statistical quantity for the purpose of this disclosure.
  • Peak to Average Power Ratio which can be measured in dB if desired.
  • PAPR sig is the peak to average power of a signal determined by dividing the instantaneous peak power excursion for the signal by its average power value. It may also be considered as a statistic or statistical quantity for the purpose of this disclosure
  • Parallel Paths A multiplicity of paths or branches possessing the attribute of a common direction of signal or process flow through a module, circuit, system or algorithm. In a simple case parallel paths may possess a comment source terminal or node and a common ending node or terminus. Each path or branch may implement unique processor or similar processes.
  • Parameter A value or specification which defines a characteristic of a system, module, apparatus, process, signal or waveform. Parameters may change.
  • Parsing The act of dividing, sub dividing, distributing or partitioning.
  • Partitions Boundaries within phase space that enclose points, lines, areas and volumes. They may possess physical or abstract description, and relate to physical or abstract quantities. Partitions may overlap one or more other partitions. Partitions may be described using scalars, vectors, tensors, real or imaginary numbers along with boundary constraints. Partitioning is the act of creating partitions.
  • Pass band Range of frequencies with a substantially defined range or channel not possessing DC response or zero Hz frequency content.
  • Patches A geometrical structure used as a building block to approximate a surface rendering from one or more patches.
  • Probability Distribution Function is a mathematical function relating a value from a probability space to another space characterized by random variables.
  • Probability Density Function is the probability that a random variable or joint random variables possess versus their argument values.
  • the pdf may be normalized so that the accumulated values of the probability space possesses a measure of the CDF.
  • Phase Space A conceptual space that may be composed of real physical dimensions as well as abstract mathematical dimensions, and described by the language and methods of physics, probability theory and geometry.
  • the phase space contemplates the state of matter within the phase space boundary, including the momentum and position for material of the apparatus.
  • Plane Two dimensional geometrical object which, is defined by two straight lines.
  • Point One dimensional mathematical or geometrical object, a single coordinate of a coordinate system.
  • Power Function Energy function per unit time or the partial derivative of an energy function with respect to time. If the function is averaged it is an average power. If the function is not averaged it may be referred to as an instantaneous power. It has units of energy per unit time and so each coordinate of a power function has an associated energy which occurs at an associated time. A power function does not alter or change the units of its time distributed resource (i.e. energy in Joules).
  • Power Level A quantity with the metric of Joules per second.
  • Power Source or Sources An energy source or sources which is/are described by a power function or power functions. It may possess a single voltage and/or current or multiple voltages and/or currents deliverable to an apparatus or a load. A power source may also be referred to as power supply.
  • Probability Frequency of occurrence for some event or events which may be measured or predicted from some inferred statistic.
  • Processing The execution of a set of operations to implement a process or procedure.
  • Processing Paths Sequential flow of functions, modules, and operations in an apparatus, algorithm, or system to implement a process or procedure.
  • Pseudo-Phase Space A representation of phase space or application phase space which utilizes variables common to the definition of the apparatus such as voltage, current, signal, complex signal, amplitude, phase, frequency, etc. These variables are used to construct a mathematical space related to the phase space. That is, there is a known correspondence in change for the pseudo-phase space for a change in phase space and vice versa.
  • Quadrature phase of a complex signal also called the complex part of the signal.
  • Radial Difference Difference in length along a straight line segment or vector which extends along the radial of a spherical or a cylindrical coordinate system
  • Radio Frequency Typically a rate of oscillation in the range of about 3 kHz to 300 GHz, which corresponds to the frequency of radio waves, and the alternating currents (AC), which carry radio signals.
  • RF usually refers to electrical rather than mechanical oscillations, although mechanical RF systems do exist.
  • Random Not deterministic or predictable.
  • Random Process An uncountable, infinite, time ordered continuum of statistically independent random variables.
  • a random process may also be approximated as a maximally dense time ordered continuum of substantially statistically independent random variables.
  • Random Variable Variable quantity which is non-deterministic, or at least partially so, but may be statistically characterized. Random variables may be real or complex quantities.
  • Range A set of values or coordinates from some mathematical space specified by a minimum and a maximum for the set
  • Rate Frequency of an event or action.
  • Real Component The real portion/component of a complex number sometimes associated with the in-phase or real portion/component of a signal, current or voltage. Sometimes associated with the resistance portion/component of an impedance.
  • Reconstituted A desired result formed from one or more than one operation and multiple contributing portions.
  • Relaxation Time A time interval for a process to achieve a relatively stable state or a relative equilibrium compared to some reference event or variable state reference process. For instance a mug of coffee heated in a microwave eventually cools down to assume a temperature nearly equal to its surroundings. This cooling time is a relaxation time differentiating the heated state of the coffee and the relatively cool state of the coffee?
  • Rendered Synthesized, generated or constructed or the result of a process, procedure, algorithm or function.
  • Rendered Signal A signal which has been generated as an intermediate result or a final result depending on context.
  • a desired final RF modulated output can be referred to as a rendered signal.
  • Rendering Bandwidth Bandwidth available for generating a signal or waveform.
  • Rendering Parameters Parameters which enable the rendering process or procedure.
  • a characterization or description for an object, or entity This may be for example, a mathematical characterization, graphical representation, model, . . . etc.
  • Rotational Energy Kinetic energy associated with circular or spherical motions.
  • Sample An acquired quantity or value. A generated quantity or value.
  • Sample Functions Set of functions which consist of arguments to be measured or analyzed or evaluated. For instance, multiple segments of a waveform or signal could be acquired or generated (“sampled”) and the average, power, or correlation to some other waveform, estimated from the sample functions.
  • Sample Regions Distinct spans, areas, or volumes of mathematical spaces which can contain, represent and accommodate a coordinate system for locating and quantifying the metrics for samples contained within the region.
  • Scalar Partition Any partition consisting of scalar values.
  • a collection A collection, an aggregate, a class, or a family of any objects.
  • Signal An example of an information bearing function of time, also referred to as information bearing energetic function of time and space that enables communication.
  • Signal Constellation Set or pattern of signal coordinates in the complex plane with values determined from a I (t) and a Q (t) and plotted graphically with a I (t) versus a Q (t) or vice versa. It may also apply to a set or pattern of coordinates within a phase space.
  • a I (t) and a Q (t) are in phase and quadrature phase signal amplitudes respectively.
  • a I (t) and a Q (t) are functions of time obtained from the complex envelope representation for a signal.
  • Signal Efficiency Thermodynamic efficiency of a system accounting only for the desired output average signal power divided by the total input power to the system on the average.
  • Signal Ensemble Set of signals or set of signal samples or set of signal sample functions.
  • Signal Envelope Magnitude This quantity is obtained from (a I 2 +a Q 2 ) 1/2 where a I is the in phase component of a complex signal and a Q is the quadrature phase component of a complex signal. a I and a Q may be functions of time.
  • Signal of Interest Desired signal. Signal which is the targeted result of some operation, function, module or algorithm.
  • the sign function is determined from the signs of a Q , a I to account for the repetition of modulo tan a Q /a I .
  • a I (t) and a Q (t) are in phase and quadrature phase signal amplitudes respectively.
  • a I (t) and a Q (t) are functions of time obtained from the complex envelope representation for a signal.
  • a signal or signals may be allocated to separate domains of a FLUTTERTM processing algorithm. Within a domain a signal may possess one or more partitions. The signal partitions are distinct ranges of amplitude, phase, frequency and/or encoded waveform information. The signal partitions are distinguishable by some number of up to and including v degrees of freedom they associate with where that number is less than or equal to the number of degrees of freedom for a domain or domains to which a signal partition belongs.
  • Sources Origination of some quantity such as information, power, energy, voltage or current.
  • Space A region characterized by span or volume which may be assigned one or more dimensional attributes.
  • Space may be a physical or mathematical construct or representation. Space possesses a quality of dimension or dimensions with associated number lines or indexing strategies suitable for locating objects assigned to the space their relative positions as well as providing a metric for obtaining characteristics of the assigned objects. Space may be otherwise defined by an extent of continuous or discrete coordinates which may be accessed. Space may be homogeneous or nonhomogeneous. A nonhomogeneous space has continuous and discrete coordinate regions or properties for calculations of metrics within the space which change from some domain or region within the space to another domain or region within the space. A homogeneous space possesses either a continuum of coordinates or a discrete set of coordinates and the rules for calculating metrics do not change as a function of location within the space. Space may possess one or more than one dimension.
  • Spectral Distribution Statistical characterization of a power spectral density.
  • Spurious Energy Energy distributed in unwanted degrees of freedom which may be unstable, unpredictable, etc.
  • Statistic A measure calculated from sample functions of a random variable.
  • Statistical Partition Any partition with mathematical values or structures, i.e., scalars, vectors, tensors, etc., characterized statistically.
  • Stimulus An input for a system or apparatus which elicits a response by the system or apparatus.
  • Storage Module A module which may store information, data, or sample values for future use or processing.
  • Subset A portion of a set. A portion of a set of objects.
  • Sub-Surfaces A portion of a larger surface.
  • Sub-system A portion of a system at a lower level of hierarchy compared to a system.
  • Subordinate A lower ranking of hierarchy or dependent on a higher priority process, module, function or operation.
  • Suitable Acceptable, desirable, compliant to some requirement, specification, or standard.
  • I ⁇ ⁇ may be applied to the sum of one or more inputs or to each input separately then summed to obtain an equivalent result in either case.
  • I ⁇ ⁇ for instance a system description or an equation, is also said to be linear.
  • Switched A discrete change in a values and/or processing path, depending on context. A change of functions may also be accomplished by switching between functions.
  • a segment of a signal (analog or digital), usually associated with some minimum integer information assignment in bits, or nats.
  • System Response A causal reaction of a system to a stimulus.
  • Tensor A mathematical object formed from vectors and arrays of values. Tensors are geometric objects that describe linear relations between vectors, scalars, and other tensors. Elementary examples of such relations include the dot product, the cross product and linear maps. Vectors and scalars themselves are also tensors. A tensor can be represented as a multi-dimensional array of numerical values
  • Tensor Partition Any partition-qualified or characterized by tensors.
  • Thermal Characteristics The description or manner in which heat distributes in the various degrees of freedom for an apparatus.
  • Thermodynamic Efficiency Usually represented by the symbol ⁇ or ⁇ tilde over ( ⁇ ) ⁇ and may be accounted for by application of the 1 st and 2 nd Laws of Thermodynamics.
  • P out is the power in a proper signal intended for the communication sink, load or channel.
  • P in is measured as the power supplied to the communications apparatus while performing it's function.
  • E out corresponds to the proper energy out of an apparatus intended for communication sink, load or channel, while E in is the energy supplied to the apparatus.
  • Thermodynamic Entropy A probability measure for the distribution of energy amongst one or more degrees of freedom for a system. The greatest entropy for a system occurs at equilibrium by definition. It is often represented with the symbol S. Equilibrium is determined when
  • Thermodynamic Entropy Flux A concept related to the study of transitory and non-equilibrium thermodynamics. In this theory entropy may evolve according to probabilities associated with random processes or deterministic processes based on certain system gradients. After a long period, usually referred to as the relaxation time, the entropy flux dissipates and the final system entropy becomes the approximate equilibrium entropy of classical thermodynamics, or classical statistical physics.
  • Thermodynamics A physical science that accounts for variables of state associated with the interaction of energy and matter. It encompasses a body of knowledge based on 4 fundamental laws that explain the transformation, distribution and transport of energy in a general manner.
  • Transformation Changing from one form to another.
  • Transition Changing between states or conditions.
  • Translational Energy Kinetic energy associated with motion along a path or trajectory.
  • Undesired Degree of Freedom A subset of degrees of freedom that give rise to system inefficiencies such as energy loss or the non-conservation of energy and/or information loss and non-conservation of information with respect to a defined system boundary. Loss refers to energy that is unusable for its original targeted purpose.
  • Unexcited State A state that is not excited compared to some relative norm defining excited. A state that is unexcited is evidence that the state is not stimulated. An indication that a physical state is unexcited is the lack of a quantity of energy in that state compared to some threshold value.
  • Variable A representation of a quantity that may change.
  • Variable Energy Source An energy source which may change values, with or without the assist of auxiliary functions, in a discrete or continuous or hybrid manner.
  • Variable Power Supply A power source which may change values, with or without the assist of auxiliary functions, in a discrete or continuous or hybrid manner.
  • Variance In probability theory and statistics, variance measures how far a set of numbers is spread out. A variance of zero indicates that one or more of the values are identical. Variance is always non-negative: a small variance indicates that the data points tend to be very close to the mean (expected value) and hence to each other, while a high variance indicates that the data points are very spread out around the mean and from each other.
  • This definition encompasses random variables that are discrete, continuous, neither, or mixed.
  • the variance can also be thought of as the covariance of a random variable with itself:
  • the variance is also equivalent to the second cumulant of the probability distribution for X.
  • the variance is typically designated as Var(X), ⁇ X 2 , or simply ⁇ 2 (pronounced “sigma squared”).
  • the expression for the variance can be expanded:
  • a mnemonic for the above expression is “mean of square minus square of mean”.
  • Vector Partition Any partition consisting of or characterized by vector values.
  • Vibrational Energy Kinetic energy contained in the motions of matter which rhythmically or randomly vary about some reference origin of a coordinate system.
  • Voltage Electrical potential difference, electric tension or electric pressure (measured in units of electric potential: volts, or joules per coulomb) is the electric potential difference between two points, or the difference in electric potential energy of a unit charge transported between two points. Voltage is equal to the work done per unit charge against a static electric field to move the charge between two points in space. A voltage may represent either a source of energy (electromotive force), or lost, used, or stored energy (potential drop). Usually a voltage is measured with respect to some reference point or node in a system referred to a system reference voltage or commonly a ground potential. In many systems a ground potential is zero volts though this is not necessarily required.
  • Voltage Domain A domain possessing functions of voltage.
  • Voltage Domain Differential Differences between voltages within a domain.
  • Waveform Efficiency This efficiency is calculated from the average waveform output power of an apparatus divided by its averaged waveform input power.
  • Work Energy exchanged between the apparatus and its communications sink, load, or channel as well as its environment, and between functions and modules internal to the apparatus.
  • the energy is exchanged by the motions of charges, molecules, atoms, virtual particles and through electromagnetic fields as well as gradients of temperature.
  • the units of work may be Joules.
  • the evidence of work is measured by a change in energy.
  • a symbol (typically 3 dots or more) used occasionally in equations, drawings and text to indicate an extension of a list of items, symbols, functions, objects, values, etc . . . as required by the context.
  • the notation v 1 , v 2 v n indicates the variable v 1 , the variable v 2 , and all variables up to and including v n , where n is a suitable integer appropriate for the context.
  • the sequence of dots may also appear in other orientations such as vertical column or semicircle configuration.
  • v+i This is the total of the number of desirable degrees of freedom of a FLUTTERTM based system also known as the blended control Span, composed of some distinct number of degrees of freedom v and some number of energy partitions i. v and i are suitable integer values.
  • v i is the i th subset of v degrees of freedom.
  • Each v 1 , v 2 , . . . v i of the set may represent a unique number and combination of the v distinct degrees of freedom.
  • the subscript i indicates an association with the i th energy partition.
  • v i is sometimes utilized as a subscript for FLUTTERTM system variables and/or blended control functions
  • v,i This represents a joint set of values which may be assigned or incremented as required depending on context.
  • the set values v,i are typically utilized as an index for blended control enumeration.
  • ⁇ tilde over (I) ⁇ H(x) v,i ⁇ has the meaning;
  • H(x) v,i may represent some portion of the system entropy H(x) depending on the values assumed by v,i.
  • x ⁇ y The arrow ( ⁇ ) between two representative symbols or variables means that the value on the left approaches the value on the right, for instance, x ⁇ y means x becomes a value substantially the same as y or the variable x is approximately the same as y.
  • x and y can be equations or logical relationships.
  • ⁇ or +/ ⁇ The value or symbol or variable following this ⁇ may assume positive or negative values. For instance, +/ ⁇ V s , means that V s may be positive or negative.
  • + or ⁇ /+ The value or symbol or variable following this + may assume negative or positive values.
  • ⁇ /+V s means that V s may be negative or positive.
  • Integration is a mathematical operation based on the calculus of Newton and Leibnitz which obtains a value for the area of a curve under the function of variable x, ⁇ (x) between the function limits of ll a lower limit value and ul the upper limit value.
  • the brackets indicate a time domain average of the quantity enclosed by the bracket.
  • Embodiments of the present invention are directed to modulation (including RF modulation) as well as information encoding architectures and include allocating resources of the architecture to optimize various forms of power efficiency including thermodynamic efficiency while optimizing the conservation of information transfer through (FLUTTERTM).
  • FLUTTERTM FLUTTERTM is a registered trademark of ParkerVision Inc., Jacksonville, Fla.
  • a variable power supply is an example of an agile energy partition.
  • One such class of power supplies may be a switching power supply, which converts variable charge increments per unit time to a specified voltage by using an impedance and an appropriate filter. Such a supply may also distribute charge to a load where variable potentials may be generated.
  • FLUTTERTM is a distributed modulation algorithm that enables the synthesis of communications signals at specified output powers and frequencies with optimized efficiency.
  • the input interface can be any collection of information samples or suitable continuous information streams.
  • the input information possesses entropy H(x) which may be measured in bits or bits/second. Both discrete and continuous information entropy metrics H(x) may be accommodated.
  • the apparatus may encode information onto the transmitted signal so as to possess multiple degrees of freedom that are excited by parallel domains of information ⁇ tilde over (I) ⁇ H(x) v,i ⁇ which are constructed from the source entropy
  • H(x) ⁇ v is a number of degrees of freedom usually associated with a modulator or encoder
  • i also degrees of freedom
  • H(x) v,i may also be represented as
  • FIG. 1 illustrates a high level operational flow 100 of the FLUTTERTM algorithm (module) 130 along with the analog and compositing segment (module) 131 of the transmitter.
  • the set ⁇ tilde over (I) ⁇ H(x) v,i ⁇ may partially share domains which are dependent through statistical correlations determined from H(x) 101 and the characteristics of the compositing and/or Multiple Input Single Output (MISO) and/or ⁇ operator 131 segment (module). Therefore, the relative prominence or weighting of the ⁇ tilde over (I) ⁇ H(x) v,i ⁇ blended controls are dynamically variable according to the FLUTTERTM algorithm.
  • the blended controls ⁇ tilde over (I) ⁇ H(x) v,i ⁇ may be realized as sampled functions and/or continuous signals generated and distributed by the (VSE) vector synthesis engine (module) 130 .
  • sampled rate of any member of the set of blended controls may be less than the minimum Nyquist sampling rate associated with a final output signal, 120 , providing certain signal processing advantages without sacrificing signal quality or losing information in the modulation process.
  • the bandwidths and power spectral densities associated with each of the blended controls 102 may be unique.
  • the compositing and/or MISO and/or ⁇ operator (module) 131 operations integrate and statistically adjust parallel processing paths, which may be nonlinear.
  • the nonlinearity when present, extends through the FLUTTERTM algorithm and blended controls, analog compositing and/or MISO operations.
  • FLUTTERTM refers to the statistical parsing of information to each blended control from the set ⁇ tilde over (I) ⁇ H(x) v,i ⁇ in a manner which excites the multiple degrees of freedom in the apparatus to form the final desired signal in the most efficient manner to conserve power, conserve information and reduce thermal footprint.
  • the nature of the algorithm 100 is feed forward and does not require feedback. Circuits forming the analog paths are not required to be linear although the final output 120 represents a desired signal with minimal ACPR, harmonics, noise and other artifacts usually associated with nonlinear operations on signals.
  • novel power source(s) which may be described as a digitally controlled power source (DCPS), which may be, for example, unipolar, or bipolar.
  • DCPS digitally controlled power source
  • These novel power source(s) may be described in terms of a digitally controlled switching power supply that is adjustable over a range of values from, for example, approximately 0 volts to V s volts, or ⁇ V s to +V s volts, accommodating maximum and minimum charge transfer at a voltage (for any corresponding load) which may have a relatively low source impedance Z s for the frequency range of interest.
  • Low impedance in this case means, R s , the real portion of Z s , is low compared to the load that is attached to the DCPS.
  • the lowest possible “real” portion of the source impedance Z s is usually desired.
  • the novel power sources provides an alternative, providing efficient “on the fly” signal envelope reconstruction, for RF modulators.
  • PAPR peak to average power ratios
  • the switching power supply becomes more difficult to design if it is used to track the envelope for a waveform during the modulation process. This issue is due, in part, to the rate of change of charge transfer allocated to follow the signal envelope with a specified precision under significant load.
  • the envelope reconstruction in a modern standards based application must be nearly exact.
  • Embodiments of the present invention are directed to architectures and algorithms that can be open loop feed forward schemes (OLFF).
  • OLFF open loop feed forward schemes
  • FLUTTERTM may be used to facilitate practical DCPS design, diverting resources to other degrees of freedom to reconstruct the information bearing function of time, which may be, for example, a waveform, or signal. Manipulation of the energy partition over a specified dynamic range in concert with additional modulator degrees of freedom enhances efficiency and preserves waveform quality.
  • the techniques described in relation to the DCPS may also be used with other suitable switching power supply and energy source technologies as well.
  • FLUTTERTM algorithms control the DCPS by assigning optimal transition states and voltage or current amplitudes at specifically designed instants of time given a fixed number of power source levels and the desired signal statistic. Optimization is determined as a maximization of thermodynamic Efficiency vs. Signal/Waveform quality.
  • a modulation device suitable for use with FLUTTERTM may be, for example, an RF power modulation apparatus capable of implementing standards based communications, yet possessing appropriate degrees of freedom whenever the tradeoff between information capacity and power efficiency and signal quality is a driving concern. It is usually desirable for the modulator to possess more degrees of freedom than legacy modulator architectures reflecting current state of the art.
  • FIG. 2 shows a block diagram 200 that illustrates a modulator, such as, for example a d2pTM apparatus, 214 , power source, or energy source 208 and local oscillator 210 .
  • a modulator such as, for example a d2pTM apparatus, 214 , power source, or energy source 208 and local oscillator 210 .
  • FIG. 2 illustrates a set of controls 202 referred to herein as a blended control function, ⁇ tilde over (I) ⁇ H(x) 1,i , H(x) 2,i , . . . H(x) v,i ⁇ .
  • ⁇ tilde over (I) ⁇ H(x) 1,i ⁇ , and ⁇ tilde over (I) ⁇ H(x) 2,i ⁇ shown as 202 ( a ) and 202 ( b ), respectively, are two of the set of controls 202 that manipulate degrees of freedom for the energy and entropy conversion functions 215 , power source 208 and local oscillator (LO) 210 , respectively.
  • LO local oscillator
  • Degrees of freedom may include, for example, undesired degrees of freedom and desired degrees of freedom.
  • the undesired degrees of freedom scavenge power from the system 200 .
  • the scavenged power is wasted and therefore is not available to support the intended apparatus function and dissipates as unwanted heat.
  • Undesired degrees of freedom include degrees of freedom that are not deliberately designed into the system 200 .
  • the desired degrees of freedom are information bearing and include degrees of freedom that are deliberately designed as part of the system 200 .
  • the desired degrees of freedom are excited or stimulated and the response or reaction of the undesired degrees of freedom is minimized by the FLUTTERTM algorithms, with respect to the degrees of freedom, v (tot) :
  • v (tot) total number of degrees of freedom.
  • v (tot) includes desired degrees of freedom as well as undesired degrees of freedom.
  • i subset of desired degrees of freedom and may also be referred to as a number of energy partitions.
  • Domains are distinguished by, for example, one or more deliberate groupings from the joint set or subsets of v,i where v,i are suitable integers with a span of v+i.
  • the indices v,i enable mathematical accounting associated with operations and functions of the domains.
  • the response to the excitation of the desired degrees of freedom is a known quantity, since the apparatus, or system is programmed for a desired response based on inputs.
  • the apparatus or system may be characterized to obtain parameters, constants and variables associated with the system which become collectively prior knowledge and from a random processes perspective apriori information or knowledge.
  • An embodiment of the present invention, for example the system 200 minimizes the probability of exciting undesired degrees of freedom by maximizing the information rate subject to minimized averaged power and constraining quality metric for the output signal 220 through resource allocation to the desired degrees of freedom.
  • Embodiments of the present invention also monitor/analyze the response of the desired degrees of freedom and the undesired degrees of freedom.
  • the optimization technique allocates resources to desired degrees of freedom to minimize influence of the undesired degrees of freedom, given the goals of efficiency and signal quality.
  • the overall purpose for blended controls ⁇ tilde over (I) ⁇ H(x) 1,i , H(x) 2,i , . . . H(x) v,i ⁇ 202 is to manipulate degrees of freedom for the modulator apparatus 214 in such a manner to maximize ⁇ the thermodynamic efficiency of the modulator apparatus 214 while minimizing unwanted degrees of freedom and constraining the modulator apparatus 214 according to a function of a specified information metric H(x), (see FIG. 3 element 309 ) known as Shannon's Information Entropy.
  • Minimizing the unwanted, or undesired, degrees of freedom controls the probability that the undesired degrees of freedom will be excited when energy is applied to the system, in accordance with information encoding and modulation.
  • ⁇ tilde over (P) ⁇ out Time Averaged power of output contained by the signal of interest only, this excludes noise, ACPR, harmonics, spurious, etc. according to a standard's-based metric.
  • P in Time Averaged power of input provided by one or more power sources such as a battery, for example.
  • E out Time Averaged output energy for the signal of interest.
  • FIG. 2 illustrates the LO (local oscillator) 210 and power source, E s , 208 separate from the modulator apparatus 214 , which may be, for example, a d2pTM modulator apparatus, this is only one embodiment.
  • Architectures which include the LO synthesizer 210 and an agile E s , 208 as well as partitions that completely exclude their control are also embodiments of the present invention and may be considered as part of the algorithm options and technology.
  • P in 212 P out 216 and output signal 220 .
  • Energy and entropy conversion unit 215 receives input with power P in 212 from E s 208 and input from LO synthesizer 210 .
  • the power or energy source 208 may be any A.C. or D.C current or voltage source or combination thereof.
  • the associated characterization pdf for the source may possess stochastic and deterministic attributes.
  • the energy and entropy conversion unit 215 generates output signal 220 , according to a portion of the blended control input 202 .
  • Each of the blended controls ( 202 ) from subsets of combinations and permutations of v. i indices, may be realized by multiple signals per control path. For instance ⁇ tilde over (I) ⁇ H(x) 2,i ⁇ may be instantiated using multiple signals.
  • the signals may be digital, analog, serial, parallel or multiplexed with one or more than one connecting structure such as a wire or bus and a suitable number of connecting nodes.
  • architectures which contemplate “on the fly” control of the system energy source, E s , 208 as one of several degrees of freedom are described. Control of E s 208 over some portion of the dynamic range of signal envelope along with any number of other signal parameters, is one embodiment of FLUTTERTM.
  • FIG. 3 shows an architecture 300 that illustrates an example using optimization parameters.
  • FIG. 3 shows one example of a model that may be adapted to multiple applications that are appropriate for analyzing communication's systems to determine thermodynamic quantities.
  • energy partitions 324 ( a ) . . . ( n ) (where “n” is any suitable number) from the source E s 308 are weighted and transformed according to the associated ⁇ v i 326 ( a ) . . . ( n ) (where “n” is any suitable number) and ⁇ operators to produce a result, as shown in block 319 .
  • the subscript v i pertains to the i th subset from v degrees of freedom.
  • Each v i forms a domain for degrees of freedom associated with i partitions where v,i are suitable integers which may vary.
  • v may vary for each i.
  • ⁇ are a class of mathematical and logical operations which optimize the compositing step in a FLUTTERTM algorithm according to a blended control.
  • the blended controls 330 , 332 and 334 are derived from ⁇ tilde over (I) ⁇ H(x) v,i ⁇ 309 .
  • the thermodynamic entropy flux, S J 350 as well as E e out 352 gives rise to signals and signal energy, which are referred to as essential signals and essential energy.
  • Energy 321 shown as essential energy, as well as unwanted phenomena 322 such as heat, ACPR, inter modulation distortion (IMD) Harmonics, quantization noise, thermal noise, radiation, and/or other waste energy, is also partially stimulated as a function of ⁇ tilde over (I) ⁇ H(x) v,i ⁇ 309 .
  • FIG. 3 does not explicitly illustrate the specific entropy flow; however, it is implied since the input includes Shannon's metric for information entropy.
  • Information entropy and apriori system knowledge is used as a prescription or instruction for developing blended control which motivate or stimulate or excite the various physical degrees of freedom within the apparatus, in turn generating a corresponding causal rise to thermodynamic entropy flux S J 350 which is manifest as a perturbation of the variables within the system phase space.
  • This process is coupled to a modulator apparatus that generates the output signal constellation 318 .
  • FIG. 3 is useful to follow the optimization theory, and the description below provides expressions for Energy and Entropy flux.
  • Energy and Entropy flux are functions of time coordinates in addition to the indices v,i.
  • E e out ⁇ ( t k ) ⁇ v ⁇ ⁇ i ⁇ [ ⁇ v i ⁇ ⁇ v i ⁇ E S v i ] ( t k )
  • E w out ⁇ ( t k ) ⁇ v ⁇ ⁇ i ⁇ [ ⁇ v i ⁇ ( ⁇ v i - 1 ) ⁇ E S v i ] ( t k )
  • S J tot ⁇ ( t k ) ⁇ v ⁇ i ⁇ [ ⁇ v , i ⁇ ⁇ E S v i ⁇ ] ( t k )
  • v pertains to the macroscopic partition of the information source domains ⁇ tilde over (I) ⁇ H v 1 , H v 2 , . . . H v i ⁇ .
  • (i) accounts for the macroscopic energy partitions which are also dependent on H(x) as a function ⁇ tilde over (I) ⁇ H x v,i ⁇ (shown in FIG. 3 as element 309 ).
  • the assignment of energy partitions to information domains is flexible and depends on particular design considerations.
  • H(x) or alternatively, H(p(x)) is known as Shannon's information entropy, uncertainty or measure of information or information metric. These may be referred to herein by the shorthand notations H(x) and H x . Also the information metric may be enumerated according to H(x) v,i or
  • H x v,i or H v i where v and i are integers corresponding to degrees of freedom and partitions. Subsets of index values (v,i) can be used to define domains. Each of the i energy partitions may possess any number of degrees of freedom up to and including v. Any subset from the v degrees of freedom is permissible. H(x) is given in the discrete and continuous forms;
  • the metric H(x) may have units of bits or bits/per second depending on context but is defined by
  • H ⁇ ( x ) - ⁇ - ⁇ + ⁇ ⁇ p ⁇ ( x ) ⁇ ln ⁇ ⁇ p ⁇ ( x ) m ⁇ ( x ) ⁇ ⁇ x
  • p(x) is the probability density functions (pdf) of symbols emitted from the information source.
  • m(x) normalizes Shannon's continuous entropy formulation to avoid conditions of negative entropy.
  • thermodynamic entropy flux of the system is given by
  • the flux S J e is part of the total entropy flux S J tot and not in full relaxation with the environment in a thermal sense until some period after entropy production ceases.
  • t eq the following entropy relationship applies in a specified irreversible direction, consistent with the 2 nd Law of Thermodynamics.
  • the arrow ⁇ can be interpreted as “tends toward”.
  • a message duration in time is given by ⁇ .
  • the total decoding time which is the time interval to extract information from an encoded signal, is greater than or equal to message length, which can become arbitrarily large depending on the required channel capacity.
  • channel refers to the modulator apparatus and portions of surrounding support circuitry.
  • the entropies S e and S w are equilibrium entropies since they approach a maximum
  • channel may be any medium used to transport some portion of information entropy H(x) even if the channel (medium) is bound to some portion of an apparatus.
  • Noise processes and thermal conduction arising from energy dissipation are contemplated along with causal perturbations determined by the apparatus response to a function of H(x) (shown in FIG. 3 as element 309 ). Hence, both driving forces and spontaneous actions coexist.
  • waste entropy may be defined as the logarithm of the number of significant accessible states associated with the portions of the phase space containing undesirable degrees of freedom and their cascaded energetic modes for the apparatus, multiplied by Boltzmann's constant for consistency with general thermodynamic treatments.
  • the application density of states within the phase space consists of functions of particle and charge motion, dq/dt, their electromagnetic fields, as well as undesired molecular thermal agitation, translation, rotation, and/or vibration (molecular kinetic energy), and other kinetic anomalies which may be described as undesired degrees of freedom.
  • the effective entropy is derived from the number of accessible states attributed to the portion of phase space encompassing the desirable energetic modes encompassing or enabling desired degrees of freedom. These definitions capture the spirit of a statistical mechanics description without demanding conditions of thermal equilibrium. However, it should also be noted that both forms of entropy (waste and effective) may assume intermediate flux expressions, which ultimately will seek a maximum entropy state when fully absorbed by the environment. This dissipation is eventually realized as heat, or other waste energy. Nonetheless, system thermal relaxation times may be significant when compared to intermediate modes of entropic transfer. This fact promotes efficient transport of energy within the multiple degrees of freedom for the apparatus to physically encode information in a form compliant for consumption by an information sink once the component entropies are reintegrated, or composited.
  • This reintegration or compositing enables functions of the information domains (subsets of H(x) v,i ) to be used with appropriate statistical weight, substantially simultaneously (or concurrently or in parallel) to render a representation of an information bearing function of time, such as a signal, waveform, electronic representation of an information bearing function of time or a facsimile of an information bearing function of time.
  • Statistical parsing associated with a compositing procedure may also occur sequentially according to a FLUTTERTM algorithm. This compositing may form the representation of the information bearing function of time and/or reconstruct an information bearing function of time and/or render the information bearing function of time, or a facsimile thereof.
  • Compositing involves combining, mixing and/or unifying/integrating/reintegrating, a collection of signals, into an information bearing function of time.
  • Another embodiment of the present invention is directed to a method for assigning ⁇ tilde over (I) ⁇ H(x) v,i ⁇ (generally shown in FIG. 3 as element 309 ) the weighting of ⁇ v 1 , ⁇ v 2 , . . . ⁇ v i , (generally 326 ) the partitions of E s , ( 308 ) (generally 324 ) and the optimization process in a modulation system that utilizes FLUTTERTM.
  • This approach maximizes efficiency, minimizes waste entropy production and conserves information transfer.
  • Embodiments of the present invention contemplate exploiting an advantageous hardware architecture given practical technology restrictions, while applying the optimization criteria of the FLUTTERTM algorithm.
  • the description herein uses ⁇ v,i ⁇ subscripts to account for v distinct degrees of freedom and i energy partitions.
  • the i energy partitions also represent particular degrees of freedom.
  • Macroscopic degrees of freedom may be defined as the unique portions of application phase space whose separable probability densities may be manipulated by unique physical controls derivable from the function or set of functions ⁇ tilde over (I) ⁇ H(x) v,i ⁇ . This function takes into consideration, or is influenced by, desired degrees of freedom and undesired degrees of freedom for the system.
  • degrees of freedom can be a function of system variables, such as temperature, and may be characterized by prior knowledge of the apparatus/system.
  • the two indices v,i may include any number of operations, manipulations or processes that can be described mathematically or with logic or both mathematically and with logic.
  • an overall density of states for the application phase space is dependent on applicable subsets of v,i probability distributions. These domain distributions will have varying degrees of statistical co-dependence.
  • the degree of freedom will possess two attributes: 1) be associated with some portion of the density of states within the phase space; which in turn relate to physical encoding mechanisms/facility of the apparatus and 2) permit articulation of energetic functions which are encoded with information, distributed according to ⁇ tilde over (I) ⁇ H(x) v,i ⁇ , where ⁇ tilde over (I) ⁇ H(x) v,i ⁇ controls the encoding mechanism/facilities of the apparatus.
  • FIG. 4 shows an alternate block diagram 400 illustrating the parsing of H(x) through a control ⁇ tilde over (I) ⁇ H(x) v,i ⁇ 402 .
  • FIG. 4 is a particular example of a portion of the embodiment of FIG. 3 and shows some examples of additional electronic functions.
  • FIG. 4 shows that the energy source E s 408 is manipulated by some function of a subset ⁇ tilde over (I) ⁇ H(x) v,i ⁇ of 402 ( a ), derived from the information metric H(x).
  • ⁇ tilde over (I) ⁇ H(x) v,i ⁇ 402 is related to the control of magnitude and phase functions of the carrier wave, where such carrier wave of radian frequency ⁇ c is obtained from one or more local oscillators (a single local oscillator (LO) 410 is shown). It is also an embodiment of the present invention that there may be any suitable number of local oscillators 410 .
  • the embodiments contemplated herein may utilize multiple LOs, such that the number of LOs is based on design considerations.
  • ⁇ c of may be greater than or equal to zero radians per second.
  • H(x) 402 is translated to the load encoded in the form of a signal while minimizing distortions at specified power and maximum efficiency through a large dynamic range for a number of operational variables.
  • Potential energy from E s 408 is converted to a desired form, via the trans-impedance of the multiple input single output module (MISO) 466 , as shown by trans-impedance node 462 , and transferred directly from the power source 408 to the output load R L 464 through energy storage elements 467 and complex impedance Z m 469 , in charge increments, dq/dt.
  • MISO multiple input single output module
  • the algorithm for distribution of ⁇ tilde over (I) ⁇ H(x) v,i ⁇ ( 402 ) is open loop, yet based on prior knowledge concerning the physical principles and characterized parameters of the apparatus 400 .
  • the multiple input single output operator module MISO 466 is implemented by hardware and algorithms, which in aggregate may be associated with the operators ⁇ v i , ⁇ , referenced in FIG. 3 . Degrees of freedom implemented via MISO module 466 are assigned in a manner that permits separate and joint manipulation of composite and other subordinate phase spaces.
  • the energy flow path 465 through energy storage element 467 which may be, for example, an inductive element and energy flow path 468 through element 469 , which is shown as an impedance element, are also shown.
  • the energy paths 465 and 468 are used to illustrate that the energy is displaced from one point in time and space to a second point in time and space.
  • the energy storage element and related circuits use space and time as required to transport charge.
  • the energy storage element may be any combination of reactive elements, for instance capacitors and inductors as well as transmission lines, or resonators arranged in any suitable circuit topology.
  • the power or energy source 408 may be any A.C., D.C. current or voltage source or combination thereof.
  • the associated characterizing pdf for the source may possess Stochastic and deterministic quantities.
  • Each of the blended controls 402 from subsets of combinations and permutations of v,i indicies may be accomplished by distribution of multiple signals per control path.
  • path 402 ( a ) may be digital, analog, serial, parallel or multiplexed with one or more than one connecting structure such as a wire or bus and suitable number of connecting nodes.
  • phase space herein is expanded from that of Statistical Mechanics.
  • the phase space as described herein, accommodates the consideration of both apparatus macroscopic and microscopic degrees of freedom.
  • the expanded definition recognizes joint evolution of these domains over variable relaxation times. This definition is consistent with maximal entropy non-equilibrium statistical characterizations as well as non-equilibrium thermodynamics.
  • thermodynamics the motivator for classical thermodynamics.
  • multiple forms of energy can coexist.
  • dynamic charge and its electromagnetic field and thermal agitation play roles in electronics though heat is usually not desired for most modern forms of communication and therefore is generally regarded as the degradation of energy to a form possessing maximum entropy.
  • the majority of (1 ⁇ )E s may consist of Joule heat, though not exclusively.
  • Intermediate energetic expressions such as noise, harmonics, intermodulation distortion, unwanted oscillations, crosstalk, interference, rotational, vibrational, translational and spurious waveforms, represent examples of scavenging phenomena, which decrease ⁇ at the point of delivery.
  • these other forms eventually also degrade to the most primitive form, heat, after causing errors such as distortions and defects in signals.
  • an apparatus phase space contemplates one or more degrees of freedom, which may include macroscopic and microscopic degrees of freedom. Furthermore, the phase space will typically possess transitory properties. Both circumstances can include a nonhomogeneous phase space. Statistical properties of constituent phase space domains can be exploited in concert with the diversity of phenomena relaxation time constants to decouple otherwise intractable dependencies. Semiconductors, conductors, inductors, and capacitors transport charge, and energy characterized by microscopic and/or macroscopic statistics. However, these infra structures are also composed of matter that is subject to thermal agitation at the microscopic level. When describing efficiency and information transport, to be complete, both regimes should be addressed, explicitly or implicitly. These extended concepts of application phase space may be referred to herein as simply “phase space”.
  • FIG. 5 show a circuit representation treated as a channel 500 .
  • This circuit representation 500 includes a signal source 570 which possesses a describing a pdf p(x) possessing information entropy H x
  • the variable x is mapped into voltage V src 572 .
  • the signal source 570 has a source impedance with real part R s 571 .
  • the signal V src 572 traverses a channel 573 .
  • the output of the channel 573 is a load voltage V L . 574 .
  • the information entropy associated with the load voltage is H y 575 and the signal V L . 574 is dissipated by the real part of a load impedance R L 564 .
  • Collectively 500 can conceptually represent some portion of an apparatus of system which transports or processes a signal, at a high level of abstraction.
  • the input signal voltage V src 572 may be different than V L 574 the output signal voltage because the channel 573 may modify the input V src 572 by some nonlinear distortion and/or addition of noise interference.
  • the original mapping of information and its associate entropy H x can be modified by the channel with the loss of information.
  • the channel and its distortions represents apparatus imperfections which may be included in the definition of or description of phase space or application phase space or pseudo-phase.
  • the probability densities (pdf's) used to describe charge, voltage, information and related functions of those quantities also may be distorted by the channel 573 .
  • the pdf (probability density function) describes the distribution of a parameter, or quantity, such as voltage or charge of functions thereof, which may be utilized. This is useful since such parameters can be related to properties of the phase space. Also, their distributions play a significant role in allocating ⁇ tilde over (I) ⁇ H(x) v,i ⁇ . V ⁇ (dq) represents energy where dq plays the extensive role. V can be a complex quantity and therefore provides a minimum of two degrees of freedom in signal space or pseudo-phase space.
  • the pseudo-phase space may be, for example, an abstract representation or approximation of a portion of phase space or application phase space. Distortions that impact the phase space and pseudo-phase space may sometimes be corrected, or avoided, by exploiting additional degrees of freedom.
  • phase space may be used to encompass the meanings of pseudo-phase space or application phase space depending on context.
  • FIG. 6 shows a graphical representation 600 of an approximate Gaussian PDF with 0.5 mean.
  • V src is plotted on the X-axis (horizontal) 672 and the probability for a specific value of V src , p(V src ), is plotted on the Y-axis (vertical) 676 .
  • Curve or plot 677 implies a linear channel.
  • Another embodiment of the present invention is that, for example, suppose an asymmetric nonlinear function is applied to a channel with a Gaussian signal which limits values of V src above V ⁇ .
  • the Gaussian signal may have the pdf for V src depicted in FIG. 6 applied to the channel nonlinearity of FIG. 5 .
  • FIG. 7 shows a graphical representation 700 , which shows V src is plotted on the X-axis (horizontal) 772 and p( ⁇ tilde over (V) ⁇ src ) is plotted on the Y-Axis (vertical) 776 .
  • Curve or plot 777 is shown. At point 0.6, as shown by 773 a vertical delta function, the curve 777 is truncated.
  • H ( x )+ H x ( y ) H ( y )+ H y ( x )
  • H ( x ) ⁇ H y ( x ) H ( y ) ⁇ H x ( y )
  • C deg represents the percentage channel capacity degradation.
  • C deg may be a useful metric for assessing the information impact of algorithm nonlinearities.
  • H ⁇ ( x V src ) - ⁇ p ⁇ ( x V src ) ⁇ log ⁇ ⁇ p ⁇ ( x V src ) m ⁇ ( x V src ) ⁇ ⁇ ( x V src )
  • V src 2 is the normalized power delivered to the apparatus.
  • Expressions of physical entropies in flux may be recognized as more familiar concepts such as uncertainty in changes of phase and magnitudes of signals along with their corresponding time dependent fluctuating cross-correlation functions. This includes the related signals of interest as well as spurious waveforms, harmonics, amplitude and phase noise, and intermodulation distortions. Heat may be measured separately, though in some cases the list above demonstrates some thermal dependencies.
  • the correspondence of these quantities and the functional descriptions that link them to various physical and information forms of entropy is an embodiment of the present invention, which is an advancement in the art.
  • the association of information useful in communications application with the time dependent configuration of matter and energy at fundamental scales is also an embodiment of the present invention and is also an advancement in the state of the art.
  • RF modulation is the process of imparting information from the information source possessing H(x) to the complex envelope of the RF carrier.
  • the uncertainty metric quantified by H(x) possesses a physical counterpart mimicking the component symbol probabilities in units of charge transfer per unit time.
  • the resulting signal takes the form
  • any point in the complex signaling plane can be traversed by using the appropriate mapping of a I (t) and a Q (t).
  • a description based on the magnitude and phase of the complex carrier envelope.
  • Battery operated mobile communications platforms typically possess unipolar energy sources.
  • the random variables defining a I (t) and a Q (t) are characterized by non-central statistical parameters.
  • a case of interest arises whenever a I (t) and a Q (t) are non-zero mean quasi-Gaussian. It is possible to refer to this case as a complex non-zero mean Gaussian pdf or Gaussian with 2 macroscopic statistical degrees of freedom, not to be confused with the v of the apparatus.
  • a subsequent analysis provides a general treatment for an apparatus that transfers power to a load given a unipolar energy source and a signal that is approximately Gaussian.
  • the signal plus offset may be DC coupled or AC coupled to a load. In general, AC coupled circumstances are more efficient.
  • the analysis can be extended to the complex Gaussian case by deploying an apparatus for an in phase signal and one for a quadrature phase signal.
  • the signal modulations defining a I (t) and a Q (t) thus correspond to a 2-dimensional signaling space that can approach Shannon's capacity limit. This represents a classical case suitable for bounding performance of efficiency for signals that possess large PAPRs.
  • Circuits designed as embodiments of the present invention to accomplish these modulations can fit many topologies and architectures. However, for linear modulations with unipolar offset, they reduce to two general classes for the amplitude envelope modulator, namely; series and shunt impedance control. The following discussion progresses around these models in terms of efficiency performance for series and shunt configurations as examples suitable for advancing concepts. The treatment for efficiency enhancement illustrated for the following simple models also enjoys common principles which apply to other classes of more advanced modulators.
  • FIGS. 13 and 14 represent higher level architectures which absorb modulator functions such as the ones to be subsequently discussed.
  • FIG. 8 shows a schematic 800 of a summing node with two input signals and/or waveforms 878 , 879 and one output signal 881 .
  • This summing node 880 is a linear processing operator enabling the superposition of its inputs.
  • x(t) 878 may be a complex signal of interest and n(t) 879 may be a complex noise or interference process.
  • FIGS. 9A , 9 B and 10 A, 10 B show examples of differential and single ended versions of the series modulator and shunt modulator topology, respectively. Two of these models may be used to create a complex signal. These models represent examples for implementing some portion of the degrees of freedom for an apparatus which may be associated with modulation derived from FLUTTERTM algorithm, for instance portions of FIGS. 13 and 14 . Examination of these models provide insight into the nature of efficiency enhancement.
  • the impedance Z ⁇ is variable from (0+0 j ) ⁇ to ( ⁇ + ⁇ j ) ⁇ .
  • the power transfer is a maximum only when the series impedance is zero or when the shunt impedance is infinite.
  • these models may represent general classes of linear devices, depending on the selection of the complex impedances, the models may be nonlinear as well. It is helpful to focus on those devices first that possess at least some non-zero real components for Z s Z L , and Z ⁇ .
  • Type I models are hereafter referred to as Type I models. They are useful for reference analysis and do not represent specific implementation.
  • FIG. 9A shows a differential Type I series modulator 900 .
  • This modulator 900 includes V s 982 , Z S 2 983 , 986 , Z ⁇ 2 984 , 987 blended control function ⁇ tilde over (I) ⁇ H(x) v,i ⁇ 985 , Z L 988 , and V L 974 blended control function ⁇ tilde over (I) ⁇ H(x) v,i ⁇ 985 .
  • FIG. 9B shows a single ended Type I series modulator 910 embodiment that includes V s 982 , Z s 989 Z ⁇ 990 , V L 974 and Z L 988 .
  • Blended control function ⁇ tilde over (I) ⁇ H(x) v,i ⁇ 985 provides input to Z ⁇ 990 , changing its impedance in some proportion to a desired modulation amplitude with an appropriate statistic.
  • FIGS. 10A , 10 B show a differential and single ended Type I shunt modulator, respectively.
  • the differential Type I shunt modulator 1000 of FIG. 10A includes V s 1082 , Z s /2 1083 , Z ⁇ 1090 , Z L 1088 , V L 1074 , Z s /2 1086 .
  • Blended control function ⁇ tilde over (I) ⁇ H(x) v,i ⁇ 1085 provides input to Z ⁇ 1090 .
  • the single ended Type I shunt modulator 1010 of FIG. 10B includes V s 1082 , Z s 1089 , V s 1090 , V L 1074 , Z L 1088 , blended control function ⁇ tilde over (I) ⁇ H(x) v,i ⁇ 1085 .
  • This shunt modulator includes a differential voltage source, V s 1082 , differential source impedances Z s 1089 , differential shunt impedance Z ⁇ 1090 , and load impedance Z L 1088 .
  • Blended control 1085 in both 1000 and 1010 provide a signal to Z ⁇ 1090 in both configurations, changing its impedance in some proportion to a desired modulation amplitude, with an appropriate statistic for output voltages.
  • V s ( 982 , 1082 , respectively) provides a voltage source.
  • the control statistic for ⁇ tilde over (I) ⁇ H(x) v,i ⁇ ( 985 , 1085 , respectively,) can be fairly intricate depending on the impedances Z s , Z ⁇ and Z L (i.e., 989 , 1089 , 990 , 1090 and 988 , 1088 , respectively).
  • Z ⁇ +Z s must not equal zero in this (shunt) topology for practical application.
  • the dynamics of ⁇ tilde over (I) ⁇ H(x) v,i ⁇ shown in FIGS.
  • V L 9B and 10B as elements 985 , 1085 , respectively
  • the voltage V L 974 , 1074 which changes as a function of Z ⁇ 990 , 1090 , controlled by ⁇ tilde over (I) ⁇ H(x) v,i ⁇ 985 , 1085 may therefore be represented by the function of a complex phasor, where the subscripts I, Q refer to in-phase and quadrature phase components of the signal, respectively.
  • the sign operator keeps track of the complex signal quadrant and further defines ⁇ (t), which represents the phase angle.
  • the phase angle describes the angle of a vector representation of a complex signal.
  • FIGS. 13 and 14 illustrate two architectural methods of implementing modulators based on FLUTTERTM and blended control-centric algorithms which can be used to render information bearing functions of time. These architectural methods can apply to the ongoing discussions concerning efficiency optimization. That is, the Type I modulator structures as well as virtually any suitable modulator or encoding method may be absorbed by FIGS. 13 and 14 for baseband or RF application.
  • Architectural figures, such as, FIGS. 1 , 2 , 3 , 4 , 9 A, 9 B, 10 A, 10 B, 15 , 18 , 20 , 21 , 22 , 27 , 28 , 29 , 30 , 31 , and 32 are relevant instantiations related to aspects of discussions for FIGS. 13 and 14 .
  • FIGS. 1 , 2 , 3 , 9 A, 9 B, 10 A, 10 B, 15 , 18 , 20 , 21 , 22 , 27 , 28 , 29 , 30 , 31 , and 32 are considered as possible structures and/or algorithms or modules which may be distributed as some subset of the FIGS. 13 and 14 architectures and modules.
  • FIG. 13 illustrates an example of a general architecture 1300 suitable for implementing the portion of the FLUTTERTM algorithm which encodes or modulates information onto a waveform.
  • the FLUTTERTM encoding or modulation segment 1300 is capable of producing baseband signals as well as RF signals at the output ( 1370 ).
  • Load 1380 may be driven by output 1370 .
  • a baseband signal may be produced by suitable choice of ⁇ c , and ⁇ in function/module 1341 .
  • Function/module 1341 can also become a local oscillator (LO) by suitable selection of ⁇ c , the carrier frequency and ⁇ the phase of the carrier frequency.
  • LO local oscillator
  • Blended controls 1301 manipulate multiple degrees of freedom by adjusting the power source 1320 with output signals 1321 and MISO and/or compositing function 1360 .
  • the blended controls are functions of system input entropy H(x), represented by ⁇ tilde over (I) ⁇ H(x) v,i ⁇ where v,i are indices suitable for managing the controls.
  • the blended controls are generated in a vector synthesis engine (VSE) according to the FLUTTERTM algorithm.
  • k A bits from the blended control are allocated 1302 to control the variable or switched energy or power source 1320 , to a desired resolution, maximizing efficiency for a minimum number k A ⁇ k B bits of control 1303 from the blended control 1301 are allocated as additional degrees of freedom to generate an information bearing function of time via a MISO and/or compositing function 1360 .
  • k ⁇ bits of the control 1304 from the blended control 1301 are allocated to select ⁇ c , and/or ⁇ to a desired value and resolution.
  • both ⁇ c , and/or ⁇ may be functions of time.
  • k A , k B , k ⁇ are allocated based on the number of available degrees of freedom for the apparatus, 1300 , the efficiency for each degree of freedom, and the corresponding potential to distribute a specific signal rate in each degree of freedom.
  • FIG. 14 illustrates an example of a general architecture 1400 suitable for implementing a portion of the FLUTTERTM algorithm which encodes or modulates complex information onto a waveform.
  • the FLUTTERTM based modulator segment 1400 produces RF signals with corresponding output 1470 that can accomplish universal modulation of a carrier.
  • a local oscillator 1441 can be selected or adjusted for a carrier frequency, ⁇ c , and phase ⁇ , where one or both may be functions of time and an input information source.
  • the local oscillator (LO) waveform 1440 is distributed in quadrature at a relative phase of 0° 1451 and 90° 1452 with respect to waveform 1440 using a quadrature generating function 1450 .
  • the MISO and/or compositing function module 1460 utilizes inputs 1451 and 1452 as quadrature carrier inputs which may be frequency and phase agile functions of time (They may be modulated, and encoded with information).
  • the output of module 1460 is an RF modulated signal 1470 .
  • the blended control 1401 are functions of system input information entropy and generated by a vector synthesis engine (VSE).
  • Controls 1402 and 1404 select or adjust the variable or switched energy or power sources, 1420 and 1430 respectively, for in-phase and quadrature branches of the MISO and/or compositing function 1460 .
  • the resolutions, in bits, for selecting power in these branches are k Q A and k I A , associated with waveforms 1421 and 1431 .
  • k Q B and k B are the number of bits from the blended controls 1403 and 1405 respectively, providing additional degrees of freedom for the compositing function 1460 .
  • k ⁇ is the number of bits of resolution allocated for signal or waveform 1406 which selects or determines ⁇ c , and ⁇ in the LO function 1441 associated with signals or waveform 1440 .
  • k Q A , k Q B , k I A , k I B , and k ⁇ are allocated based on the number of degrees of freedom for the apparatus 1400 the efficiency for each degree of freedom, and corresponding, potential to distribute a specific signal rate as well as information in each degree of freedom.
  • the output signal 1470 can be provided to load 1480 .
  • FIG. 15 shows a representation 1500 of a parallel “branched” channel configuration to reduce PAPR per branch according to an embodiment of the present invention.
  • H(X 1 , X 2 . . . X v ) 1502 is split, or fractured or distributed into component elements ⁇ tilde over (I) ⁇ H 1 ⁇ 1504 ( a ), ⁇ tilde over (I) ⁇ H 2 ⁇ , 1504 ( b ) and ⁇ tilde over (I) ⁇ H v ⁇ 1504 ( n ) (where “n” is any suitable number).
  • These component elements (generally 1504 ) have an associated metrics represented as
  • This composite entropy function 1575 is associated with a rendering, or representation of a desired information bearing function of time. It may be an information bearing function of time, waveform, signal, RF modulated carrier signal, or electronic data that can be converted, downloaded or reproduced as a rendered information bearing function of time. It may also be some intermediate signal to be further processed.
  • a v branch channel may replace a single branch channel where each branch possesses a lower PAPR. This is achieved by controlling the normalized channel capacity C v /W v , (generally 1505 ) per branch such that;
  • Each ratio C v /W v may be set as desired.
  • the derivations have assumed certain aspects of the waveform statistic in the given bounds.
  • Each separate branch of the composited channel can possess a smaller PAPR and therefore a correspondingly greater ⁇ .
  • the topological information flow indicated in FIG. 15 which illustrates a distribution, or dispersal, of information in the form ⁇ tilde over (I) ⁇ H 1 ⁇ , ⁇ tilde over (I) ⁇ H 2 ⁇ , . . . ⁇ tilde over (I) ⁇ H v ⁇ , (generally 1504 ) does not specify how the information is parsed to each path 1504 ( a ) . . .
  • FLUTTERTM permits the trade between efficiency and capacity by manipulating smaller portions of phase space volume 1504 ( a ) . . . ( n ) that collectively reconstitute 1575 statistically while regulating domain interactions.
  • This can be a time-variant nonlinear operation.
  • the time variant nonlinear operations may be distributed to each branch 1504 , absorbed by the ⁇ operator or some combination thereof.
  • the domain interactions may be managed in a way that moderates the effects of multi-branch loading phenomena described above through the proper design of ⁇ .
  • FIG. 16 illustrates an example 1600 of a conceptual phase space or pseudo-phase space, which has been arranged in three tiers corresponding to regions of differing energy levels, or energy partitions. Coordinates within the phase space are randomly highlighted to illustrate the arbitrary samples within partition ranges. The max radii of the concentric scatter volumes roughly mark the energy boundaries. Each unique point in the space represents a member from a signal ensemble.
  • FIG. 16 shows phase space 1600 with three axes. X-axis 1602 , Y-axis 1604 and Z-axis 1606 .
  • p( ⁇ hacek over ( ⁇ ) ⁇ ) be the probability density for the instantaneous waveform efficiency associated with FIG. 9B .
  • p( ⁇ hacek over ( ⁇ ) ⁇ ) can be used for both the series and the shunt cases and will be obtained to facilitate an example.
  • V L 1 2 ⁇ ⁇ ⁇ ⁇ V L ⁇ ⁇ - ( V L - ⁇ V L ⁇ ) 2 2 ⁇ ⁇ ⁇ V L 2
  • FIG. 11 shows graph 1100 that has X-axis (horizontal) 1102 showing V L and Y-axis (vertical), 1104 showing p(V L ).
  • Curve 1106 is a plot of the Gaussian pdf (probability density function).
  • ⁇ hacek over ( ⁇ ) ⁇ is an instantaneous waveform efficiency. It is not the proper thermodynamic efficiency. However, optimization of ⁇ hacek over ( ⁇ ) ⁇ can be shown to optimize proper thermodynamic efficiency under certain conditions contemplated by the FLUTTERTM algorithm. Sometimes this alternate efficiency metric ( ⁇ hacek over ( ⁇ ) ⁇ ) is a desirable object of optimization.
  • FIG. 12 A plot of this pdf (probability density function) is shown in FIG. 12 as graph 1200 .
  • FIGS. 11 and 12 represent a starting reference point for enhanced efficiency example, given the assumption of the simplified amplitude/envelope modulator models.
  • the signal PAPR for this example is approximately 11.11.
  • FIG. 17 shows an example plot 1700 .
  • the X-axis 1702 shows V L and the Y-axis shows p(V L ) 1704 .
  • Curve 1706 is shown as having three distinct portions.
  • Portion 1716 shows E 1
  • portion 1718 shows E 2
  • portion 1720 shows E 3 .
  • An area under curve 1706 is shown as 1714 .
  • the apparatus as described herein, can be considered as possessing three separate energy sources that are multiplexed at the interface between the potential boundaries, V 1 , V 2 , (shown as elements 1712 and 1713 , respectively) as the amplitude statistic dictates.
  • Voltages V 1 ( 1712 ) and V 2 ( 1713 ) may assume values from 0 to 1 volt as required for an application associated with the statistic of FIG. 17 . It is possible to define the domain association rule as;
  • FIG. 17 information is preserved across the energy domain boundaries while in FIG. 7 information is lost, or annihilated and environmental entropy is correspondingly increased.
  • FIG. 7 has been avoided for this example.
  • ⁇ can be a thermodynamic efficiency or an instantaneous waveform efficiency depending on the suitable choice of the definition for ( ⁇ ) or pdf ( ⁇ hacek over ( ⁇ ) ⁇ ), a derived quantity based on the signal statistic and circuit parameters and topology.
  • the kernels of the integrals are constant functions which are calculated from the ratios of pre averaged quantities, ⁇ L 2 i / P in i ⁇ ⁇ L 2 i is the output signal variance (output signal power) of the i th partition.
  • P in i is the input power for the circuit in the i th partition.
  • ⁇ 1,2,3 may also be obtained from (where ⁇ is associated with a threshold index);
  • k i — norm provides a normalization of each domain such that each separate domain possesses a cdf (cumulative distribution function) equal to a maximum measure of 1 at the upper boundary.
  • k i — norm or suitable equivalents, will be included in the factors ⁇ i also known as weighting factors. In some discussions these factors shall remain separate.
  • thermodynamic efficiency (respectively) apply to a Type I series dissipative modulator with a power source resistance equal to the load resistance.
  • the final weighted average is;
  • ⁇ hacek over ( ⁇ ) ⁇ ⁇ sx ( ⁇ 1 ⁇ hacek over ( ⁇ ) ⁇ 1 + ⁇ 2 ⁇ hacek over ( ⁇ ) ⁇ 2 + ⁇ 3 ⁇ hacek over ( ⁇ ) ⁇ 3 ) ⁇ 0.517
  • the final weighted average is;
  • ⁇ hacek over ( ⁇ ) ⁇ tot ⁇ sx ( ⁇ 1 ⁇ hacek over ( ⁇ ) ⁇ 1 + ⁇ 2 ⁇ hacek over ( ⁇ ) ⁇ 2 + ⁇ 3 ⁇ hacek over ( ⁇ ) ⁇ 3 ) ⁇ 0.517
  • the switch efficiency ⁇ sx is set to the value of 1.
  • FIG. 18 The corresponding block diagram for an architecture associated with this calculation is shown as FIG. 18 .
  • FIG. 18 shows a power switching module and series type 1 modulator 1800 .
  • This switching module and series modulator 1800 includes I ⁇ H(x) v i , H(x) v 2 , . . . H(x) v i ⁇ 1802 ,( a ) . . . ( n ) (blended controls where “n” is any suitable number).
  • Blocks 1888 , 1889 and 1890 which are impedances associated with a shunt modulator, are also shown.
  • V L 1874 is developed by an output current flowing through Z L 1888 . As shown in FIG.
  • the apparatus 1800 transitions as each statistical boundary is traversed, selecting a new energy partition according to ⁇ tilde over (I) ⁇ H(x) v 1 , H(x) v 2 , . . . H(x) v i ⁇ (generally 1802 ).
  • ⁇ hacek over ( ⁇ ) ⁇ 1 ⁇ tilde over (I) ⁇ V s 1 ⁇
  • ⁇ hacek over ( ⁇ ) ⁇ 2 ⁇ tilde over (I) ⁇ V s 1 ,V s 2 ⁇
  • ⁇ hacek over ( ⁇ ) ⁇ 3 ⁇ tilde over (I) ⁇ V s 2 ,V s 3 ⁇
  • H(x) ⁇ H(y) can be minimized so that the desired signal is faithfully composited. This is accomplished by manipulating i degrees of freedom as well as other degrees of freedom in the modulator, for example the v i degrees of freedom associated with Z ⁇ 1890 , of FIG. 18 . Then application of the maximization algorithm max ⁇ ⁇ hacek over ( ⁇ ) ⁇ tot ⁇ may be solved using the calculus of variations to obtain solution for V s 1 and V s 2.
  • the FLUTTERTM energy partition optimization solution provides a noticeable improvement over an arbitrary 2 bit assignment for thresholds. Moreover, the improvement over a single power source partition is approximately a factor of 2 or 100% improvement of the instantaneous waveform efficiency metric.
  • the FLUTTERTM algorithm demonstrates that application of optimal thresholds is not ad hoc or arbitrary. For instance, ad hoc binary weighting was illustrated to be inferior to a FLUTTERTM optimization. Standard Legacy envelope tracking schemes which have been digitized do not optimize according to a FLUTTERTM algorithm and therefore are different as well as inferior. A significant benefit of FLUTTERTM is evident in the relatively reduced number of partitions required to provide relative efficiency enhancement. In addition, the partition selection rate may be reduced when additional information entropy is distributed in alternate degrees of freedom. Furthermore, the other degrees of freedom v restore information in the signal envelope not accommodated by the sparse number of partitions. These v degrees of freedom also smooth and/or interpolate the envelope to a desired standard. Legacy approaches and technologies do not restore an envelope using a small number of quantization levels for power supply envelope restoration or envelope following.
  • PAPR ⁇ - ⁇ ⁇ P out ⁇ ⁇ _ ⁇ ⁇ peak ⁇ P out ⁇ ⁇ ⁇ ⁇ ⁇ - ⁇ ⁇ ⁇ P out ⁇ ⁇ P i ⁇ ⁇ n ⁇ ⁇ ⁇ ⁇ ⁇ ⁇ P out ⁇ ⁇ _ ⁇ ⁇ peak ( PAPR ) ⁇ ⁇ P i ⁇ ⁇ n ⁇
  • ⁇ i is the statistical weighting for ⁇ i over the i th partition so that
  • ⁇ i ⁇ V L ⁇ ( ⁇ - 1 ) V L ⁇ ⁇ p ⁇ ( V L ) ⁇ ⁇ ⁇ V L
  • the generalized ⁇ optimization procedure (Type I modulator) may be prescribed for setting partition threshold ⁇ ⁇ .
  • ⁇ (will be used an index associated with threshold number at the boundary of the partition.
  • the number of thresholds is one less than the number of partitions.
  • the differences between adjacent threshold are considered as differential quantities in this example.
  • ⁇ i ⁇ V L ⁇ - 1 V L ⁇ ⁇ p ⁇ ( V L ) ⁇ ⁇ V L ⁇ i ⁇ ⁇ i ⁇ ⁇ _ ⁇ 1 V L ⁇ ⁇ ⁇ _ ⁇ V S ⁇ 2 Z r ⁇ ⁇ _ ⁇ Z s Z L
  • FIG. 19 shows a graph 1900 that illustrates the trend of ⁇ hacek over ( ⁇ ) ⁇ plotted on Y-axis (vertical) 1904 as a function of the number of partitions, plotted on X-axis (horizontal) 1902 , as curve 1906 .
  • FIG. 19 shows instantaneous waveform efficiency (plotted as curve 1906 ) as a function of energy partition number for an example of a Type I modulator model processing signal amplitudes characterized by non central Gaussian statistics, for a particular Z r . Notice how the ⁇ hacek over ( ⁇ ) ⁇ (instantaneous efficiency) is greatly enhanced for the allocation of only several partitions.
  • thermodynamic efficiency ⁇ and the instantaneous efficiency ⁇ hacek over ( ⁇ ) ⁇ , for this modulator, are related by (for a single energy partition);
  • PAPR sig is the peak to average power ratio for the signal portion of the waveform.
  • thermodynamic efficiency may also be directly optimized.
  • An additional example will illustrate the results of optimizing thermodynamic efficiency using a direct approach.
  • thermodynamic efficiency improvement ⁇ i / ⁇ 1 vs. partition number. Notice that the percentage improvement is 40% for 2 partitions, 54% for 3 partitions and 73.5% for 8 partitions.
  • the ratio is the efficiency for the modulator using i partitions divided by the efficiency for a single power source based modulator.
  • This calculation may also be approximated by a more tangible associated metric that is particularly convenient for lab application as most modern signal analyzers may be equipped with cross-correlation or other relevant error metric measurement capabilities.
  • the minimization is often accomplished by one of several means;
  • R xy ⁇ ⁇ ⁇ ⁇ ⁇ ⁇ xyp ( y,x ) dxdy
  • This form is a statistical cross-correlation.
  • the cross-covariance which may be used in certain circumstances is the same operation after extracting the mean values of x, y. It is noted that the y variable is often normalized or scaled to compensate for test system scaling.
  • V L 1874 should be a faithful reproduction of ⁇ tilde over (I) ⁇ H(x) v,i ⁇ 1802 by definition.
  • Z ⁇ 1890 may be distributed with many controls.
  • Voltages 1812 , 1813 , 1814 may be nonlinear and each may be determined by multiple controls. In such cases, imprecision, quantization noise and a host of other variables may potentially compromise the desired cross-correlations thereby increasing S J w .
  • the cross-correlation or cross-covariance or covariance metric or a reasonable similar metric may be employed to assess the particular synthesized architecture.
  • cross-correlation may be used whenever p(x,y) can be obtained or suitably approximated. In cases where this is not convenient, the time cross-correlation may be employed for a conditionally-stationary random process. This form of cross-correlation is given by;
  • R xy ⁇ ( ⁇ ) lim T O cc -> ⁇ ⁇ ⁇ - T O CC T O CC ⁇ x ⁇ ( t ) ⁇ y ⁇ ( t + ⁇ ) ⁇ ⁇ t
  • the input and output spectral masks are compared from;
  • R x ( ⁇ ) and R y ( ⁇ ) are suitable auto correlations.
  • compliance can also be assessed in the frequency domain.
  • Other comparison metrics are useful as well, such as covariance, MMSE, phase error versus frequency, phase error versus time, and variations thereof.
  • V n ⁇ n / 2 ⁇ ⁇ ( n 2 + 1 ) ⁇ ( 2 ⁇ ⁇ ⁇ ⁇ W ⁇ ( ⁇ P ⁇ + N ) ) n
  • This hyper sphere possesses an analog in statistical mechanics related to the states of particles in phase space, where the coordinates in classical phase space are defined by momentum p and position q, respectively.
  • the probability densities for the degrees of freedom and their energy distributions, as well as corresponding information distributions, have been absorbed into the construct of application phase space at a higher level of abstraction for the purpose of this disclosure.
  • This higher level of abstraction may also be referred to as a pseudo-phase space.
  • N s samples amongst the i partitions will distribute according to the probability density p(V L ) and the ancillary rules that assign the respective domains. These samples are only partially utilized by the energy partitioning facilities of the apparatus. Additional samples may be required to support v degrees of freedom. In general, it is possible to assign i ⁇ 2 k partitions to enable an efficient system.
  • the average frequency of samples within each bin (a bin may be thought of as a subset of values or span of values within some range or domain) can be calculated from;
  • 2 k sets the sampling resolution for the system.
  • the potential between fixed and/or sampled energy partitions can be greater than or equal to V L max /2 k specifically set by the FLUTTERTM algorithm to realize an optimized efficiency gain.
  • the rules for assigning the number and frequency of the samples N s to each of the i bins may be directly attributed to the mapping of H(x) symbol emission to V L and (V L ), via ⁇ tilde over (I) ⁇ H(x) v,i ⁇ .
  • the number of partition transitions per unit time per degree of freedom fluctuate in each path of a FLUTTERTM algorithm according to signal statistics and therefore these partition sampling events may be slower than the final composited signal envelope Nyquist sampling rate or bandwidth.
  • the additional (non-energy partition selection) required signal reconstruction sample clusters are distributed to other degrees of freedom and composited through other blended control paths, thus preserving the requirements of the sampling theorem. This is a preferred approach given the minimum fixed number of energy partitions to practically achieve a specified efficiency.
  • An efficient algorithm should also accommodate simultaneous or joint (or concurrent or parallel) optimization max ⁇ n ⁇ , min ⁇ H x ⁇ H y ⁇ . If joint dependency of efficiency and quality are not explicitly contemplated then the algorithm is ‘ad hoc’.
  • variable for amplitude of a signal may be quantized and that the energy partitions be less than or equal to the number of quantization levels. This is a flexible, or loose, upper bound. The idea of quantization is justified since the continuous random variable V L can be exactly reproduced according to the sampling theorem and could correspond to an efficiency optimization without requiring an infinite number of differentially spaced partition potentials.
  • FIGS. 20 and 21 show examples of a Type II modulator model for series and shunt realization, respectively. Equivalent differential topologies are possible and may be assumed in the treatment just as single ended and differential topologies were included for Type I models, as described herein.
  • FIG. 20 shows an example of a series Type II modulator 2000 .
  • This modulator 2000 includes a phase/frequency control input 2092 , time variant source voltage V s 2082 , source impedance Z s 2089 . Also shown is variable branch impedance Z ⁇ 2090 , which receives control input from amplitude control 2091 and signal input from source V s 2082 . The output from Z ⁇ 2090 is provided to Z L 2088 and V L 2074 .
  • V s 2082 may for example be an agile RF carrier with phase modulation from control 2092 .
  • the amplitude of V L 2074 may be changed by changing Z ⁇ 2090 via control 2091 . Therefore, output V L may be phase modulated and amplitude modulated through changes imparted by controls 2092 and 2091 .
  • FIG. 21 shows an example of a shunt Type II modulator 2100 .
  • This modulator 2100 includes a phase/frequency control input 2192 , time variant source voltage V 2182 , Z s 2189 . Also shown is a variable impedance Z ⁇ 2190 , which receives control input from amplitude control 2191 .
  • the impedance from Z ⁇ 2190 is in parallel with Z L 2188 and affects the amplitude of V L 2174 .
  • the output voltage amplitude of V L 2174 and phase of V L 2174 may be changed by varying controls 2191 and 2192 .
  • the series modulator instantaneous waveform efficiency can be derived similar to the methods developed for analyzing the Type I modulators.
  • the partially reduced result is;
  • Type II shunt model yields approximately the following provided the condition of a short circuit is avoided.
  • thermodynamic efficiency P out sig / P in ⁇ also increases as ⁇ hacek over ( ⁇ ) ⁇ increases for these Type II modulator examples.
  • a D.C. blocking circuit such as capacitor or other filter, as part of Z s 2189 may improve efficiency in this case.
  • Type II modulator models follow the Type I model performance closely over significant dynamic range of the relevant signals.
  • One possible difference is the explicit inclusion of an oscillator source with phase/frequency control as a unique control.
  • a plurality of Type I models can also create complex passband signals.
  • Z ⁇ 2090 , 2190 may be in general a complex function and its control may likewise be considered as a complex number, thus suitable for complex envelope generation.
  • a Type II model is convenient for complex signal generation since the controls may be independently manipulated by scalar functions if desired.
  • reserving the ability to drive Z ⁇ 2090 , 2190 by a signal consisting of complex numbers can offer some desirable degrees of freedom.
  • the complex numbers may control the real and imaginary portions of the complex impedance Z ⁇ 2090 , 2190 .
  • Many useful complex signaling scheme can be realized with this model by applying the circuit architectures of FIGS. 20 and 21 to in-phase and quadrature-phase modulation schemes.
  • thermodynamic efficiency ⁇
  • modulation techniques such as those techniques using any modulator technology, or such as d2pTM technology. It is useful to develop the similar efficiency themes but relate the discussion to the encoding of the information metric H(x) into phase, since this is a significant macroscopic degree of freedom for signals and such agility is helpful for modern signaling standards.
  • phase space is smaller dimensionally whenever amplitude modulation is denied and therefore capacity decreases for specified link performance. This usually demands greater transmitter power and bandwidth to offset capacity losses.
  • regulatory and standards body restrictions render some phase modulation waveforms as obsolete or of narrow application, so as to have limited use.
  • phase modulation when required to support greater information rates, begins to impact the efficiency of practical infrastructure electronics. This is especially true for significant transmitter power requirements.
  • Changing phase of a carrier at increasingly greater rates corresponds to accelerating and decelerating electrons, which have mass and are also associated with the corresponding electromagnetic fields of radiation possessing momentum.
  • the changing inertia associated with accelerating and decelerating electrons and their fields requires more energy than the case where currents are relatively constant.
  • phase modulation can be a powerful technique to conserve energy if the phase changes are properly controlled and of moderate rates.
  • the most beneficial solutions address both amplitude and phase, which is assumed in the subsequent portions of this disclosure.
  • Embodiments of the present invention are also directed to criteria for obtaining energy partitions, which can enhance efficiency for RF modulation processes which includes amplitude and phase modulated signals.
  • the signal envelope magnitude often drives these criteria and the greater the uncertainty metric H(x) the greater the uncertainty for the signal envelope. Rapid and uncertain carrier phase fluctuations, can also impact efficiency.
  • Unipolar signals can be defined as being positive so that 0 ⁇ a(t) ⁇ V L max . This range is parsed into (i) domains consistent with the FLUTTERTM algorithm to improve efficiency.
  • v degrees of freedom may also be independently deployed to control signaling degrees of freedom within the modulation, such as d2pTM modulation, so that signals may be reconstructed, or rendered, accurately while optimizing efficiency.
  • v degrees of freedom may also control magnitude and phase of the complex signal given the constraints imposed within the i th energy partition.
  • the indices, v,i thus point to portions of information space ⁇ tilde over (I) ⁇ H(x) v,i ⁇ which are accessed to generate the physical expression of the v domains.
  • a final output is obtained as a function of blended controls according to
  • E e is the effective output signal energy.
  • One quality of the E e metric is given by;
  • the other quality metric can be related to the difference in uncertainties H(x) and H(y) for the input and output of the modulation process respectively;
  • ⁇ can be an arbitrarily small number which may be estimated using error vector magnitudes and minimum mean square error techniques which calculate energy differences between the input variable x and output variable y.
  • FIG. 22 is another illustration of a blended control function distribution architecture which processes vectors of FLUTTERTM algorithm values per each sample or state. These parallel vector states enable v degrees of freedom and i partitions to synthesize portions of subordinate signals with statistical co-dependencies.
  • a vector synthesis engine (VSE) module 2203 calculates the blended control function and renders the parallel control vector per sample of the information bearing function of time.
  • VSE vector synthesis engine
  • each of the v i processing branches possesses its distinct set of degrees of freedom and i th energy partition. The degrees of freedom and partitions may overlap domains between the branches.
  • each branch or the weighting of each branch is a random variable ⁇ 1 (part of 2211 a ) through ⁇ i (part of 2211 n ) (effective weighting factors) and each branch will possess a corresponding variable efficiency through ⁇ tilde over ( ⁇ ) ⁇ i .
  • the variable efficiency ⁇ tilde over ( ⁇ ) ⁇ i may also be expressed in terms of ⁇ hacek over ( ⁇ ) ⁇ and/or ⁇ the instantaneous and thermodynamic efficiencies respectively.
  • the subordinate signals are in general complex quantities, which are functions of the final desired output amplitude a n and phase ⁇ n at n th the sample.
  • Each branch may possess a nonlinear characteristic and a final signal synthesis is composited through the action of the output operator ⁇ 2217 and distributed blended controls that optimally integrates each statistically weighted nonlinear branch.
  • FIG. 22 is a diagram that illustrates one embodiment 2200 and how information and energy partitions may be organized in terms of topological signal flow.
  • This representation 2200 shows assignment of information resources to each branch with consideration of nonlinearity.
  • flow diagram 2200 includes portions of VSE (Vector Synthesis Engine) 2203 .
  • the VSE module 2203 generates I ⁇ H v,i ⁇ 2205 ( a ) . . . ( n ) (where “n” is any suitable number).
  • These functions (generally 2205 ) v 1 . . .
  • the output of function 2209 ( a ) . . . ( n ) (generally 2209 ) is shown as 2211 ( a ) . . . ( n ), respectively (generally 2211 ).
  • the outputs from 2215 ( a ) . . . ( n ) are composited by operation module “ ⁇ ” 2217 and operations of each algorithm branch and render output 2219 .
  • the operator ⁇ module 2217 leverages the FLUTTERTM algorithm using apriori knowledge of the apparatus and a desired signal as well relationships derived from the following variables, functions and parameters:
  • the vector synthesis engine (VSE) module 2203 calculates the per sample, functions for the v i , domains supporting functions 2207 , 2209 , 2211 , and 2215 .
  • the calculations include apriori knowledge of the apparatus configuration and technology characterization. Models consider efficiency and signal space geometries for one or more system states ⁇ which contemplate, signal type, signal rate, temperature, dynamic range, power supply variation, etc.
  • FIG. 22 is an operational mixture of functions that illustrate the joint processing of signal energy and the associated information metrics encoded into y n (t) 2219 mapping, or blending, or compositing, at the output.
  • Functions/modules 2209 ( a . . . n ), 2211 ( a . . . n ), 2215 ( a . . . n ), 2217 , 2205 ( a . . . n ), and 2203 may be implemented by a suitable blend of hardware and software using microprocessor and/other appropriate configurable and/or programmable technologies. Also analog technology may be used to implement these functions with suitable A/D and D/A interfaces where applicable to transition between analog and digital processing functions/modules.
  • R xy or corresponding covariance is a useful metric for indirectly assessing S J e , S J w .
  • FIG. 22 illustrates the Vector Synthesis Engine (VSE) 2203 , which generates the intermediate blended controls 2211 based on knowledge of the apparatus partitions, desired output signal 2219 , targeted efficiency vs. signal quality metric, and modeled or characterized nonlinearities, NL 1 , NL 2 , . . . NL i 2215 ( a ), 2215 ( b ) . . . 2215 ( n ) (where “n” is any suitable number).
  • VSE Vector Synthesis Engine
  • embodiments of the present invention are directed to creating an image that provides what may be described as an “entropy flux surface”, or herein after, simply “differential surface”.
  • the surfaces are extracted as sets of 3-dimensional cross sections of higher order complex hyper-geometric manifolds. Each set of surfaces corresponds to a particular state of one or more modulators plus supporting functions, or collectively the apparatus and each state is characterized by at least 2 differential surfaces that may be obtained from a cross-correlation function, or a corresponding covariance.
  • FIGS. 23A and 23B are graphics that illustrate an example of the differential surfaces for a particular state. Specifically, FIG. 23A shows a graphical illustration 2300 of a differential magnitude entropy surface 2307 and FIG. 23B shows a graphical illustration 2301 of a phase entropy surface 2317 .
  • the differential magnitude entropy surface 2307 is plotted on X-axis 2302 , Y-axis 2304 and Z-axis 2306 .
  • the differential magnitude entropy surface 2307 has a substantially flat portion 2308 and a substantially conical portion 2310 .
  • the substantially conical portion 2310 of the phase entropy surface 2307 is illustrated as being “positive” which is merely a convention choice.
  • the differential surface 2307 could also be represented as “negative”.
  • the designation of the X, Y and Z axes is a convention choice. Any suitable coordinate system may be used to plot the differential magnitude entropy surface.
  • surface portion 2310 appears conical for this example, it may assume other forms.
  • FIG. 23B shows a graphical illustration 2301 of a differential phase entropy surface 2317 .
  • This differential phase entropy surface 2317 is plotted on a coordinate space, shown as X-axis 2312 , Y-axis 2314 and Z-axis 2316 .
  • Differential phase entropy surface 2317 has a substantially flat portion 2318 and a substantially conical portion 2320 .
  • the substantially conical portion 2320 of the differential phase entropy surface 2317 is illustrated as being “negative” which is merely a convention choice.
  • the surface 2317 could also be represented as “positive”.
  • the designation of the X, Y and Z axes is a convention choice. Any suitable coordinate system may be used to plot the differential phase entropy surface.
  • surface portion 2320 appears conical for this example if may assume other forms.
  • FIG. 24A shows a graphical illustration 2400 of a reduced differential magnitude entropy surface 2408 .
  • This reduced differential magnitude entropy surface 2408 is plotted on X-axis 2402 , Y-axis 2404 and Z-axis 2406 .
  • the reduced differential magnitude entropy surface 2408 has a substantially flat portion. (“Substantially” is used as a relative term with respect to a quality metric that is a system design parameter.)
  • the designation of the X, Y and Z axes is a convention choice. Any suitable coordinate system may be used to plot the differential magnitude entropy surface.
  • FIG. 24B shows a graphical illustration 2401 of a reduced differential phase entropy surface 2418 .
  • This reduced differential phase entropy surface 2418 is plotted X-axis 2412 , Y-axis 2414 and Z-axis 2416 .
  • the reduced differential phase entropy surface 2418 has a substantially flat portion 2420 and a substantially conical portion 2419 .
  • the substantially conical portion 2419 of the reduced differential phase entropy surface 2418 is substantially more narrow (less surface area) than the phase entropy error conical portion of FIG. 23B .
  • the designation of the X, Y and Z axes is a convention choice. Any suitable coordinate system may be used to plot the differential phase entropy surface.
  • the error metric S J w is reduced to the lowest acceptable, or lowest compliant, value through ⁇ tilde over (I) ⁇ H v,i ⁇ while articulating the most efficient resources available within the apparatus to produce S J e .
  • nonlinearities in one branch as shown in FIG. 22 , 2205 , may reduce the capacity of that branch while enhancing efficiency, another branch makes up the difference in information capacity.
  • the relative partial information capacities and efficiencies of algorithm branches may fluctuate dynamically during compositing. Branch domains may overlap through the sets of ⁇ tilde over (I) ⁇ H v,i ⁇ even if energy domains (i) may or may not overlap.
  • FIG. 25 shows an example of a joint probability space diagram 2500 .
  • an output amplitude domain waveform pdf (probability density function) p(V L ) 2506 is generated from ⁇ tilde over (I) ⁇ H(p 1 , p 2 , . . . p v ) ⁇ , v which is composite, or blended control, PDFs (probability distribution function).
  • Each member of this composited set is a pdf (probability density function) of a non-stationary random variable, which may be continuous, discrete or both (illustrated as continuous for example).
  • the solid line 2506 illustrates the composited pdf (probability density function) p v (V L ) can be considered as a joint distribution that is dependent on several subordinate pdfs joint (probability density functions) or joint sub-distributions ⁇ tilde over (I) ⁇ p(V 1
  • V v ⁇ 2523
  • the graph 2500 is plotted with respect to X-axis 2502 vs. Y-axis 2504 .
  • v degrees of freedom
  • FIG. 25 provides a statistical description of a representation of an information bearing function of time. Components of phase, amplitude and frequency are contemplated as extensions of the composited statistic.
  • the variables possess some correlation for the region of overlap. This correlation is a variable which is a function of the set of voltages or signals V L , ⁇ tilde over (I) ⁇ (V 1 , V 2 , . .
  • each energy partition 2516 , 2518 and 2520 may span a subset of the blend from the available p v ⁇ .
  • a suitable blend of subordinate joint pdfs is possible which possess tailored cross covariance.
  • FIG. 25 shows a 2-dimensional RV; however, the RV is in general applicable to any suitable number of complex dimensions.
  • FIG. 25 illustrates how an output V L may be a composited result of several constituents (V 1 , V 2 , V 3 . . . V v ).
  • FIG. 26 shows a flow chart 2600 that illustrates a FLUTTERTM algorithm development approach that considers up to v plus i additional macroscopic degrees of freedom for the apparatus.
  • the flow chart 2600 begins with start step 2602 having a particular set of FLUTTERTM operational parameters and apriori knowledge of the apparatus characteristics.
  • Energy partitions (i) are chosen, as shown in step 2604 according to input 2602 . This selection of a number of energy partitions to partition one or more energy sources depends on a desired resolution to render a signal or a waveform that can be encoded with information (generally referred to herein as an information bearing function of time).
  • the (i) partitions may be fixed domain (as shown in step 2606 ) or fixed plus switch PS domain (as shown in step 2608 ).
  • step 2610 v degrees of freedom are allocated, as shown in step 2610 .
  • the allocation of step 2610 is used for compositing, as well as p v (V L ) distributions.
  • step 2614 Joint optimization of ⁇ , H x ⁇ H y is performed, as shown in step 2614 .
  • This joint optimization of step 2614 also is a function of ⁇ S 2612 .
  • the result of the joint optimization is analyzed as shown in step 2616 .
  • This analysis includes checking ⁇ tilde over (I) ⁇ ⁇ tot ⁇ and ⁇ tilde over (I) ⁇ R xy ⁇ .
  • the result of this analysis of step 2616 is either acceptable, as shown by reaching step 2630 or rejected, as shown by line 2618 , which shows that the optimized blending function is iterated, as shown in step 2620 .
  • This optimization may be accomplished by some combination of characterization, measurement and calculation which can be iterative or solved through the calculus of variations.
  • the result of the possibly iterative optimization process ( 2620 ) is used in step 2610 , as shown by line 2615 .
  • the result from the iterative optimization process ( 2620 ) may also be used in the partitioning step 2604 , as shown by line 2622 .
  • the resulting optimization parameters may be applied in a feed forward application of FLUTTERTM.
  • FIG. 26 illustrates a general method for obtaining a statistical characterization of an apparatus supporting the FLUTTERTM algorithm which utilizes the characterization as prior system knowledge and apriori knowledge
  • the number of signal samples per energy partition can be approximately obtained from;
  • the sampling rate for the i th can then be given by 2W i , where W i is the required bandwidth of joint FLUTTERTM processes in i th partition, although there is a finite probability of switching between any of the domains from sample to sample, the averaged switch frequency on a per domain basis is given by;
  • R sx is the maximum switch rate
  • ⁇ i is a suitable rate multiplier
  • This rate can be further reduced by redistribution of, or suitable distribution of, the frequency components of the FLUTTERTM blended controls. Additional amplitude and phase information not accommodated by switching power supply or switched power supply control is allocated to the v remaining degrees of freedom. These parallel paths permit the full dynamic range and resolution of the signal to be reconstructed “on the fly”, sample by sample, using the VSE (Vector Synthesis Engine) module to optimize ⁇ and R xy.
  • VSE Vector Synthesis Engine
  • the amplitude modulations are partially instantiated by the energy domain control at each V S i boundary. Additional amplitude control is facilitated in the v remaining degrees of freedom (as shown by step 2610 ) for the modulator device.
  • FIG. 27 shows an example of FLUTTERTM with (i) partitions and v auxiliary degrees of freedom. Indeed, FIG. 27 shows one topology 2700 related to d2pTM application with Type I modulation properties.
  • FIG. 27 shows an example of one embodiment 2700 of the present invention.
  • FIG. 27 shows energy sources V S 1 V S 2 . . . V S i 2708 ( a ), 2708 ( b ) and 2708 ( n ), respectively) where “n” is any suitable number. It is an embodiment of the present invention that any suitable number of energy sources may be used. Although illustrated as DC batteries for this example, it is understood that the energy sources may possess any statistic of voltage or current and may also be encoded with information. Blended controls, ⁇ tilde over (I) ⁇ H(x) v,i ⁇ 2702 are generated from a VSE (Vector Synthesis Engine), as described herein.
  • VSE Vector Synthesis Engine
  • a portion 2702 ( a ) of the control function 2702 is provided to a switching control to selectively access one of the energy sources (generally 2708 ) connection as shown by 2711 , 2709 and 2713 .
  • the switch contact, 2709 and connection nodes 2713 ( a . . . n ) are activated based on the control signals of 2702 ( a ) and switch control 2711 .
  • the selected energy source of the plurality of sources (generally 2708 ) provides energy, in any suitable form, which may include voltage, current, excitation or other stimulus to impedance module ⁇ Z S 2789 .
  • a second portion of blended control, 2702 is 2702 ( b ), which is provided to LO (local oscillator) 2710 , which then provides input to modulator module 2766 .
  • the modulator module 2766 may be, for example a MISO (multiple input single output module).
  • the matching impedance 2769 receives the interaction of Z S 2789 -modulator module 2766 , and the sources 2708 ( a ) . . . ( n ).
  • V L ⁇ y(t) 2774 is rendered at load 2764 .
  • the energy sources 2708 are partitioned according to control signals 2702 ( a ), which partition the energy samples into a number of partitions, which can be enumerated as i ⁇ 2 k where k is the resolution used for reconstructing the signal amplitude and/or phase typically i ⁇ k for fixed partitions.
  • i may be a suitable integer of fixed partitions to obtain a desirable efficiency.
  • i could be an integer such as 2 and offer performance advantage (compared to legacy technologies) in the rendered output signal V L 2774 at load R L 2764 .
  • none of the partitions require switching power supplies. Switching power supplies may also be used.
  • the additional v dimensions provide for complex signal reconstruction, or rendering, of both desired magnitude and phase at the output 2774 given the constraint of the i th energy partition.
  • FIG. 28 shows the Thévenized equivalent of FIG. 27 .
  • FIG. 28 the embodiment shown as 2800 shows that the several voltages of FIG. 27 are replaced by the parallel combination of I i and Z i .
  • These combinations of I i and Z 1 are shown as pairs 2818 , 2819 ; 2820 , 2821 ; and 2822 , 2823 .
  • Current is provided to Z s 2889 as a function of control signals, such as FLUTTERTM blended control signals, 2802 , which includes 2802 ( a ) and 2802 ( b ).
  • a portion ( 2802 ( a )) of the control function 2802 is provided to a switching control to selectively access one of the pairs ( 2818 , 2819 ; 2820 , 2821 ; 2822 , 2823 ) as shown by 2813 and 2811 .
  • This selective access is shown as element 2807 .
  • the connections 2815 , 2813 and 2811 are activated based on the control signals of 2802 ( a ).
  • the selected energy source of the plurality of sources provides energy, in any suitable form, which may include voltage, current, power or any other excitation force to impedance module Z s 2889 . Although illustrated as a generic current sources for this example, it is understood that the energy sources may possess any statistic of current and may also be encoded with information (portion of H(x)).
  • a second portion of control, or FLUTTERTM blended control function 2802 is 2802 ( b ), which is provided to LO (local oscillator) 2810 , which then provides input to a modulator module which may be for example a MISO 2866 .
  • LO local oscillator
  • control signals from 2802 may also be provided to a modulator module which may be for example a MISO 2866 .
  • the modulator module 2866 may be, for example a MISO (multiple input single output module).
  • the matching impedance 2869 receives the output from Z s 2889 and the interaction of modulator module 2866 renders V L 2874 at load 2864 .
  • the energy sources of FIG. 28 are partitioned according to control signals 2802 ( a ), which partition the energy sample into a number of partitions, which can be explained as i ⁇ 2 k where k is the resolution used for reconstructing the signal amplitude and/or phase.
  • i ⁇ k for fixed partitions.
  • ti may be a suitable integer based on the available resources desired efficiency and signal quality as well cost of implementation, to obtain a desirable efficiency.
  • i may be an integer such as 2 and offer performance advantage.
  • FIG. 29 shows an embodiment 2900 of the present invention.
  • FIG. 29 accommodates variable switching power supplies for one or more of the partitions.
  • power supplies 2908 ( a ) . . . ( n ) receive a first portion of control signals 2902 ( a ).
  • the power supplies receive control signals 2902 ( a ).
  • Switching of switch 2909 is controlled by switch control 2911 via some portion of the signals 2902 ( a ).
  • a power source 2908 ( a ) . . . ( n ) provides energy to Z S 2989 as well as other portions of 2900 .
  • a second portion of the control function signals 2902 ( b ) is provided to modulator module, which may be, for example a MISO (multiple input single output module) 2966 and LO (local oscillator) 2910 .
  • the modulator module 2966 power source interacts with circuit impedances Z S 2989 , Z m 2969 , R S 2964 , LO 2910 , switch 2909 , power sources 2908 ( a . . . n ) and controls 2902 to generate an output V L 2974 .
  • the architecture shown in FIG. 29 represents nesting of partitions within partitions.
  • Each of the (i) partitions 2902 may be separately subdivided into partitions that can be implemented by a variable, or switching, power supply.
  • Controls 2902 (c . . . n) provide a means of adjusting energy source voltages 2908 ( a . . . n ) within a selected partition.
  • One or more of the (1) partitions can be realized in this manner.
  • ⁇ may be increased while providing finer control of amplitude reconstruction over some portion of the envelope dynamic range.
  • Any domain not controlled by a switching power supply may be supplied by a fixed source (source with a significantly constant describing pdf for voltage or current).
  • a Thévenized architecture may replace the variable, or selectable, voltage sources.
  • FIG. 30 shows an alternate embodiment 3000 of the present invention.
  • the embodiment 3000 presents the power source cascading, alternative.
  • Portions of the control function signals 3002 ( 3002 ( a ) and 3002 ( b )) are provided to energy sources 3008 ( a ) . . . ( n ) (where “n” is any suitable number) and to modulator module 3066 as well as LO 3010 .
  • the energy sources (generally 3008 ) may provide voltage, current, power, or any other suitable excitation waveform or energy of any suitable statistic to Z s module 3089 via controlled switching mechanisms 3011 and 3009 .
  • Node 3062 is also shown.
  • Node 3062 is a node which possesses a composite signal statistic.
  • a signal generated at node 3062 from the interaction of 3066 , and 3089 , 3009 , as well as 3008 is also provided to Z m 3069 , which is then provided to the load 3064 , to render V L 3074 .
  • the structure may also be Thévenized.
  • both series and parallel power sources can be utilized in place of the fixed series power source bank.
  • none of the power supplies may be variable or any subset may be variable.
  • Variable supplies are typically switching power supplies, or other equivalently efficient technology.
  • FIG. 31 illustrates another embodiment 3100 of the invention.
  • 3100 is a modulation architecture which supports the FLUTTERTM algorithm. This structure 3100 may also be referred to as a Type 3 modulator. 3100 may be instantiated one or more times to support complex baseband or pass band modulations.
  • 3101 is any suitable energy source consisting of up to 2 (i+1) distinct sources and associated branches which may possess currents which have D.C., A.C. characteristics or both.
  • the voltages+/ ⁇ V s 1 3102 , +/ ⁇ V s 2 3103 up to +/ ⁇ V i+1 3104 where i+1 is some suitable integer supporting up to i partitions, along with the voltages +/ ⁇ circumflex over (V) ⁇ s 1 3105 , +/ ⁇ circumflex over (V) ⁇ s 2 3106 up to +/ ⁇ circumflex over (V) ⁇ i+1 3107 are supplied by module 3101 .
  • Impedance Z 1 , 3108 is allocated to the circuit branch associated with +/ ⁇ V s 1 3102 .
  • Impedance Z 2 , 3109 is allocated to the circuit branch associated with +/ ⁇ V s 2 3103 .
  • Impedance Z i+1 3110 is allocated for the circuit branch associated with the voltage +/ ⁇ V s i+1 3104 in the (i+1) th power supply branch.
  • Impedance ⁇ circumflex over (Z) ⁇ 1 3111 is allocated to the circuit branch associated with ⁇ /+ ⁇ circumflex over (V) ⁇ s i 3105 .
  • Impedance ⁇ circumflex over (Z) ⁇ 2 3112 is allocated to the circuit branch associated with ⁇ /+V s 2 3106 .
  • Impedance ⁇ circumflex over (Z) ⁇ i+1 3113 is allocated to the circuit branch associated with ⁇ /+ ⁇ circumflex over (V) ⁇ s i+1 3107 .
  • Switch or Commutator 3114 accesses voltages+/ ⁇ V s 1 3102 , +/ ⁇ V s 2 3103 +/ ⁇ V s i+1 3104 after interaction with impedances Z 1 , 3108 , Z 2 , 3109 , up to and including Z i+1 3110 .
  • Switch or Commutator 3115 accesses voltages ⁇ /+ ⁇ circumflex over (V) ⁇ s 1 3105 , ⁇ /+ ⁇ circumflex over (V) ⁇ s 2 3106 . . . ⁇ /+ ⁇ circumflex over (V) ⁇ s i+1 3107 after interaction with impedances ⁇ circumflex over (Z) ⁇ 1 3111 , ⁇ circumflex over (Z) ⁇ 2 3112 , up to and including ⁇ circumflex over (Z) ⁇ i+1 3113 .
  • Switches or commutators 3114 , 3115 are controlled via function 3119 which is a subset of blended controls ⁇ tilde over (I) ⁇ H(x) v,i ⁇ distributed from a VSE 3121 .
  • Z L 3118 Load Impedance develops a differential output voltage V L 3122 according to currents flowing in the circuit determined by selected power sources, voltages+/ ⁇ V s 1 3101 , +/ ⁇ V s 2 3103 . . . +/ ⁇ V s i+1 3104 , voltages ⁇ /+ ⁇ circumflex over (V) ⁇ s 1 3105 , ⁇ /+ ⁇ circumflex over (V) ⁇ s 2 3106 . . . ⁇ /+ ⁇ circumflex over (V) ⁇ s i+1 3107 as well as impedances Z 1 3108 , Z 2 3109 , . . .
  • Z i+1 3110 impedances ⁇ circumflex over (Z) ⁇ 1 3111 , ⁇ circumflex over (Z) ⁇ 2 3112 . . . ⁇ circumflex over (Z) ⁇ i+1 3113 , impedance Z ⁇ 2 3116 , impedance ⁇ circumflex over (Z) ⁇ ⁇ 2 3117 , and Z L 3118 .
  • This modulator topology can deliver unipolar, bipolar, balanced or unbalanced signals, V L 3122 across the load Z L 3118 depending on the choice of supply voltages and their relative average values with respect to some system reference potential.
  • a fully differential and balanced output with an average of zero volts at V L 3122 improves efficiency.
  • the impedances Z ⁇ /2 3116 and ⁇ circumflex over (Z) ⁇ ⁇ 2 3117 can be implemented with transistors or other suitable structure including MISO functions conveying trans-impedances which may be modeled as Z ⁇ /2 3116 and ⁇ circumflex over (Z) ⁇ ⁇ /2 3117 .
  • a Type 4 modulator may be implemented by adding Z ⁇ s 3125 a shunt impedance used across the Z L 3118 load impedance terminals and controlled by a subset of blended control 3119 .
  • Impedances Z 1 3108 , Z 2 3109 , up to and including Z i+1 3110 as well as ⁇ circumflex over (Z) ⁇ 1 3111 , ⁇ circumflex over (Z) ⁇ 2 3112 up to and including ⁇ circumflex over (Z) ⁇ i+1 3113 are partially reflective of source power supply parasitic impedances. However, these impedances may be augmented with reactive components to assist in the reconstruction of analytic signal envelopes from circuit currents and voltages.
  • the modulator structure 3100 of FIG. 31 may be embedded in FIG. 14 to implement complex modulation schemes.
  • the variable or switched energy or power source module 3123 may be deployed in part or whole to modules 1420 and 1430 of FIG. 14 .
  • module 3124 the variable impedance module, may be deployed in part or whole to module 1460 of FIG. 14 as part of the ⁇ operator.
  • controls 3119 correspond to some subset of the controls 1401 of FIG. 14 .
  • Type 3 modulator requires variable impedances Z ⁇ /2 3116 , ⁇ circumflex over (Z) ⁇ ⁇ s /2 3117 is considered optional.
  • a Type 4 modulator utilizes the shunt impedance Z ⁇ s /2 3125 .
  • the switching and/or switched power supply sources may consist of up to 2(i+1) discrete fixed/constant power sources or up to 2(i+1) variable power sources, or a mix of constant and variable types.
  • the power sources may be current sources or voltage sources.
  • the characteristics and values associated with each power source giving rise to voltages+/ ⁇ V s 1 3102 , +/ ⁇ V s 2 3103 . . . +/ ⁇ V s i+1 3104 , ⁇ /+ ⁇ circumflex over (V) ⁇ s 1 3105 , ⁇ /+ ⁇ circumflex over (V) ⁇ s 2 3106 . . . ⁇ /+ ⁇ circumflex over (V) ⁇ s i+1 3107 , are selected and controlled via a subset of blended controls 3119 distributed from a VSE 3121 by suitable analog or digital means.
  • the power spectral density (psd) of each blended control may be unique.
  • the psd of each blended control may be dynamic and a function of time or state of 3100 .
  • each blended control may be tailored to select or adjust each switch, function, or impedance to reconstruct a desired signal V L 3122 according to some desired metric.
  • the rates and/or control bandwidths are distributed to maximize apparatus efficiency while conserving H(x) some desired information entropy conveyed through the system to produce V L 3122 .
  • each function block of 3100 may possess unique reference voltages which are distributed to internal circuit nodes of the indicated or associated impedances or functions.
  • the reference voltage, V ref — sys 3140 is associated with 3101 , switching and/or switched power supply sources.
  • Reference voltage V ref 1 3130 is associated with Z 1 3108 .
  • Reference voltage V ref 2 3131 is associated with Z 2 3109 .
  • Reference voltage V ref i+1 3132 is associated with Z i+1 3110 .
  • Reference voltage ⁇ circumflex over (V) ⁇ ref 1 3133 is associated with ⁇ circumflex over (Z) ⁇ 1 3111 .
  • Reference voltage ⁇ circumflex over (V) ⁇ ref 2 3134 is associated with ⁇ circumflex over (Z) ⁇ 2 3112 .
  • Reference voltage ⁇ circumflex over (V) ⁇ ref i+1 3135 is associated with ⁇ circumflex over (Z) ⁇ i+1 3113 .
  • Reference voltage V ref ⁇ 3136 is associated with Z ⁇ /2 3116
  • Voltage Reference ⁇ circumflex over (V) ⁇ ref ⁇ 3137 is associated with ⁇ circumflex over (Z) ⁇ ⁇ /2 3117 .
  • Voltage Reference V ref out 3139 is associated with Z L 3118 .
  • reference voltages for the impedances and functions of circuit 3100 may possess differing values.
  • the reference voltages may possess the same values.
  • the reference voltages may be zero or any other suitable value.
  • the choice of reference voltages will depend on the bias requirements for each circuit impedance or function, the interface requirements for connected circuits or functions and the requirement to implement waveform or signal offsets within 3100 .
  • Blended control Distribution 3121 provides blended controls ⁇ H(x) v,i ⁇ 3119 to various functions and impedances within 3100 .
  • the controls 3119 may be digital, analog or a mix of both.
  • Each control path is labeled with a dimension indicating the number of unique control signals allocated to the indicated path.
  • k ps 3150 is a number of controls less than or equal to 2(v+i) and associated with the switching and/or switched power supply sources 3101 .
  • k sx 3152 is a number of controls less than or equal to v+i, and associated with switch 3114 .
  • 3151 is a number of controls less than or equal to v+i, and associated with switch 3115 .
  • k Z ⁇ is a number of controls less than or equal to v+i, and associated with variable impedance Z ⁇ /2 3116 .
  • k ⁇ circumflex over (Z) ⁇ ⁇ is a number of controls less than or equal to v+i, and associated with variable impedance ⁇ circumflex over (Z) ⁇ ⁇ /2 3117 .
  • control circuit is a number of controls less than or equal to v+i, and associated with variable impedance Z ⁇ s 3125 .
  • the number of control signals may or may not correspond exactly to the number of physical connections in each control path at each function interface. Controls may be distributed serially or otherwise distributed or multiplexed on a common connection, wire, or path.
  • FIG. 32 Another embodiment 3200 of the invention is illustrated in FIG. 32.
  • 3200 is a general modulation architecture capable of supporting FLUTTERTM algorithms. 3200 can create virtually any signal in an efficient manner when operated in conjunction with the FLUTTERTM algorithm.
  • variable voltage or current sources associated with upper branch modulator 3227 .
  • variable voltage or current sources associated with the lower branch modulator 3228 . Collectively these sources are controlled via blended controls distributed through digital and/or analog methods from a VSE 3219 . Collectively the voltage and/or current sources
  • 3203 are referred to as upper branch sources. Collectively, the voltage and/or current sources
  • the upper branch sources and lower branch sources may be composed of any combination of current and voltage sources.
  • the upper branch sources and lower branch sources may be D.C., A.C., or mixed and possess any suitable statistic of voltages or currents.
  • the upper branch sources and lower branch sources may be harmonic functions or modulated harmonic functions.
  • the upper branch sources and lower branch sources may be random.
  • the upper branch sources and lower branch sources may possess both harmonic and random waveform metrics as may be required.
  • the fundamental frequency of each of the upper branch sources and each of the lower branch sources may be independently varied from 0 Hz (D.C. case) to any suitable upper frequency limit.
  • the phase of each of the upper branch sources and each of the lower branch sources may be independently varied from 0° degrees to modulo 360° degrees as required.
  • the amplitudes for each of the upper branch sources and each of the lower branch sources may be independently controlled as required.
  • Z U 1 3207 is a variable impedance associated with voltage or current source
  • Z U 2 3208 is a variable impedance associated with voltage or current source
  • variable impedances are associated with up to and including
  • Z L 1 3210 is a variable impedance associated with voltage or current source
  • Z L 2 3205 is a variable impedance associated with voltage or current source
  • variable impedances are associated with up to and including
  • Z U 1 3207 , Z U 2 3208 up to and including Z U i 3209 variable impedances are referred to as upper branch source impedances.
  • Z L 1 3210 , Z L 2 3211 , up to and including Z L i 3212 variable impedances are referred to as lower branch source impedances.
  • a variable portion of each upper branch impedance and each lower branch impedance are controlled via a subset of blended controls 3220 distributed by digital and/or analog means from a VSE 3219 .
  • the index value i enumerating the upper branch sources, upper branch source impedances, lower branch sources, and lower branch source impedances, may assume any suitable integer value.
  • An upper branch commutator or switch 3213 selects an upper branch source via an associated upper branch source impedance based on a subset of blended controls 3220 .
  • a lower branch commutator or switch 3214 selects a lower branch source via an associated lower branch source impedance based on a subset of blended controls 3220 .
  • the selected upper branch commutator or switch 3213 output 3222 is routed to variable upper branch impedance Z ⁇ U 3215 .
  • the selected lower branch commutator or switch 3214 output 3225 is routed to variable lower branch impedance Z ⁇ L 3216 .
  • Z ⁇ U 3215 and Z ⁇ L 3216 variable upper branch and lower branch impedances respectively are controlled by a subset of blended controls 3220 distributed by digital and/or analog means from a VSE 3219 .
  • An output 3222 from variable upper branch impedance Z ⁇ U 3215 is routed to output compositing Function 3217 also labeled as ⁇ .
  • An output 3223 from variable lower branch impedance Z ⁇ L 3216 is routed to output compositing Function 3217 also labeled as ⁇ .
  • Output Compositing Function 3217 operates on inputs 3222 and 3223 to create output composited signal V L 3226 at load impedance Z L 3218 .
  • Controls 3221 varies of the output Compositing Function 3217 according to a subset of blended controls 3221 .
  • the upper branch modulator 3227 and lower branch modulator 3228 along with blended controls 3220 and 3221 distribution of suitable prepared controls from the VSE 3219 and Compositing Function 3217 include a universal modulator generating virtually any modulated waveform/signal at V L 3226 , over frequency spans from baseband to any suitable carrier frequency.
  • blended controls 3220 , 3221 may be at suitable rates to support desired signal data rates and bandwidths, any signal path as well as at the output V L 3226 .
  • Each upper branch source, each lower branch source, each upper branch source impedance, each lower branch source impedance, variable upper branch impedance, variable lower branch impedance as well as compositing function may possess independent controls with independently variable information control rates and/or bandwidths.
  • each variable function or module of 3200 is supported or conveyed by each variable function or module of 3200 such that an output compositing function 3217 conserves input information entropy H(x) at the output V L 3226 albeit in a signaling format of choice which may be for example a modulated RF carrier signal.
  • Each variable function or module of 3200 is assigned some portion of the input entropy H(x) based on the portion of the originating information describing probability density function p(x) which exploits the most efficient modes of the apparatus.
  • an original density function p(x) with associated information entropy H(x) may be parsed to a set of joint probability densities p(x) v,i each with associated entropies H(x) v,i which may be independent or partially correlated.
  • the manner in which the set p(x) v,i is defined is based on a maximization of distributed apparatus efficiency (and hence total efficiency) and the requirement to conserve H(x) in the modulation process.
  • each blended control may possess an associated unique power spectral density (psd). Each blended control may possess a power spectral density that varies.
  • the output modulation of signal V L 3226 is a composited blend of functions within the apparatus which are optimized according to control rate vs. efficiency and dynamic range vs. efficiency per function or module.
  • the total efficiency is the average efficiency for all functions or modules of 3200 operating in concert.
  • each unique desired output signal statistic may utilize new rates for all functions and modules and redefine the set p(x) v,i which in turn modifies the weighting of the blended controls ⁇ tilde over (I) ⁇ H(x) v,i ⁇ .
  • All degrees of freedom illustrated in FIG. 32 may not be required for every application. For instance, some applications may not require upper branch source impedances which vary and lower branch source impedances which vary. In some circumstances upper branch source frequency and lower branch source frequency may be fixed. Logical redaction is apparent to those skilled in the art.
  • either the upper branch modulator 3227 or lower branch modulator 3228 may function as modulators separate from one another provided they benefit from suitable blended controls 3220 , 3219 and output compositing function 3217 .
  • the output compositing Function 3217 is a specific portion of a distributed compositing function. Most generally, compositing is a distributed function embedded in the blended control attributes, in the form of rates relative sample weighting and nonlinear mappings. However, the operator ⁇ possesses a prominent position in the modulator signal processing flow and final entropy reconstruction and thus is also referred to as an output compositing function in this topology. More specifically, it is a final mapping in the compositing process which constructs the desired output signal whilst conserving H(x).
  • Reference Voltage ref_u 1 3230 is associated with Z U 1 3207 .
  • Reference Voltage ref_u 2 3231 is associated with Z U 2 3208 .
  • Reference Voltage ref_u i 3232 is associated with Z U i 3209 .
  • Reference Voltage ref_L 1 3233 is associated with Z L 1 3210 .
  • Reference Voltage ref_L 2 3234 is associated with Z L 2 3211 .
  • Reference Voltage ref_L i 3235 is associated with Z L i 3212 .
  • Reference Voltage ref_ ⁇ U 3236 is associated with Z ⁇ U 3215 .
  • Reference Voltage ref_ ⁇ L 3237 is associated with Z ⁇ L 3216 .
  • Reference Voltage ref_ ⁇ ( 3238 ) is associated with output Compositing Function ( 3217 ).
  • Reference Voltage ref out 3239 is associated with output load Z L 3218 .
  • the above listed reference voltages may assume any suitable value for distribution to circuit nodes internal to the associated impedances or functions.
  • the reference voltages may or may not be equal.
  • the reference voltages may or may not be zero.
  • the choice of reference voltage for each function or impedance depends on whether the functions impedances require some particular operational bias voltage to implement a respective function, facilitate interface to connected impedances or functions, or to implement waveform or signal offset values.
  • each circuit internal to the impedances Z U 1 3207 , Z U 2 3208 , up to and including Z U i 3209 , Z L 1 3210 , Z L 2 3211 up to and including Z L i 3212 , Z ⁇ U 3215 , Z ⁇ L 3216 and Z L 3218 may possess series and shunt circuit elements with respect to input, output, and reference voltage terminals as well as any defined system ground potential.
  • output compositing function ⁇ may consist of series and shunt circuit elements with respect to input, output, blended control and reference voltage ref_ ⁇ 3238 voltage terminals as well as any defined system ground potential.
  • Blended controls 3220 and 3221 distributed from VSE 3219 consist of the illustrated control paths from 3219 to each respective applicable function within 3200 .
  • Each illustrated control path is assigned a dimension labeled k 1 3240 , k 2 3241 , k 3 3242 , k 4 3243 , k 5 3244 , k 5 3245 , k 7 3246 , k 8 3247 , k 9 3248 .
  • Each dimension can assume a number less than or equal to the number v+i the total number of control degrees of freedom.
  • Each of the dimensions k 1 , k 2 k 3 , k 4 , k 5 , k 6 k 7 , k 8 k 9 may be unique.
  • the dimension values indicate the number of control signals assigned to each control path.
  • Each control path is some subset of the blended controls 3220 , 3221 .
  • the number of control signals per path may or may not correspond to the number of physical connections between the distribution interface of the VSE 3219 and the respectively connected function within 3200 .
  • Each control path may support a number of signals different than the number of physical path connections through techniques of serial control, parallel control, as well as multiplexing or a mixture of these techniques.
  • Control path dimension k 1 3240 is associated with Z ⁇ U 3215.
  • Control path dimension k 2 3241 is associated with Switch (3213).
  • Control path dimension k 3 3242 is associated with Impedances Z U 1 3207, Z U 2 3208 . . . Z U i 3209.
  • Control path dimension k 4 3243 is associated with Power Sources V S U 1 ⁇ 3201 , V S U 2 ⁇ 3202 ⁇ . . . ⁇ V S U i ⁇ 3203.
  • Control path dimension k 5 3244 is associated with Power Sources V S L 1 ⁇ 3204 , V S L 2 ⁇ 3205 ⁇ . . . ⁇ V S L i ⁇ 3206.
  • Control path dimension k 6 3245 is associated with Impedances Z L 1 3210 , Z L 2 3211 . . . Z L i 3212.
  • Control path dimension k 7 3246 is associated with Switch 3214.
  • Control path dimension k 8 3247 is associated with Z ⁇ L 3216.
  • Control path dimension k 9 3248 is associated with output composite Function 3217 also on occasion referred to as operator .
  • FIG. 33 illustrates a graphic ( 3300 ) depicting an example composited signal 3301 along with 2 constituent signals, constituent signal (a) 3302 and constituent signal (b) 3303 .
  • Each of the illustrated constituents, 3302 and 3303 may also be a composite of other constituents, not illustrated.
  • the constituent signals (a and b) 3302 and 3303 are used as a part of a streamlined example to illustrate several aspects of FLUTTERTM as pertains to the use of blended controls which manipulate architectures such as the kind illustrated in FIGS. 1 , 2 , 3 , 4 , 13 , 14 , 18 , 22 , 26 , 27 , 28 , 29 , 30 , 31 and 32 .
  • Constituent signals (a) 3302 and (b) 3303 are obtained from subsets of blended controls ⁇ tilde over (I) ⁇ H(x) v,i ⁇ which shall be labeled ⁇ tilde over (I) ⁇ H(x) v,i ⁇ a for subset (a) corresponding to constituent signal (a) 3302 and ⁇ tilde over (I) ⁇ H(x) v,i ⁇ b subset (b) corresponding to constituent signal (b) 3303 .
  • ⁇ tilde over (I) ⁇ H(x) v,i ⁇ a , ⁇ tilde over (I) ⁇ H(x) v,i ⁇ b may also be referred to as domains of blended controls or simply as Domains depending on context.
  • Graphic 3301 is a desired output signal. It may also represent an amplitude envelope for the amplitude modulated portion of an RF carrier modulated signal, where the carrier wave has been omitted for convenience of illustration. Signal 3301 therefore possesses the associated desired information entropy H(x). Signal 3302 possesses some information entropy H a (x) which is less than H(x). Signal 3303 likewise possesses some information entropy H b (x) which is less than H(x).
  • constituent signal (a) 3302 Close examination of constituent signal (a) 3302 reveals an apparent bandwidth different than the final composite 3301 .
  • This signal 3302 possesses less than half the bandwidth of signal 3301 for purposes of illustration, and this specific example.
  • constituent signal (b) 3303 reveals an apparent bandwidth on the order of the output signal 3301 .
  • the effective bandwidth and/or sample rate for ⁇ tilde over (I) ⁇ H(x) v,i ⁇ a may be different than ⁇ tilde over (I) ⁇ H(x) v,i ⁇ b .
  • This can represent an advantage for cases involving apparatus hardware functions which possess varying degrees of performance limitations as a function of sample rate and/or bandwidth. Both efficiency and information entropy conservation may be tailored as sample rate requirements and bandwidth requirements increase, or decrease.
  • the constituent probability densities ⁇ p a (x) ⁇ v,i and ⁇ p b (x) ⁇ v,i may be tailored to match the degrees of freedom available in the apparatus, allocating information amongst these degrees of freedom to optimize efficiency, and permit conservation of H(x) in the output signal complex envelope.
  • the composite output signal 3301 is a simple sum of constituent (a) 3302 and constituent (b) 3303 to facilitate disclosure. That is, the output operator ⁇ is linear in this simplified example. In general this may not be the case and ⁇ example may be a more intricate nonlinear function of its input constituents. Moreover, the ⁇ output operator may possess more than two input constituents.
  • the constituent signals associated with ⁇ tilde over (I) ⁇ H(x) v,i ⁇ a and ⁇ tilde over (I) ⁇ H(x) v,i ⁇ b may be optional inputs to the output compositing procedure on occasion referred to as ⁇ . In general ⁇ tilde over (I) ⁇ H(x) v,i ⁇ a and ⁇ tilde over (I) ⁇ H(x) v,i ⁇ b may be regarded as nonlinear functions.
  • composite output signal 3301 represents an output envelope or a signal derived from a complex envelope
  • constituent signals (a) 3302 and (b) 3303 do not follow the envelope of 3301 .
  • FLUTTERTM relaxes the requirement for signal processing functions such as switching power supplies, for example, to possess extreme instantaneous dynamic range in concert with bandwidth.
  • constituent signal (a) 3302 may be formed from the variation of such a variable power source.
  • Such a power source may vary without explicitly tracking the output signal envelope while enhancing efficiency.
  • 3303 may possess a single power supply partition to facilitate ⁇ tilde over (I) ⁇ H(x) v,i ⁇ b processing for this example.
  • Constituent signal (a) 3302 and constituent signal (b) 3303 are characterized by random variables with probability density functions. These constituents are subordinate to the composite output signal 3301 .
  • the three signals possess differing power spectral densities.
  • constituent signals subordinate to constituent (a) 3302 and constituent signals subordinate to constituent signal (b) 3303 may possess differing power spectral densities.
  • FLUTTERTM trades efficiency vs. processing bandwidth and spectral characteristics according to the sustainable efficiency vs. information throughput for each function of the apparatus.
  • Linearity is not required for each function nor is it necessarily preferred. Rather efficiency is preferred, metering, subordinate signals approximately through nonlinearities such that the compositing process reconstitutes a desired signal without waste or distortion. Undesirable qualities of nonlinear processing are effectively suppressed at the composited output signal 3301 exploiting algorithm symmetries, nonlinear discrimination techniques as well as filtering.
  • FLUTTERTM technology and philosophy significantly contrast with pre-distortion technologies which strive to correct all system nonlinearities. FLUTTERTM accentuates the prominence and role of certain classes of nonlinearities rather than eliminating them.
  • FIG. 34 illustrates an example composite output signal 3401 which is the same as for the example of FIG. 33 .
  • Graphic 3402 illustrates a waveform corresponding to switched voltages of a variable or switched power source.
  • this graphic could be associated with one or more outputs of function/module 3101 in FIG. 31 .
  • it may apply to any power source for FIGS. 1 , 2 , 3 , 4 , 14 , 18 , 22 , 26 , 27 , 28 , 29 , 30 , 31 and 32 .
  • the number of partition thresholds associated with i partitions of the waveform 3402 and the threshold levels between partitions are functions of the required efficiency, limitations of the switched power source circuitry and the pdf associated with the information entropy allocated to the switched power source function. Nonlinearities of the waveform 3402 are effectively suppressed by other discriminating techniques of the FLUTTERTM algorithm, as well as filters.
  • FIG. 35 An example of hierarchical cascading, which is convenient for binary distributions, is shown in FIG. 35 .
  • embodiment 3500 shows three stages 3501 , 3503 and 3505 , defined by boundaries 3507 and 3509 .
  • 3511 , 3520 , 3522 , 3524 , 3526 , 3528 , and 3530 represent signal paths accessing switching stages 3501 , 3503 , and 3505 respectively.
  • the switching stages are composed of one or more switching elements 3515 , 3516 , 3517 and 3518 . Although three stages are illustrated the architecture may continue, accommodating a sequence of more stages. Furthermore, one stage may suffice for some applications. Such switching architectures may also be deployed in parallel or series.
  • Source 3602 supplies energy or signal or waveform to nodes 3604 ( a ) . . . ( n ) where “n” is any suitable number, via the switch selection process.
  • An “on” switch 3606 ( a ) . . . ( n ) can connect nodes 3604 ( a ) . . . ( n ) to nodes 3608 ( a ) . . . ( n ).
  • each switch possesses a “no connect” (NC) option 3610 ( a ) . . . ( n ) respectively.
  • only one switch may access a power partition or a signal or a waveform 3602 at any given instant and transfer 3602 to 3606 ( a ) . . . ( n ).
  • the efficiency, of this switch topology is on the order of ⁇ sx .
  • the load impedances attached to this switch at nodes 3608 ( a ) . . . ( n ) (outputs), as well as “soft” shut down, and “soft” start must be specifically tailored for the source at 3602 to avoid deleterious contentions and poorly behaved initial conditions when switching between outputs.
  • the equivalent of a time variable transition conductance may be employed within the switching circuits in conjunction with adjustment of the source at 3602 and the loads connected to the switch to eliminate transition discontinuities in charge transfer through various circuit nodes of 3600 .
  • loads are not illustrated it is understood that suitable impedances may be connected to nodes 3608 ( a ) . . . ( n ).
  • the FLUTTERTM algorithms and its related energy partitioning schemes may be adapted to traditional RF modulators and transmitters to enhance efficiency.
  • FLUTTERTM does not require exclusive implementation.
  • FLUTTERTM processing algorithms may enhance the efficiency for;

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Cited By (9)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US9729378B1 (en) * 2015-04-13 2017-08-08 The United States Of America As Represented By The Secretary Of The Navy Receiver architecture for constant envelope OFDM
US20180034416A1 (en) * 2016-07-29 2018-02-01 Qualcomm Incorporated Adjusting envelope tracking power supply
CN110069732A (zh) * 2019-03-29 2019-07-30 腾讯科技（深圳）有限公司 一种信息展示的方法、装置及设备
CN110248046A (zh) * 2018-08-16 2019-09-17 浙江大华技术股份有限公司 一种确定复合视频信号中视频有效区域的方法及装置
CN110276122A (zh) * 2019-06-19 2019-09-24 复旦大学 适用于多比特数字正交发射机的数字预失真前端电路
CN110750288A (zh) * 2019-10-23 2020-02-04 广州华多网络科技有限公司 原生工程配置方法、装置、电子设备及存储介质
WO2020041135A1 (en) * 2018-08-21 2020-02-27 Bae Systems Information And Electronic Systems Integration Inc. Variational design of companders for papr reduction in ofdm systems
US20220076150A1 (en) * 2018-04-16 2022-03-10 Nec Corporation Method, apparatus and system for estimating causality among observed variables
CN114646441A (zh) * 2022-03-16 2022-06-21 北京卫星环境工程研究所 基于界面力等效的三轴六自由度振动试验条件设计方法

Families Citing this family (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US10454427B2 (en) * 2017-11-01 2019-10-22 Mitsubishi Electric Research Laboratories, Inc. Power amplifier system and learning-based autotuning method thereof
US10346093B1 (en) * 2018-03-16 2019-07-09 Xilinx, Inc. Memory arrangement for tensor data
CN111075745A (zh) * 2019-12-13 2020-04-28 苏州浪潮智能科技有限公司 一种基于系统总电流的服务器风扇调控方法及系统

Citations (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US8013675B2 (en) * 2007-06-19 2011-09-06 Parkervision, Inc. Combiner-less multiple input single output (MISO) amplification with blended control

Family Cites Families (685)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US2734100A (en) 1956-02-07 Kendall
BE341637A (zh) 1926-05-10
FR41364E (fr) 1931-07-29 1933-01-07 Radio Electr Soc Fr Perfectionnements aux méthodes de radio-communications
US2116667A (en) 1934-04-11 1938-05-10 Csf Radio beacon and blind landing system
US2210028A (en) 1936-04-01 1940-08-06 Bell Telephone Labor Inc Amplifier
US2220201A (en) 1937-06-11 1940-11-05 Bliss William Roderic Modulation
NL57174C (zh) 1938-12-02
US2282706A (en) 1938-12-29 1942-05-12 Csf Modulated wave amplifier
US2294800A (en) 1940-04-03 1942-09-01 Rca Corp Modulation system
US2857591A (en) 1943-09-04 1958-10-21 Westinghouse Electric Corp Radio locators
FR993869A (fr) 1944-10-25 1951-11-08 Radio Electr Soc Fr Montage amplificateur de puissance pour ondes très courtes
US2508524A (en) 1945-12-15 1950-05-23 American Bosch Corp Electromagnetic device
US2555039A (en) 1947-02-13 1951-05-29 Baldwin Co Generator assembly in electrical musical instruments
US2677806A (en) 1949-03-29 1954-05-04 Radio Electr Soc Fr Phase-modulated piezoelectric crystal oscillator system
FR993120A (fr) 1949-06-03 1951-10-26 Materiel Telephonique Dispositifs modulateurs en amplitude avec élimination de la fréquence porteuse et a ` très large bande passante
BE499490A (zh) 1949-12-02
US3078456A (en) 1951-06-12 1963-02-19 Frederick C Alpers Split signal tracking circuit
GB737847A (en) 1952-12-05 1955-10-05 Radio Ind Improvements in or relating to distant synchronisation of television equipment
BE530175A (zh) 1953-07-24
BE535012A (zh) 1954-01-23
US2714634A (en) 1954-04-16 1955-08-02 Rca Corp Modulated radio frequency signal amplifier
LU35363A1 (zh) 1956-09-29
US2964622A (en) 1957-10-21 1960-12-13 Sylvania Electric Prod Image suppressed superheterodyne receiver
US2963933A (en) 1958-06-02 1960-12-13 Baldwin Piano Co Transistor circuit
US2968697A (en) 1958-09-15 1961-01-17 Gen Dynamics Corp Electronic switching telephone system
US3154782A (en) 1960-01-01 1964-10-27 Nippon Electric Co System for lengthening the effective range of radar
US3544697A (en) 1960-01-25 1970-12-01 Baldwin Co D H Keying system for electrical musical instruments
US3176060A (en) 1960-07-01 1965-03-30 Baldwin Co D H Gating system for electrical musical instrument
US3121198A (en) 1960-08-24 1964-02-11 F V Topping Electronics Ltd A.c. signal polarizing circuit
US3170127A (en) 1961-04-21 1965-02-16 Philco Corp Amplitude modulation system
US3212008A (en) 1961-06-14 1965-10-12 Leonard R Kahn Compatible single-sideband system
FR1307361A (fr) 1961-09-15 1962-10-26 Jaeger Ets Ed Procédé de démarrage et de mise en synchronisme automatiques de moteurs à hystérésis asynchrones et moteurs obtenus par sa mise en oeuvre
US3341697A (en) 1964-02-28 1967-09-12 Kaufman Myron Norman Wake simulator utilizing digital storage
US3263019A (en) 1964-03-18 1966-07-26 Hurvitz Hyman Randomization of phases and frequencies of musical spectra
DE1277376B (de) 1964-07-15 1968-09-12 Tesla Np Schaltung fuer die Amplitudenmodulation eines Senders
US3437945A (en) 1965-11-10 1969-04-08 Fairchild Camera Instr Co Transformerless transistor output amplifier
US3413570A (en) 1966-02-23 1968-11-26 Collins Radio Co High efficiency rf power amplification with modulation signal controlled "on"-"off" switch varied amplifier dc potentials
GB1092586A (en) 1966-03-01 1967-11-29 Decca Ltd Improvements in or relating to radio transmitters
FR1528861A (fr) 1967-05-03 1968-06-14 Compteurs Comp D Perfectionnements aux dispositifs de protection de lignes électriques triphasées
US3525941A (en) 1967-06-28 1970-08-25 Tracor Stepwave converter
US3418595A (en) 1967-07-28 1968-12-24 Sylvania Electric Prod Automatic frequency control system
US3493718A (en) 1968-10-15 1970-02-03 Gen Electric Semi-conductor welding circuit
US3651429A (en) 1970-12-09 1972-03-21 Bell Telephone Labor Inc Modulator compensated for varying modulating signal level
US3716730A (en) 1971-04-19 1973-02-13 Motorola Inc Intermodulation rejection capabilities of field-effect transistor radio frequency amplifiers and mixers
US3697692A (en) 1971-06-10 1972-10-10 Dynaco Inc Two-channel,four-component stereophonic system
US3789314A (en) 1971-12-06 1974-01-29 Bell Telephone Labor Inc Amplifier utilizing input signal power
BE793746A (fr) 1972-01-11 1973-07-09 Sercel Rech Const Elect Amplificateur d'echantillons de signaux analogiques avec reglage de gain automatique
US3777275A (en) 1972-01-31 1973-12-04 Bell Telephone Labor Inc Linear amplification with nonlinear devices
US3815040A (en) 1973-03-02 1974-06-04 Bell Telephone Labor Inc Feed-forward, error-correcting systems
US3852530A (en) 1973-03-19 1974-12-03 M Shen Single stage power amplifiers for multiple signal channels
US3852669A (en) 1973-06-26 1974-12-03 Us Army Circuit to protect rf output amplifier against mismatch damage
GB1452081A (en) 1973-10-26 1976-10-06 Post Office Transfer function control networks
US5307069A (en) 1973-11-02 1994-04-26 Hughes Aircraft Company Improved radar receiver system
US3895304A (en) 1974-03-20 1975-07-15 Westinghouse Electric Corp Tunable microwave notch filter
US3896395A (en) 1974-07-18 1975-07-22 Bell Telephone Labor Inc Linear amplification using quantized envelope components to phase reverse modulate quadrature reference signals
US3909742A (en) 1974-08-19 1975-09-30 Bell Telephone Labor Inc Linear amplification using nonlinear devices and feedback
US3927379A (en) 1975-01-08 1975-12-16 Bell Telephone Labor Inc Linear amplification using nonlinear devices and inverse sine phase modulation
US3991343A (en) 1976-01-07 1976-11-09 Henry Delpy Control circuit for progressively varying illumination intensity of lamps
US4104946A (en) 1976-06-17 1978-08-08 Peterson Richard H Voicing system for electronic organ
US4151517A (en) 1977-02-14 1979-04-24 Motorola, Inc. Closed loop companding ratio control for continuously variable slope delta modulation
US4090147A (en) 1977-07-20 1978-05-16 Bell Telephone Laboratories, Incorporated Interferometric amplifier
US4095196A (en) 1977-07-20 1978-06-13 Bell Telephone Laboratories, Incorporated Arc-cosine phase modulators
EP0011464A3 (en) 1978-11-14 1980-06-25 Continental Electronics Mfg. Co. Circuit and method for generating modulated oscillations and a modulated oscillatory signal generated by the method
US4178557A (en) 1978-12-15 1979-12-11 Bell Telephone Laboratories, Incorporated Linear amplification with nonlinear devices
US4229715A (en) 1978-12-15 1980-10-21 Bell Telephone Laboratories, Incorporated Precision phase modulators utilizing cascaded amplitude modulators
US4378530A (en) 1979-07-04 1983-03-29 Unisearch Limited High-efficiency low-distortion amplifier
US4301490A (en) 1979-07-09 1981-11-17 American Standard Inc. Electronic overload protection circuit
US4346354A (en) 1980-09-29 1982-08-24 Continental Electronics, Inc. Amplitude modulator using variable width rectangular pulse generator
NL8101109A (nl) 1981-03-09 1982-10-01 Philips Nv Electronische inrichting voor het opwekken van een in amplitude en faze gemoduleerd draaggolfsignaal.
US4511813A (en) 1981-06-12 1985-04-16 Harris Corporation Dual-gate MESFET combiner/divider for use in adaptive system applications
US4509017A (en) 1981-09-28 1985-04-02 E-Systems, Inc. Method and apparatus for pulse angle modulation
CA1341378C (en) 1984-07-16 2002-07-23 Richard W. Burrier Apparatus and method for frequency modulation
US4441080A (en) 1981-12-17 1984-04-03 Bell Telephone Laboratories, Incorporated Amplifier with controlled gain
US4433312A (en) 1981-12-18 1984-02-21 Kahn Leonard R Method and means for modulating waves
US4439744A (en) 1981-12-24 1984-03-27 Rca Corporation Variable power amplifier
US4580111A (en) 1981-12-24 1986-04-01 Harris Corporation Amplitude modulation using digitally selected carrier amplifiers
US4446440A (en) 1982-01-26 1984-05-01 Hewlett-Packard Company Dual mode amplifier
US4605902A (en) 1982-09-03 1986-08-12 Rockwell International Corporation Hybrid junction signal combiner
JPS6063517A (ja) 1983-09-16 1985-04-11 Sumitomo Electric Ind Ltd 位相変調器
SE8306109L (sv) 1983-11-07 1985-05-08 Ericsson Telefon Ab L M Diversitetskombinator
AU589119B2 (en) 1984-04-17 1989-10-05 Nec Corporation Digital radio communication system utilizing quadrature modulated carrier waves
US4584541A (en) 1984-12-28 1986-04-22 Rca Corporation Digital modulator with variations of phase and amplitude modulation
FR2576725B1 (fr) 1985-01-25 1988-07-08 Thomson Csf Amplificateur en classe ab et son correcteur de distorsion
US4628286A (en) 1985-04-17 1986-12-09 Rca Corporation Digital frequency modulator
FR2581277A1 (fr) 1985-04-30 1986-10-31 Labo Electronique Physique Circuit de recuperation de l'onde porteuse de systemes de transmissions numeriques
SU1322183A1 (ru) 1985-05-27 1987-07-07 Предприятие П/Я В-2489 Амплифазометр СВЧ
GB2177273A (en) 1985-06-26 1987-01-14 Philips Electronic Associated R f power amplifier
US4682149A (en) 1985-10-02 1987-07-21 Hughes Aircraft Company High resolution pipelined digital-to-analog converter
US4827516A (en) 1985-10-16 1989-05-02 Toppan Printing Co., Ltd. Method of analyzing input speech and speech analysis apparatus therefor
US4701716A (en) 1986-05-07 1987-10-20 Rca Corporation Parallel distributed signal amplifiers
US4796253A (en) 1986-07-03 1989-01-03 Hughes Aircraft Company Time base converter employing two reference position phase lock loop
US4686448A (en) 1986-08-01 1987-08-11 The United States Of America As Represented By The Secretary Of The Air Force Slewing power supply for programmable phase shifter drive
ES2003363A6 (es) 1986-10-02 1988-11-01 Gh Ind Sa Perfeccionamientos en generadores de alta frecuencia para aplicaciones de calentamiento por induccion laser plasma y similares
US4717894A (en) 1986-10-23 1988-01-05 Hewlett-Packard Company Calibration of vector modulators using a scalar detector
DE3733374A1 (de) 1987-10-02 1989-05-11 Messerschmitt Boelkow Blohm Verfahren und vorrichtung zur linearen verstaerkung von signalen in satellitentranspondern
GB2214374A (en) 1988-01-06 1989-08-31 Philips Electronic Associated Ssb signal generator
US4816783A (en) 1988-01-11 1989-03-28 Motorola, Inc. Method and apparatus for quadrature modulation
RO100466B1 (en) 1988-02-11 1992-08-20 Inst Cercetari Stiintifice Outphasing device
JPH0622302B2 (ja) 1988-05-11 1994-03-23 日本電信電話株式会社 増幅装置
US5005419A (en) 1988-06-16 1991-04-09 General Electric Company Method and apparatus for coherent imaging system
US4995055A (en) 1988-06-16 1991-02-19 Hughes Aircraft Company Time shared very small aperture satellite terminals
JPH0793546B2 (ja) 1988-09-26 1995-10-09 日本電信電話株式会社 増幅装置
US5081673A (en) 1988-10-11 1992-01-14 Engelke Robert M Voice bridge for relay center
US4951303A (en) 1988-10-31 1990-08-21 Larson Lawrence E High speed digital programmable frequency divider
JP2790215B2 (ja) 1988-10-31 1998-08-27 株式会社日立製作所 半導体集積回路装置
US4873492A (en) 1988-12-05 1989-10-10 American Telephone And Telegraph Company, At&T Bell Laboratories Amplifier with modulated resistor gain control
RO102824B1 (ro) 1989-01-06 1991-12-31 Institutul De Cercetare Stiintifica Si Inginerie Tehnologica Pentru Electronica Metoda si circuit pentru defazare automata
DE3906448C1 (zh) 1989-03-01 1990-03-15 Messerschmitt-Boelkow-Blohm Gmbh, 8012 Ottobrunn, De
US5239275A (en) 1989-08-04 1993-08-24 Motorola, Inc. Amplitude modulator circuit having multiple power supplies
JP2758683B2 (ja) 1990-02-07 1998-05-28 富士通株式会社 定振幅波合成形増幅器
US5287069A (en) 1990-02-07 1994-02-15 Fujitsu Limited Constant-amplitude wave combination type amplifier
GB9002788D0 (en) 1990-02-08 1990-04-04 Marconi Co Ltd Circuit for reducing distortion produced by an r.f.power amplifier
JPH0795650B2 (ja) 1990-02-26 1995-10-11 日本無線株式会社 結合量可変形方向性結合器
JPH0654878B2 (ja) 1990-03-27 1994-07-20 日本電信電話株式会社 出力可変送信装置
US5115203A (en) 1990-06-25 1992-05-19 Rockwell International Corporation Digital power amplifier
EP0465709A1 (de) 1990-07-12 1992-01-15 Thomcast Ag Verfahren zur Kompensation von Nichtlinearitäten einer Verstärkerschaltung
JPH0495409A (ja) 1990-08-13 1992-03-27 Fujitsu Ltd 増幅器
JPH04104604A (ja) 1990-08-24 1992-04-07 Fujitsu Ltd 高周波増幅器
US5093636A (en) 1990-09-25 1992-03-03 Hewlett-Packard Company Phase based vector modulator
EP0483435A1 (en) 1990-10-31 1992-05-06 International Business Machines Corporation Equalization system and method for equalizing a base-band telecommunication line
US5185762A (en) 1991-05-15 1993-02-09 Scs Mobilecom, Inc. Spread spectrum microwave overlay with notch filter
US5077539A (en) 1990-12-26 1991-12-31 Apogee Technology, Inc. Switching amplifier
US5239686A (en) 1991-04-29 1993-08-24 Echelon Corporation Transceiver with rapid mode switching capability
JPH0522046A (ja) 1991-07-10 1993-01-29 Matsushita Electric Ind Co Ltd オーデイオ用増幅回路
JPH0537263A (ja) 1991-07-30 1993-02-12 Fujitsu Ltd 定振幅波合成形増幅器
US5438591A (en) 1991-07-31 1995-08-01 Kabushiki Kaisha Toshiba Quadrature amplitude modulation type digital radio communication device and method for preventing abnormal synchronization in demodulation system
US5353347A (en) 1992-02-04 1994-10-04 Acs Communications, Inc. Telephone headset amplifier with battery saver, receive line noise reduction, and click-free mute switching
BR9305438A (pt) 1992-03-13 1994-08-02 Motorola Inc Rede combinada amplificadora de potência de sinal de radiofrequência (RF) e dispositivo de comunicações de sinal de radiofrequência de modo duplo
US5767750A (en) 1992-03-30 1998-06-16 Kabushiki Kaisha Toshiba Modulator
US5229735A (en) 1992-03-30 1993-07-20 Macrovision Corporation Wide frequency deviation voltage controlled crystal oscillator having plural parallel crystals
GB9209982D0 (en) 1992-05-08 1992-06-24 British Tech Group Method and apparatus for amplifying modulating and demodulating
US5302914A (en) 1992-10-20 1994-04-12 At&T Bell Laboratories Method and apparatus for reducing the peak-to-average power in multi-carrier RF communication systems
US5530722A (en) 1992-10-27 1996-06-25 Ericsson Ge Mobile Communications Inc. Quadrature modulator with integrated distributed RC filters
US5304943A (en) 1992-11-16 1994-04-19 Harris Corporation In-phase combiner and RF recovery system
GB2272589B (en) 1992-11-16 1995-11-29 Linear Modulation Tech Automatic calibration of the quadrature balance within a cartesian amplifier
DE4306690A1 (de) 1993-03-04 1994-09-08 Thomcast Ag Turgi Modulationsverstärker für Rundfunksender
WO1994023420A1 (en) 1993-04-07 1994-10-13 Noise Cancellation Technologies, Inc. Hybrid analog/digital vibration control system
US5365190A (en) 1993-05-03 1994-11-15 Duly Research, Inc. Feed-forward digital phase and amplitude correction system
JPH06338728A (ja) 1993-05-27 1994-12-06 Hitachi Ltd 高周波高効率増幅回路
FR2705844B1 (fr) 1993-05-28 1995-07-21 Thomson Csf Procédé et dispositif de modulation en amplitude d'un signal radiofréquence.
US5420541A (en) 1993-06-04 1995-05-30 Raytheon Company Microwave doherty amplifier
US8089324B2 (en) 2006-08-05 2012-01-03 Min Ming Tarng Varactor-free amplitude controlled oscillator(ACO) for system on chip and system on card Xtaless clock SOC
US5432473A (en) 1993-07-14 1995-07-11 Nokia Mobile Phones, Limited Dual mode amplifier with bias control
US5477735A (en) 1993-08-11 1995-12-26 Bently Nevada Corporation Two-wire constant current powered transducer
US5345189A (en) 1993-09-20 1994-09-06 Hewlett-Packard Company Vectorial signal combiner for generating an amplitude modulated carrier by adding two phase modulated constant envelope carriers
US5854571A (en) 1993-10-28 1998-12-29 Motorola Inc. Method and apparatus for controlling a peak envelope power of a power amplifier
US5365187A (en) 1993-10-29 1994-11-15 Hewlett-Packard Company Power amplifier utilizing the vector addition of two constant envelope carriers
DE69422010T2 (de) 1993-12-22 2000-07-20 Koninkl Philips Electronics Nv Phasenschiebverstärker und seine Verwendung in einer Zusammenführungsschaltung
US5574967A (en) 1994-01-11 1996-11-12 Ericsson Ge Mobile Communications, Inc. Waste energy control and management in power amplifiers
US5563556A (en) 1994-01-24 1996-10-08 Quantum Optics Corporation Geometrically modulated waves
US5426641A (en) 1994-01-28 1995-06-20 Bell Communications Research, Inc. Adaptive class AB amplifier for TDMA wireless communications systems
US6137355A (en) 1994-04-17 2000-10-24 Sevic; John F. Dual-mode amplifier with high efficiency and high linearity
US5574992A (en) 1994-04-29 1996-11-12 Motorola, Inc. Method and apparatus for reducing off-channel interference produced by a linear transmitter
US5404114A (en) 1994-06-23 1995-04-04 Rockwell International Corporation Method and apparatus for providing transmitter protection
US5490172A (en) 1994-07-05 1996-02-06 Airnet Communications Corporation Reducing peak-to-average variance of a composite transmitted signal via out-of-band artifact signaling
US5485120A (en) 1994-07-28 1996-01-16 Aval Communications Inc. Feed-forward power amplifier system with adaptive control and control method
US5495500A (en) 1994-08-09 1996-02-27 Intermec Corporation Homodyne radio architecture for direct sequence spread spectrum data reception
US5694433A (en) 1994-09-14 1997-12-02 Ericsson Inc. Efficient linear power amplification
US5633893A (en) 1994-09-29 1997-05-27 Ericsson Inc. Digital modulation method with controlled envelope variation
DE19535075A1 (de) 1994-10-21 1996-04-25 Deutsche Telekom Ag Digitalmodulation
FR2726719B1 (fr) 1994-11-04 1996-11-29 Thomson Consumer Electronics Appareil de reception video et procede d'asservissement de recepteurs
CN1154245C (zh) 1994-11-30 2004-06-16 松下电器产业株式会社 接收电路
JPH08163189A (ja) 1994-12-06 1996-06-21 Nec Corp 送信回路
EP1168598A3 (en) 1994-12-13 2003-01-02 Hughes Electronics Corporation High precision, low phase noise synthesizer with vector modulator
FR2728416B1 (fr) 1994-12-15 1997-01-24 France Telecom Procede pour equilibrer les voies d'un amplificateur de type "linc"
US5559471A (en) 1994-12-21 1996-09-24 Motorola, Inc. Amplifier and biasing circuit therefor
JP2571033B2 (ja) 1994-12-30 1997-01-16 日本電気株式会社 送信電力増幅回路の出力制御回路
US5508657A (en) 1995-01-30 1996-04-16 Aml Communications, Inc. Feed forward cancellation amplifier utilizing dynamic vector control
JP2885660B2 (ja) 1995-01-31 1999-04-26 日本無線株式会社 振幅変調回路
US5541554A (en) 1995-03-06 1996-07-30 Motorola, Inc. Multi-mode power amplifier
JP2762950B2 (ja) 1995-03-29 1998-06-11 日本電気株式会社 電源切替回路
US5697074A (en) 1995-03-30 1997-12-09 Nokia Mobile Phones Limited Dual rate power control loop for a transmitter
JPH08307159A (ja) 1995-04-27 1996-11-22 Sony Corp 高周波増幅回路、送信装置、及び受信装置
JP3304683B2 (ja) 1995-05-02 2002-07-22 富士通株式会社 無線装置
US5554865A (en) 1995-06-07 1996-09-10 Hughes Aircraft Company Integrated transmit/receive switch/low noise amplifier with dissimilar semiconductor devices
JPH0918536A (ja) 1995-06-28 1997-01-17 Nec Corp 変調増幅方式
US5678208A (en) 1995-07-19 1997-10-14 Motorola, Inc. Transmission system
US6026286A (en) 1995-08-24 2000-02-15 Nortel Networks Corporation RF amplifier, RF mixer and RF receiver
JPH0974320A (ja) 1995-09-05 1997-03-18 Nippon Motorola Ltd 定振幅波合成型電力増幅回路
US5739723A (en) 1995-12-04 1998-04-14 Motorola, Inc. Linear power amplifier using active bias for high efficiency and method thereof
US5974041A (en) 1995-12-27 1999-10-26 Qualcomm Incorporated Efficient parallel-stage power amplifier
US5872481A (en) 1995-12-27 1999-02-16 Qualcomm Incorporated Efficient parallel-stage power amplifier
US5612651A (en) 1996-01-02 1997-03-18 Loral Aerospace Corp. Modulating array QAM transmitter
US6373901B1 (en) 1996-04-04 2002-04-16 Motorola, Inc. Method and apparatus for conditioning modulated signals using window expansion
US5805640A (en) 1996-04-04 1998-09-08 Motorola, Inc. Method and apparatus for conditioning modulated signals for digital communications
US5724005A (en) 1996-04-25 1998-03-03 Lucent Technologies Inc. Linear power amplifier with automatic gate/base bias control for optimum efficiency
SE9601619L (sv) 1996-04-29 1997-10-30 Radio Design Innovation Tj Ab Anordning med sändarkombinerare
US5774017A (en) 1996-06-03 1998-06-30 Anadigics, Inc. Multiple-band amplifier
US5815531A (en) 1996-06-12 1998-09-29 Ericsson Inc. Transmitter for encoded data bits
US6185259B1 (en) 1996-06-12 2001-02-06 Ericsson Inc. Transmitter/receiver for GMSK and offset-QAM
US5764704A (en) 1996-06-17 1998-06-09 Symmetricom, Inc. DSP implementation of a cellular base station receiver
US5710520A (en) 1996-06-28 1998-01-20 Harris Corporation Pulse step modulator and transformer
JP3124229B2 (ja) 1996-06-28 2001-01-15 富士通株式会社 Ｐｈｓを利用したｗｌｌシステムにおける無線基地局、その運用方法およびインタフェース変換装置
US5757229A (en) 1996-06-28 1998-05-26 Motorola, Inc. Bias circuit for a power amplifier
JPH1022756A (ja) 1996-07-04 1998-01-23 Mitsubishi Electric Corp 無線送信機およびその送信制御方法
US5892394A (en) 1996-07-19 1999-04-06 Holtek Microelectronics Inc. Intelligent bias voltage generating circuit
DE69619509D1 (de) 1996-07-24 2002-04-04 St Microelectronics Srl Pulsbreitenmodulationsmethode und -vorrichtung
US5770971A (en) 1996-07-26 1998-06-23 Northern Telecom Limited Distortion compensation control for a power amplifier
JPH1070451A (ja) 1996-08-27 1998-03-10 Nippon Telegr & Teleph Corp <Ntt> Ｆｅｔ型出力回路，ｆｅｔ型入力回路およびｆｅｔ型入出力回路
US5862460A (en) 1996-09-13 1999-01-19 Motorola, Inc. Power control circuit for a radio frequency transmitter
US5898338A (en) 1996-09-20 1999-04-27 Spectrian Adaptive digital predistortion linearization and feed-forward correction of RF power amplifier
US5786727A (en) 1996-10-15 1998-07-28 Motorola, Inc. Multi-stage high efficiency linear power amplifier and method therefor
US6510309B1 (en) 1996-11-20 2003-01-21 Conexant Systems, Inc. Intermediate frequency amplifier circuit for use in receive and transmit modes
US6072361A (en) 1996-11-27 2000-06-06 Motorola, Inc. Wideband class-S modulator and method therefor
US5835128A (en) 1996-11-27 1998-11-10 Hughes Electronics Corporation Wireless redistribution of television signals in a multiple dwelling unit
FI117494B (fi) 1996-11-29 2006-10-31 Nokia Corp Menetelmä digitaalisessa kvadratuurimodulaattorissa ja kvadratuuridemodulaattorissa, digitaalinen kvadratuurimodulaattori ja kvadratuuridemodulaattori
DE19651334A1 (de) 1996-12-10 1998-06-25 Ericsson Telefon Ab L M Betriebstestvorrichtung und Verfahren zur Ausführung eines Betriebstests für ein zu testendes System
US5901346A (en) 1996-12-11 1999-05-04 Motorola, Inc. Method and apparatus utilizing a compensated multiple output signal source
US5933766A (en) 1996-12-16 1999-08-03 Ericsson Inc. Intermodulation compensation in multi-channel amplifiers
US6085074A (en) 1997-02-28 2000-07-04 Motorola, Inc. Apparatus and method for amplifying an amplitude-varying signal
US6256482B1 (en) 1997-04-07 2001-07-03 Frederick H. Raab Power- conserving drive-modulation method for envelope-elimination-and-restoration (EER) transmitters
US6637030B1 (en) 1997-04-09 2003-10-21 Micron Technology, Inc. Broadband cable television and computer network
US6069525A (en) 1997-04-17 2000-05-30 Qualcomm Incorporated Dual-mode amplifier with high efficiency and high linearity
US6148220A (en) * 1997-04-25 2000-11-14 Triquint Semiconductor, Inc. Battery life extending technique for mobile wireless applications
US5880633A (en) 1997-05-08 1999-03-09 Motorola, Inc. High efficiency power amplifier
US6097252A (en) 1997-06-02 2000-08-01 Motorola, Inc. Method and apparatus for high efficiency power amplification
KR100251561B1 (ko) 1997-06-19 2000-04-15 윤종용 디지털통신시스템의송신기선형화장치및방법
US6130916A (en) 1997-07-10 2000-10-10 3Com Corporation Method and apparatus for improving a transmission data rate of baseband data in a wireless network
DE19730086A1 (de) 1997-07-14 1999-01-21 Bosch Gmbh Robert Sendeeinrichtung für Hochfrequenzsignale
US6311045B1 (en) 1997-07-28 2001-10-30 Roke Manor Research Limited Apparatus for signal isolation in a radio transmitter-receiver
EP0897213B1 (en) 1997-08-11 2004-03-31 SGS-THOMSON MICROELECTRONICS S.r.l. Monitoring of current in an inductive load, PWM driven through a bridge stage
US6252461B1 (en) 1997-08-25 2001-06-26 Frederick Herbert Raab Technique for wideband operation of power amplifiers
DE19738780A1 (de) 1997-09-04 1999-03-11 Thomson Brandt Gmbh Verfahren und Schaltungsanordnung zur Korrektur von Phasen- und/oder Frequenzfehlern digitaler Multicarrier-Signale
US5952947A (en) 1997-09-09 1999-09-14 Raytheon Company Flexible and programmable delta-sigma analog signal converter
US5886575A (en) 1997-09-30 1999-03-23 Motorola, Inc. Apparatus and method for amplifying a signal
JP3119216B2 (ja) 1997-10-15 2000-12-18 日本電気株式会社 高周波増幅回路
US6385439B1 (en) 1997-10-31 2002-05-07 Telefonaktiebolaget Lm Ericsson (Publ) Linear RF power amplifier with optically activated switches
US6130910A (en) 1997-11-03 2000-10-10 Motorola, Inc. Method and apparatus for high efficiency wideband power amplification
US6308048B1 (en) 1997-11-19 2001-10-23 Ericsson Inc. Simplified reference frequency distribution in a mobile phone
US6133789A (en) 1997-12-10 2000-10-17 Nortel Networks Corporation Method and system for robustly linearizing a radio frequency power amplifier using vector feedback
US6125266A (en) 1997-12-31 2000-09-26 Nokia Mobile Phones Limited Dual band architectures for mobile stations having transmitter linearization feedback
US6510310B1 (en) 1998-01-26 2003-01-21 Conexant Systems, Inc. Dual mode phone architecture utilizing a single transmit-receive switch
US6232835B1 (en) 1998-02-13 2001-05-15 Nortel Networks Limited System and method of linearizing the gain error of a power amplifier
US6104991A (en) 1998-02-27 2000-08-15 Lucent Technologies, Inc. Speech encoding and decoding system which modifies encoding and decoding characteristics based on an audio signal
US6215354B1 (en) 1998-03-06 2001-04-10 Fujant, Inc. Closed loop calibration for an amplitude reconstruction amplifier
GB9804835D0 (en) 1998-03-06 1998-04-29 Wireless Systems Int Ltd Predistorter
US5886573A (en) 1998-03-06 1999-03-23 Fujant, Inc. Amplification using amplitude reconstruction of amplitude and/or angle modulated carrier
US6154093A (en) 1998-04-01 2000-11-28 Lucent Technologies Inc. Fast adaptive wideband power amplifier feed forward linearizer using a RLS parameter tracking algorithm
US5963091A (en) 1998-04-01 1999-10-05 Chen; Jiunn-Tsair Article comprising a power amplifier with feed forward linearizer using a RLS parameter tracking algorithm
US6285251B1 (en) 1998-04-02 2001-09-04 Ericsson Inc. Amplification systems and methods using fixed and modulated power supply voltages and buck-boost control
US6311046B1 (en) 1998-04-02 2001-10-30 Ericsson Inc. Linear amplification systems and methods using more than two constant length vectors
US6889034B1 (en) 1998-04-02 2005-05-03 Ericsson Inc. Antenna coupling systems and methods for transmitters
EP1068666B1 (en) 1998-04-02 2003-05-28 Ericsson, Inc. Hybrid chireix/doherty amplifiers power waveform synthesis
US6133788A (en) 1998-04-02 2000-10-17 Ericsson Inc. Hybrid Chireix/Doherty amplifiers and methods
US6359506B1 (en) 1998-04-02 2002-03-19 Ericsson Inc. Linear modulation using a linear and a non-linear amplifier
US6212172B1 (en) 1998-05-08 2001-04-03 Omnipoint Corporation Filtering method to allow FDD and TDD operation in PCS transreceivers
US7092675B2 (en) 1998-05-29 2006-08-15 Silicon Laboratories Apparatus and methods for generating radio frequencies in communication circuitry using multiple control signals
US7035607B2 (en) 1998-05-29 2006-04-25 Silicon Laboratories Inc. Systems and methods for providing an adjustable reference signal to RF circuitry
US5973568A (en) 1998-06-01 1999-10-26 Motorola Inc. Power amplifier output module for dual-mode digital systems
JP3314724B2 (ja) 1998-06-02 2002-08-12 日本電気株式会社 電力増幅回路および電力自動制御方法
US5999046A (en) 1998-06-10 1999-12-07 Motorola, Inc. Power combiner for use in a radio frequency system and a method of constructing a power combiner
US5990738A (en) 1998-06-19 1999-11-23 Datum Telegraphic Inc. Compensation system and methods for a linear power amplifier
US6054896A (en) 1998-12-17 2000-04-25 Datum Telegraphic Inc. Controller and associated methods for a linc linear power amplifier
US5990734A (en) 1998-06-19 1999-11-23 Datum Telegraphic Inc. System and methods for stimulating and training a power amplifier during non-transmission events
US6054894A (en) 1998-06-19 2000-04-25 Datum Telegraphic Inc. Digital control of a linc linear power amplifier
US6404823B1 (en) 1998-07-01 2002-06-11 Conexant Systems, Inc. Envelope feedforward technique with power control for efficient linear RF power amplification
FR2781106B1 (fr) 1998-07-10 2001-04-13 Commissariat Energie Atomique Modulateur vectoriel
US6028485A (en) 1998-08-03 2000-02-22 Motorola, Inc. Power amplification apparatus and method therefor
US7548787B2 (en) 2005-08-03 2009-06-16 Kamilo Feher Medical diagnostic and communication system
US6525605B2 (en) 1998-08-19 2003-02-25 Harris Corporation Power amplifier system having frequency and amplifier failure compensation
US6424216B2 (en) 1998-08-19 2002-07-23 Harris Corporation Power amplifier system having amplifier failure compensation
US6188277B1 (en) 1998-08-19 2001-02-13 Harris Corporation Power amplifier having monitoring and circuit protection
US6577691B2 (en) 1998-09-03 2003-06-10 Time Domain Corporation Precision timing generator apparatus and associated methods
US6842495B1 (en) 1998-11-03 2005-01-11 Broadcom Corporation Dual mode QAM/VSB receiver
US6775334B1 (en) 1998-11-03 2004-08-10 Broadcom Corporation Equalization and decision-directed loops with trellis demodulation in high definition TV
US6111462A (en) 1998-11-18 2000-08-29 Mucenieks; Lance T. RF power amplifier linearization using parallel RF power amplifiers having intermod-complementing predistortion paths
JP3241012B2 (ja) 1998-11-26 2001-12-25 日本電気株式会社 送信時消費電力低減回路及びこれを用いた無線通信装置並びに線形動作制御方法
US6295442B1 (en) 1998-12-07 2001-09-25 Ericsson Inc. Amplitude modulation to phase modulation cancellation method in an RF amplifier
US6201452B1 (en) 1998-12-10 2001-03-13 Ericsson Inc. Systems and methods for converting a stream of complex numbers into a modulated radio power signal
US6411655B1 (en) 1998-12-18 2002-06-25 Ericsson Inc. Systems and methods for converting a stream of complex numbers into an amplitude and phase-modulated radio power signal
US6181199B1 (en) 1999-01-07 2001-01-30 Ericsson Inc. Power IQ modulation systems and methods
US6043707A (en) 1999-01-07 2000-03-28 Motorola, Inc. Method and apparatus for operating a radio-frequency power amplifier as a variable-class linear amplifier
JP2000209291A (ja) 1999-01-20 2000-07-28 Hitachi Ltd 直交変調器
JP3532782B2 (ja) 1999-02-22 2004-05-31 株式会社東芝 信号入力回路及びこれを用いた可変利得増幅器
US6775344B1 (en) 1999-04-02 2004-08-10 Storage Technology Corporation Dropout resistant phase-locked loop
US6882711B1 (en) 1999-09-20 2005-04-19 Broadcom Corporation Packet based network exchange with rate synchronization
US6198416B1 (en) 1999-04-16 2001-03-06 Scott R. Velazquez Linearity error compensator
US6584090B1 (en) 1999-04-23 2003-06-24 Skyworks Solutions, Inc. System and process for shared functional block CDMA and GSM communication transceivers
US6560296B1 (en) 1999-05-04 2003-05-06 Lucent Technologies Inc. Method and apparatus for modulating digital data
JP2000332666A (ja) 1999-05-24 2000-11-30 Toshiba Tec Corp 無線通信システム
US6242975B1 (en) 1999-05-25 2001-06-05 Conexant Systems, Inc. Envelope peak and trough limiting to improve amplifier efficiency and distortion characteristics
DE69922266D1 (de) 1999-05-25 2004-12-30 Nokia Corp Linearisierungs- und modulationsvorrichtung
US6307894B2 (en) 1999-05-25 2001-10-23 Conexant Systems, Inc. Power amplification using a direct-upconverting quadrature mixer topology
US6614854B1 (en) 1999-05-28 2003-09-02 Carriercomm, Inc. System and method for adaptive predistortion
WO2001003292A1 (en) 1999-07-02 2001-01-11 Nokia Networks Oy Power control for non-constant envelope modulation
US6356146B1 (en) 1999-07-13 2002-03-12 Pmc-Sierra, Inc. Amplifier measurement and modeling processes for use in generating predistortion parameters
US6697436B1 (en) 1999-07-13 2004-02-24 Pmc-Sierra, Inc. Transmission antenna array system with predistortion
US6587514B1 (en) 1999-07-13 2003-07-01 Pmc-Sierra, Inc. Digital predistortion methods for wideband amplifiers
US6798843B1 (en) 1999-07-13 2004-09-28 Pmc-Sierra, Inc. Wideband digital predistortion linearizer for nonlinear amplifiers
US6421389B1 (en) 1999-07-16 2002-07-16 Time Domain Corporation Baseband signal converter for a wideband impulse radio receiver
US6307468B1 (en) 1999-07-20 2001-10-23 Avid Identification Systems, Inc. Impedance matching network and multidimensional electromagnetic field coil for a transponder interrogator
US6349216B1 (en) 1999-07-22 2002-02-19 Motorola, Inc. Load envelope following amplifier system
GB2352570B (en) 1999-07-28 2003-12-24 Wireless Systems Int Ltd Distortion reduction
US6198347B1 (en) 1999-07-29 2001-03-06 Tropian, Inc. Driving circuits for switch mode RF power amplifiers
US7054296B1 (en) 1999-08-04 2006-05-30 Parkervision, Inc. Wireless local area network (WLAN) technology and applications including techniques of universal frequency translation
US7260369B2 (en) 2005-08-03 2007-08-21 Kamilo Feher Location finder, tracker, communication and remote control system
US6559722B1 (en) 1999-08-10 2003-05-06 Anadigics, Inc. Low bias current/temperature compensation current mirror for linear power amplifier
JP2001053552A (ja) 1999-08-10 2001-02-23 Nec Corp フィードフォワード増幅回路、及びフィードフォワード増幅回路における非線形歪の補償方法。
US6157253A (en) 1999-09-03 2000-12-05 Motorola, Inc. High efficiency power amplifier circuit with wide dynamic backoff range
GB2354126B (en) 1999-09-13 2004-07-21 Wireless Systems Int Ltd Signal processing
US6714776B1 (en) 1999-09-28 2004-03-30 Microtune (Texas), L.P. System and method for an image rejecting single conversion tuner with phase error correction
US6738601B1 (en) 1999-10-21 2004-05-18 Broadcom Corporation Adaptive radio transceiver with floating MOSFET capacitors
US6246286B1 (en) 1999-10-26 2001-06-12 Telefonaktiebolaget Lm Ericsson Adaptive linearization of power amplifiers
US6504447B1 (en) 1999-10-30 2003-01-07 Hrl Laboratories, Llc Microelectromechanical RF and microwave frequency power limiter and electrostatic device protection
JP3433707B2 (ja) 1999-11-04 2003-08-04 日本電気株式会社 差動入力回路
US6292054B1 (en) 1999-11-19 2001-09-18 Lucent Technologies Inc. System and method for producing an amplified signal
US7558391B2 (en) 1999-11-29 2009-07-07 Bizjak Karl L Compander architecture and methods
JP3381689B2 (ja) 1999-11-30 2003-03-04 日本電気株式会社 非線形歪み補償回路及びそれを用いた送信装置並びに移動通信機
GB2356992B (en) 1999-12-02 2004-07-14 Wireless Systems Int Ltd Control scheme for distorton reduction
US6374092B1 (en) 1999-12-04 2002-04-16 Motorola, Inc. Efficient multimode power amplifier
US6697603B1 (en) 1999-12-13 2004-02-24 Andrew Corporation Digital repeater
KR20010056500A (ko) 1999-12-15 2001-07-04 서평원 전력증폭기의 왜곡 성분 검출장치
JP2001177436A (ja) 1999-12-15 2001-06-29 Nec Corp 移動通信システムにおけるａｆｃ制御装置及びその方法並びにそれを使用した移動通信機
KR20010064900A (ko) 1999-12-20 2001-07-11 서평원 적응성 선왜곡 선형화 장치
US6449465B1 (en) 1999-12-20 2002-09-10 Motorola, Inc. Method and apparatus for linear amplification of a radio frequency signal
US6259320B1 (en) 1999-12-27 2001-07-10 Nortel Networks Limited Error correction within power amplifiers
EP1113637B1 (en) 1999-12-28 2006-04-05 NTT DoCoMo, Inc. Circuit for the compression of the dynamic range of a signal
KR100674586B1 (ko) 1999-12-30 2007-01-25 엘지전자 주식회사 전력증폭기의 전치왜곡 선형화기
KR20030009337A (ko) 2000-01-07 2003-01-29 스펙트리안 코퍼레이션 알 에프 전력 증폭기 왜곡을 측정 및 정정하는데 사용된검출기를 소인하는 반송파-블랭킹 메카니즘
US6384681B1 (en) 2000-01-07 2002-05-07 Spectrian Corporation Swept performance monitor for measuring and correcting RF power amplifier distortion
US6681101B1 (en) 2000-01-11 2004-01-20 Skyworks Solutions, Inc. RF transmitter with extended efficient power control range
JP2001203540A (ja) 2000-01-19 2001-07-27 Hitachi Ltd 高周波電力増幅器
US6300828B1 (en) 2000-01-20 2001-10-09 Next Level Communications Switchless high efficiency amplifier
EP1122735B1 (en) 2000-01-31 2010-09-01 STMicroelectronics Srl Interleaved data path and output management architecture for an interleaved memory and load pulser circuit for outputting the read data
DE60019081D1 (de) 2000-01-31 2005-05-04 St Microelectronics Srl Verschachtelter Burst-Speicher mit Burst-Zugriff bei synchronen Lesezyklen, wobei die beiden untergeordneten Speicherfelder unabhängig lesbar sind mit wahlfreiem Zugriff während asynchroner Lesezyklen
SE522564C2 (sv) 2000-02-01 2004-02-17 Ericsson Telefon Ab L M Gruppantennkalibrering
US6366177B1 (en) 2000-02-02 2002-04-02 Tropian Inc. High-efficiency power modulators
JP2001217659A (ja) 2000-02-03 2001-08-10 Mitsubishi Electric Corp マイクロ波増幅器
GB2359206B (en) 2000-02-08 2004-06-23 Wireless Systems Int Ltd Amplifier arrangement
US6801567B1 (en) 2000-03-30 2004-10-05 Texas Instruments Incorporated Frequency bin method of initial carrier frequency acquisition
WO2001077706A1 (en) 2000-04-07 2001-10-18 The Chief Controller, Research And Development Transmit/receiver module for active phased array antenna
US6677821B2 (en) 2000-04-21 2004-01-13 Sony Corporation Distortion compensating apparatus
JP3452865B2 (ja) 2000-04-27 2003-10-06 株式会社国際電気エンジニアリング 送信電力増幅装置
US6396347B1 (en) 2001-05-03 2002-05-28 International Business Machines Corporation Low-power, low-noise dual gain amplifier topology and method
JP3877937B2 (ja) 2000-05-18 2007-02-07 株式会社エヌ・ティ・ティ・ドコモ フィードフォワード増幅器
US6504428B2 (en) 2000-05-19 2003-01-07 Spectrian Corporation High linearity multicarrier RF amplifier
US6825719B1 (en) 2000-05-26 2004-11-30 Intel Corporation RF power amplifier and methods for improving the efficiency thereof
US6590449B2 (en) 2000-05-30 2003-07-08 Matsushita Electric Industrial Co., Ltd. Predistortion circuit, low-distortion power amplifier, and control methods therefor
SE516847C2 (sv) 2000-07-07 2002-03-12 Ericsson Telefon Ab L M Sammansatt förstärkare samt sändare som innefattar en sådan förstärkare
US7248841B2 (en) * 2000-06-13 2007-07-24 Agee Brian G Method and apparatus for optimization of wireless multipoint electromagnetic communication networks
IL153112A0 (en) 2000-06-13 2003-06-24 California Inst Of Techn Mode translating waveguide adapter for a quasi-optic grid array
US6735424B1 (en) 2000-06-14 2004-05-11 The Regents Of The University Of California S-band low-noise amplifier with self-adjusting bias for improved power consumption and dynamic range in a mobile environment
US6633200B2 (en) 2000-06-22 2003-10-14 Celiant Corporation Management of internal signal levels and control of the net gain for a LINC amplifier
US20020027958A1 (en) 2000-06-22 2002-03-07 Kolanek James C. Feedback channel signal recovery
US6342812B1 (en) 2000-06-27 2002-01-29 International Business Machines Corporation Power amplification system for low power radio frequency signals
US6512416B2 (en) 2000-07-03 2003-01-28 Broadcom Corporation Extended range variable gain amplifier
US6459337B1 (en) 2000-07-05 2002-10-01 Teledyne Technologies Incorporated System and method for noise and spurious suppression in power amplifier systems
JP4493809B2 (ja) 2000-07-10 2010-06-30 株式会社アドバンテスト 光特性測定装置、方法、記録媒体
JP2002033441A (ja) 2000-07-14 2002-01-31 Mitsubishi Electric Corp 半導体装置
US6351189B1 (en) 2000-07-31 2002-02-26 Nokia Networks Oy System and method for auto-bias of an amplifier
US6359508B1 (en) 2000-08-17 2002-03-19 Spectrian Corporation Distortion detection apparatus for controlling predistortion, carrier cancellation and feed-forward cancellation in linear RF power amplifiers
US6246599B1 (en) 2000-08-25 2001-06-12 Delta Electronics, Inc. Constant frequency resonant inverters with a pair of resonant inductors
US6622198B2 (en) 2000-08-31 2003-09-16 United Memories, Inc. Look-ahead, wrap-around first-in, first-out integrated (FIFO) circuit device architecture
US6751265B1 (en) 2000-09-13 2004-06-15 Tropian, Inc. Method and system of amplitude modulation using dual/split channel unequal amplification
US6522201B1 (en) 2000-09-28 2003-02-18 Eic Corporation RF amplifier having switched load impedance for back-off power efficiency
JP2002111415A (ja) 2000-09-29 2002-04-12 Hitachi Ltd 高周波電力増幅装置及び無線通信機
EP1195892B1 (en) 2000-10-06 2009-04-22 Alcatel Lucent Method and corresponding transmitter for predistorting a wideband radio signal to avoid clipping
US6606483B1 (en) 2000-10-10 2003-08-12 Motorola, Inc. Dual open and closed loop linear transmitter
EP1344315B1 (en) 2000-10-10 2008-03-26 California Institute Of Technology Class e/f switching power amplifiers
US6545535B2 (en) 2000-10-12 2003-04-08 Telefonaktiebolaget Lm Ericsson (Publ) Method and apparatus for reducing distortion
WO2002033820A1 (en) 2000-10-17 2002-04-25 Telefonaktiebolaget L M Ericsson (Publ) Communications systems
EP1199723B1 (en) 2000-10-18 2008-12-31 STMicroelectronics S.r.l. Interlaced memory device with random or sequential access
US7031382B2 (en) 2000-10-24 2006-04-18 Harris Corporation Non-linear equalizer system and method
US6975686B1 (en) 2000-10-31 2005-12-13 Telefonaktiebolaget L.M. Ericsson IQ modulation systems and methods that use separate phase and amplitude signal paths
US6785342B1 (en) 2000-11-06 2004-08-31 Wideband Semiconductors, Inc. Nonlinear pre-distortion modulator and long loop control
US6472937B1 (en) 2000-11-15 2002-10-29 Conexant Systems, Inc. Bias enhancement circuit for linear amplifiers
US6535060B2 (en) 2000-12-05 2003-03-18 Teledyne Technologies Incorporated System and method for noise and spurious supression in power amplifier systems
US6577199B2 (en) 2000-12-07 2003-06-10 Ericsson, Inc. Harmonic matching network for a saturated amplifier
US7027500B1 (en) * 2000-12-12 2006-04-11 Ati Research, Inc. Linear prediction based initialization of a single-axis blind equalizer for VSB signals
US6690233B2 (en) 2000-12-21 2004-02-10 Tropian, Inc. Efficient, precise RF modulation using multiple amplifier stages
KR100360273B1 (ko) 2000-12-28 2002-11-09 엘지전자 주식회사 디지탈 티브이 중계기의 선형보상 적응 등화기 및 그의제어방법
US6522194B1 (en) 2000-12-29 2003-02-18 Ericsson Inc. Envelope restoration scheme for linear high-efficiency power amplification
US6396341B1 (en) 2000-12-29 2002-05-28 Ericsson Inc. Class E Doherty amplifier topology for high efficiency signal transmitters
US6380802B1 (en) 2000-12-29 2002-04-30 Ericsson Inc. Transmitter using input modulation for envelope restoration scheme for linear high-efficiency power amplification
US6472934B1 (en) 2000-12-29 2002-10-29 Ericsson Inc. Triple class E Doherty amplifier topology for high efficiency signal transmitters
US6452446B1 (en) 2000-12-29 2002-09-17 Spectrian Corporation Closed loop active cancellation technique (ACT)-based RF power amplifier linearization architecture
US6622044B2 (en) 2001-01-04 2003-09-16 Cardiac Pacemakers Inc. System and method for removing narrowband noise
US6960956B2 (en) 2001-01-12 2005-11-01 Telefonatiebolaget L.M. Ericsson Telefonplan Apparatus and methods for monitoring and controlling power amplifier linearity using detected fundamental and harmonic components
DE10101911B4 (de) 2001-01-16 2004-03-18 Interessengemeinschaft für Rundfunkschutzrechte GmbH Schutzrechtsverwertung & Co. KG. Signalverarbeitung eines amplituden- und/oder phasenmodulierten Hochfrequenzsignals
US7075967B2 (en) 2001-01-19 2006-07-11 Raze Technologies, Inc. Wireless communication system using block filtering and fast equalization-demodulation and method of operation
US7333422B2 (en) 2003-09-12 2008-02-19 Zarbana Digital Fund Llc Optimized FFT/IFFT module
US6982593B2 (en) 2003-10-23 2006-01-03 Northrop Grumman Corporation Switching amplifier architecture
US6961368B2 (en) 2001-01-26 2005-11-01 Ericsson Inc. Adaptive antenna optimization network
US6587511B2 (en) 2001-01-26 2003-07-01 Intel Corporation Radio frequency transmitter and methods thereof
US6359513B1 (en) 2001-01-31 2002-03-19 U.S. Philips Corporation CMOS power amplifier with reduced harmonics and improved efficiency
GB0104535D0 (en) 2001-02-23 2001-04-11 Univ Bristol Digital cartesian loop
US20020146996A1 (en) 2001-03-06 2002-10-10 Bachman Thomas A. Scanning receiver for use in power amplifier linearization
US6829471B2 (en) 2001-03-07 2004-12-07 Andrew Corporation Digital baseband receiver in a multi-carrier power amplifier
US6538509B2 (en) 2001-03-09 2003-03-25 Dragonwave Inc. Linearizer for a power amplifier
US7551024B2 (en) 2001-03-13 2009-06-23 Marvell World Trade Ltd. Nested transimpedance amplifier
US20020130729A1 (en) 2001-03-14 2002-09-19 Lawrence Larson Circuit and method improving linearity, and reducing distortion, in microwave RF bandpass filters, especially superconducting filters
US20020130716A1 (en) 2001-03-14 2002-09-19 Lawrence Larson Linearization circuit and technique for a power combining network, or diplexer; especially as may use high temperature superconducting filters
JP4347531B2 (ja) 2001-03-19 2009-10-21 三星電子株式会社 非線形歪み補償方法及び非線形歪み補償回路
US6785521B2 (en) 2001-03-21 2004-08-31 Ericsson Inc. System and method for current-mode amplitude modulation
US6738432B2 (en) 2001-03-21 2004-05-18 Ericsson Inc. System and method for RF signal amplification
US20020159532A1 (en) 2001-03-23 2002-10-31 Icefyre Semiconductor Corporation Computational circuits and methods for signal deconstruction/reconstruction in wireless transceivers
US7127005B2 (en) 2001-03-23 2006-10-24 James Stuart Wight Computational circuits and methods for processing modulated signals having non-constant envelopes
TW503345B (en) 2001-03-26 2002-09-21 Mediatec Inc Power controller
CA2704041C (en) 2001-03-30 2013-09-03 M&Fc Holding, Llc Enhanced wireless packet data communication system, method, and apparatus applicable to both wide area networks and local area networks
US7010276B2 (en) 2001-04-11 2006-03-07 Tropian, Inc. Communications signal amplifiers having independent power control and amplitude modulation
JP3880329B2 (ja) * 2001-04-20 2007-02-14 株式会社日立国際電気 ループゲイン制御方法及び電力増幅回路
US6672167B2 (en) 2001-04-23 2004-01-06 The Aerospace Corporation Method and system for processing laser vibrometry data employing bayesian statistical processing techniques
US6915117B2 (en) 2001-05-03 2005-07-05 International Business Machines Corporation Multistage modulation architecture and method in a radio
FR2824437B1 (fr) 2001-05-04 2005-06-03 Eads Defence & Security Ntwk Generateur d'un signal radiofrequence module en phase ou frequence et en amplitude, et emetteur l'incorporant
US6850574B2 (en) 2001-05-14 2005-02-01 Motorola, Inc. Multiple bandwidth amplifier control systems for mobile stations and methods therefor
CA2386477C (en) 2001-05-15 2004-11-23 Research In Motion Limited Feedback compensation detector for a direct conversion transmitter
SE521268C2 (sv) 2001-05-18 2003-10-14 Ericsson Telefon Ab L M Sammansatt förstärkare med optimerad linjäritet och effektivitet
ATE378728T1 (de) 2001-05-18 2007-11-15 Alcatel Lucent Operationsverstärkeranordnung mit ruhestromeinstellungschaltung
US20020171485A1 (en) 2001-05-18 2002-11-21 Spectrian Corporation Digitally implemented predistorter control mechanism for linearizing high efficiency RF power amplifiers
US6924681B2 (en) 2001-05-23 2005-08-02 Texas Instruments Incorporated Efficient pulse amplitude modulation transmit modulation
JP3809777B2 (ja) 2001-05-30 2006-08-16 ソニー株式会社 電力増幅器
US6925171B2 (en) 2001-06-04 2005-08-02 Texas Instruments Incorporated Universal impedance matching network for the subscriber line integrated circuits
US7062237B2 (en) 2001-06-05 2006-06-13 Telefonaktiebolaget Lm Ericsson (Publ) Power amplifier (PA) with improved power regulation
US6864742B2 (en) 2001-06-08 2005-03-08 Northrop Grumman Corporation Application of the doherty amplifier as a predistortion circuit for linearizing microwave amplifiers
US20020186079A1 (en) 2001-06-08 2002-12-12 Kobayashi Kevin W. Asymmetrically biased high linearity balanced amplifier
US6469581B1 (en) 2001-06-08 2002-10-22 Trw Inc. HEMT-HBT doherty microwave amplifier
US6462617B1 (en) 2001-06-08 2002-10-08 Lucent Technologies Inc. Method and apparatus for calculating the predistortion function from a power amplifier model
GB2376584B (en) 2001-06-15 2005-02-16 Wireless Systems Int Ltd Signal correction techniques
US7409004B2 (en) 2001-06-19 2008-08-05 Matsushita Electric Industrial Co., Ltd. Hybrid polar modulator differential phase Cartesian feedback correction circuit for power amplifier linearization
EP1271792A1 (en) 2001-06-25 2003-01-02 Motorola, Inc. Low leakage local oscillator system
JP3599001B2 (ja) 2001-06-25 2004-12-08 ソニー株式会社 自動利得制御回路およびその方法、並びにそれらを用いた復調装置
US6583679B1 (en) 2001-06-28 2003-06-24 The Board Of Trustees Of The Leland Stanford Junior University High-efficiency high-power amplifier
US6496062B1 (en) 2001-07-13 2002-12-17 Lucent Technologies Inc. Predistortion system and method using a pilot signal
JP3947373B2 (ja) 2001-07-31 2007-07-18 株式会社ルネサステクノロジ 高周波電力増幅器
US6529773B1 (en) 2001-08-01 2003-03-04 The United States Of America As Represented By The Secretary Of The Air Force Communication and control by means of brainwave and other processes causing voltage changes that can be measured from the body
US6593806B1 (en) 2001-08-10 2003-07-15 Cirrus Logic, Inc. Circuits and methods for compensating switched mode amplifiers
US6564636B2 (en) 2001-08-22 2003-05-20 Honeywell International Inc. Wide band digital phase locked loop (PLL) with a half-frequency output
US6917246B2 (en) 2001-09-10 2005-07-12 Skyworks Solutions, Inc. Doherty bias circuit to dynamically compensate for process and environmental variations
US6690232B2 (en) 2001-09-27 2004-02-10 Kabushiki Kaisha Toshiba Variable gain amplifier
SE522119C2 (sv) 2001-10-15 2004-01-13 Ericsson Telefon Ab L M HF-effektförstärkning genom konvertering och tidsmultiplexering av basbandssignaler
CN100337397C (zh) 2001-10-16 2007-09-12 皇家飞利浦电子股份有限公司 Rf功率放大器电路
TW545806U (en) 2001-10-26 2003-08-01 Kye Systems Corp Wireless transmitting circuit capable of regulating RF amplifying power
EP1306978B1 (fr) 2001-10-26 2005-05-25 STMicroelectronics N.V. Récepteur à conversion directe pour un système de communication utilisant une modulation à enveloppe non constante
JP2003136764A (ja) 2001-11-06 2003-05-14 Canon Inc インクジェット記録装置における画像補正方法
US7068099B2 (en) 2001-11-07 2006-06-27 Koninklijke Philips Electronics, N.V. Power amplifier module with distortion compensation
US6587010B2 (en) 2001-11-27 2003-07-01 Motorola, Inc. Modulated radio frequency signal generation method and modulated signal source
SE521673C2 (sv) 2001-11-29 2003-11-25 Ericsson Telefon Ab L M Sammansatt förstärkare
US6653896B2 (en) 2001-11-30 2003-11-25 Tropian, Inc. Differential rf/microwave power amplifier using independent synchronized polar modulators
US6603352B2 (en) 2001-12-03 2003-08-05 Icefyre Semiconductor Corporation Switched-mode power amplifier integrally performing power combining
JP2003168931A (ja) 2001-12-04 2003-06-13 Nec Corp 歪補償回路
US6737914B2 (en) 2001-12-07 2004-05-18 4D Connect, Inc. Removing effects of gain and phase mismatch in a linear amplification with nonlinear components (LINC) system
JP3928421B2 (ja) 2001-12-13 2007-06-13 三菱電機株式会社 送信出力の制御装置及び制御方法
US6794934B2 (en) 2001-12-14 2004-09-21 Iterra Communications, Llc High gain wideband driver amplifier
US6597916B2 (en) 2001-12-26 2003-07-22 Siemens Information And Communication Networks, Inc. Hybrid architecture for supporting location determination in a wireless network
US20030123566A1 (en) 2001-12-27 2003-07-03 Jaime Hasson Transmitter having a sigma-delta modulator with a non-uniform polar quantizer and methods thereof
US20030125065A1 (en) 2001-12-27 2003-07-03 Ilan Barak Method and apparatus for generating an output signal
SE522479C2 (sv) 2002-01-16 2004-02-10 Ericsson Telefon Ab L M Sammansatt effektförstärkare
SE0200127D0 (en) 2002-01-16 2002-01-16 Ericsson Telefon Ab L M Composite amplifier
US6806789B2 (en) 2002-01-22 2004-10-19 M/A-Com Corporation Quadrature hybrid and improved vector modulator in a chip scale package using same
US7024169B2 (en) 2002-01-25 2006-04-04 Qualcomm Incorporated AMPS receiver using a zero-IF architecture
US6791417B2 (en) 2002-01-28 2004-09-14 Cree Microwave, Inc. N-way RF power amplifier circuit with increased back-off capability and power added efficiency using selected phase lengths and output impedances
KR100553252B1 (ko) 2002-02-01 2006-02-20 아바고테크놀로지스코리아 주식회사 휴대용 단말기의 전력 증폭 장치
US6566944B1 (en) 2002-02-21 2003-05-20 Ericsson Inc. Current modulator with dynamic amplifier impedance compensation
US6724252B2 (en) 2002-02-21 2004-04-20 Rf Micro Devices, Inc. Switched gain amplifier circuit
US7924937B2 (en) 2002-03-04 2011-04-12 Stmicroelectronics N.V. Resonant power converter for radio frequency transmission and method
US7042927B2 (en) 2002-03-11 2006-05-09 James Stuart Wight Pseudo-noise carrier suppression/image rejection up and down converters
US6741840B2 (en) 2002-03-13 2004-05-25 Motorola, Inc. RF transmitters with saturation detection and correction and methods therefor
US6794938B2 (en) 2002-03-19 2004-09-21 The University Of North Carolina At Charlotte Method and apparatus for cancellation of third order intermodulation distortion and other nonlinearities
US7953174B2 (en) 2002-03-20 2011-05-31 The Regents Of The University Of California Radio transmission frequency digital signal generation
US6646505B2 (en) 2002-03-26 2003-11-11 Motorola, Inc. Power amplifier array with same type predistortion amplifier
JP2003298361A (ja) 2002-03-29 2003-10-17 Shimada Phys & Chem Ind Co Ltd 電力増幅方法および電力増幅器
JP2003298357A (ja) 2002-03-29 2003-10-17 Shimada Phys & Chem Ind Co Ltd 電力増幅方法および電力増幅器
US6882829B2 (en) 2002-04-02 2005-04-19 Texas Instruments Incorporated Integrated circuit incorporating RF antenna switch and power amplifier
US6801086B1 (en) 2002-04-03 2004-10-05 Andrew Corporation Adaptive digital pre-distortion using amplifier model that incorporates frequency-dependent non-linearities
JP2003298368A (ja) 2002-04-03 2003-10-17 Mitsubishi Electric Corp 増幅回路
SE521746C2 (sv) 2002-04-05 2003-12-02 Ericsson Telefon Ab L M Multimoduleringssändare
JP4071526B2 (ja) 2002-04-10 2008-04-02 松下電器産業株式会社 非線形歪補償装置および送信装置
US6914487B1 (en) 2002-04-19 2005-07-05 National Semiconductor Corporation Method and system for providing power management in a radio frequency power amplifier using adaptive envelope tracking
US6720831B2 (en) 2002-04-26 2004-04-13 Rf Micro Devices, Inc. Power amplifier protection circuit
JP3823296B2 (ja) 2002-05-17 2006-09-20 富士通株式会社 歪み補償機能を有する無線機
US7194044B2 (en) 2002-05-22 2007-03-20 Alexander Neil Birkett Up/down conversion circuitry for radio transceiver
US20030220086A1 (en) 2002-05-23 2003-11-27 Icefyre Semiconductor Corporation Oscillator frequency offsets
JP4083167B2 (ja) 2002-05-31 2008-04-30 富士通株式会社 増幅装置
US7230996B2 (en) 2002-06-13 2007-06-12 Matsushita Electric Industrial Co., Ltd. Transmitting circuit device and wireless communications device
US6674326B1 (en) 2002-06-17 2004-01-06 The Boeing Company Digitally controllable nonlinear pre-equalizer
US6700453B2 (en) 2002-06-18 2004-03-02 Nokia Corporation Amplitude imbalance compensation of quadrature modulator
US7486894B2 (en) 2002-06-25 2009-02-03 Finisar Corporation Transceiver module and integrated circuit with dual eye openers
CN1152467C (zh) * 2002-06-27 2004-06-02 上海交通大学 焊接电源电网电压波动等分区间查表补偿方法
US6737916B2 (en) 2002-06-27 2004-05-18 Harris Corporation RF amplifier system having improved power supply
US6819720B1 (en) 2002-06-28 2004-11-16 Nortel Networks Limited Noise cancellation in a predistortion architecture
EP1381154A1 (en) 2002-07-09 2004-01-14 Lucent Technologies Inc. Power amplification by using different fixed power supply signals for the amplifier
US6806767B2 (en) 2002-07-09 2004-10-19 Anadigics, Inc. Power amplifier with load switching circuit
US7177418B2 (en) 2002-07-22 2007-02-13 Texas Instruments Incorporated Power efficient ADSL central office downstream class G power switch
US7330072B2 (en) 2002-08-01 2008-02-12 Telefonaktiebolaget Lm Ericsson (Publ) Circuit for power amplification
US7318189B2 (en) 2002-08-01 2008-01-08 Zarbana Digital Fund Llc Parallel convolutional encoder
US20040021517A1 (en) 2002-08-05 2004-02-05 Spectrian Corporation Power minimization, correlation-based closed loop for controlling predistorter and vector modulator feeding RF power amplifier
US6930547B2 (en) 2002-08-09 2005-08-16 Andrew Corporation Linearizing LINC amplifiers using pre-distortion
KR20050046731A (ko) 2002-08-19 2005-05-18 코닌클리즈케 필립스 일렉트로닉스 엔.브이. 고전력 도허티 증폭기 회로 및 고전력 도허티 증폭기 회로패키지
KR100484507B1 (ko) 2002-08-29 2005-04-20 학교법인 포항공과대학교 피드포워드 증폭기 및 피드포워드 증폭기의 성능 개선 방법
US9065537B2 (en) 2002-09-03 2015-06-23 Broadcom Corporation Method and system for calibrating a multi-mode, multi-standard transmitter and receiver
AU2002334520A1 (en) 2002-09-06 2004-03-29 Telefonaktiebolaget L M Ericsson (Publ) Composite power amplifier
US7123664B2 (en) 2002-09-17 2006-10-17 Nokia Corporation Multi-mode envelope restoration architecture for RF transmitters
GB0221593D0 (en) 2002-09-17 2002-10-23 Nokia Corp Envelope elimination and restoration linear amplifier
US6700441B1 (en) 2002-09-17 2004-03-02 Motorola, Inc. Method and apparatus for reduction of distortion in a feed forward amplifier
US7415112B2 (en) 2002-09-18 2008-08-19 Zarbana Digital Fund Llc Parallel scrambler/descrambler
US6900749B2 (en) 2002-09-20 2005-05-31 Sanyo Electric Co., Ltd. Analog-to-digital conversion circuit
US7173980B2 (en) 2002-09-20 2007-02-06 Ditrans Ip, Inc. Complex-IF digital receiver
JP4209652B2 (ja) 2002-09-24 2009-01-14 三菱電機株式会社 高周波電力増幅器
US6882217B1 (en) 2002-09-27 2005-04-19 3Com Corporation Cubic spline predistortion, algorithm and training, for a wireless LAN system
US7091777B2 (en) 2002-09-30 2006-08-15 Lucent Technologies Inc. Controller for an RF power amplifier
US6891432B2 (en) 2002-11-14 2005-05-10 Mia-Com, Inc. Apparatus, methods and articles of manufacture for electromagnetic processing
US6924699B2 (en) 2003-03-06 2005-08-02 M/A-Com, Inc. Apparatus, methods and articles of manufacture for digital modification in electromagnetic signal processing
US7043208B2 (en) 2002-10-15 2006-05-09 Motorola, Inc. Method and apparatus to reduce interference in a communication device
US6836183B2 (en) 2002-10-16 2004-12-28 Icefyre Semiconductor Corporation Chireix architecture using low impedance amplifiers
US7085327B2 (en) 2002-10-18 2006-08-01 Parker Kevin R Phasor fragmentation circuitry and method for processing modulated signals having non-constant envelopes
US6970039B2 (en) 2002-10-23 2005-11-29 Anadigics Efficiency enhancement for MMIC amplifiers
US7483711B2 (en) 2002-10-24 2009-01-27 Bbn Technologies Corp Spectrum-adaptive networking
US6834183B2 (en) 2002-11-04 2004-12-21 Motorola, Inc. VCO gain tracking for modulation gain setting calibration
US20040095192A1 (en) 2002-11-14 2004-05-20 Enver Krvavac Radio frequency power amplifier adaptive bias control circuit
KR100480496B1 (ko) 2002-11-18 2005-04-07 학교법인 포항공과대학교 도허티 증폭기를 이용한 신호 증폭 장치
US7260157B2 (en) 2002-11-21 2007-08-21 Sotoudeh Hamedi Hagh Phase shifted transmitter architecture for communication systems
ATE422108T1 (de) 2002-12-19 2009-02-15 Ericsson Telefon Ab L M Zusammengesetzte verstärkerstruktur
US6765519B2 (en) 2002-12-23 2004-07-20 Agilent Technologies, Inc. System and method for designing and using analog circuits operating in the modulation domain
US6831491B2 (en) 2002-12-23 2004-12-14 Agilent Technologies, Inc. Systems and methods for correcting phase locked loop tracking error using feed-forward phase modulation
US7212041B2 (en) 2002-12-23 2007-05-01 Intel Corporation Weighted multi-input variable gain amplifier
US20040131131A1 (en) 2003-01-03 2004-07-08 Peach Charles T. Double-sampled, sample-and-hold circuit with downconversion
JP2004221646A (ja) 2003-01-09 2004-08-05 Nec Corp ドハ−ティ増幅器
US6859098B2 (en) 2003-01-17 2005-02-22 M/A-Com, Inc. Apparatus, methods and articles of manufacture for control in an electromagnetic processor
US20040142667A1 (en) 2003-01-21 2004-07-22 Lochhead Donald Laird Method of correcting distortion in a power amplifier
KR100488431B1 (ko) 2003-01-24 2005-05-11 전자부품연구원 정 진폭 이진직교 변조 및 복조장치
KR100473811B1 (ko) 2003-02-21 2005-03-10 학교법인 포항공과대학교 링크 전력 송신기
JP4111003B2 (ja) 2003-02-27 2008-07-02 住友電気工業株式会社 Ｌｉｎｃ方式線形増幅器
US7185268B2 (en) 2003-02-28 2007-02-27 Maher Amer Memory system and method for use in trellis-based decoding
US6983024B2 (en) 2003-03-18 2006-01-03 Qualcomm Inc. Quadra-polar modulator
US7057461B1 (en) 2003-03-19 2006-06-06 Dynalinear Technologies, Inc. Heterostructure bipolar transistor power amplifier module with dynamic voltage supply for improved efficiency
JP4033794B2 (ja) 2003-03-24 2008-01-16 株式会社エヌ・ティ・ティ・ドコモ 高効率線形電力増幅器
US6922102B2 (en) 2003-03-28 2005-07-26 Andrew Corporation High efficiency amplifier
US7260368B1 (en) 2003-04-07 2007-08-21 Intel Corporation Linear amplification with non-linear components (LINC) modulator and method for generating out-phased signals for a LINC transmitter
EP1469594A1 (en) 2003-04-17 2004-10-20 Dialog Semiconductor GmbH Multi level Class-D amplifier by means of 2 physical layers
US7197284B2 (en) 2003-04-25 2007-03-27 Telefonaktiebolaget Lm Ericsson (Publ) Antenna switches including field effect transistors
WO2004100576A2 (en) 2003-05-02 2004-11-18 Hotspot Wireless Devices, Inc. Service advisor for detecting availability of a wireless communication service
US7038539B2 (en) 2003-05-06 2006-05-02 Powerwave Technologies, Inc. RF amplifier employing active load linearization
US20040224715A1 (en) 2003-05-07 2004-11-11 Rosenlof John R. System and method for correcting transmitter impairments
US6972622B2 (en) 2003-05-12 2005-12-06 Andrew Corporation Optimization of error loops in distributed power amplifiers
US7345531B2 (en) 2003-05-21 2008-03-18 Agere Systems Inc. Comparator circuit, related method of comparing a vector to comparison boundaries and transmitter employing the same
US6798377B1 (en) * 2003-05-31 2004-09-28 Trimble Navigation, Ltd. Adaptive threshold logic implementation for RAIM fault detection and exclusion function
KR20040104177A (ko) 2003-06-03 2004-12-10 삼성전기주식회사 시분할방식 전력증폭모듈
US6975177B2 (en) 2003-06-09 2005-12-13 Nokia Corporation Method and system for a generation of a two-level signal
EP1487100A1 (en) 2003-06-09 2004-12-15 STMicroelectronics S.r.l. Multi-channel power amplifier with channels independently self-configuring bridge or single-ended output, particulary for audio applications
US6917244B2 (en) 2003-06-10 2005-07-12 Nokia Corporation Power control for a switching mode power amplifier
US7043213B2 (en) 2003-06-24 2006-05-09 Northrop Grumman Corporation Multi-mode amplifier system
US6853244B2 (en) 2003-06-24 2005-02-08 Northrop Grumman Corproation Multi-mode multi-amplifier architecture
US6987417B2 (en) 2003-06-24 2006-01-17 Northrop Grumman Corpoation Polar and linear amplifier system
US7054597B2 (en) 2003-06-25 2006-05-30 Nokia Corporation Power control for a transmitter
US7336753B2 (en) 2003-06-26 2008-02-26 Marvell International Ltd. Transmitter
US7359692B2 (en) 2003-06-30 2008-04-15 Zarbana Digital Fund, Llc Method of and device for antennae diversity switching
US7158851B2 (en) 2003-06-30 2007-01-02 Tokyo Electron Limited Feedforward, feedback wafer to wafer control method for an etch process
US7342300B2 (en) 2003-06-30 2008-03-11 Zarbana Digital Fund Llc Integrated circuit incorporating wire bond inductance
US7409193B2 (en) 2003-07-03 2008-08-05 Zarbana Digital Fund Llc Predistortion circuit for a transmit system
US7026871B2 (en) 2003-07-03 2006-04-11 Icefyre Semiconductor, Inc. Adaptive predistortion for a transmit system
US7068101B2 (en) 2003-07-03 2006-06-27 Icefyre Semiconductor Corporation Adaptive predistortion for a transmit system
US6975167B2 (en) 2003-07-03 2005-12-13 Icefyre Semiconductor Corporation Adaptive predistortion for a transmit system with gain, phase and delay adjustments
US7453952B2 (en) 2003-07-03 2008-11-18 Saed Aryan Predistortion circuit for a transmit system
GB2403613B (en) 2003-07-04 2005-07-06 Motorola Inc Cartesian loop transmitter and method of adjusting an output level of such transmitter
US6879209B2 (en) 2003-07-08 2005-04-12 Icefyre Semiconductor Corp. Switched-mode power amplifier using lumped element impedance inverter for parallel combining
US6819176B1 (en) 2003-07-11 2004-11-16 Remec, Inc. High power, wide bandwidth operational amplifier
US6838942B1 (en) 2003-07-17 2005-01-04 Standard Microsystems Corporation Efficient class-G amplifier with wide output voltage swing
CN1225849C (zh) 2003-07-18 2005-11-02 大唐移动通信设备有限公司 一种对无线信号进行双向同步转发的方法及装置
US7042287B2 (en) 2003-07-23 2006-05-09 Northrop Grumman Corporation System and method for reducing dynamic range and improving linearity in an amplication system
US7103328B2 (en) 2003-07-24 2006-09-05 Sige Semiconductor Inc. Power transfer measurement circuit for wireless systems
US7280612B2 (en) 2003-07-25 2007-10-09 Zarbana Digital Fund Llc Digital branch calibrator for an RF transmitter
US20050024262A1 (en) 2003-08-01 2005-02-03 Ben Cantrell Simultaneous transmission of multiple signals through a common shared aperture
JP2005064658A (ja) 2003-08-08 2005-03-10 Mitsubishi Electric Corp 電力増幅器用過出力電圧保護回路
JP2005072031A (ja) 2003-08-22 2005-03-17 Renesas Technology Corp 高周波用半導体装置および通信用電子部品並びに無線通信システム
JP4202852B2 (ja) 2003-08-27 2008-12-24 株式会社ルネサステクノロジ 通信用電子部品および送受信切替え用半導体装置
US6873211B1 (en) 2003-09-10 2005-03-29 Skyworks Solutions, Inc. Multi-mode bias circuit for power amplifiers
US7567631B2 (en) 2003-09-12 2009-07-28 Neil Birkett Method for amplitude insensitive packet detection
US7433431B2 (en) 2003-09-12 2008-10-07 Zarbana Digital Fund, Llc Staggered AGC with digitally controlled VGA
US7362802B2 (en) 2003-09-12 2008-04-22 Zarbana Digital Fund Llc Frequency domain equalizer for wireless commuications system
GB2406008B (en) 2003-09-15 2008-04-02 Wolfson Ltd Class D amplifier
JP3910167B2 (ja) 2003-09-25 2007-04-25 松下電器産業株式会社 増幅回路
SE0302586D0 (sv) 2003-09-26 2003-09-26 Ericsson Telefon Ab L M Composite power amplifier
US20050111574A1 (en) 2003-09-30 2005-05-26 Jan-Erik Muller Transmission device with digital predistortion, and method for regulating predistortion in a transmission device
US7030714B2 (en) 2003-10-01 2006-04-18 Intel Corporation Method and apparatus to match output impedance of combined outphasing power amplifiers
EP1521359A1 (en) 2003-10-04 2005-04-06 Lucent Technologies Network Systems GmbH Amplifier assembly with an adjustable performance
US7023273B2 (en) 2003-10-06 2006-04-04 Andrew Corporation Architecture and implementation methods of digital predistortion circuitry
JP2005151543A (ja) 2003-10-20 2005-06-09 Matsushita Electric Ind Co Ltd 増幅回路
US7436894B2 (en) 2003-10-28 2008-10-14 Harris Corporation Method and apparatus for efficient bandwidth communication
KR20050041481A (ko) 2003-10-31 2005-05-04 삼성전자주식회사 아날로그 구적 변조 에러 보상 장치 및 방법
US6970040B1 (en) 2003-11-13 2005-11-29 Rf Micro Devices, Inc. Multi-mode/multi-band power amplifier
US7421037B2 (en) 2003-11-20 2008-09-02 Nokia Corporation Reconfigurable transmitter with direct digital to RF modulator
US7009447B2 (en) 2003-11-25 2006-03-07 Intel Corporation Outphasing modulator
US7071777B2 (en) 2003-12-02 2006-07-04 Motorola, Inc. Digital memory-based predistortion technique
US7356315B2 (en) 2003-12-17 2008-04-08 Intel Corporation Outphasing modulators and methods of outphasing modulation
US7064607B2 (en) 2003-12-29 2006-06-20 Texas Instruments Incorporated Bias system and method
US20050181746A1 (en) 2004-02-13 2005-08-18 Icefyre Semiconductor Corporation Methods and systems for signal amplification through envelope removal and restoration
EP1564897A1 (en) 2004-02-13 2005-08-17 Thomson Licensing S.A. Control of a power amplifier for reducing power consumption in a transceiver
US8077691B2 (en) 2004-03-05 2011-12-13 Qualcomm Incorporated Pilot transmission and channel estimation for MISO and MIMO receivers in a multi-antenna system
US20050201483A1 (en) 2004-03-12 2005-09-15 Edmund Coersmeier Error adjustment for multi-antenna transmitter
US20050227646A1 (en) 2004-03-18 2005-10-13 Ryo Yamazaki Detecting and maintaining linearity in a power amplifier system through comparing peak and RMS power levels
US8170081B2 (en) 2004-04-02 2012-05-01 Rearden, LLC. System and method for adjusting DIDO interference cancellation based on signal strength measurements
DE102004017528A1 (de) 2004-04-08 2005-11-03 Infineon Technologies Ag Sendeanordnung und Verfahren zum Betreiben eines Verstärkers in einer Sendeanordnung
US7440733B2 (en) 2004-04-09 2008-10-21 Powerwave Technologies, Inc. Constant gain nonlinear envelope tracking high efficiency linear amplifier
US7023272B2 (en) 2004-04-19 2006-04-04 Texas Instruments Incorporated Multi-band low noise amplifier system
US7068103B2 (en) 2004-04-30 2006-06-27 Texas Instruments Incorporated Operational transconductance amplifier input driver for class D audio amplifiers
KR101126401B1 (ko) 2004-05-11 2012-03-29 삼성전자주식회사 전력 증폭기에 디지털 전치 왜곡 장치 및 방법
KR100724934B1 (ko) 2004-05-11 2007-06-04 삼성전자주식회사 광대역 전력 증폭기를 위한 디지털 전치 왜곡 장치 및 방법
US7369822B2 (en) 2004-05-18 2008-05-06 Sige Semiconductor Inc. Segmented switching power amplifier
US7088970B2 (en) 2004-05-26 2006-08-08 Halliburton Energy Services, Inc. Amplification apparatus, systems, and methods
US7193459B1 (en) 2004-06-23 2007-03-20 Rf Micro Devices, Inc. Power amplifier control technique for enhanced efficiency
US7672648B1 (en) 2004-06-26 2010-03-02 Quintics Holdings System for linear amplitude modulation
US7358806B2 (en) 2004-07-08 2008-04-15 Amalfi Semiconductor, Inc. Method and apparatus for an improved power amplifier
US7242245B2 (en) 2004-07-08 2007-07-10 Amalfi Semiconductor, Inc. Method and apparatus for an improved power amplifier
WO2006020838A1 (en) 2004-08-12 2006-02-23 Shieldtech Systems, Llc Wireless data communication device
US7460612B2 (en) 2004-08-12 2008-12-02 Texas Instruments Incorporated Method and apparatus for a fully digital quadrature modulator
US8428650B2 (en) 2004-09-03 2013-04-23 Samsung Electronics Co., Ltd. Reconfigurable base station using mobile station RF ASIC
US7391317B2 (en) 2004-09-08 2008-06-24 Satius, Inc. Apparatus and method for transmitting digital data over various communication media
US7292189B2 (en) 2004-09-10 2007-11-06 Worcester Polytechnic Institute Methods and apparatus for high resolution positioning
US7668509B2 (en) 2004-09-24 2010-02-23 Sensor And Antenna Systems, Lansdale, Inc. Frequency selective leveling loop for multi-signal phased array transmitters
US20060088081A1 (en) 2004-10-22 2006-04-27 Time Domain Corporation Transmit-rake apparatus in communication systems and associated methods
US7327803B2 (en) 2004-10-22 2008-02-05 Parkervision, Inc. Systems and methods for vector power amplification
US7355470B2 (en) 2006-04-24 2008-04-08 Parkervision, Inc. Systems and methods of RF power transmission, modulation, and amplification, including embodiments for amplifier class transitioning
US7738853B2 (en) 2004-10-29 2010-06-15 Antone Wireless Corporation Low noise figure radiofrequency device
US7907671B2 (en) 2004-12-03 2011-03-15 Motorola Mobility, Inc. Method and system for scaling a multi-channel signal
US7084702B1 (en) 2005-01-19 2006-08-01 Micro Mobio Corp. Multi-band power amplifier module for wireless communication devices
US7308234B2 (en) 2005-01-19 2007-12-11 Northrop Grumman Corporation Feedforward spur cancellation approach using low IP amplifier
US7239115B2 (en) 2005-04-04 2007-07-03 Power-One, Inc. Digital pulse width modulation controller with preset filter coefficients
US7477711B2 (en) 2005-05-19 2009-01-13 Mks Instruments, Inc. Synchronous undersampling for high-frequency voltage and current measurements
JP4255929B2 (ja) 2005-05-20 2009-04-22 パナソニック株式会社 送信機
US20060264190A1 (en) 2005-05-23 2006-11-23 Boris Aleiner System and method for linearizing nonlinear power amplifiers
US7345534B2 (en) 2005-05-31 2008-03-18 M/A-Com Eurotec Bv Efficient power amplification system
WO2006135977A1 (en) 2005-06-24 2006-12-28 Carl Peter Renneberg A circuit and method for fitting the output of a sensor to a predetermined linear relationship
US7382182B2 (en) 2005-06-29 2008-06-03 Motorola, Inc. System for reducing calibration time of a power amplifier
JP2007019939A (ja) 2005-07-08 2007-01-25 Renesas Technology Corp 無線通信装置及びそれを用いた携帯電話端末
US7562001B2 (en) 2005-07-29 2009-07-14 International Business Machines Corporation Creating a behavioral model of a hardware device for use in a simulation environment
WO2007029429A1 (ja) 2005-09-06 2007-03-15 Mitsubishi Electric Corporation 漏洩信号相殺装置
US20070082630A1 (en) 2005-09-26 2007-04-12 Aridas Narendra K Radio frequency power amplifier circuit and method
US7778320B2 (en) 2005-10-03 2010-08-17 Clariphy Communications, Inc. Multi-channel equalization to compensate for impairments introduced by interleaved devices
US7911272B2 (en) 2007-06-19 2011-03-22 Parkervision, Inc. Systems and methods of RF power transmission, modulation, and amplification, including blended control embodiments
US8334722B2 (en) 2007-06-28 2012-12-18 Parkervision, Inc. Systems and methods of RF power transmission, modulation and amplification
KR100871858B1 (ko) 2005-11-16 2008-12-03 삼성전자주식회사 시분할복신 무선통신시스템의 전력증폭기 장치
US7602844B2 (en) 2005-12-05 2009-10-13 National Taiwan University On-line step-size calculation using signal power estimation and tone grouping of the frequency-domain equalizer for DMT-based transceiver
US20070155344A1 (en) 2005-12-29 2007-07-05 Motorola, Inc. Wireless multimode co-band receiver device and method employing receiver bypass control
US8195103B2 (en) 2006-02-15 2012-06-05 Texas Instruments Incorporated Linearization of a transmit amplifier
EP1821445A1 (en) * 2006-02-16 2007-08-22 Siemens S.p.A. Method to improve the channel estimate in broadband simo/mimo cellular radio networks during abrupt interference variations
US7345629B2 (en) 2006-02-21 2008-03-18 Northrop Grumman Corporation Wideband active phased array antenna system
US8099061B2 (en) 2006-03-15 2012-01-17 Cisco Technology, Inc. TDD receiver protection
US7509102B2 (en) 2006-04-07 2009-03-24 Broadcom Corporation DAC based switching power amplifier
US7459893B2 (en) 2006-04-20 2008-12-02 Mark E Jacobs Optimal feedback control of switch-mode power converters
US8031804B2 (en) 2006-04-24 2011-10-04 Parkervision, Inc. Systems and methods of RF tower transmission, modulation, and amplification, including embodiments for compensating for waveform distortion
US7937106B2 (en) 2006-04-24 2011-05-03 ParkerVision, Inc, Systems and methods of RF power transmission, modulation, and amplification, including architectural embodiments of same
WO2007149346A2 (en) 2006-06-16 2007-12-27 Pulsewave Rf, Inc. Radio frequency power amplifier and method using a controlled supply
US7817962B2 (en) 2006-06-29 2010-10-19 Broadcom Corporation Polar transmitter amplifier with variable output power
US7724839B2 (en) 2006-07-21 2010-05-25 Mediatek Inc. Multilevel LINC transmitter
WO2008026326A1 (fr) 2006-08-30 2008-03-06 Hitachi Communication Technologies, Ltd. Modulateur optique
US8321489B2 (en) 2006-09-15 2012-11-27 National Semiconductor Corporation Software reconfigurable digital phase lock loop architecture
KR20080034251A (ko) 2006-10-16 2008-04-21 삼성전자주식회사 시분할 복신 무선통신 시스템에서 수신회로를 보호하기위한 장치 및 방법
EP2097818A4 (en) 2006-11-22 2014-01-29 Parkervision Inc MULTIDIMENSIONAL ERROR CORRECTION FOR COMMUNICATION SYSTEMS
US7620129B2 (en) 2007-01-16 2009-11-17 Parkervision, Inc. RF power transmission, modulation, and amplification, including embodiments for generating vector modulation control signals
US7873852B2 (en) * 2007-02-01 2011-01-18 Zetta Research, Llc Logical battery partitions configured by user interface
KR101164835B1 (ko) 2007-03-02 2012-07-11 퀄컴 인코포레이티드 적응형 안테나 어레이를 이용하는 적응형 온-채널 중계기에서 필터 뱅크의 이용
US7974373B2 (en) 2007-03-13 2011-07-05 Pine Valley Investments, Inc. Method and architecture for digital pulse shaping and rate conversion
US8428002B2 (en) 2007-04-18 2013-04-23 Broadcom Corporation Cooperative transceiving between wireless interface devices of a host device
WO2008144017A1 (en) 2007-05-18 2008-11-27 Parkervision, Inc. Systems and methods of rf power transmission, modulation, and amplification
US20080301473A1 (en) * 2007-05-29 2008-12-04 International Business Machines Corporation Method and system for hypervisor based power management
US7865149B2 (en) 2007-06-01 2011-01-04 Broadcom Corporation On chip MOS transmit / receive switch
JP4850786B2 (ja) 2007-06-15 2012-01-11 ルネサスエレクトロニクス株式会社 送受信機
US20090004981A1 (en) 2007-06-27 2009-01-01 Texas Instruments Incorporated High efficiency digital transmitter incorporating switching power supply and linear power amplifier
US7809927B2 (en) 2007-09-11 2010-10-05 Texas Instruments Incorporated Computation parallelization in software reconfigurable all digital phase lock loop
US8193761B1 (en) * 2007-11-08 2012-06-05 Honeywell International, Inc. Hybrid power source
US8718582B2 (en) 2008-02-08 2014-05-06 Qualcomm Incorporated Multi-mode power amplifiers
US8073078B2 (en) 2008-02-08 2011-12-06 Freescale Semiconductor, Inc. Split channel receiver with very low second order intermodulation
US8279913B2 (en) 2008-03-19 2012-10-02 Intel Mobile Communications GmbH Configurable transceiver
US8134411B2 (en) 2008-04-17 2012-03-13 Texas Instruments Incorporated Computation spreading utilizing dithering for spur reduction in a digital phase lock loop
US8629650B2 (en) 2008-05-13 2014-01-14 Qualcomm Incorporated Wireless power transfer using multiple transmit antennas
TWI396033B (zh) 2008-11-07 2013-05-11 Univ Nat Chiao Tung Multi - frequency electrical signal of the photoelectric device
US8195118B2 (en) 2008-07-15 2012-06-05 Linear Signal, Inc. Apparatus, system, and method for integrated phase shifting and amplitude control of phased array signals
US7999749B2 (en) 2008-10-23 2011-08-16 Sony Ericsson Mobile Communications Ab Antenna assembly
US8423092B2 (en) * 2008-12-12 2013-04-16 Qualcomm Incorporated Power management in a mobile device
US8433745B2 (en) 2008-12-19 2013-04-30 Scintera Networks, Inc. Scalable cost function generator and method thereof
US8824604B2 (en) * 2008-12-30 2014-09-02 QUACLCOMM Incorporated Method and apparatus for symbol decoding using tree pruning based sphere search
US8223885B2 (en) 2009-02-19 2012-07-17 Research In Motion Limited Mobile wireless communications device with separate In-phase (I) and Quadrature (Q) phase power amplification and power amplifier pre-distortion and IQ balance compensation
US8489041B2 (en) 2009-06-08 2013-07-16 Anthony Teillet Multi-element amplitude and phase compensated antenna array with adaptive pre-distortion for wireless network
US8355466B2 (en) 2009-09-25 2013-01-15 General Dynamics C4 Systems, Inc. Cancelling non-linear power amplifier induced distortion from a received signal by moving incorrectly estimated constellation points
US8369807B2 (en) 2010-06-03 2013-02-05 Broadcom Corporation Polar-based RF receiver
US9154166B2 (en) 2010-06-03 2015-10-06 Broadcom Corporation Front-end module network
US9853478B2 (en) 2010-07-28 2017-12-26 Qualcomm Incorporated Low power detection of wireless power devices
US8427257B2 (en) 2011-02-11 2013-04-23 M/A-Com Technology Solutions Holdings, Inc. Broadside-coupled transformers with improved bandwidth
JP5668979B2 (ja) 2011-03-10 2015-02-12 ソニー株式会社 受信装置、受信方法、およびプログラム
US8913698B2 (en) 2011-04-11 2014-12-16 Softwaveradio, Inc. Programmable, frequency agile direct conversion digital receiver with high speed oversampling
US9479203B2 (en) 2011-04-14 2016-10-25 Mediatek Inc. Transceiver capable of IQ mismatch compensation on the fly and method thereof
EP2715867A4 (en) 2011-06-02 2014-12-17 Parkervision Inc ANTENNA CONTROL
US8768419B2 (en) * 2012-01-26 2014-07-01 Verizon Patent And Licensing Inc. Mobile battery partitioning system and method
WO2013172896A2 (en) 2012-02-17 2013-11-21 California Institute Of Technology Dynamic polarization modulation and control
EP2706684B1 (en) * 2012-09-10 2018-11-07 MStar Semiconductor, Inc Apparatus for MIMO channel performance prediction

Patent Citations (2)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US8013675B2 (en) * 2007-06-19 2011-09-06 Parkervision, Inc. Combiner-less multiple input single output (MISO) amplification with blended control
US8461924B2 (en) * 2007-06-19 2013-06-11 Parkervision, Inc. Systems and methods of RF power transmission, modulation, and amplification, including embodiments for controlling a transimpedance node

Cited By (11)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US9729378B1 (en) * 2015-04-13 2017-08-08 The United States Of America As Represented By The Secretary Of The Navy Receiver architecture for constant envelope OFDM
US20180034416A1 (en) * 2016-07-29 2018-02-01 Qualcomm Incorporated Adjusting envelope tracking power supply
US10128798B2 (en) * 2016-07-29 2018-11-13 Qualcomm Incorporated Adjusting envelope tracking power supply
US20220076150A1 (en) * 2018-04-16 2022-03-10 Nec Corporation Method, apparatus and system for estimating causality among observed variables
CN110248046A (zh) * 2018-08-16 2019-09-17 浙江大华技术股份有限公司 一种确定复合视频信号中视频有效区域的方法及装置
WO2020041135A1 (en) * 2018-08-21 2020-02-27 Bae Systems Information And Electronic Systems Integration Inc. Variational design of companders for papr reduction in ofdm systems
US10594529B1 (en) * 2018-08-21 2020-03-17 Bae Systems Information And Electronic Systems Integration Inc. Variational design of companders for PAPR reduction in OFDM systems
CN110069732A (zh) * 2019-03-29 2019-07-30 腾讯科技（深圳）有限公司 一种信息展示的方法、装置及设备
CN110276122A (zh) * 2019-06-19 2019-09-24 复旦大学 适用于多比特数字正交发射机的数字预失真前端电路
CN110750288A (zh) * 2019-10-23 2020-02-04 广州华多网络科技有限公司 原生工程配置方法、装置、电子设备及存储介质
CN114646441A (zh) * 2022-03-16 2022-06-21 北京卫星环境工程研究所 基于界面力等效的三轴六自由度振动试验条件设计方法

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