CN101720526B - 可减少反馈信号的功率因数校正控制器 - Google Patents
可减少反馈信号的功率因数校正控制器 Download PDFInfo
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Abstract
一个功率控制系统(900)包括一个具有功率因数校正功能的反馈回路(PFC)和输出电压控制器(904)和一个开关功率变换器(906)。该开关功率变换器(906)包括一个可向输出电容器(106)供应电荷的电感器(110)和一个控制电感器电流升高时间的开关(908)。PFC与输出电压控制器(904)向开关(908)提供控制信号(CS1),控制PFC并调节开关功率变换器(906)的输出电压Vc(t)。在控制信号的但各周期内,PFC与输出电压控制器(904)利用接收自开关功率变换器(906)的单个反馈信号获得开关功率变换器(906)的线输入电压Vx(t)和输出电压Vc(t)。
Description
优先权要求和相关专利申请
本专利申请要求依据35U.S.C.§119(e)和37C.F.R.§1.78享有2007年5月2日递交名为“功率因数校正(PFC)控制器装置和方法”的60/915,547号美国临时专利申请的权益,其通过引用被整体纳入本专利申请。
技术领域
本发明一般涉及信号处理领域,具体指功率因数校正及可降低反馈率的功率因数校正器。
背景技术
功率校正系统可提供可校正及可调控输出电压,该输出电压也广泛应用与可调控电压装置。图1示出了一个功率控制系统100,它包括有一个开关功率转换器102。该开关功率转换器102可进行功率因数校正,并提供恒定复合电压功率至负载112。电压输出装置101向全波段二极管桥式103提供交流电流(AC)输入电压Vin(t)。譬如,电压源101是公共电源,而AC交流电源线电压Vin(t)是60Hz/110V电源线电压,在欧洲是50Hz/220V线电源电压。整流器103将输入电压Vin(t)进行整流后,向开关功率变换器提供一个经过整流的随时间变化的直流输入电压Vx(t)。
开关功率转换器102的开关108调节经整流的时变输入电压Vx(t)通过电感器110到电容器106的能量传递。当开关108导通时,即接通“ON”时,电感器电流iL骤然上升。当开关108断开即显示“OFF”时电感器电流下降,并向电容器106提供电流iL以对其充电。一般将电感器电流iL骤然下降的时间周期称为“电感器回扫时间”。在至少一个实施例中,开关功率转换器102以间断电流的模式工作,即,电感器电流iL的上升时间加电感器回扫时间少于开关108接通的时间。开关108打开时电容器106向负荷电源112提供储存的能量。电容器106足够大,可使PFC和输出电压控制器114(将在以下详细讨论)所建立起的输出电压Vc(t)较好地保持恒定。输出电压Vc(t)在负载恒定条件下基本保持恒定。但是当负载条件改变时,输出电压Vc(t)将变化。PFC及输出电压控制器114可对Vc(t)变化作出反应,尽快调整控制信号CS0以维持线输出电压基本恒定。输出电压控制器114包括一个小电容器115,以滤掉初级供电电压Vx(t)中的任何高频信号。
功率控制系统100还包括一个控制开关108的PFC及输出电压控制器114,以便控制功率因数校正并调节开关功率变换器102的输出电压。功率因数校正技术的目的是使开关功率转换器102对电压源101体现电抗性。于是,PFC和输出电压控制器114试图控制电感器电流iL,使得平均电感器电流iL线性地且直接地与直流输入电压Vx(t)相关。《功率因数校正整流器的快速电压环路的补偿器设计与稳定性评价》(Compensator Design andStability Assessment for Fast Voltage Loops of Power FactorCorrection Rectifiers),IEEE Transactions on Power Electronics(IEEE电力电子学汇刊),第22卷,第5期,2007年9月,第1719-1729页。(在本文内称为),该文描述了一个PFC和输出电压控制器114的例子。PFC和输出电压控制器114提供一个脉冲宽度调制的(PWM)控制信号CS0,以控制开关108的导通性。在至少一个实施例中,开关108为一个场效应管(FET),而控制信号CS0是开关108的门电压。控制信号CS0的脉冲宽度值和占空比取决于两个反馈信号,即直流输入电压Vx(t)和电容电压/输出电压Vc(t)。
开关功率变换器114通过一个宽带电流回路116和一个低电压回路118接收两种反馈信号直流输入电压Vx(t)和输出电压Vc(t)。电流回路116以频率fc运转,该频率允许PFC与输出电压控制器114对直流输入电压Vx(t)作出回应调整,导致电感器电流iL随着该直流输入电压而变化,以便完成功率因数校正。电流回路频率一般被设定为介于20kHz与150kHz之间的一个值。电压回路118以一个较低的频率fv运行,典型的值为10-20Hz。电容器电压Vc(t)包括一个纹波电流元件,其频率为输入电压Vin(t)频率的两倍,如120Hz。因此,通过以10-20Hz频率运行,电压回路118可发挥一个滤流装置功能,对纹波电流元件的纹波电流进行过滤。
PFC与输出电压控制器114常常作为一个集成电路(IC)使用。因此,PFC与输出电压控制器114包括两个不同的管脚分别与电流反馈回路118连接。管脚是相对较贵的IC元件。此外,电压回路118中诸如高电压电阻等高电压元件也会增加PFC与输出电压控制器114的成本。
发明内容
在本发明的一个实例中,PFC控制器为一个控制功率因数校正并调节开关功率变换器输出电压的元件。开关功率变换器包括一个与直流输入电压节点偶联的电感器和一个与该电感器偶联的开关。PFC控制器包括一个接收来自开关功率变换器反馈信号的输入装置。PFC控制器的配置使之能够:
(a)至少确定:(i)直流输入电压和(ii)反馈信号开关功率变换器的输出电压其中一个。
(b)向开关提供控制信号,因此在开关的各个时期开关功率变换器可对控制信号作出回应,开关闭合时在首次间隔期电感器电流上升,开关断开时电感器回扫时间间隔期电感器电流下降。
(c1)这时,如果直流输入电压由(a)得到确定,那么PFC控制器又可被用来确定开关功率变换器的输出电压,其根据为该直流输入电压、电感器回扫时间和首次间隔;
(c2)此时,如果开关功率变换器输出电压由(a)得到确定,那么PFC控制器可被用来确定开关功率变换器的输入电压,其根据为该输出电压,电感器回扫时间和首次间隔。
在本发明的另一实例中,PFC控制器被用作控制功率因数校正,并调节开关功率变换器的输出电压。开关功率变换器包括一个与直流输入电压节点偶联的电感器和一恶搞与该电感器偶联的开关。PFC控制器包括一个可接收来自开关功率变换器反馈信号的输入装置。配备PFC控制器用于确定直流输入电压,并向开关提供控制信号,这样,在开关的各个时期开关功率变换器就可对控制信号作出回应,开关闭合时在首次间隔期电感器电流上升,开关断开时电感器回扫时间间隔电感器电流下降。该控制器还可用于确定启动功率输出电压,其根据为直流输入电压、电感器回扫时间和首次间隔期。
在本发明的另一实例中,PFC控制器用于控制功率因数校正并调节开关功率变换器的输出电压。开关功率变换器包括一个与直流输入电压偶联的电感器和一个与该电感器偶联的开关。PFC控制器包括一个可接收来自开关功率变换器的反馈信号输入装置。PFC控制器用于确定来自反馈信号的开关功率变换器输出电压,并向开关提供控制信号,这样,在开关的各个时期,开关功率变换器就可对控制信号作出回应,开关闭合时首次间隔期电感器电流上升,开关断开时电感器回扫时间间隔电感器电流下降。PFC控制器还可用于确定直流输入电压,其根据为输出电压、电感器回扫时间间隔和首次间隔期。
在本发明的有一个实例中,一种控制功率因数校正并调节开关功率变换器输出电压的方法包括接收来自开关功率变换器的反馈信号,这里指的开关功率变换器包括一个与直流输入电压节点偶联的电感器和一个与该电感器留恋的开关。该方法还包括:
(a)至少确定:(i)直流输入电压和(ii)反馈信号开关功率变换器的输出电压其中一个;
(b)向开关提供控制信号,这样,在开关的各个时期开关功率变换器就可对控制信号作出回应,开关闭合时首次间隔期电感器电流上升,开关断开时电感器回扫时间间隔期电感器电流下降;
(c1)这时,如果直流输入电压由(a)得到确定,可根据该输入电压、电感器回扫时间间隔期和首次间隔期确定开关功率变换器的输出电压;
(c2)此时,入股开关功率变换器的输出电压由(a)得到确定,可根据该输出电压、电感器回扫时间间隔期和首次间隔期确定直流输入电压。
在本发明另一实例中,控制功率因数校正并调节开关功率变换器输出电压的方法包括接收来自开关功率变换器的反馈信号和确定一个直流输入电压,此处开关功率变换器包括一个与直流输入电压节点偶联的传感器和一个该电感器偶联的开关。还包括向开关提供控制信号,这样,在开关的各个时期开关功率变换器就会对控制信号作出回应,开关闭合时首次间隔期电感器电流上升,开关断开时电感器回扫时间间隔期电感器电流下降。该方法还包括根据直流输入电压、电感器回扫时间间隔期和首次间隔期确定开关功率变换器的输出电压。
在本发明的另一实例中,一种控制功率因数校正并调节开关功率变换器输出电压地方法包括接收来自开关功率变换器的反馈信号和确定反馈信号开关功率变换器的输出电压,这里提到的开关功率变换器包括一个与直流输入电压偶联的电感器和与该电感器偶联的开关。该方法还包括向开关提供控制信号,这样,在开关的各个时期开关功率变换器就会对控制信号作出回应,开关闭合时首次间隔期电感器电流上升,开关闭合时电感器回扫时间间隔期电感器电流下降。该方法还包括根据输出电压、电感器回扫时间间隔期和首次间隔期确定直流输入电压。
附图说明
参考附图可以更好地理解本发明,还可以使熟悉该技术领域者明白本发明的各种目的、特征和优点。在这些附图中使用相同参考号代表相同或相似要素。
图1(已有技术)描绘的是一个功率控制系统的功率因数校正与输出电压调节。
图1A描绘一个功率控制系统确定直流输入电压与输出电压的单个反馈信号。
图2描绘图1A功率控制系统的一个实例。
图3描绘功率因数校正及输出电压调节过程。
图4和图5描绘传感器/转换器。
图6描绘电压反馈信号、电感器电流iL及其相对应的开关功率变换器开关状态的时间域图。
图7描绘电感器回扫时间间隔确定模块。
图8描绘PFC与输出电压控制器。
图9描绘图1A功率控制系统的一个实例。
图10描绘开关功率变换器开关的反馈信号及其相应的理论门电压与实际门电压及实际电流图解。
图11描绘电感器回扫时间间隔确定模块。
图12描绘图1A功率控制系统的一个实例。
图13描绘一个电感器回扫时间间隔确定模块。
图14描绘包括一个富余性与可靠性模块的图1A功率控制系统的一个实例。
具体实施方式
功率控制系统包括一个开关功率变换器和一个功率因数校正(PFC)与输出电压控制器。该开关功率变换器包括一个向输出电容器提供电荷的电感器和一个控制电感器电流上升时间与能量向输出电容器转移的开关。在不止一个实例中,PFC与输出电压控制器向控制功率因数校正并调节开关功率变换器输出电压的开关提供控制信号。在不止一个实例中,在单个控制信号周期内,PFC与输出电压控制根据从开关功率变换器接收的单个反馈信号确定开关功率变换器的直流输入电压与输出电压。在不止一个实例中,PFC与输出电压控制器可从反馈信号确定电感器回扫时间。PFC与输出电压控制器可确定直流输入电压或者输出电压,其中无论哪个都不能利用以确定电压、电感器回扫时间和受控制信号控制开关闭合(处于“ON”状态)时间经反馈信号确定。PFC与输出电压控制器利用直流输入电压和输出电压产生控制信号,以此完成功率因数校正和输出电压调节。
在不止一个实例中,PFC与输出电压控制器输入终端的总体数目减少或者额外的管脚具有其他用途。例如,通过仅运用一种反馈信号获得开关功率变换器的直流输入电压和输出电压,集成电路(IC)开关功率变换器的管脚数可减少一个。此外,在不止一个实例中,通过减少PFC与输出电压控制器接收的反馈信号数目,在不止一个实例中可减少诸如电压和/或电流递减电路等外周元件数目。减少套脚和相关重要性偏低的组件能降低成本。在不止一个实例中,PFC与输出电压控制器接收一个或更多用于保证可靠性与富余性的反馈信号,而未减少管脚数目。
图1A描绘功率控制系统150一个反馈信号VS(t)实例。功率控制系统150包括一个开关功率变换器154,可向电荷负载器112提供经功率因数校正并调节的输出电压Vc(t)。PFC与输出电压控制器156向开关功率变换器154控制考官108提供一个控制信号CS1,以此控制功率因数校正和电压调节。确定控制信号CS1时,PFC与输出电压控制器156接收来自开关功率变换器154的反馈信号VS(t)。PFC与输出电压控制器154可根据单个反馈信号CS1确定控制信号VS(t)。相应地,在不止一个实例中,PFC与输出电压控制器可利用诸如集成电路管脚等极少几个输入终端及极少外围元件。功率控制系统150可通过数字和/或类似硬件或者软硬件联用运行。在不止一个实例中,PFC与输出电压控制器156为一个可编程PFC与输出电压控制器,由Cirrus Logic代理公司代理发明人John L.Melanson申请的,代理人档案编号1759-CA,题为“可编程功率控制系统”(Programmable PowerControl System)的美国专利申请材料中也有同样的描述说明。
图2描绘了带有一个PFC与输出电压控制器202的功率控制器,该控制器包括一个来自开关节点的反馈信号VS(t),根据该反馈信号可确定直流输入电压Vx(t)和输出电压Vc(t)。功率控制系统200和PFC与输出电压控制器202各自代表功率控制系统150与PFC及输出电压控制器156的一个实例。开关功率变换器201向电荷负载器112提供一个劲功率因数校正和调节的输出电压Vc(t)。整个输出电容器106的输出电压Vc(t)相当于负荷电压VL(t)。功率控制系统200包括一个反馈路径203,可向PFC与输出电压控制器202提供来自开关节点的反馈信号VS(t)。在不止一个实例中,向PFC与输出电压控制器202提供的反馈信号VS(t)是一个电压VS(t)或者电流,二者由在开关节点处感应而产生。反馈路径203包括开关节点、PFC与输出电压控制器202和开关108。PFC与输出电压控制器202可由单个反馈信号VS(t)确定直流输入电压Vx(t)和输出电压Vc(t)。PFC与输出电压控制器202利用已确定的开关功率变换器201直流输入电压Vx(t)和输出电压Vc(t)产生控制信号CS1。
图3描绘了一个典型的PFC与输出电压调节过程300。在不止一个实例中,PFC与输出电压控制器202遵照PFC与输出电压调节程序300运行,确定启动功率控制器102的直流输入电压Vx(t)与输出电压Vc(t),控制功率因数校正,调节启动功率控制器102的输出电压Vc(t)。在运行程序302中,PFC与输出电压控制器202接收来自开关功率变换器201的反馈信号VS(t)。在不止一个实例中,反馈信号VS(t)是这样的一种信号,PFC与输出电压控制器202可从该信号获得直流输入电压Vx(t)和输出电Vc(t),并确定电感器回扫时间间隔T2在不止一个实例中,反馈信号VS(t)(参见图2)为开关功率变换器201的开关节点处感应的电压VS(t)。PFC与输出电压调解程序300可在硬件或软件中实施完成,并由PFC与输出电压控制器202的一个处理器来执行。
在不止一个实例中,反馈信号VS(t)的最大额定电压由电荷负载器112的电压需求决定。例如,如果电荷负载器112为一个12V的发动机,反馈信号VS(t)的最大额定电压将为12V;如果电荷负载器112为发光双电极固定装置,该反馈信号VS(t)的最大额定电压可能为400V,等等。开关节点反馈信号VS(t)的确切最大额定电压典型的特征为,其随着由于系统阻抗引起的输出电压Vc(t)变化(如通过双电极111的电压下降)而变化。
在不止一个实例中,PFC与输出电压控制器202的类似电路元件用于产生控制信号CS1,而且该反馈信号VS(t)可直接被该类似电路元件接收。在不止一个实例中,PFC与输出电压控制器202作为一个集成电路(IC)运行,而PFC与输出电压控制器202的输入信号即为电压或电流,其大小受到限制,以防破坏PFC与输出电压控制器202。因此,在不止一个实例中,功率控制系统200包括一个传感器/转换器206,可将反馈信号VS(t)转换为最大值,如+1V,可由经集成电路实施完成的PFC与输出电压控制器202直接接收。传感器/转换器206可通过PFC与输出电压控制器202或者PFC与输出电压控制器202的全部或部分集成元件单独运行。
图4与图5分别描绘了典型的传感器/转换器。传感器/转换器402代表传感器/转换器206的一个实例。传感器/转换器402包括一个电压分离器/类数字系统。传感器/转换器402包括一个具有阻抗的电压分离器R0/R1,可使信号VS(t)递减至可被PFC与输出电压控制器202利用的水平。R0与R1的电阻值取决于与R0和R1偶联的电压以及经PFC与输出电压控制器202接收的输入电压与电流水平。在一个实例中,电阻R0为399欧姆,电阻R1为1欧姆。传感器/转换器402还包括一个类数字(A/D)转换器404,可将经过电阻R1转换为典型数字反馈信号V(n),供数字系统406处理,此处“n”表示一个特定的例子。在不止一个实例中,数字系统406代表PFC与输出电压控制器202的处理加工、驱动器及其它功能。
图5描绘了电流输出装置及A/D传感器/转换器502。传感器/转换器502代表传感器/转换器206的另一个实例。传感器/转换器502包括一个电流输出装置504,可向A/D转换器404提供一个电流输出信号i(t).电流输出信号i(t)值与反馈信号VS(t)保持一致。传感器/转换器502还包括A/D 404,可将输出信号i(t)转换为典型的数字反馈信号V(n),供数字系统406处理加工。
图6描绘了(i)来自开关节点(图602)的电压反馈信号VS(t),(ii)电感器电流iL(图604)和(iii)开关108(图606)相应状态的时间域图表。参照图2与图6发现,开关108的状态受控制信号CS1控制。控制信号CS1频率等于1/TTx,此处TTx为第x帧控制信号CS1的周期,“x”指整数标号。控制信号CS1的频率fCS1受PFC与输出电压控制器202控制。在不止一个实例中,PFC与输出电压控制器202不断变换着频率fCS1t,以提供调节输出电压Vc(t),且为了诸如减少电磁干扰波发射应按照预定的宽谱策略变换频率。控制信号CS1的频率极有可能在20kHZ与150kHz之间,这两个值分别可避免成音频率和无效频率出现。
在传感器电流iL上升时间间隔T1,即开关108处于“ON”状态时,传感器电流iL升高,而开关节点处感应电压VS(t)则降低至大约0电压VS(t)降至“大约”0是因为,较小非理想电压可出现下降,例如当开关108闭合或经过双电极111的电压下时就会出现电压下降,正因为如此,通过这种非理想电压下降可将反馈信号VS(t)的电压可与例如直流输入电压Vx(t)或者输出电压Vc(t)加以区分。然而,除非有其他含义,确定或获得开关功率变换器201的直流输入电压Vx(t)和/或输出电压VS(t)的应用目的包括确定或获得开关功率变换器201大约或按比例放大的直流输入电压和/或大约或按比例放大的输出电压。
在电感器回扫时间间隔T2期间,当开关处于“OFF”状态时,双电极111导电,电感器电流iL下降为0安培,电压VS(t)升至Vc(t)。电感器电流iL降至0安培后,双电极二极管111体制停止导电,经过电感器110的电压下降大约为0,反馈信号电压VS(t)等于Vx(t)。当电感器电流iL达到0时,诸如经过电感器110的寄生电容等寄生阻抗开关节点处的608纹波电流衰减。
参照图2、图3与图6可看出,PFC与输出电压控制器202根据输出电压调节调节程序300对反馈信号VS(t)进行加工处理。运行程序304可确定来自反馈信号VS(t)的线输入电压Vx(t)或输出电压Vc(t)。运行程序304是否能确定线输入电压Vx(t)或输出电压Vc(t)可在设计中做出选择。一般来说,输出电压Vc(t)确定后就可设定开关功率变换器201的所有功率输出值,即控制信号CS1的最小与最大脉宽。然而,在最大输出功率(即控制信号CS1的最大脉宽)设定过程中,纹波电流608会对线输入电压Vx(t)的确定带来麻烦,这是因为纹波电流608在控制信号进入下一循环控制信号CS1之前不会下降。如果线输入电压Vx(t)由运行程序304确定,PFC与输出电压控制器202则按运行程序308来确定该输出电压Vx(t)。如果输出电压Vc(t)由运行程序304确定,PFC与输出电压控制器202则按运行程序308确定该线输入电压。开关“ON”状态持续时间在控制信号CS1的各周期内经由PFC与输出电压控制器202设定,因此,电感器电流iL升高时间间隔T1属于已知值。
通过在电感器回扫时间间隔T2内感应反馈信号VS(t),PFC与输出电压控制器202可确定来自反馈信号VS(t)的输出电压Vc(t)。在不止一个实例中,电感器回扫时间间隔T2未知。相应地,开关功率变换器201在时间间隔T1结束之后等待足够时间,以便使任意瞬时信号消失,然后确定来自反馈信号VS(t)的输出电压Vc(t)。正如前文所述,反馈信号VS(t)可以代表一个放大的输出电压Vc(t)。然而,在不止一个实例中,当利用输出电压Vc(t)确定运行程序308中的线输入电压Vx(t)时,放大比例由开关转换器201决定。相应地,除非有其他含义,确定输出电压Vc(t)包括确定一个放大的或者大约的输出电压Vc(t)。
通过在电感器回扫时间间隔T2内感应反馈信号Vx(t),PFC与输出电压控制器202确定来自反馈信号VS(t)的输出电压VS(t)。相应地,在不止一个实例中,确定来自反馈信号VS(t)(见下文说明)的线输入电压Vx(t)时,运行程序306可在运行程序304之前确定电感器回扫时间间隔T2。直接从反馈信号VS(t)确定线输入电压Vx(t),在电感器回扫时间间隔T2之后及可确定线输入电压Vx(t)的控制信号CS1进入下一个周期的T1时间间隔开始之前的任意时间,在控制信号CS1一个周期内均可感应到反馈信号VS(t)。在不止一个实例中,在波纹电流信号608消失后可感应到反馈信号VS(t),以便获得线输入电压Vx(t)的更准确的值,并在控制信号CS1开始下一个周期之前有足够的条件使开关功率变换器201执行运行程序308、310和312。在不止一个实例中,开关功率变换器201通过平均反馈信号Vx(t)在电感器回扫时间间隔T2之后即刻确定线输入电压VS(t)。对于输出电压Vc(t),在不止一个实例中提到,当利用线输入电压Vx(t)确定输出电压Vc(t)时,放大倍数可由开关功率变换器201确定。相应地,除非有其他含义,确定输出电压Vx(t)包括确定一个放大的或大约的线输入电压Vx(t)。
运行程序306可确定电感器回扫时间间隔T2。图7描绘了电感器回扫时间间隔确定模块的一个实例702(这里指的是“回扫时间模块”)。电感器回扫时间间隔T2可经由回扫时间模块702确定。例如,通过在时间间隔T2开始时感应反馈信号VS(t),检测在时间tx电压由VS(t)向Vx(t)的传输,并确定电感器电流iL上升时间间隔T1结束与电压在时间tx由VS(t)向Vx(t)传输之间的时间(此处“x”表示控制信号CS1某一特定周期的标记)。回扫时间模块702可分别由PFC与输出电压控制器202或PFC与输出电压控制器202全部或部分集成电路元件实施完成。
回扫时间模块702包括一个可将反馈信号VS(t)和预定的参照电压VREF0进行比较的比较模块704,并提供一个输出信号VSENSE_0。当电压VS(t)低于参照电压VREF0时,输出信号VSENSE_0由一个逻辑状态向另一个(在本例中为从HIGH到LOW)转换。因此,反馈信号VS(t)和VREF0的对比允许回扫时间模块702感应反馈信号VS(t)由输出电压Vc(t)水平向线输入电压Vx(t)水平转换。参照电压VREF0设定在Vc(t)与Vx(t)之间。在不止一个实例中,在电感器回扫时间间隔T2内参照电压VREF0设定在反馈信号VS(t)中任意瞬时电压以下,且足够高,以至于比较模块输出信号VSENSE_0值在电感器回扫时间间隔T2结束时迅速转换。在不止一个实例中,比较模块704分别由集成PFC与输出电压控制器202独立实施。在另一实例中,比较模块704与集成PFC与输出电压控制器202整合(即“单片”),传感器/转换器206将反馈信号VS(t)转化为PFC与输出电压控制器202可处理的水平。在本实例中,参照电压VREF0也被放大至与反馈信号VS(t)相同的水平。
比较模块704比较输出信号VSENSE_0由HIGH逻辑状态向LOW状态转换指的是电感器回扫时间间隔T2的结束。回扫时间模块702包括一个计数器/处理器706,在电感器回扫时间间隔T2开始时开始计数。电感器回扫时间间隔T2的开始是已知的,因为这个开始恰巧在时间间隔T1结束相吻合。PFC与输出电压控制器202可确定时间间隔的结束,当控制信号CS1使开关108变为“OFF”状态时就表示该时间间隔结束。在不止一个实例中,PFC与输出电压控制器202在电感器回扫时间间隔T2开始时产生一个启动信号,重新设定并启动计数器/处理器706。计数器/处理器706以时钟频率fCLK运行。该频率fCLK与设计选择相关。频率fCLK的较高值增加已确定的电感器回扫时间间隔T2的准确性。在不止一个实例中,频率fCLK为10MHz。计数器/处理器706在时间间隔T1结束时以频率fCLK开始计数,当信号VSENSE_0由HIGH状态转换为LOW状态时计数终止。被时钟频率fCLK分开的计数值表示回扫时间间隔T2。
运行程序308可确定任一种电压,即线输入电压Vx(t)或输出电压Vc(t),在运行程序304中利用已确定电压、电感器电流iL升高时间间隔T1和已确定电感器回扫时间间隔T2未确定这种电压。如果运行程序304可确定线输入电压Vx(t),在不止一个实例中,运行程序308根据方程[1]可确定输出电压Vc(t):
方程[1].
其中,T1为电感器电流iL升高时间间隔,T2为电感器回扫时间间隔。方程[1]中电压Vx与电压Vc分别表示实际的、大约的、或抽样线输入电压Vx(t)和输出电压Vc(t)。
如果运行程序304可确定输出电压Vc(t),在不止一个实例中,运行程序308可根据方程[2]确定线输入电压Vx(t)。
方程[2]
其中T1为电感器电流iL升高时间间隔,T2为电感器回扫时间间隔。方程[2]中电压Vx与电压Vc分别表示实际的、大约的、放大的或抽样线输入电压Vx(t)和输出电压Vc(t)。
运行程序310可确定开关控制信号CS1的脉宽PW和占空率D。PFC与输出电压控制器202控制控制信号CS1的脉宽PW与周期T。功率控制系统200表示一个非线性过程,这是因为开关功率变换器201输送的功率与线输入电压Vx(t)有关。PFC和输出电压控制器202控制着开关功率转换器201的过程,以将预期的能量转送给电容器106。所需的能量取决于负载112的电压和电流要求。控制信号CS1的占空比设定后可维持理想的输出电压VC(t)和负载电压VL(t),并且在不止一个实例中,控制信号CS1的占空率D等于[VL(t)/(VC(t)+VL(t))]。当线输入电压Vx(t)升高时,能量传递在这一时段也增大。
为了调节传输的能量并将功率因数保持在接近1,PFC和输出电压控制器202改变着控制信号CS1的周期,使输入电流iL能够追踪到输入电压Vx(t)中的变化,并使输出电压VC(t)保持恒定。因此,当线输入电压Vx(t)升高时,PFC与输出电压控制器202延长控制信号CS1周期TT(见图6),而当线输入Vx(t)下降,PFC与输出电压控制器202缩短控制信号CS1的周期TT(见图6)。同时,控制信号CS1的脉冲宽度PW经过调节,以保持恒定的占空比D,并使电容器电压VC(t)保持恒定。在至少一个实施例中,PFC和输出电压控制器202以远高于输入电压Vx(t)的频率更新控制信号CS1。线输入电压Vx(t)的频率一般为50至60Hz。例如,控制信号CS1的频率1/T介于20kHz与150kHz之间。等于或高于20kHz的频率避免了音频干扰,等于或低于150kHz的频率避免了有较大影响的开关无效性,同时又能保持良好的功率因数校正,比如0.9和1之间的功率因数校正,且电容器电压VC(t)保持近似的恒定值。
图8描绘了PFC与输出电压控制器800,这表示的是PFC与输出电压控制器202的一个实例。PFC和输出电压控制器800产生控制信号CS1,以控制开关功率变换器201的非线性能量转移过程。。非线性Δ-∑模块802接收能量输入信号E(n),表示在控制信号CS1的下一个周期实现了理想的能量转移,可维持输出电压Vc(t)的理想值。非线性Δ-∑调节器802处理该输入信号E(n),并产生量化器输出信号QPW。非线性Δ-∑模块802的非线性反馈模型803代表开关功率变换器201的一个非线性能量转移过程,因此数字转换器输出信号QPW表示控制信号CS1的脉宽,该脉宽符合电容器106能量转移要求,以维持一个大体恒定的输出电压Vc(t)。PFC与输出电压控制器800与非线性反馈模型803的典型实例在发明人John L.Melanson与2007年9月30日提交的题为“利用带有非线性处理模型的非线性Δ-∑模块的控制系统”(Control System Using A Nonlinear Delta-Sigma ModulatorWith Nonlinear Process Modeling)的美国专利申请号11/865,032文件(Melanson I)中有详细的说明,并在Cirrus Logic公司代理发明人John L.Melanson申请提交的题为“利用带有非线性功率转换过程模型的非线性Δ-∑模块的控制系统”(Power ControlSystem Using a Nonlinear Delta-Sigma Modulator With NonlinearPower Conversion Process Modeling)美国专利申请文件和律师诉讼事件编号1745-CA(Mealson II)文件中亦有详细描述。Melanson I与Melanson II以全文引用方式并入本文。
在至少一个实施例中,输入信号Vx(t)是整流电压,因此随着时间变化而上升和下降。PFC与输出电压控制器800用于跟踪线输入信号Vx(t),并调整控制信号CS1周期,随着线输入信号Vx(t)增强而延长,随着线输入信号Vx(t)减弱而缩短。为了确定控制信号CS1的各个周期,PFC与输出电压控制器800包括一个输入信号评估器805,用以评估控制信号CS1各循环线输入电压Vx(t)的瞬时值,并产生一个评估电压值EV(n)。在不止一个实例中,输入信号评估器805执行运行程序304从反馈信号Vx(t)确定线输入电压VS(t)。PFC与输出电压控制器800包括一个传统Δ-∑模块804,可处理评估电压值EV(n),并将该评估电压值EV(n)转换为一个数字转换器输出信号QT。量化器输出信号QT代表一个控制信号CS1周期,用于输入电压Vx(t)的估算值。常规Δ-∑调节器的典型设计和运行请参见Schreier和Temes的著作“了解Δ-∑数据转换器”(Understanding Delta-Sigma Data Converters),IEEE Press,2005,ISBN 0-471-46585-2。
PFC与输出电压控制器800包括一个脉宽模块806,可将数字转换器输出信号QPW(n)转换为一个脉宽和一个数字转换器输出信号QT(n),从而进入控制信号CS1的一个周期中,此处n可为表示相关变量的一个特定瞬时值的编号。为了进行此转换,在至少一个实施例中,脉冲宽度调节器806包括一个计数器。量化器输出信号QPW(n)显示脉冲控制信号CS1的计数,而量化器输出信号QT(n)显示控制信号CS1的周期计数。脉冲宽度调节器806将量化器输出信号QPW(n)和量化器输出信号QT(n)的计数转换为控制信号CS1的相应脉冲宽度和周期。在至少一个实例中,PFC与输出电压控制器800利用数字技术实现运行。在其他实例中,PFC与输出电压控制器800可利用类似或混合数字和类比技术实现运行。
参照图2和图8可看出,当非线性Δ-∑模块802用作PFC与输出电压控制器部件(例如PFC与输出电压控制器800(图8))时,为了维持功率因数校正功能,能量输入信号E(n)与(1-(Vx(t)/VC(t))·K呈一定比例。”K”为常量,指的是负载112要求的功率,由一个按比例集成代偿电路(未显示)确定,该代偿电路将输出电压Vc(t)作为参照电压,确定一个同时具有整合输出电压误差和按比例分配输出电压误差两种功能的反馈信号。比例积分补偿器的一个例子请参见Alexander 的著作“功率因数校正整流器的快速电压环路的补偿器设计与稳定性评价”(Compensator Design and Stability Assessment for Fast Voltage Loopsof Power Factor Correction Rectifiers),IEEE Transactions on PowerElectronics(IEEE电力电子学汇刊),第22卷,第5册,2007年9月,以及Erickson和的著作,“功率电子基础”(Fundamentals of Power Electronics),第2版,Boston,MA:Kluwer,2000年中均对按比例集成代偿电路作了说明,以上两者均以全文引用方式并入本文。在不止一个实例中,能量输入信号E(n)受到限制,以确保开关功率变换器201以不连续电流方式运行。
运行程序312向开关功率变换器201提供开关控制信号CS1。运行程序312后,PFC与输出电压调节程序300返回运行程序302,进入下一个控制喜好CS1周期。
运行程序304与306可利用各种系统和处理程序进行确定。图9描绘了功率控制系统900,该系统为功率控制系统150的一个实例。功率控制系统包括PFC与输出电压控制器904,PFC与输出电压控制器904根据PFC与输出电压调节程序300运行。然而,运行程序304与306特定执行有别于结合了功率控制系统200的PFC与输出电压调解程序300。开关908是一个FET,同时控制信号CS1应用于一个门开关908。可对开关108的门电压Vg实施监测,这一电压也可用于确定电感器回扫时间间隔T2。
在不止一个实例中,运行程序306通过监测开关908的门电压特征来确定电感器回扫时间间隔T2的终止,并检测电感器回扫时间间隔T2的终止。图10表1000描绘了反馈信号VS(t)与相应的理论与实际门电压Vg和实际电流ig。参照图9和10可看出,在理想状态下,控制信号CS1各周期内门电流Vg具有一个逻辑为HIGH的脉冲1002,对应于开关908的开启ON时间,否则就是逻辑LOW。同样,在理想状态下,控制信号CS1各周期内的实际电流具有一个简短脉冲1004为开关908带上门电电荷,还具有一个简短脉冲1006,为开关908去门电荷。理想条件下,脉冲1004和1006是门电流ig的唯一脉冲。但是,开关108具有一个寄生栅极-漏极电容914。如果在电感器回扫时间间隔T2终止时开关节点的反馈信号VS(t)由电压Vc(t)转化为电压Vx(t),寄生电容导致产生瞬时电压信号1008和瞬时电流信号1010。(图10中瞬时信号不必要进行拉取放大,瞬时信号的放大倍数会随着用于实施开关功率变换器906功能的电子元件不同而变化。)在不止一个实例中,瞬时电流信号、瞬时电压信号或者二者均可通过PFC与输出电压控制器904的实例分别检测到。因此,通过确定电感器回扫时间间隔的起始,并通过确定信号消逝时间直至瞬时信号被检测到,运行程序306中的PFC与电压输出控制器904可确定电感器回扫时间间隔T2。
在不止一个实例中,结合功率控制系统900的运行程序304时,线输入电压Vx(t)可直接通过检测来自节点916处反馈信号的线输入电压Vx(t)得到确定,或者如前所述,由反馈信号VS(t)进行确定。在另一实例中,为了执行运行程序结合功率控制系统900的运行程序304,输出电压Vc(t)可通过直接检测来自节点918处反馈信号的输出电压Vc(t)得到确定,或者如前所述,由反馈信号VS(t)进行确定。来自开关节点的虚线和节点916与节点918表示,通过利用任意一个反馈信号,即Vx(t)、Vc(t)或VS(t),运行程序304可得到执行。输出电压Vc(t)可用各种方法进行检测,其中包括在美国专利申请文件“运用数字FIR过滤输出电压抽样技术的功率因数校正”(Power Factor Correction Controller WithDigital FIR Filter Output Voltage Sampling)(发明人为John L.Melanson,由Cirrus Logic公司代理)和律师诉讼事件编号1760-CA(Melanson III)以及美国专利申请文件“功率供应Dc电压抵消检测器”(Power Supply Dc Voltage Offset Detector)(发明人为John L.Melanson,由Cirrus Logic公司代理)与律师诉讼事件编号1761-CA(Melanson IV)的典型实例中描述的方法。Melanson III与Melanson IV因全文引用方式并入本文。
运行程序308-312由上述PFC与输出电压控制器904结合PFC与输出电压控制器202共同执行。
图11描绘了使用瞬时信号1008确定电感器回扫时间间隔T2的一个典型电感器回扫时间间隔确定模块(回扫时间模块)1100。在不止一个实例中,PFC与输出电压控制器906包括回扫时间模块1100。回扫时间模块1100可检测门电压Vg,比较模块1102可比较门电压与参照电压VREF1。参照电压VREF1要经过预先确定,并设定在电感器回扫时间间隔T2内稳定状态门电压Vg和瞬时信号1008最小电压之间。在不止一个实例中,VREF1被设为-0.5V。当反馈信号VS(t)由电压Vc(t)向电压Vx(t)转换时,瞬时信号1008的门电Vg降至参照电压VREF1以下,比较模块1102的输出信号VSENSE_1由HIGH逻辑状态变为LOW逻辑状态。
比较模块1102的比较模块输出信号VSENSE_1由HIGH逻辑状态向LOW状态的转换表示电感器回扫时间间隔T2的终止。回扫时间模块1100包括计数器/处理器706,可在电感器回扫时间间隔T2起始时开始计数。如前所述,电感器回扫时间间隔T2是已知的,因为T2起始正好与电感器电流iL升高时间间隔T1吻合。PFC与输出电压控制器904确定时间间隔T1的终止,当控制信号CS1导致开关908处于关闭(OFF)状态时这一事件就会发生。在不止一个实例中,PFC与输出电压控制器906在电感器回扫时间间隔T2起始时产生一个“START”信号,以重新设定计数器/处理器706。利用输入信号VSENSE_1,如前所述,计数器/处理器706确定电感器回扫时间间隔T2。
图12描绘了一个功率控制系统1200,该系统为功率控制系统150的一个实例。功率控制系统1200包括PFC与输出电压控制器1204,PFC与输出电压控制器1204按照PFC与输出电压调节程序300实施运行。然而,运行程序304与306的执行有别于结合功率控制系统200的PFC与输出电压调节程序300的应用过程。
参照图3和图12可看出,运行程序306利用与电感器110磁偶联的复卷绕组1206感应电感器电压VL(t)。电感器110表示一个初级绕组,电感器电压VP(t)直接与电感器电流iL成一定比例。因此,电感器回扫时间间隔T2可直接通过感应电感器电压VP(t)得到确定,电压与电感器电流iL下降相对应。在不止一个实例中,PFC与输出电压孔子和气1204包括两个终端,可接收由复卷绕组1206产生的反馈信号VS(t)。
电感器110诱导复卷绕组1206中的复卷电压VS(t),该电压与电感器电压VP(t)的倒数成一定比例关系。复卷电压VS(t)表示传给PFC与输出电压控制器1204的反馈信号。该反馈信号VS(t)与电感器电压相关,相关方程见方程[3]:
方程[3].
其中,“nS”为复卷绕组1206的绕卷数,“nP”为电感器110中的绕卷数,且k=nS/nP。“nP”的值由电感器110选择设定。“nS”值可被设定以便PFC与输出电压控制器1204可不经任何转换直接接收反馈信号VS(t)。
参照图3、图6、图11、图12和图13可看出,在时间间隔T1内开关108导电时,反馈信号VS(t)等于-Vx(t)·k。因此,运行程序304可通过在时间间隔T1内感应反馈信号Vx(t)和经-k将反馈信号加以分类来确定线输入电压VS(t)。在电感器回扫时间间隔T2期间,按照方程[4]反馈信号VS(t)与输出电压Vc(t)和线输入电压成相关关系。
VS(t)=(Vc(t)-Vx(t))·k 方程[4]
图13描绘了执行运行程序306的电感器回扫间隔确定模块。回扫时间模块1300接收反馈信号VS(t),比较模块1302比较反馈信号与参照电压VREF2。并确定时间间隔T1终止和反馈信号VS(t)转换至VREF2以下之间的时间间隔,这里参照电压VREF2设定在(Vc(t)-Vx(t))·k和-Vx(t)之间。
运行程序308-312由PFC与输出电压控制器1204结合PFC与输出电压控制器202共同执行。
图14描绘了功率控制系统1400,该系统为图1A所示功率控制系统的一个实例。功率控制系统1400包括一个富余性与可靠性模块1406,属于PFC与输出电压控制器1404的元件,可向功率控制系统1400提供可靠性和/或富余性。在不止一个实例中,功率控制系统1400可采用与功率控制系统200、900、1100相同的方式发挥功能,并得以实施,只是功率控制系统1400包含更多反馈信号,以提供备份和可靠性。在不止一个实例中,功率控制系统1400可提供一个诸如400V的高输出电压Vc(t)。高输出电压可引起特定安全性问题和硬件运行失败问题。因此,除了按照前述任一实例确定输出电压Vc(t)与线输入电压Vx(t)之外,利用如前所述的复卷绕组还可使用附加的反馈信号,例如直接感应节点1408的线输入电压Vx(t)、节点1410的输出电压Vc(t)、来自开关节点的线输入电压Vx(t)和/或输出电压Vc(t)和/或经过电感器110的电感器电压等。
额外感应的富余参数可利用期望的传感器/换算器206经过换算得出,可靠性与富余性模块1406可将线输入电压Vx(t)和输出电压Vc(t)的值比作由PFC与输出电压调节程序300确定的相应值。可靠性与富余性模块1406包括逻辑状态,如如果实际值与预定的极限值不一致,那么就会关闭该功率控制系统1400。在不止一个实例中,如果PFC与输出电压调节程序300无法确定输出电压VC(t)或线输入电压Vx(t),可靠性与富余性模块1406可将额外感应的值用作替代值,这样就可提供富余性。
因此,在控制信号的单个周期内,运用接收自开关功率变换器的单个反馈信号,PFC与输出电压控制器获得开关功率变换器的线输入电压和输出电压。
尽管已经对本发明作了详细描述,但应明白,在不偏离所附权利要求中定义的本发明之范围和精神情况下仍可以进行多种变化、替代和更改。
Claims (20)
1.一种功率因数校正(PFC)控制器,控制功率因数校正并调节开关功率变换器输出电压,其中,开关功率变换器包括一个与线输入电压节点偶联的电感器和一个与该电感器偶联的开关,PFC控制器包括:
一个输入设备,接收来自开关功率变换器的反馈信号;
其PFC控制器被配置为使所述开关功率变换器能够在不连续导通模式下工作,并且被进一步配置为以下步骤:
(a)根据反馈信号确定以下中至少一个:(i)一个线输入电压和(ii)开关功率变换器的一个输出电压;
(b)向开关提供控制信号,因此,在开关的各周期开关功率变换器就会对控制信号作出回应,当开关闭合时,首次间隔电感器电流升高,开关断开时,电感器回扫时间间隔电感器电流下降;
(c)在开关门感应一个或多个电压瞬时信号,以确定电感器回扫时间间隔;
(d1)其中,如果输入电压在步骤(a)中得到确定,PFC控制器再用于确定开关功率变换器的输出电压,其依据为线输入电压、电感器回扫时间间隔和首次时间间隔;和
(d2)其中,如果开关功率变换器的输出电压在步骤(a)中得到确定,PFC控制器还用于确定线输入电压,其依据为输出电压、电感器回扫时间间隔和首次时间间隔。
2.根据权利要求1所述的PFC控制器,其中用于确定开关功率变换器输出电压的PFC控制器按照以下方程运行:
其中,T1为首次时间间隔,T2为电感器回扫时间间隔,Vc为输出电压,VX为线输入电压。
3.根据权利要求1所述的PFC控制器,其中此PFC控制器按照以下方程用于确定开关功率变换器的线输入电压:
其中,T1为首次时间间隔,T2为电感器回扫时间间隔,Vc为输出电压,VX线输入电压。
4.根据权利要求1所述的PFC控制器,其中开关包括一个电场效应转换器,而且该PFC与输出电压控制器用于在开关门感应电压瞬时信号,以确定电感器回扫时间间隔T2。
5.根据权利要求1所述的PFC控制器,其中在PFC控制器和开关功率变换器运行期间,传感器感应经过电感器的线输入电压。
6.根据权利要求5所述的PFC控制器,其中传感器还包括一个复卷绕组,与该电感器磁偶联,感应经过电感器的电压。
7.根据权利要求1所述的PFC控制器,其中此PFC控制器还用于根据线输入电压、传感器回扫时间间隔和首次时间间隔确定开关功率变换器的输出电压,还根据输出电压、电感器回扫时间间隔和首次时间间隔确定线输入电压。
8.根据权利要求1所述的PFC控制器,其中此PFC控制器包括一个集成电路,该电路具有大量连接点,提供外部链接,其中PFC控制器的连接点包括一个元件组中一个元件的连接点:来自反馈信号的开关功率变换器的(i)线输入电压和(ii)输出电压。
9.一个PFC控制器,其控制功率因数校正并调节开关功率变换器的输出电压,其中,开关功率变换器包括一个与线输入电压节点偶联的电感器和一个与该电感器偶联的开关,PFC控制器包括:
一个输入设备,接收来自开关空滤交换器的反馈信号;
其PFC控制器被配置为使所述开关功率变换器能够在不连续导通模式下工作,并且被进一步配置为:
确定一个线输入电压;
向开关提供控制信号,因此,在开关的各个周期,开关功率变换器就会对控制信号作出回一个,当开关闭合时首次时间间隔电感器电流升高,开关断开时电感器回扫时间间隔电感器电流下降;
在开关门感应一个或多个电压瞬时信号,以确定电感器回扫时间间隔,以及
确定开关功率变换器的输出电压,其依据为线输入电压、电感器回扫时间间隔和首次时间间隔。
10.一个PFC控制器,其控制功率因数校正并调节开关功率变换器的输出电压,其中,开关功率变换器包括一个与线输入电压节点偶联的电感器和一个与该电感器偶联的开关,PFC控制器包括:
一个输入设备,接收来自开关功率交换器的反馈信号;
其中PFC控制器被配置为使所述开关功率变换器能够在不连续导通模式下工作,并且被进一步配置为:
确定来一个自反馈信号的开关功率变换器线输入电压;
向开关提供控制信号,因此,在开关的各个周期,开关功率变换器就会对控制信号作出回一个,当开关闭合时首次时间间隔电感器电流升高,开关断开时电感器回扫时间间隔电感器电流下降;
在开关门感应一个或多个电压瞬时信号,以确定电感器回扫时间间隔,以及
确定开关功率变换器的输出电压,其依据为线输入电压、电感器回扫时间间隔和首次时间间隔。
11.一种控制功率因数并调节开关功率变换器输出电压的方法,其中开关功率变换器包括一个与线输入电压节点偶联的电感器和一个与该电感器偶联的开关,本方法包括以下步骤:
接收来自开关功率变换器的反馈信号;
(a)至少确定:来自反馈信号的开关功率变换器(i)一个支流输入电压和(ii)输出电压二者至少一个参数;
(b)向开关提供控制信号,因此,在开关的各周期开关功率变换器就会对控制信号作出回应,当开关闭合时,首次间隔电感器电流升高,开关断开时,电感器回扫时间间隔电感器电流下降;
(c)在开关门感应一个或多个电压瞬时信号,以确定电感器回扫时间间隔,
(d1)其中,如果输入电压在步骤(a)中得到确定,PFC控制器再用于确定开关功率变换器的输出电压,其依据为线输入电压、电感器回扫时间间隔和首次时间间隔;
(d2)其中,如果开关功率变换器的输出电压在步骤(a)中得到确定,PFC控制器还用于确定线输入电压,其依据为输出电压、电感器回扫时间间隔和首次时间间隔;以及
使所述开关功率变换器能够在不连续导通模式下工作。
12.权利要求11所述的方法还包括:
按照下列方程确定开关功率变换器的输出电压:
其中T1为首次时间间隔,T2为电感器回扫时间间隔,Vc为输出电压,VX为线输入电压。
13.权利要求11所述的方法还包括:
按照下列方程确定开关功率变换器的线输入电压:
其中,T1为首次时间间隔,T2为电感器回扫时间间隔,Vc为输出电压,VX为线输入电压。
14.根据权利要求11所述的方法,其中所述开关包括一个场效应晶体管,该方法还包括:
感应开关的门瞬时信号,确定电感器回扫时间间隔T2。
15.权利要求11所述的方法还包括:
通过与电感器磁偶联的复卷绕组产生反馈信号。
16.权利要求11所述的方法还包括:
感应经过电感器的线输入电压。
17.根据权利要求16所述的方法,其中感应经过电感器线输入电压的方法包括:
从电感器电流诱导复卷绕组电流;
感应诱导电流;
将感应的诱导电流转换为与该线输入电压对应的电压;
感应与线输入电压对应的电压。
18.根据权利要求11所述的方法,其中所述开关功率变换器还包括一个与电感器偶联的电容器、开关盒一个输入电压节点,该方法还包括:
感应经过电感器的开关功率变换器输出电压。
19.一种控制功率因数校正并调节开关功率变换器输出电压的方法,其中,该开关功率变换器包括一个与线输入电压节点偶联的电感器和与该电感器偶联的开关,本方法包括:
接收来自开关功率变换器的反馈信号;
确定一个线输入电压;
向开关提供控制信号,因此,在开关的各周期开关功率变换器就会对控制信号作出回应,当开关闭合时,首次间隔电感器电流升高,开关断开时,电感器回扫时间间隔电感器电流下降;
在开关门感应一个或多个电压瞬时信号,以确定电感器回扫时间间隔;
利用线输入电压、电感器回扫时间间隔和首次时间间隔确定开关功率变换器的输出电压,以及
使所述开关功率变换器能够在不连续导通模式下工作。
20.一种控制功率因数校正并调节开关功率变换器输出电压的方法,其中,该开关功率变换器包括一个与线输入电压节点偶联的电感器和与该电感器偶联的开关,本方法包括:
接收来自开关功率变换器的反馈信号;
确定一个来自反馈信号的开关功率变换器输出电压;
向开关提供控制信号,因此,在开关的各周期开关功率变换器就会对控制信号作出回应,当开关闭合时,首次间隔电感器电流升高,开关断开时,电感器回扫时间间隔电感器电流下降;
在开关门感应一个或多个电压瞬时信号,以确定电感器回扫时间间隔;
利用线输入电压、电感器回扫时间间隔和首次时间间隔确定开关功率变换器的输出电压;以及
使所述开关功率变换器能够在不连续导通模式下工作。
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- 2008-05-02 EP EP08747479A patent/EP2153512A2/en not_active Withdrawn
- 2008-05-02 US US12/114,130 patent/US8120341B2/en active Active
- 2008-05-02 CN CN200880014462A patent/CN101730972A/zh active Pending
- 2008-05-02 WO PCT/US2008/062381 patent/WO2008137654A1/en active Application Filing
- 2008-05-02 JP JP2010506672A patent/JP2010526496A/ja active Pending
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2011
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Patent Citations (2)
Publication number | Priority date | Publication date | Assignee | Title |
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US6259614B1 (en) * | 1999-07-12 | 2001-07-10 | International Rectifier Corporation | Power factor correction control circuit |
CN1308407A (zh) * | 2000-12-26 | 2001-08-15 | 深圳市华为电气技术有限公司 | 单相功率因数校正升压变换器 |
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