WO2013046805A1 - 電力変換装置 - Google Patents
電力変換装置 Download PDFInfo
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- WO2013046805A1 WO2013046805A1 PCT/JP2012/064304 JP2012064304W WO2013046805A1 WO 2013046805 A1 WO2013046805 A1 WO 2013046805A1 JP 2012064304 W JP2012064304 W JP 2012064304W WO 2013046805 A1 WO2013046805 A1 WO 2013046805A1
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M5/00—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases
- H02M5/40—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc
- H02M5/42—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters
- H02M5/44—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters using discharge tubes or semiconductor devices to convert the intermediate dc into ac
- H02M5/453—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters using discharge tubes or semiconductor devices to convert the intermediate dc into ac using devices of a triode or transistor type requiring continuous application of a control signal
- H02M5/458—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters using discharge tubes or semiconductor devices to convert the intermediate dc into ac using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/14—Arrangements for reducing ripples from dc input or output
- H02M1/15—Arrangements for reducing ripples from dc input or output using active elements
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
- H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
- H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M7/4826—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode operating from a resonant DC source, i.e. the DC input voltage varies periodically, e.g. resonant DC-link inverters
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
- H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
- H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M7/53—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M7/537—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
- H02M7/5387—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration
- H02M7/53871—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration with automatic control of output voltage or current
- H02M7/53875—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration with automatic control of output voltage or current with analogue control of three-phase output
Definitions
- This invention relates to a power converter.
- an indirect AC power converter that converts a commercial AC voltage into a DC voltage through a rectifier circuit and a smoothing circuit and obtains an AC output by a voltage source converter is generally used. Yes.
- a three-phase capacitorless inverter is known as a method for obtaining AC output directly from AC voltage, and a large capacitor and reactor that smooth the voltage pulsation due to commercial frequency are not required. Is possible.
- Patent Document 1 Japanese Patent No. 4488122
- Patent Document 2 Japanese Patent Publication No. 61-48356 (Patent Document 2)).
- an object of the present invention is to provide a power conversion device that can suppress harmonics of an inductive load while suppressing resonance by an LC filter and can perform optimal control with good responsiveness to the inductive load.
- a power conversion device of the present invention is A rectifier that rectifies a single-phase or multi-phase AC voltage into a DC voltage; A PWM-controlled inverter unit that converts the DC voltage output from the rectifier unit into an AC voltage and outputs the AC voltage; A capacitance element connected between the input terminals of the inverter unit; An inductance element constituting an LC filter with the capacitance element; A voltage detector for detecting a voltage across the inductance element; A control unit for controlling the inverter unit based on the voltage across the inductance element detected by the voltage detection unit; The LC filter has a resonance frequency set so as to pass a ripple current component included in the DC current output from the rectification unit and attenuate a current component having the same frequency as the carrier frequency of the inverter unit.
- the control unit controls the inverter unit so that a transfer characteristic of the input voltage of the inverter unit with respect to the DC voltage from the rectifying unit is an attenuation characteristic by a phase advance element and a secondary delay element connected in series.
- the attenuation coefficient of the transfer characteristic of the input voltage of the inverter unit with respect to the DC voltage from the rectifying unit is set to be larger than 1.
- the inverter unit is controlled by the control unit so that the transfer characteristic of the input voltage of the inverter unit with respect to the DC voltage from the rectifying unit becomes an attenuation characteristic by the phase advance element and the secondary delay element connected in series.
- the attenuation coefficient of the transfer characteristic of the input voltage of the inverter unit with respect to the DC voltage from the rectifying unit is set to be larger than 1, the harmonics caused by the inductive load are effectively suppressed while suppressing the resonance by the LC filter.
- Optimal control with good response to an inductive load such as a motor can be achieved.
- the control unit In the transfer characteristic of the input voltage of the inverter unit with respect to the DC voltage from the rectifying unit, the voltage across the inductance element detected by the voltage detection unit is negatively fed back to the input current of the inverter unit.
- the first feedback loop for controlling the current flowing through the inductance element and the input voltage of the inverter unit are positively fed back with respect to the input current of the inverter unit, thereby controlling the current flowing through the capacitance element.
- a second feedback loop The transfer characteristic of the input voltage of the inverter unit with respect to the DC voltage from the rectifier unit and the transfer characteristic of the direct current flowing through the inductance element with respect to the input current of the inverter unit are predetermined transfer characteristics. as such, the gain k 2 of the first gain k 1 of 1 feedback loop and said second feedback loop is set.
- the control unit Cut-off frequency of the transfer characteristic of the input voltage of the inverter unit with respect to the DC voltage from the rectifier unit, and a low-frequency cut-off frequency of the transfer characteristic of DC current flowing through the inductance element with respect to the input current of the inverter unit; so it becomes the same, the gain k 2 of the first gain k 1 of 1 feedback loop and said second feedback loop is set.
- the gain k 1 of the first feedback loop and the gain k 2 of the second feedback loop are set, and the cutoff frequency of the transfer characteristic of the input voltage of the inverter unit with respect to the DC voltage from the rectifying unit is
- the transfer frequency of the direct current flowing through the inductance element with respect to the input current of the inverter part is made less susceptible to the influence of the sampling frequency (carrier frequency) of PWM control. It becomes possible to set an attenuation coefficient.
- the inductance value of the inductance element can be reduced, and the inductance element can be reduced in size.
- the control unit In the transfer characteristic of the input voltage of the inverter unit with respect to the DC voltage from the rectifier unit, the single-phase or multi-phase AC voltage is supplied to the second feedback loop of the input voltage of the inverter unit by the rectifier unit.
- a ripple removing unit that removes a ripple voltage component included in the DC voltage output from the rectifying unit by rectification is provided.
- the ripple voltage component included in the DC voltage output from the rectifying unit is removed by the ripple removing unit in the second feedback loop of the input voltage of the inverter unit, so the inverter unit in the second feedback loop.
- the control unit It is substantially zero gain k 1 of the first feedback loop of the detected voltage across the inductance element by the voltage detection unit.
- the transfer characteristic of the input voltage of the inverter section for DC voltage from the rectifying unit By setting the cut-off frequency, it is possible to effectively suppress harmonics due to inductive loads while suppressing resonance by the LC filter.
- a resistor connected in parallel to both ends of the inductance element, The gain k 1 of the first feedback loop of the voltage across the inductance element detected by the voltage detecting unit is set by the resistance value of the resistor.
- the stability of control is improved because it is less affected by the sampling frequency (carrier frequency) of PWM control.
- the control unit is configured such that a cut-off frequency of the transfer characteristic of the input voltage of the inverter unit with respect to the DC voltage from the rectifying unit is higher than a resonance frequency of the LC filter, and an input current of the inverter unit The inverter unit is controlled so that a cut-off frequency of a transfer characteristic of a direct current flowing through the inductance element with respect to is lower than a resonance frequency of the LC filter.
- the cutoff frequency of the resonance suppression system that suppresses resonance by the LC filter is increased, and the inductance element for the input current of the inverter unit is increased.
- the transfer characteristic of the flowing direct current it is possible to lower the cutoff frequency of the harmonic suppression system that suppresses the harmonics of the inductive load.
- the capacitance of the capacitance element is C [F]
- the inductance of the inductance element is L [H]
- the standard capacity of the capacitance element is C R [F]
- the standard capacity C R [F] of the capacitance element is L R [H]
- L / C ⁇ LR / CR Satisfy the condition of
- the standard capacity of the capacitance element is the inductance of the inductive load such as a motor, the power supply inductance, the charging voltage of the capacitance element, the power consumption of the motor load, the frequency of the ripple component of the DC link voltage, and the motor excitation.
- the capacitance value should be determined so as to prevent the destruction of the circuit element due to the operation stop of the inverter unit while suppressing the harmonics.
- the standard capacity is determined from the allowable ripple current or temperature rise value of the capacitance element.
- the inductance element can be reduced in size while suppressing the resonance by the LC filter and the harmonics of the inductive load.
- the capacitance of the capacitance element is C [F]
- the inductance of the inductance element is L [H]
- the standard capacity of the capacitance element is C R [F]
- the standard capacity C R [F] of the capacitance element is L R [H]
- the cut-off frequency of the transfer characteristic of the direct current flowing through the inductance element with respect to the input current of the inverter unit is the direct current output from the rectifier unit by rectifying the single-phase or multiphase AC voltage by the rectifier unit. It is larger than the repetition frequency of the ripple voltage component included in the voltage.
- the cutoff frequency of the transfer characteristic of the direct current flowing in the inductance element with respect to the input current of the inverter unit is made larger than the repetition frequency of the ripple component included in the DC voltage output from the rectifier unit.
- the cut-off frequency of the transfer characteristic of the direct current flowing through the inductance element with respect to the input current of the inverter unit is the direct current output from the rectifier unit by rectifying the single-phase or multiphase AC voltage by the rectifier unit. It is smaller than the repetition frequency of the ripple voltage component included in the voltage.
- the cutoff frequency of the transfer characteristic of the direct current flowing through the inductance element with respect to the input current of the inverter unit is made smaller than the repetition frequency of the ripple voltage component included in the DC voltage output from the rectifier unit.
- the inductance element is connected between one output terminal of the rectifying unit and one input terminal of the inverter unit.
- the inductance element since the AC component of the resonance current and the harmonic current flows through the inductance element connected between the one output end of the rectification unit and the one input end of the inverter unit, the inductance element The voltage signal suitable for control of resonance suppression and harmonic suppression of the inverter unit is obtained by detecting the voltage between both ends of the inverter.
- the inductance element is connected between an output end of an AC power supply that supplies the AC voltage and an input end of the rectifying unit.
- the inductance element connected between the output end of the AC power supply that supplies the AC voltage and the input end of the rectifying unit includes: Since an alternating current component of the resonance current and the harmonic current flows, a voltage signal suitable for controlling the inverter unit can be obtained by detecting the voltage across the inductance element with the voltage detection unit.
- an inductance element connected to each phase between the output terminal of the AC power source that supplies the AC voltage and the input terminal of the rectifier unit includes each phase. Since the AC current components of the resonance current and the harmonic current flow respectively, the voltage signal suitable for controlling the resonance suppression and the harmonic suppression of the inverter unit is obtained by detecting the voltage across each inductance element by the voltage detection unit. It is done.
- the power conversion device of the present invention the power conversion that can suppress the harmonics of the inductive load while suppressing the resonance by the LC filter, and can perform the optimal control with good responsiveness to the inductive load.
- An apparatus can be realized.
- FIG. 1 is a configuration diagram of a power conversion device according to a first embodiment of the present invention.
- FIG. 2 is a diagram showing an equivalent circuit of the power converter.
- FIG. 3 is a block diagram of the power converter.
- FIG. 4 is a diagram showing a transfer function of the power converter.
- FIG. 5 is a diagram showing an example of the harmonic current of the concentrated winding 6-pole motor.
- FIG. 6 is a diagram showing an equivalent circuit of the power converter.
- FIG. 7 is a block diagram showing the transfer characteristic of the reactor current with respect to the DC link current of the power converter.
- FIG. 8 is a diagram showing an equivalent circuit of the power converter.
- FIG. 9 is a block diagram of the power converter.
- FIG. 1 is a configuration diagram of a power conversion device according to a first embodiment of the present invention.
- FIG. 2 is a diagram showing an equivalent circuit of the power converter.
- FIG. 3 is a block diagram of the power converter.
- FIG. 4 is a diagram showing
- FIG. 10 is a diagram illustrating the characteristics of the cutoff frequency of the resonance suppression system with respect to the attenuation coefficient of the power converter and the cutoff frequency of the harmonic suppression system with respect to the attenuation coefficient.
- FIG. 11 is a Bode diagram showing the characteristics of the resonance suppression system of the power converter.
- FIG. 12 is a Bode diagram showing the characteristics of the harmonic suppression system of the power converter.
- FIG. 13 shows the step response characteristics of the resonance suppression system of the power converter.
- FIG. 14 is a diagram showing step response characteristics of the harmonic suppression system of the motor of the power converter.
- FIG. 17 is a diagram showing the characteristics of the voltage detection gain with respect to the harmonic frequency of the power converter.
- FIG. 18 is a diagram showing simulation waveforms of the power converter.
- FIG. 19 is a diagram showing the characteristics of the cutoff frequency of the resonance suppression system with respect to the attenuation coefficient of the power converter and the cutoff frequency of the harmonic suppression system with respect to the attenuation coefficient.
- FIG. 20 is a block diagram of a power conversion device according to the second embodiment of the present invention.
- FIG. 21 is a Bode diagram showing the characteristics of the resonance suppression system of the power conversion device of the first embodiment.
- FIG. 22 is a Bode diagram showing the characteristics of the resonance suppression system of the power conversion device of the second embodiment.
- FIG. 23 is a Bode diagram for explaining the stability of the power converter.
- FIG. 24 is a Bode diagram for explaining the stability of the power converter.
- FIG. 25 is a diagram illustrating a transfer function for explaining the gain margin of the power conversion device according to the first embodiment.
- FIG. 26 is a Bode diagram for explaining the gain margin of the power conversion device of the first embodiment.
- FIG. 27 is a diagram illustrating a transfer function for explaining the gain margin of the power conversion device according to the second embodiment.
- FIG. 28 is a Bode diagram for explaining the gain margin of the power converter of the second embodiment.
- FIG. 29 is a diagram illustrating a transfer function for explaining the stability of the power conversion device according to the modification of the second embodiment.
- FIG. 30 is a diagram illustrating a transfer function for explaining the stability of the power conversion device.
- FIG. 31 is a diagram illustrating a transfer function for explaining the characteristics of the harmonic suppression system of the power conversion device according to the second embodiment.
- FIG. 32A is a diagram showing a transfer function when a high-pass filter for direct current cut is applied to the power conversion device of the second embodiment.
- FIG. 32B is a diagram illustrating a transfer function when a high-pass filter for cutting direct current and a ripple removing unit are applied to the power conversion device of the second embodiment.
- FIG. 33 is a diagram showing the amplitude characteristic of the ripple voltage.
- FIG. 34 is a Bode diagram when a high-pass filter for cutting direct current and a ripple removing unit are applied to the power converter.
- FIG. 35 is a diagram illustrating characteristics of the cutoff frequency of the resonance suppression system with respect to the attenuation coefficient and the cutoff frequency of the harmonic suppression system with respect to the attenuation coefficient of the power conversion device according to the second embodiment.
- FIG. 36A is a diagram illustrating frequency characteristics of the power conversion device according to the first embodiment.
- FIG. 36B is a diagram illustrating frequency characteristics of the power conversion device according to the second embodiment.
- FIG. 36C is a diagram illustrating frequency characteristics of the power converter using only DC voltage feedback.
- FIG. 37 is a diagram showing a simulation waveform when harmonics are superimposed on the power supply voltage of the power converters of the first and second embodiments.
- FIG. 38 is a diagram showing a simulation waveform when the power supply voltage of the power conversion device according to the first and second embodiments drops.
- FIG. 39 is a diagram showing simulation waveforms when motor harmonic currents of the power converters of the first and second embodiments are superimposed.
- FIG. 1 shows a configuration diagram of a power conversion device according to a first embodiment of the present invention.
- this power conversion device includes a diode bridge 11 as an example of a rectifying unit including six diodes D1 to D6 constituting a three-phase diode bridge circuit, and six switchings constituting a three-phase bridge circuit. And an inverter unit 12 including elements S1 to S6.
- the power converter includes a reactor L as an example of an inductance element connected between the positive output side of the diode bridge 11 and the positive input side of the inverter unit 12, and the input end of the inverter unit 12.
- a capacitor C as an example of a capacitance element connected to the.
- the reactor L and the capacitor C constitute an LC filter. Furthermore, the power converter includes a voltage detection unit 101 that detects a voltage across the reactor L, and a switching signal of the inverter unit 12 based on a VL signal that represents the voltage across the reactor L from the voltage detection unit 10. A control unit 100 that outputs a PWM signal is provided in S1 to S6.
- the diode bridge 11 rectifies the three-phase AC voltage from the three-phase AC power source 10 into a direct current, converts the rectified DC voltage into a predetermined three-phase AC voltage by the inverter unit 12 and outputs it.
- a motor 13 is connected as a load of the inverter unit 12.
- the capacitance of the capacitor C of the LC filter in the DC link portion of the power converter shown in FIG. 1 is as small as 1 or less, which is several tenths of the conventional value, and the resonance frequency of the LC filter is several kHz to attenuate the carrier current component of the inverter device.
- the inductance of the reactor L is set to a small value.
- the reactor L and the capacitor C in the DC link section do not have the effect of smoothing the commercial frequency component, and the DC link section generates a maximum phase potential based on the minimum phase of the phase voltage, which is 6 times the commercial frequency. Pulsates at frequency. Similarly, with respect to the input current, a direct current flows between the lines of the maximum phase and the minimum phase. Therefore, when the input current of the inverter unit is constant, a 120 ° energization waveform is obtained.
- FIG. 2 shows an equivalent circuit of the power converter.
- 14 is a current source representing the inverter section load is connected in a simple manner
- V s is the DC voltage outputted from the diode bridge 11
- V c is the voltage across the capacitor C
- I L is the reactor L
- I c is the current flowing through the capacitor C
- I o is the current flowing through the DC link section.
- FIGS. 3A to 3C are block diagrams in which the characteristics of the resonance suppression system are obtained when the voltage V L across the reactor L is used for resonance suppression, and the DC voltage V s output from the diode bridge 11. It shows the transfer characteristics across voltage V c of the capacitor C (i.e. the input voltage of the inverter unit 12) for.
- control unit 100 controls the inverter unit 12 so as to have an attenuation characteristic in which the phase advance element and the secondary delay element shown in FIG. 3C are connected in series.
- FIG. 4 shows the transfer function G (s) of the block diagram of FIG. 3. Since the second item is a secondary system, the attenuation characteristic can be improved by the gain k, and one item is the phase advance. Therefore, a characteristic close to a stable first-order lag system can be achieved by both.
- V s is a DC voltage output from the diode bridge 11
- V c is a voltage across the capacitor C
- L is an inductance of the reactor L
- C is a capacitance of the capacitor C
- s is a Laplace variable.
- FIG. 5 shows an example of the harmonic current of the concentrated winding 6-pole motor.
- the horizontal axis represents the harmonic order
- the vertical axis represents the harmonic current content.
- the harmonic current is changed for each frequency [Hz] of the AC power source for driving the concentrated winding 6-pole motor, that is, for every 90 Hz, 120 Hz, 151 Hz, 180 Hz, 211 Hz, 239 Hz, 271 Hz, 300 Hz, and 331 Hz.
- the content rate is shown.
- E La , E Lb , E Lc Motor voltage effective value e La , e Lb , e Lc : Motor voltage instantaneous value I La , I Lb , I Lc : Motor current effective value i La , i Lb , i Lc : Motor current instantaneous value P La , P Lb , P Lc : Motor instantaneous active power harmonic component ⁇ L : Motor drive angular frequency
- E L Motor voltage effective value (three-phase equilibrium state)
- I L Effective motor current value (three-phase equilibrium state)
- P L Instantaneous active power harmonic component (for three phases, equivalent to DC unit instantaneous power)
- the cutoff frequency of the resonance suppression system for suppressing resonance by the LC filter, the motor, etc will be described below.
- FIG. 6 shows an equivalent circuit of the above power converter
- FIG. 7 shows the reactor current i Lh (power input) with respect to the DC link current i oh shown in FIG. 6 in the control system of the power converter shown in FIG.
- the transfer characteristics are obtained. It can be seen that the transfer function becomes a quadratic system by performing the equivalent transformation shown in FIGS. 7 (A) to 7 (C).
- the second order system of the transfer function G (s) in FIG. 7C at this time is regarded as a series connection of first order lag systems, Then, the transfer function G (s) has the relationship shown in the following equation (12), which can be modified and expressed by the following equation (13).
- the transfer function G (s) has a real root when the damping coefficient ⁇ ⁇ 1, and when ⁇ is large, the cutoff frequency fc of the transfer function of the reactor current i Lh (power input) with respect to the DC link current i oh . Is It becomes.
- the damping coefficient ⁇ when the damping coefficient ⁇ is larger than 1, it has a real root, so it can be regarded as a serial connection of a first-order lag system.
- the damping coefficient ⁇ When the damping coefficient ⁇ is large, one item of Expression (13) is obtained. Since the time constant is large and the time constant of the two items in equation (13) is small, the band of the harmonic suppression system (cut-off frequency f c ) depends on one item and is expressed by equation (14). . Therefore, by setting the ⁇ damping coefficient larger, the time constant is increased, since the band is narrower lower cutoff frequency f c, it is possible to widen the frequency range for attenuating the reverse.
- FIG. 8 shows an equivalent circuit of the power converter
- FIGS. 9A to 9F show block diagrams of the power converter.
- FIG. 8 shows a current flow including a harmonic current generated by the motor load.
- V s is a DC voltage output from the diode bridge 11
- V Lh is a voltage across the reactance L
- V ch is a voltage across the capacitor C
- I Lh is a reactor current flowing through the reactor L
- I ch is a capacitor C.
- I oh is a DC link current flowing through the DC link unit.
- FIG. 9A shows the transfer characteristic of the voltage V c across the capacitor C with respect to the DC voltage V s output from the diode bridge 11 as in FIG. 3A.
- FIG. 10 shows the characteristics of the cutoff frequency of the resonance suppression system with respect to the attenuation coefficient ⁇ of the power converter and the cutoff frequency of the harmonic suppression system with respect to the attenuation coefficient ⁇ .
- the horizontal axis represents the attenuation coefficient
- the vertical axis represents the cut-off frequency [Hz] zH
- “ ⁇ ” indicates the characteristic of the cut-off frequency of the resonance suppression system
- “ ⁇ ” indicates the harmonic.
- the characteristic of the cut-off frequency of the wave suppression system is shown.
- FIG. 10 shows the cut-off frequency with respect to the damping coefficient ⁇ for the harmonic suppression system and the resonance suppression system when the resonance frequency of the LC filter is set to 1125 Hz.
- ⁇ 0.2 to 0.4 (constant value control)
- the characteristic difference between the harmonic suppression system and the resonance suppression system can be set by setting the attenuation coefficient ⁇ larger than 1.
- FIG. 11 shows the characteristics of the resonance suppression system by the LC filter of the power converter
- FIG. 11 (A) shows the gain characteristics
- FIG. 11 (B) shows the phase characteristics.
- 11A the horizontal axis represents frequency [Hz]
- the vertical axis represents gain [dB]
- the horizontal axis represents frequency [Hz]
- the vertical axis represents phase [deg]. Yes.
- the attenuation characteristic ⁇ 2.0.
- the cut-off frequency is 4200 Hz.
- FIG. 12 shows the characteristics of the harmonic suppression system of the power converter
- FIG. 12 (A) shows the gain characteristics
- FIG. 12 (B) shows the phase characteristics.
- 12A the horizontal axis represents frequency [Hz]
- the vertical axis represents gain [dB]
- the horizontal axis represents frequency [Hz]
- the vertical axis represents phase [deg]. Yes.
- the attenuation characteristic ⁇ 2.0.
- the cut-off frequency is 302 Hz.
- FIG. 13 shows a step response characteristic of a resonance suppression system that suppresses resonance by the LC filter of the power converter
- FIG. 14 shows a step response characteristic of a harmonic suppression system that suppresses a harmonic of the motor of the power converter. Is shown.
- the horizontal axis represents time [ ⁇ 10 ⁇ 4 sec], and the vertical axis represents amplitude [arbitrary scale].
- the step response characteristics of the conventional method are ⁇ ⁇ 1, so that the response is good although it is somewhat oscillatory and accompanied by an overshoot.
- the time constant of the resonance suppression system is several hundred ⁇ sec
- the time constant of the harmonic suppression system is several msec
- the electric system time constant on the power source side and the mechanical system time constant on the motor side are Can respond.
- FIGS. 15C and 15D show the attenuation.
- FIG. 15 and 16 are simulations of the influence on the power input waveform due to the setting of the attenuation coefficient ⁇ .
- the simulation conditions are when the power supply is 200 V, 50 Hz, and 7 kW.
- the harmonics on the motor side simulate the harmonic distribution at 50 Hz in FIG. 3, and a harmonic current of 1800 Hz and 2 A flows through the DC link section. It is supposed to be.
- a pulsating current having a power supply frequency of 6 times that modulates the voltage source inverter to maintain the pulsation while maintaining the motor harmonics can be maintained.
- ⁇ 1.5 (cut-off frequency 420 Hz) and therefore 300 Hz, which is 6 times the power frequency, is maintained.
- This setting is a method suitable for constant current control in which voltage compensation is not performed by a voltage source inverter.
- the gain Gmax at the peak point is It is represented by
- FIG. 17 shows the characteristics of the voltage detection gain with respect to the harmonic frequency of the motor of the power converter, and shows the result of obtaining the voltage detection gain of each L / C at the same resonance frequency from the above equation (17).
- the L / C marked “ ⁇ ” is 12.5.
- L / C marked “ ⁇ ” is 3.13 ( ⁇ 0.25 mH / 80 ⁇ F)
- L / C marked “*” is 0.78 ( ⁇ 0.125 mH / 160 ⁇ F) It is.
- the amplitude may be small, and the L value can be set small at the same resonance frequency from the relationship shown in FIG. 17, and the reactor can be downsized.
- FIG. 18 shows a simulation waveform of the above power converter
- FIGS. 18 (A) and 18 (C) show the input current
- FIGS. 18 (B) and 18 (D) show the reactor voltage.
- the process is performed under the same conditions as in FIG.
- the waveforms of FIGS. 18C and 18D it can be seen that the reactor voltage becomes 1/2 when the L value is halved.
- the harmonic component of the 20th order or more specified by the partial weighted harmonic distortion PWHD as well as the total harmonic distortion THD becomes a problem.
- the 11th and 13th components having a small content shown in FIG. 5 have an effect and the current appearing in the DC link portion is reduced, the reactor voltage is set to be large and the detection sensitivity is increased. There is a need.
- the standard capacity C R [F] of the capacitor C is the motor load inductance, the power supply inductance, the capacitor charging voltage, and the motor load as described in the technical literature (Japanese Patent Laid-Open No. 2007-202378). Based on the power consumption, the frequency of the ripple component of the DC link voltage, and the motor excitation current, it is determined so as to reduce harmonics and prevent circuit elements from being destroyed due to the operation stop of the inverter unit. When a circuit such as a CD clamp that absorbs load induced power is used in combination, the standard capacity is determined from the allowable ripple current of the capacitor C or the temperature rise value. Based on the standard capacity C R and the resonant frequency of the LC filter of the capacitor C, to determine the inductance L R [H] of the reactor L.
- the cutoff frequency of the resonance suppression system that suppresses resonance by the LC filter is lowered, and the inverter unit 12 In the transfer characteristic of the direct current flowing through the reactor L with respect to the input current, it is possible to increase the cutoff frequency of the harmonic suppression system that suppresses the harmonics of the inductive load.
- the control unit 100 controls the inverter unit 12 to effectively suppress harmonics caused by the inductive load while suppressing resonance by the LC filter, and thereby inductive load such as a motor. It is possible to perform optimal control with good response.
- the cutoff frequency of the transfer characteristic of the direct current flowing through the reactor L with respect to the input current of the inverter unit 12 is made larger than the repetition frequency of the ripple component included in the direct current voltage output from the diode bridge 11, thereby providing a diode.
- Control suitable for the inverter unit 12 that performs control for compensating for the ripple component included in the DC voltage output from the bridge 11 is possible.
- the cutoff frequency of the transfer characteristic of the direct current flowing through the reactor L with respect to the input current of the inverter unit 12 is made smaller than the repetition frequency of the ripple component included in the direct current voltage output from the diode bridge 11. Control suitable for the inverter unit 12 that performs current control becomes possible.
- FIG. 19 shows the characteristics of the cutoff frequency of the resonance suppression system with respect to the attenuation coefficient of the power conversion device of the first embodiment and the cutoff frequency of the harmonic suppression system with respect to the attenuation coefficient.
- the horizontal axis represents the attenuation coefficient
- the vertical axis represents the cut-off frequency [Hz].
- ⁇ indicates the characteristic of the cutoff frequency of the resonance suppression system
- ⁇ indicates the characteristic of the cutoff frequency of the resonance suppression system
- the frequency of the three-phase AC voltage is 50 Hz
- the carrier frequency of the inverter unit 12 is 6 kHz.
- the cutoff frequency of the harmonic suppression system is set so as to maintain the current pulsating flow component (300 Hz)
- the settable attenuation coefficient ⁇ is The maximum is about 1.5.
- the attenuation coefficient ⁇ is about 1.1 due to the stability limit of the control system, and the harmonic suppression band (harmonic suppression). It becomes difficult to widen the frequency band higher than the cutoff frequency of the system.
- the resonance frequency of the LC filter and the sampling frequency are close to each other, it becomes difficult to ensure the stability of the control system.
- the DC voltage and current of the DC link unit are six times the power frequency. Since the pulsation is controlled at ⁇ 360 Hz, the resonance frequency of the LC filter is about 500 Hz to 1 kHz, and the resonance frequency of the LC filter is close to the sampling frequency.
- the power converter of the second embodiment of the present invention has the same configuration as that of the power converter shown in FIG. 1 of the first embodiment except for the operation of the control unit 100, and uses FIGS. 1 and 2. .
- FIG. 20 shows a block diagram of the power conversion device of the second embodiment.
- FIGS. 20A to 20C are block diagrams in which the characteristics of the resonance suppression system are obtained when the voltage V L across the reactor L is used for resonance suppression, and the DC voltage V s output from the diode bridge 11. It shows the transfer characteristics across voltage V c of the capacitor C (i.e. the input voltage of the inverter unit 12) for.
- the control unit 100 controls the inverter unit 12 so as to have an attenuation characteristic in which the phase advance element and the secondary delay element shown in FIG. 20C are connected in series.
- the difference from the block diagram of the power converter of the first embodiment is that the voltage V c across the capacitor C (that is, the input voltage of the inverter unit 12) is the input of the inverter unit 12. in that there is provided a DC voltage feedback gain k 2 for positive feedback (second feedback loop) it is with respect to the current I c.
- k 2 for positive feedback (second feedback loop) it is with respect to the current I c.
- the gain of the reactor voltage feedback to the negative feedback the voltage across V L of the reactor L with respect to the input current I c of the inverter unit 12 (first feedback loop) and k 1.
- the voltage V L across the reactor L is fed back to the reactor voltage feedback that negatively feeds back the input current I o of the inverter unit 12, and the input voltage V c of the inverter unit 12 is fed into the inverter unit 12.
- the degree of freedom of the cutoff frequency of each of the differential system and the secondary system is provided, the circuit constant of the LC filter, the gain k of the first feedback loop 1.
- FIG. 21 shows the characteristics of the resonance suppression system of the power conversion device of the first embodiment.
- the cutoff frequency f1 of the differential system (dotted line) and the secondary system (dashed line) match, the cutoff frequency of the resonance suppression system (solid line) is the high-frequency cutoff frequency of the secondary system. It is f2.
- FIG. 22 shows the characteristics of the resonance suppression system of the power conversion device of the second embodiment.
- the gain k 1 + k 2 is determined so that the attenuation coefficient ⁇ is 1.5 as in FIG. 21, and the cutoff frequency of the differential system (dotted line) is 2 it is obtained by setting the gain k 1 to match the high frequency side cutoff frequency f2 follows system (dashed line).
- the cutoff frequency of the resonance suppression system is the low-frequency cutoff frequency f1. be able to.
- FIGS. 23 (A) to (D), FIGS. 24 (A), and (B) are Bode diagrams for explaining the stability of the power converter of the second embodiment.
- the control system of FIG. 23A (shown in FIG. 20A) is equivalently converted in the order of FIGS. 23B to 23D, FIGS. 24A and 24B to obtain the target voltage V L * .
- FIGS. 27 and 28 show the power converter of the second embodiment. 2 shows a transfer function and a Bode diagram for explaining the gain margin.
- the dotted line is the differential system
- the alternate long and short dash line is the secondary system
- the thin solid line is the series system of the differential system and the secondary system
- the thick solid line is the reactor based on the target voltage V L *. It represents a control system (attenuation characteristic in which a phase advance element and a secondary delay element are connected in series) for controlling the voltage V L across L.
- the 0 dB point of the differential gain becomes lower than the resonance frequency, so that the open loop gain becomes large and is shown in FIG. Further, when the carrier frequency is 1 ⁇ 2 (3 kHz) of 6 kHz, the gain is 0 dB or more, so that it becomes unstable.
- the degree of freedom of gain setting is utilized, and as shown in FIG. to be equal, and sets the derivative gain k 1. Therefore, a sufficient gain margin of ⁇ 20 dB can be secured at 3 kHz.
- 29 and 30 show a transfer function for explaining the stability of the modified example of the power conversion device of the second embodiment, and the reactor voltage feedback (first feedback loop) of the voltage VL across the reactor L is shown. It has a gain k 1 substantially zero. In FIG. 29A, the reactor voltage feedback is omitted.
- control system of FIG. 29A in which k 1 ⁇ 0 is equivalently converted in the order of FIGS. 29B to 29D, FIGS. 29A and 29B, and the DC target voltage V Based on L * , it is expressed by a control system which controls the voltage V L across the reactor L and the voltage V c across the capacitor C.
- FIG. 31 shows a transfer function for explaining the characteristics of the harmonic suppression system of the power conversion device of the second embodiment.
- FIG. 31A shows the transfer characteristic of the voltage V c across the capacitor C with respect to the DC voltage V s output from the diode bridge 11.
- a DC voltage feedback (positive feedback input voltage V c of the inverter unit 12 with respect to the input current I o of the inverter unit 12) is a DC power source
- a high-pass filter is used in combination with the DC voltage feedback loop.
- the high-pass filter provided in the DC voltage feedback loop is restricted by the lower limit of the cutoff frequency of the high-pass filter in order to remove power supply ripple, and affects the characteristics of the resonance suppression system.
- FIG. 32A shows a transfer function when a DC cut high-pass filter is applied to the power conversion device of the second embodiment
- FIG. 32B applies a DC cut high-pass filter and a ripple removing unit. The transfer function is shown.
- FIG. 33 shows the amplitude characteristics of the ripple voltage used in the ripple removing unit.
- Cos ⁇ in of the ripple removing unit is expressed by the following equation, and ripple removal is performed using a table or a function.
- the cos ⁇ in of the ripple removing unit is synchronized with the frequency of the three-phase AC power supply 10 by a PLL (Phase-Locked Loop) or the like.
- PLL Phase-Locked Loop
- FIG. 34 shows a Bode diagram when a high-pass filter for DC cut and a ripple removing unit are applied to the power conversion device of the second embodiment.
- the dotted line shows the characteristics when the DC cut high-pass filter and the ripple removal unit are not applied
- the alternate long and short dash line shows the characteristics when the DC cut high-pass filter is applied
- the solid line applies the ripple removal unit. The characteristics are shown.
- the filter characteristic depends on the ripple frequency component, it is separated into a DC component and a harmonic component at 1 / cos ⁇ in shown in FIG. For this reason, characteristic degradation can be minimized by setting the cut-off frequency of the high-pass filter to a sufficiently low frequency from which the DC component can be removed.
- FIG. 35 shows characteristics of the cutoff frequency of the resonance suppression system with respect to the attenuation coefficient of the power conversion device of the second embodiment and the cutoff frequency of the harmonic suppression system with respect to the attenuation coefficient
- FIG. 36A shows the power conversion device of the first embodiment. The frequency characteristics are shown.
- FIG. 36B shows the frequency characteristics of the power conversion device of the second embodiment
- FIG. 36C shows the frequency characteristics of the power conversion device in the case of DC voltage feedback alone.
- FIG. 35 shows a conceptual diagram regarding the effect of the power conversion device of the second embodiment.
- the resonance frequency of the LC filter is f0
- the low-frequency cutoff frequency of the harmonic suppression system is f1
- the high-frequency cutoff frequency of the harmonic suppression system is f2.
- FIG. 37 shows simulation waveforms when harmonics are superimposed on the power supply voltage of the power converters of the first and second embodiments.
- FIG. 37A shows the input voltage waveform when the power supply side is distorted
- FIG. 37B shows the input current waveform of the power converter of the first embodiment
- FIG. 37C shows the first embodiment.
- the DC voltage waveform of the DC link part of the power converter is shown.
- FIG. 37 (D) shows the input current waveform of the power converter of the second embodiment
- FIG. 37 (E) shows the DC voltage waveform of the DC link section of the power converter of the second embodiment.
- FIG. 37 simulates a case where a single-phase inverter device is connected and voltage distortion of 3 kHz is superimposed by 10% due to the carrier current in order to compare the characteristics with respect to the power supply distortion waveform.
- the resonance suppression band is wide, voltage distortion is observed in the DC voltage waveform of the DC link unit.
- the resonance suppression band is narrow, so the influence of voltage distortion is less than that of the first embodiment.
- FIG. 38 is a diagram showing a simulation waveform when the power supply voltage of the power converters of the first and second embodiments drops.
- FIG. 38 shows the result of the characteristic comparison against the instantaneous voltage drop (15% drop).
- the resonance suppression band shown in FIGS. 38B and 38C is wide, the output voltage response is fast and the potential difference between both ends of the reactor L is small. The fluctuation of the current command value is small, and the fluctuation of the input current corresponding to the power supply voltage remains.
- the cutoff frequency of the high-pass filter shown in FIGS. 37 (D) and 37 (E) is set low, so that the voltage fluctuation is fed back and affects the compensation current.
- the current may decrease.
- the power conversion device can satisfactorily control the power supply so that there is a voltage fluctuation, and can be applied in various power supply environments.
- FIG. 39 shows a simulation waveform when the motor harmonic currents of the power converters of the first and second embodiments are superimposed.
- 39A shows the waveform of the harmonic current generated on the motor side
- FIG. 39B shows the input current waveform of the power converter of the first embodiment
- FIG. 39C shows the first embodiment.
- the DC voltage waveform of the DC link part of the power converter is shown.
- FIG. 39 (D) shows the input current waveform of the power converter of the second embodiment
- FIG. 39 (E) shows the DC voltage waveform of the DC link section of the power converter of the second embodiment.
- the simulation conditions at this time are when the power supply is 200 V, 50 Hz, and 7 kW, and the harmonic current of 1800 Hz and 2 A flows through the DC link section.
- the harmonic suppression system of the power conversion device of the second embodiment is expressed by the same system as the power conversion device of the first embodiment, the second embodiment shown in FIGS.
- the effect of suppressing the harmonics of the power conversion device is equivalent to that of the power conversion device of the first embodiment shown in FIGS. 39 (B) and (C).
- the transfer characteristic of the input voltage of the inverter unit 12 with respect to the DC voltage from the diode bridge 11 becomes the attenuation characteristic by the phase advance element and the secondary delay element connected in series.
- the control unit 100 controls the inverter unit 2 and the attenuation coefficient ⁇ of the transfer characteristic of the input voltage of the inverter unit 12 with respect to the DC voltage from the diode bridge 11 is set to be larger than 1, thereby Harmonics due to inductive loads can be effectively suppressed while suppressing resonance, and optimal control with good responsiveness to inductive loads such as motors can be performed.
- the gain k 2 of the DC voltage feedback (second feedback loop) for controlling the current flowing in the capacitor C by positively feeding back the input voltage of the inverter unit 12 with respect to the 12 input current the diode bridge
- the cutoff frequency of the transfer characteristic of the input voltage of the inverter unit 12 with respect to the DC voltage from 11 and the cutoff frequency of the transfer characteristic of the DC current flowing through the reactor L with respect to the input current of the inverter unit 12 can be set individually. Become.
- the reactor voltage feedback by setting the gain k 2 gain k 1 and the DC voltage feedback (first feedback loop) (second feedback loop), the input voltage of the inverter unit 12 with respect to the DC voltage from the diode bridge 11
- the sampling frequency (carrier frequency) of the PWM control is made the same by making the cut-off frequency of the transfer characteristic of the same and the cut-off frequency of the low frequency of the transfer characteristic of the direct current flowing through the reactor L with respect to the input current of the inverter unit 12 It becomes difficult to be influenced, and a larger attenuation coefficient ⁇ can be set.
- the inductance value of the reactor L can be reduced, and the reactor L can be reduced in size.
- the ripple voltage component included in the DC voltage output from the diode bridge 11 is removed by the ripple removing unit in the DC voltage feedback (second feedback loop) of the input voltage of the inverter unit 12, so that the DC voltage feedback ( In the second feedback loop), the high-frequency component of the current flowing through the capacitor C can be controlled by positively feeding back only the high-frequency component of the input voltage of the inverter unit 12 with respect to the input current of the inverter unit 12.
- the inverter unit 12 With respect to the DC voltage from the diode bridge 11.
- the gain k 1 of the reactor voltage feedback (first feedback loop) of the voltage V L across the reactor L detected by the voltage detector 101 is set by the resistance value of the resistor connected in parallel across the reactor L.
- the reactor L can be reduced in size while suppressing resonance by the LC filter and harmonics of the inductive load.
- the cutoff frequency of the transfer characteristic of the direct current flowing through the reactor L with respect to the input current of the inverter unit 12 is made larger than the repetition frequency of the ripple component included in the direct current voltage output from the diode bridge 11, thereby providing a diode.
- Control suitable for the inverter unit 12 that performs control for compensating for the ripple component included in the DC voltage output from the bridge 11 is possible.
- the cutoff frequency of the transfer characteristic of the direct current flowing through the reactor L with respect to the input current of the inverter unit 12 is made smaller than the repetition frequency of the ripple component included in the direct current voltage output from the diode bridge 11. Control suitable for the inverter unit 12 that performs current control becomes possible.
- the three-phase alternating voltage was rectified to direct current voltage and the power converter device which converted and output the direct current voltage to three-phase alternating current voltage was demonstrated, it is single phase or more than three phases
- the present invention may be applied to a power converter that rectifies the AC voltage into a DC voltage, converts the DC voltage into a single-phase or three-phase or higher AC voltage, and outputs the AC voltage.
- the said 1st, 2nd embodiment demonstrated the power converter device with which the reactor L was connected as an inductance element between one output terminal of the diode bridge 11, and one input terminal of the inverter part 12,
- the present invention is not limited to this, and the inductance element may be connected between the output terminal of the AC power source that supplies the AC voltage and the input terminal of the rectifying unit.
- the inductance element connected between the output end of the AC power supply that supplies the AC voltage and the input end of the rectifying unit includes a resonance current and a harmonic. Since an alternating current component of the wave current flows, a voltage signal suitable for controlling the inverter unit can be obtained by detecting the voltage across the inductance element with the voltage detection unit.
- an inductance element connected to each phase between the output terminal of the AC power source that supplies the AC voltage and the input terminal of the rectifier unit includes each phase. Since the AC current components of the resonance current and the harmonic current flow respectively, the voltage signal suitable for controlling the resonance suppression and the harmonic suppression of the inverter unit is obtained by detecting the voltage across each inductance element by the voltage detection unit. It is done.
- the power converter of this invention is A rectifier that rectifies a single-phase or multi-phase AC voltage into a DC voltage; A PWM-controlled inverter unit that converts the DC voltage output from the rectifier unit into an AC voltage and outputs the AC voltage; A capacitance element connected between the input terminals of the inverter unit; An inductance element constituting an LC filter with the capacitance element; A voltage detector for detecting a voltage across the inductance element; A control unit for controlling the inverter unit based on the voltage across the inductance element detected by the voltage detection unit; The LC filter has a resonance frequency set so as to pass a ripple current component included in the DC current output from the rectification unit and attenuate a current component having the same frequency as the carrier frequency of the inverter unit.
- the control unit sets the attenuation coefficient ⁇ of the transfer characteristic of the input voltage of the inverter unit with respect to the DC voltage from the rectifier unit to be greater than 1, so that the cutoff frequency of the transfer characteristic is
- the inverter unit is set so that the cutoff frequency of the transfer characteristic of the direct current flowing through the inductance element with respect to the input current of the inverter unit is lower than the resonance frequency of the LC filter so as to be higher than the resonance frequency. You may control.
- the cutoff frequency of the resonance suppression system that suppresses the resonance by the LC filter is increased, and flows to the inductance element for the input current of the inverter unit.
- the control unit controls the inverter unit, so that the harmonics due to the inductive load can be effectively suppressed while suppressing the resonance by the LC filter. And optimal control with good response.
- the capacitance of the capacitance element is C [F]
- the inductance of the inductance element is L [H]
- the standard capacity of the capacitance element is C R [F]
- the standard capacity C R [F] of the capacitance element is L R [H]
- L / C ⁇ LR / CR Satisfy the condition of
- the standard capacity of the capacitance element is the inductance of the inductive load such as a motor, the power supply inductance, the charging voltage of the capacitance element, the power consumption of the motor load, the frequency of the ripple component of the DC link voltage, and the motor excitation.
- the capacitance value should be determined so as to prevent the destruction of the circuit element due to the operation stop of the inverter unit while suppressing the harmonics.
- the standard capacity is determined from the allowable ripple current or temperature rise value of the capacitance element.
- the inductance element can be reduced in size while suppressing the resonance by the LC filter and the harmonics of the inductive load.
- the capacitance of the capacitance element is C [F]
- the inductance of the inductance element is L [H]
- the standard capacity of the capacitance element is C R [F]
- the standard capacity C R [F] of the capacitance element is L R [H]
- the cutoff frequency of the transfer characteristic of the direct current flowing through the inductance element with respect to the input current of the inverter unit is higher than the repetition frequency of the ripple component included in the direct current voltage output from the rectifier unit.
- the cutoff frequency of the transfer characteristic of the direct current flowing in the inductance element with respect to the input current of the inverter unit is made larger than the repetition frequency of the ripple component included in the DC voltage output from the rectifier unit.
- the cutoff frequency of the transfer characteristic of the direct current flowing through the inductance element with respect to the input current of the inverter unit is smaller than the repetition frequency of the ripple component included in the direct current voltage output from the rectifier unit.
- the cutoff frequency of the transfer characteristic of the direct current flowing in the inductance element with respect to the input current of the inverter unit is made smaller than the repetition frequency of the ripple component included in the DC voltage output from the rectifier unit.
- the inductance element is connected between one output terminal of the rectifying unit and one input terminal of the inverter unit.
- the inductance element since the AC component of the resonance current and the harmonic current flows through the inductance element connected between the one output end of the rectification unit and the one input end of the inverter unit, the inductance element The voltage signal suitable for control of resonance suppression and harmonic suppression of the inverter unit is obtained by detecting the voltage between both ends of the inverter.
- the inductance element is connected between an output end of an AC power supply that supplies the AC voltage and an input end of the rectifying unit.
- the inductance element connected between the output end of the AC power supply that supplies the AC voltage and the input end of the rectifying unit includes: Since an alternating current component of the resonance current and the harmonic current flows, a voltage signal suitable for controlling the inverter unit can be obtained by detecting the voltage across the inductance element with the voltage detection unit.
- an inductance element connected to each phase between the output terminal of the AC power source that supplies the AC voltage and the input terminal of the rectifier unit includes each phase. Since the AC current components of the resonance current and the harmonic current flow respectively, the voltage signal suitable for controlling the resonance suppression and the harmonic suppression of the inverter unit is obtained by detecting the voltage across each inductance element by the voltage detection unit. It is done.
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Abstract
Description
単相または多相の交流電圧を直流電圧に整流する整流部と、
上記整流部から出力された上記直流電圧を交流電圧に変換して出力するPWM制御のインバータ部と、
上記インバータ部の入力端間に接続されたキャパシタンス素子と、
上記キャパシタンス素子とでLCフィルタを構成するインダクタンス素子と、
上記インダクタンス素子の両端電圧を検出する電圧検出部と、
上記電圧検出部により検出された上記インダクタンス素子の両端電圧に基づいて、上記インバータ部を制御する制御部と
を備え、
上記LCフィルタは、上記整流部から出力された上記直流電流に含まれるリップル電流成分を通過させ、かつ、上記インバータ部のキャリヤ周波数と同じ周波数の電流成分を減衰させるように、共振周波数が設定されていると共に、
上記制御部は、上記整流部からの上記直流電圧に対する上記インバータ部の入力電圧の伝達特性が、直列接続された位相進み要素と二次遅れ要素による減衰特性になるように、上記インバータ部を制御すると共に、上記整流部からの上記直流電圧に対する上記インバータ部の上記入力電圧の伝達特性の減衰係数が1よりも大きく設定されていることを特徴とする。
上記制御部は、
上記整流部からの上記直流電圧に対する上記インバータ部の上記入力電圧の伝達特性において、上記電圧検出部により検出された上記インダクタンス素子の両端電圧を、上記インバータ部の入力電流に対して負帰還することにより、上記インダクタンス素子に流れる電流を制御する第1帰還ループと、上記インバータ部の上記入力電圧を、上記インバータ部の入力電流に対して正帰還することにより、上記キャパシタンス素子に流れる電流を制御する第2帰還ループとを有し、
上記整流部からの上記直流電圧に対する上記インバータ部の上記入力電圧の伝達特性と、上記インバータ部の上記入力電流に対する上記インダクタンス素子に流れる直流電流の伝達特性とが夫々予め定められた伝達特性となるように、上記第1帰還ループのゲインk1と上記第2帰還ループのゲインk2とが設定されている。
上記制御部は、
上記整流部からの上記直流電圧に対する上記インバータ部の上記入力電圧の伝達特性のカットオフ周波数と、上記インバータ部の入力電流に対する上記インダクタンス素子に流れる直流電流の伝達特性の低域のカットオフ周波数とが同一になるように、上記第1帰還ループのゲインk1と上記第2帰還ループのゲインk2とが設定されている。
上記制御部は、
上記整流部からの上記直流電圧に対する上記インバータ部の上記入力電圧の伝達特性において、上記インバータ部の上記入力電圧の上記第2帰還ループに、上記単相または多相の交流電圧を上記整流部で整流することにより上記整流部から出力される上記直流電圧に含まれるリップル電圧成分を除去するリップル除去部を有する。
上記制御部は、
上記電圧検出部により検出された上記インダクタンス素子の両端電圧の上記第1帰還ループのゲインk1を略ゼロにしている。
上記インダクタンス素子の両端に並列に接続された抵抗を備え、
上記電圧検出部により検出された上記インダクタンス素子の両端電圧の上記第1帰還ループのゲインk1を上記抵抗の抵抗値により設定する。
上記制御部は、上記整流部からの上記直流電圧に対する上記インバータ部の上記入力電圧の伝達特性のカットオフ周波数が上記LCフィルタの共振周波数よりも高くなるように、かつ、上記インバータ部の入力電流に対する上記インダクタンス素子に流れる直流電流の伝達特性のカットオフ周波数が上記LCフィルタの共振周波数よりも低くなるように、上記インバータ部を制御することを特徴とする。
上記キャパシタンス素子の容量をC[F]とし、上記インダクタンス素子のインダクタンスをL[H]とし、上記キャパシタンス素子の標準容量をCR[F]とし、上記キャパシタンス素子の標準容量CR[F]および上記LCフィルタの共振周波数により定まる上記インダクタンス素子のインダクタンスをLR[H]とするとき、
L/C < LR/CR
の条件を満たす。
上記キャパシタンス素子の容量をC[F]とし、上記インダクタンス素子のインダクタンスをL[H]とし、上記キャパシタンス素子の標準容量をCR[F]とし、上記キャパシタンス素子の標準容量CR[F]および上記LCフィルタの共振周波数により定まる上記インダクタンス素子のインダクタンスをLR[H]とするとき、
L/C > LR/CR
の条件を満たす。
上記インバータ部の入力電流に対する上記インダクタンス素子に流れる直流電流の伝達特性のカットオフ周波数は、上記単相または多相の交流電圧を上記整流部で整流することにより上記整流部から出力される上記直流電圧に含まれるリップル電圧成分の繰り返し周波数よりも大きい。
上記インバータ部の入力電流に対する上記インダクタンス素子に流れる直流電流の伝達特性のカットオフ周波数は、上記単相または多相の交流電圧を上記整流部で整流することにより上記整流部から出力される上記直流電圧に含まれるリップル電圧成分の繰り返し周波数よりも小さい。
上記インダクタンス素子は、上記整流部の一方の出力端と上記インバータ部の一方の入力端との間に接続されている。
上記インダクタンス素子は、上記交流電圧を供給する交流電源の出力端と上記整流部の入力端との間に接続されている。
図1はこの発明の第1実施形態の電力変換装置の構成図を示している。この電力変換装置は、図1に示すように、三相ダイオードブリッジ回路を構成する6つのダイオードD1~D6からなる整流部の一例としてのダイオードブリッジ11と、三相ブリッジ回路を構成する6つのスイッチング素子S1~S6からなるインバータ部12とを備えている。また、上記電力変換装置は、ダイオードブリッジ11の正極側出力端とインバータ部12の正極側入力端との間に接続されたインダクタンス素子の一例としてのリアクトルLと、上記インバータ部12の入力端間に接続されたキャパシタンス素子の一例としてのコンデンサCとを備えている。上記リアクトルLとコンデンサCでLCフィルタを構成している。さらに、上記電力変換装置は、リアクトルLの両端電圧を検出する電圧検出部101と、上記電圧検出部10からのリアクトルLの両端電圧を表すVL信号に基づいて、インバータ部12の各スイッチング素子S1~S6にPWM信号を出力する制御部100を備えている。
eLa, eLb, eLc:モータ電圧瞬時値
ILa, ILb, ILc:モータ電流実効値
iLa, iLb, iLc:モータ電流瞬時値
PLa, PLb, PLc:モータ瞬時有効電力高調波成分
ωL :モータ駆動角周波数
EL :モータ電圧実効値(三相平衡状態)
IL :モータ電流実効値(三相平衡状態)
PL :瞬時有効電力高調波成分(三相分、直流部瞬時電力に相当)
まず、図3で示した共振抑制系において、ダイオードブリッジ11から出力される直流電圧Vsに対するコンデンサCの両端電圧Vcについての伝達関数G(s)は、
で表され、
とすると、上記式(9)を変形して、次の式(10)で表すことができる。
図6は上記電力変換装置の等価回路を示しており、図7は図1に示す電力変換装置の制御系において、図6に示す直流リンク電流iohに対するリアクトル電流iLh(電源入力)についての伝達特性を求めたものである。図7(A)~図7(C)に示す等価変換を行うことにより、伝達関数が二次系となることが分かる。
とすると、伝達関数G(s)は次の式(12)に示す関係となり、これを変形して次の式(13)で示すことができる。
そこで、上記第1実施形態の電力変換装置の制御系の安定性をより向上できる第2実施形態の電力変換装置について以下に説明する。
単相または多相の交流電圧を直流電圧に整流する整流部と、
上記整流部から出力された上記直流電圧を交流電圧に変換して出力するPWM制御のインバータ部と、
上記インバータ部の入力端間に接続されたキャパシタンス素子と、
上記キャパシタンス素子とでLCフィルタを構成するインダクタンス素子と、
上記インダクタンス素子の両端電圧を検出する電圧検出部と、
上記電圧検出部により検出された上記インダクタンス素子の両端電圧に基づいて、上記インバータ部を制御する制御部と
を備え、
上記LCフィルタは、上記整流部から出力された上記直流電流に含まれるリップル電流成分を通過させ、かつ、上記インバータ部のキャリヤ周波数と同じ周波数の電流成分を減衰させるように、共振周波数が設定されていると共に、
上記制御部は、上記整流部からの上記直流電圧に対する上記インバータ部の入力電圧の伝達特性の減衰係数ζが1よりも大きく設定されることによって、上記伝達特性のカットオフ周波数が上記LCフィルタの共振周波数よりも高くなるように、かつ、上記インバータ部の入力電流に対する上記インダクタンス素子に流れる直流電流の伝達特性のカットオフ周波数が上記LCフィルタの共振周波数よりも低くなるように、上記インバータ部を制御してもよい。
上記キャパシタンス素子の容量をC[F]とし、上記インダクタンス素子のインダクタンスをL[H]とし、上記キャパシタンス素子の標準容量をCR[F]とし、上記キャパシタンス素子の標準容量CR[F]および上記LCフィルタの共振周波数により定まる上記インダクタンス素子のインダクタンスをLR[H]とするとき、
L/C < LR/CR
の条件を満たす。
上記キャパシタンス素子の容量をC[F]とし、上記インダクタンス素子のインダクタンスをL[H]とし、上記キャパシタンス素子の標準容量をCR[F]とし、上記キャパシタンス素子の標準容量CR[F]および上記LCフィルタの共振周波数により定まる上記インダクタンス素子のインダクタンスをLR[H]とするとき、
L/C > LR/CR
の条件を満たす。
上記インバータ部の入力電流に対する上記インダクタンス素子に流れる直流電流の伝達特性のカットオフ周波数は、上記整流部から出力される上記直流電圧に含まれる上記リップル成分の繰り返し周波数よりも大きい。
上記インバータ部の入力電流に対する上記インダクタンス素子に流れる直流電流の伝達特性のカットオフ周波数は、上記整流部から出力される上記直流電圧に含まれる上記リップル成分の繰り返し周波数よりも小さい。
上記インダクタンス素子は、上記整流部の一方の出力端と上記インバータ部の一方の入力端との間に接続されている。
上記インダクタンス素子は、上記交流電圧を供給する交流電源の出力端と上記整流部の入力端との間に接続されている。
11…ダイオードブリッジ
12…インバータ部
13…モータ
14…電流源
L…リアクトル
C…コンデンサ
100…制御部
101…電圧検出部
Claims (13)
- 単相または多相の交流電圧を直流電圧に整流する整流部(11)と、
上記整流部(11)から出力された上記直流電圧を交流電圧に変換して出力するPWM制御のインバータ部(12)と、
上記インバータ部(12)の入力端間に接続されたキャパシタンス素子(C)と、
上記キャパシタンス素子(C)とでLCフィルタを構成するインダクタンス素子(L)と、
上記インダクタンス素子(L)の両端電圧を検出する電圧検出部(101)と、
上記電圧検出部(101)により検出された上記インダクタンス素子(L)の両端電圧に基づいて、上記インバータ部(12)を制御する制御部(100)と
を備え、
上記LCフィルタは、上記整流部(11)から出力された上記直流電流に含まれるリップル電流成分を通過させ、かつ、上記インバータ部(12)のキャリア周波数と同じ周波数の電流成分を減衰させるように、共振周波数が設定されていると共に、
上記制御部(100)は、上記整流部(11)からの上記直流電圧に対する上記インバータ部(12)の入力電圧の伝達特性が、直列接続された位相進み要素と二次遅れ要素による減衰特性になるように、上記インバータ部(12)を制御すると共に、上記整流部(11)からの上記直流電圧に対する上記インバータ部(12)の上記入力電圧の伝達特性の減衰係数が1よりも大きく設定されていることを特徴とする電力変換装置。 - 請求項1に記載の電力変換装置において、
上記制御部(100)は、
上記整流部(11)からの上記直流電圧に対する上記インバータ部(12)の上記入力電圧の伝達特性において、上記電圧検出部(101)により検出された上記インダクタンス素子(L)の両端電圧を、上記インバータ部(12)の入力電流に対して負帰還することにより、上記インダクタンス素子(L)に流れる電流を制御する第1帰還ループと、上記インバータ部(12)の上記入力電圧を、上記インバータ部(12)の入力電流に対して正帰還することにより、上記キャパシタンス素子(C)に流れる電流を制御する第2帰還ループとを有し、
上記整流部(11)からの上記直流電圧に対する上記インバータ部(12)の上記入力電圧の伝達特性と、上記インバータ部(12)の上記入力電流に対する上記インダクタンス素子(L)に流れる直流電流の伝達特性とが夫々予め定められた伝達特性となるように、上記第1帰還ループのゲインk1と上記第2帰還ループのゲインk2とが設定されていることを特徴とする電力変換装置。 - 請求項2に記載の電力変換装置において、
上記制御部(100)は、
上記整流部(11)からの上記直流電圧に対する上記インバータ部(12)の上記入力電圧の伝達特性のカットオフ周波数と、上記インバータ部(12)の入力電流に対する上記インダクタンス素子(L)に流れる直流電流の伝達特性の低域のカットオフ周波数とが同一になるように、上記第1帰還ループのゲインk1と上記第2帰還ループのゲインk2とが設定されていることを特徴とする電力変換装置。 - 請求項2または3に記載の電力変換装置において、
上記制御部(100)は、
上記整流部(11)からの上記直流電圧に対する上記インバータ部(12)の上記入力電圧の伝達特性において、上記インバータ部(12)の上記入力電圧の上記第2帰還ループに、上記単相または多相の交流電圧を上記整流部(11)で整流することにより上記整流部(11)から出力される上記直流電圧に含まれるリップル電圧成分を除去するリップル除去部を有することを特徴とする電力変換装置。 - 請求項2から4までのいずれか1つに記載の電力変換装置において、
上記制御部(100)は、
上記電圧検出部(101)により検出された上記インダクタンス素子(L)の両端電圧の上記第1帰還ループのゲインk1を略ゼロにしていることを特徴とする電力変換装置。 - 請求項2から5までのいずれか1つに記載の電力変換装置において、
上記インダクタンス素子(L)の両端に並列に接続された抵抗(R)を備え、
上記電圧検出部(101)により検出された上記インダクタンス素子(L)の両端電圧の上記第1帰還ループのゲインk1を上記抵抗(R)の抵抗値により設定することを特徴とする電力変換装置。 - 請求項1に記載の電力変換装置において、
上記制御部(100)は、上記整流部(11)からの上記直流電圧に対する上記インバータ部(12)の上記入力電圧の伝達特性のカットオフ周波数が上記LCフィルタの共振周波数よりも高くなるように、かつ、上記インバータ部(12)の入力電流に対する上記インダクタンス素子(L)に流れる直流電流の伝達特性のカットオフ周波数が上記LCフィルタの共振周波数よりも低くなるように、上記インバータ部(12)を制御することを特徴とする電力変換装置。 - 請求項1から7までのいずれか1つに記載の電力変換装置において、
上記キャパシタンス素子(C)の容量をC[F]とし、上記インダクタンス素子(L)のインダクタンスをL[H]とし、上記キャパシタンス素子(C)の標準容量をCR[F]とし、上記キャパシタンス素子(C)の標準容量CRおよび上記LCフィルタの共振周波数により定まる上記インダクタンス素子(L)のインダクタンスをLR[H]とするとき、
L/C < LR/CR
の条件を満たすことを特徴とする電力変換装置。 - 請求項1から7までのいずれか1つに記載の電力変換装置において、
上記キャパシタンス素子(C)の容量をC[F]とし、上記インダクタンス素子(L)のインダクタンスをL[H]とし、上記キャパシタンス素子(C)の標準容量をCR[F]とし、上記キャパシタンス素子(C)の標準容量CRおよび上記LCフィルタの共振周波数により定まる上記インダクタンス素子(L)のインダクタンスをLR[H]とするとき、
L/C > LR/CR
の条件を満たすことを特徴とする電力変換装置。 - 請求項1から9までのいずれか1つに記載の電力変換装置において、
上記インバータ部(12)の入力電流に対する上記インダクタンス素子(L)に流れる直流電流の伝達特性のカットオフ周波数は、上記単相または多相の交流電圧を上記整流部(11)で整流することにより上記整流部(11)から出力される上記直流電圧に含まれるリップル電圧成分の繰り返し周波数よりも大きいことを特徴とする電力変換装置。 - 請求項1から9までのいずれか1つに記載の電力変換装置において、
上記インバータ部(12)の入力電流に対する上記インダクタンス素子(L)に流れる直流電流の伝達特性のカットオフ周波数は、上記単相または多相の交流電圧を上記整流部(11)で整流することにより上記整流部(11)から出力される上記直流電圧に含まれるリップル電圧成分の繰り返し周波数よりも小さいことを特徴とする電力変換装置。 - 請求項1から11までのいずれか1つに記載の電力変換装置において、
上記インダクタンス素子(L)は、上記整流部(11)の一方の出力端と上記インバータ部(12)の一方の入力端との間に接続されていることを特徴とする電力変換装置。 - 請求項1から11までのいずれか1つに記載の電力変換装置において、
上記インダクタンス素子(L)は、上記交流電圧を供給する交流電源の出力端と上記整流部(11)の入力端との間に接続されていることを特徴とする電力変換装置。
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EP2763306A4 (en) | 2015-08-12 |
CN103828212A (zh) | 2014-05-28 |
JP5257533B2 (ja) | 2013-08-07 |
JP2013085444A (ja) | 2013-05-09 |
EP2763306A1 (en) | 2014-08-06 |
US9246398B2 (en) | 2016-01-26 |
US20140328091A1 (en) | 2014-11-06 |
AU2012313585B2 (en) | 2015-04-30 |
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CN103828212B (zh) | 2017-03-08 |
AU2012313585A1 (en) | 2014-04-10 |
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