WO2014141527A1 - モータ制御装置 - Google Patents
モータ制御装置 Download PDFInfo
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- WO2014141527A1 WO2014141527A1 PCT/JP2013/079354 JP2013079354W WO2014141527A1 WO 2014141527 A1 WO2014141527 A1 WO 2014141527A1 JP 2013079354 W JP2013079354 W JP 2013079354W WO 2014141527 A1 WO2014141527 A1 WO 2014141527A1
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- motor
- voltage
- voltage command
- current
- inverter
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
- H02P29/00—Arrangements for regulating or controlling electric motors, appropriate for both AC and DC motors
- H02P29/02—Providing protection against overload without automatic interruption of supply
- H02P29/032—Preventing damage to the motor, e.g. setting individual current limits for different drive conditions
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
- H02P23/00—Arrangements or methods for the control of AC motors characterised by a control method other than vector control
- H02P23/14—Estimation or adaptation of motor parameters, e.g. rotor time constant, flux, speed, current or voltage
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
- H02P27/00—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage
- H02P27/04—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage
- H02P27/06—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage using dc to ac converters or inverters
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
- H02P3/00—Arrangements for stopping or slowing electric motors, generators, or dynamo-electric converters
- H02P3/06—Arrangements for stopping or slowing electric motors, generators, or dynamo-electric converters for stopping or slowing an individual dynamo-electric motor or dynamo-electric converter
- H02P3/18—Arrangements for stopping or slowing electric motors, generators, or dynamo-electric converters for stopping or slowing an individual dynamo-electric motor or dynamo-electric converter for stopping or slowing an ac motor
Definitions
- the present invention relates to a motor control device having means for suddenly decelerating or braking the motor, and more particularly to a control technique for rapidly increasing the motor loss for realizing rapid deceleration or sudden braking.
- the control for increasing the loss is simply referred to as rapid deceleration control.
- Patent Document 2 temporarily stops the increase in voltage amplitude when the current exceeds a predetermined value and overcurrent detection is detected during sudden deceleration control. In some cases, it is not possible to suppress the overshoot of the current only by temporarily stopping the increase. Furthermore, chattering may occur and the current may be greatly disturbed by repeating sudden deceleration control pause due to overcurrent detection and sudden deceleration control restart due to overcurrent state cancellation. In this state, not only overcurrent can be prevented, but also appropriate rapid deceleration control may not be possible. In addition, no consideration has been given to the rate of increase in voltage amplitude.
- the technique disclosed in Patent Document 3 has a problem that the voltage output from the inverter cannot be accurately grasped and cannot be controlled during the rapid motor deceleration control. For this reason, an excessive voltage may be applied to the motor depending on the operating conditions, and an excessive current may be applied to the motor, resulting in fatigue or damage to the motor or inverter.
- the output voltage of the inverter is determined by the product of the voltage of the DC circuit unit and the duty command to the inverter.
- the duty command to the inverter is not changed even during sudden deceleration control, and the change in the output voltage of the inverter is determined by the voltage of the DC circuit section.
- the voltage of this DC circuit section is not limited to the electric circuit constant of the motor, the inertia moment value of the load machine, the smoothing capacitor capacity value, etc. It is generated by a non-linear system that summarizes the phenomenon of charging / discharging of the smoothing capacitor of the inverter, and it is not possible to accurately grasp the amount of change during motor rapid deceleration control. For this reason, the rising change of the DC circuit section becomes remarkable depending on the operating conditions, and the above-mentioned excessive voltage output problem occurs.
- Patent Document 3 also includes a mechanism that detects the current and adjusts the amplitude of the voltage command to suppress overcurrent.
- the DC circuit unit that cannot accurately control the path of the signal to be adjusted Therefore, there is a problem that it is difficult to adjust the gain of the overcurrent suppressing mechanism.
- the motor control device includes: Motor deceleration control means for controlling the deceleration of the motor by inputting a deceleration processing execution command for controlling the deceleration of the motor using an inverter and a voltage command amplitude commanded to the inverter,
- the motor deceleration control means includes Excitation control means for calculating the first voltage command amplitude amplification factor used for control for rapid motor deceleration by inputting the deceleration processing execution command and the voltage signal of the DC circuit portion of the inverter; Input the inverter current amplitude limit value, which is the limit value of the current that can be applied to the inverter, and the motor current signal, and calculate the second voltage command amplitude amplification factor used for control for motor overcurrent suppression.
- An adding means for adding the first voltage command amplitude amplification factor and the second voltage command amplitude amplification factor to output a third voltage command amplitude amplification factor used for motor rapid deceleration control;
- Multiplication means for multiplying and outputting the voltage command amplitude and the third voltage command amplitude amplification factor, And controlling the inverter in accordance with a voltage command amplitude after multiplication by the multiplication means.
- the ratio of the voltage command amplitude amplification is determined based on the voltage of the inverter DC circuit unit.
- current control is performed so that the motor current amplitude is within the limit value, and in parallel with the above-described voltage command amplitude amplification processing, smooth current amplitude suppression is achieved, and stable motor suddenness is achieved.
- deceleration processing there is an effect of realizing deceleration processing.
- Embodiment 1 of this invention It is explanatory drawing of the apparatus which concerns on Embodiment 1 of this invention. It is a figure which shows an example of the calculation method of the 1st voltage command amplitude gain in Embodiment 1 of this invention. It is a figure which shows an example of the calculation method of the 2nd voltage command amplitude gain in Embodiment 1 of this invention. It is a modeling figure of the design of the control system in Embodiment 1 of this invention.
- Embodiment 1 FIG. The first embodiment of the present invention will be described below with reference to the drawings.
- an inverter, a motor, a current detector, etc. are also shown.
- the motor is an induction motor
- V / f control in which the ratio of the frequency command to the motor and the voltage command amplitude is constant will be described as an example.
- other types of motors and control systems can be applied without any problem.
- a diode converter that cannot process regenerative power is often used for the DC power source 1 that outputs DC power.
- the inverter 3 converts the DC power from the DC power source 1 into AC power having an amplitude and frequency suitable for driving the motor 5 and supplies the AC power.
- the smoothing capacitor 2 smoothes the voltage in the DC circuit section between the DC power source 1 and the inverter 3.
- the motor control means 6 (the larger one of the rectangular frames shown by dotted lines in the figure) used in the present invention will be described.
- the frequency command 8 output from the frequency command generation means 7 is input to the V / f conversion means 9 and converted into a voltage command amplitude 10.
- the motor deceleration control means 14 (the smaller one of the rectangular frames indicated by dotted lines in the figure) increases the voltage command amplitude 10 when the motor is suddenly decelerated with respect to the voltage command amplitude 10 to increase the voltage command. Compensation processing for outputting the amplitude 17 is performed, but this is only when the motor is suddenly decelerated. Normally, no compensation processing is performed. At that time, the voltage command amplitude 10 and the voltage command amplitude 17 have the same value. Become.
- a pulse width modulation means (hereinafter abbreviated as PWM means) 12 receives a voltage command amplitude 17 and a frequency command 8 to generate a voltage command, and also outputs a voltage signal from the smoothing capacitor 2 (“voltage signal of the inverter DC circuit section”). The same is true of “.” The same applies hereinafter. 11 is converted into a duty command, and further PWM processing such as triangular wave comparison is performed, and a switching command 13 is output.
- the voltage value obtained by averaging the output voltage of the inverter 3 over one period of the triangular wave coincides with the voltage command.
- the duty command indicates the ON / OFF ratio of the switching element of the inverter 3.
- the output terminal voltage of the inverter 3 outputs both the high potential side voltage and the low potential side voltage of the DC circuit section by the action of the switching element. That is, the previous duty command indicates the time ratio of the output of these two voltage values.
- the inverter 3 outputs a desired voltage in a pseudo manner by changing the time ratio between the two voltage values. At this time, if the voltage of the DC circuit unit can be grasped, the time ratio can be accurately determined.
- the average output voltage in a section of about one triangular wave period can be matched with the voltage command.
- f * corresponds to the frequency command 8.
- ⁇ is a voltage command phase
- Vamp * is a voltage command amplitude 17
- Vu * is a U-phase voltage command
- Vv * is a V-phase voltage command
- Vw * is a W-phase voltage command
- Du * is a U-phase duty command
- Dv * Indicates a V-phase duty command
- Dw * indicates a W-phase duty command.
- the inverter 3 performs a power conversion operation based on the switching command 13.
- the operation of each component shown above is very general and will not be described in detail.
- the motor deceleration control means 14 at the time of motor rapid deceleration control will be described in detail.
- a voltage command amplification mechanism for rapid motor deceleration will be described.
- the voltage command amplitude amplification factor A1 (14b) before filtering at the time of sudden deceleration control is calculated by the voltage command amplitude amplification factor setting function 14a using the voltage signal 11 of the inverter DC circuit unit.
- the voltage command amplitude gain 14c indicates a pre-filtering voltage command amplitude gain A2 when the rapid deceleration control is not performed, and is 1.
- the selection unit 14d selects the pre-filtering voltage command amplitude amplification factor A1 (14b) when the deceleration process execution command 16 is input and the rapid deceleration control is performed, and the pre-filtering voltage when the rapid deceleration control is not performed.
- the command amplitude amplification factor A2 (14c) is selected and output.
- the deceleration processing execution command 16 is output from the deceleration processing execution command output means 26.
- the deceleration processing execution command output means 26 makes such a determination and outputs a deceleration processing execution command 16.
- FIG. since it is not the essence of this invention about a specific judgment system and the detail, description is abbreviate
- the low-pass filter (LPF) 14e suppresses a sudden change in the voltage command amplitude amplification factor output from the selection unit 14d due to the start of the motor rapid deceleration control by the processing of the selection unit 14d, and the first voltage command It has the function of outputting the amplitude amplification factor (14f) and has the effect of suppressing disturbances such as overshoot of the motor current as described in the problem to be solved by the invention.
- the cutoff frequency of the low-pass filter is set to a value that can sufficiently remove the resonance frequency component of the secondary transfer function from the voltage of the motor to the current, any order may be used.
- the inverter DC circuit is calculated by calculating the voltage command amplitude amplification factor based on the voltage signal 11 of the inverter DC circuit section by the excitation control means 14o indicated by the one-dot chain line on the left side of FIG. 1 as a whole.
- Motor rapid deceleration control according to the voltage of the part can be realized. For example, when the DC circuit section voltage is close to the overvoltage level and there is no margin, the voltage command amplitude amplification factor is quickly increased, the motor current is increased to increase the regenerative energy consumption in the motor, and the overvoltage in the DC circuit section is prevented. .
- the operating voltage range is determined for the components constituting the inverter, and such overvoltage causes fatigue and destruction of the components. By preventing overvoltage, it is possible to prevent deterioration and breakage of the inverter components.
- FIG. 2 shows an example of the configuration of the voltage command amplitude amplification factor setting function 14a at this time.
- the horizontal axis corresponds to the voltage Vdc (11) of the inverter DC circuit section to be input, and the vertical axis corresponds to the pre-filtering voltage command amplitude amplification factor A1 (14b) to be output.
- Vdc exceeds the threshold voltage Vth
- the voltage command amplitude amplification factor is increased.
- the voltage command amplitude 17 can be increased rapidly in accordance with the voltage Vdc (11), and the above-described overvoltage can be ensured. There is an effect that can be prevented.
- a current amplitude signal 14h is calculated from the detected current signal 15 output from the current detecting means 4 by the current amplitude calculating means 14g.
- iu, iv, and iw correspond to the detected current signal 15.
- iamp corresponds to the current amplitude signal 14h.
- i ⁇ , i ⁇ , and iamp indicate the ⁇ direction component of the current on the two-phase stationary coordinates ( ⁇ , ⁇ ), the ⁇ direction component of the current on the two-phase stationary coordinates ( ⁇ , ⁇ ), and the current amplitude, respectively. .
- the PI controller 14j inputs the difference between the current amplitude signal 14h and the current amplitude limit value 14i and outputs the second voltage command amplitude amplification factor (14k).
- the purpose of the PI controller is to prevent motor overcurrent.
- the PI controller has an upper limit of 0 at the integrator and PI controller output so that it does not operate below the current limit value, and the current amplitude signal 14h is greater than the current amplitude limit value 14i. When it is small, the second voltage command amplitude amplification factor (14k) is zero.
- the configuration of the PI controller is as shown in FIG. As described above, since the control for directly limiting the current amplitude is performed using the PI controller, there is a sure overcurrent suppressing effect.
- the first voltage command amplitude gain (14f) and the second voltage command amplitude gain (14k) obtained as described above are added by the adder 14l, and the third voltage command amplitude gain ( 14m) is obtained.
- the voltage command amplitude 17 is obtained by multiplying the third voltage command amplitude amplification factor (14 m) by the voltage command amplitude 10.
- the time constant order of the electric circuit system of the motor and the time constant order of the mechanical torque transmission system are greatly different.
- the transfer characteristic from the applied voltage of the motor to the motor current is a first-order lag characteristic, and when the induction motor parameters shown in Non-Patent Document 1 are used, the time constant Tcst_ele of the current change is expressed by the equation (11).
- the primary resistance and primary leakage inductance are 0.00853 [sec]. This shows the time until the motor current reaches approximately 63% of its saturation value when a step voltage is applied to the electric circuit of the motor.
- the frequency transfer characteristic from the motor torque to the rotational speed of the motor is an integral characteristic.
- the time Tcst_mec until accelerating to about 63% of the rated speed is 0.11236 [ sec].
- ⁇ is a leakage coefficient
- L s is a primary inductance
- R s is a primary resistance
- W r is a rated speed
- T q is a rated torque
- J m is a mechanical moment of inertia value.
- the motor speed and frequency command of the motor can be handled as constants because of the slow time change of the system when viewed from the electric circuit system.
- FIG. 4 shows the details of the modeling, and is a model showing the minute fluctuation amount of each physical quantity in the vicinity of a certain operating point.
- the motor rotation speed Wrm0 and the voltage Vdc0 of the smoothing capacitor 2 in the inverter DC circuit section are used as operating points.
- the Vdc0 indicates the same physical quantity as the voltage Vdc (11) of the inverter DC circuit unit, but for the convenience of analysis, it is necessary to indicate a value near the operating point, and the subscript 0 is added for the distinction.
- the control system is designed based on FIG. 4 given the same reference numerals as those in FIG.
- the purpose is to analyze each physical quantity and signal minute fluctuation amount in a motor, an inverter, or a control system.
- the inverter 3 does not have time characteristics (transient characteristics) except for the smoothing capacitor 2 of the DC circuit section, and does not have an essential influence on the analysis in FIG.
- the inverter 3 is omitted as one that outputs a voltage according to the voltage command.
- the expression “small fluctuation amount” is added in parentheses.
- means a ⁇ b> 1 surrounded by a dotted rectangle indicates the motor current control means 14 p in the motor deceleration control means 14.
- the current amplitude limit value 14i corresponds to a target command value in the PI controller 14j.
- the stability of the control system can be ensured by designing the control system so that the main signal to be handled is a minute fluctuation amount and each signal in the control feedback loop converges to zero.
- the current amplitude limit value 14i which is a target command, is not a signal that causes minute fluctuations, and is simply zero here.
- the set value of the target command has no essential influence on the control system design.
- FIG. 4 (a) means a2 surrounded by a dotted rectangle indicates multiplication of the third voltage command amplification factor (small fluctuation amount) 14m and the voltage command amplitude 10 by V / f control.
- an induction motor is described as an example of a connection form to an inverter.
- a circuit model 18 of the induction motor is introduced in FIG. 4.
- the circuit equation of the induction motor in vector notation for the circuit model 18 of the induction motor is expressed by equation (13).
- I and J are represented by the following formula (14).
- means a5 surrounded by a dotted rectangle indicates the excitation control means 14o in the motor deceleration control means 14.
- the configuration is such that the voltage signal 11 (small fluctuation amount) of the inverter DC circuit section is fed back, the difference is taken with respect to the value of the predetermined command (14q), and the first voltage command amplification factor 14f (small fluctuation amount) is output.
- the command 14q is a command for the voltage signal 11 (small fluctuation amount) of the inverter DC circuit unit.
- the value is simply described here as zero.
- FIG. 4B is a diagram showing the result of linear approximation of FIG.
- the frequency command 8 can be regarded as a constant value at a location corresponding to the means a2 surrounded by a dotted rectangle, so the product of the frequency command f * at the start of the motor rapid deceleration control and the V / f coefficient.
- the gain is 23.
- the frequency corresponding to the means a3 enclosed by the dotted rectangle is assumed to be a frequency on the order of the time constant of the electric circuit system. It becomes very small and can be ignored. Accordingly, the gain 24 is the product of the motor rotation speed Wrm0 and the torque constant Kt at the start of the motor rapid deceleration control.
- the smoothing capacitor has a sufficiently large capacitance, the charging voltage of the smoothing capacitor at the start of the motor rapid deceleration control, that is, the inverter DC circuit
- the voltage Vdc0 of the part is often sufficiently larger than the voltage signal 11 (small fluctuation amount) of the inverter DC circuit part. Therefore, the division unit for the voltage signal 11 (a small fluctuation amount) is substantially unnecessary, and the voltage model of the DC circuit unit is a simple integrator and gain as shown in the rightmost block 25 in FIG. It becomes a combination.
- FIG. 4A the current amplitude signal (minute fluctuation amount) 14h fed back to the motor overcurrent suppression mechanism in the motor deceleration control means 14 of the means a1 surrounded by a dotted rectangle is a minute fluctuation amount. This is almost equivalent to the signal (small fluctuation amount) 15.
- FIG. 4A can be linearly approximated as shown in FIG.
- FIG. 4B is a model that handles minute fluctuations, and is a linear approximation in the vicinity of a predetermined operating point of the model shown in FIG.
- a classically used transfer function-based design theory can be applied.
- the open loop transfer characteristic is calculated from the X point to the Y point in FIG. 4B, and the gain of the PI controller 14j is designed so that the gain margin and phase margin at this time are within appropriate predetermined ranges. Or finely adjusting the cutoff frequency of the low-pass filter 14e.
- the motor deceleration control means 14 has a good view of the entire system, and various quantities such as the electric circuit constant of the motor, the moment of inertia of the load machine, and the smoothing capacitor capacity value If it is possible to grasp, there is an advantage that it is easy to design and adjust.
- the voltage command amplitude amplification factor A1 (Ga1) is configured to increase in a linear function when the threshold voltage Vth is exceeded. As described above, the voltage command is promptly increased and the motor loss is increased to suppress the overvoltage of the DC circuit unit. In addition, the gain of the control system can be easily designed.
- the reciprocal of the DC circuit section voltage Vdc0 is inserted as a coefficient. Is done. That is, the open loop transfer characteristic changes from the X point to the Y point depending on the value of the DC circuit section voltage. As shown in FIG.
- the voltage command amplitude amplification factor A1 is increased according to the DC circuit unit voltage by 14a (voltage command amplitude amplification factor setting function) in FIG. 4B, so that Vdc0 of the integrator is increased.
- the reciprocal characteristic can be canceled.
- the open loop characteristics in FIG. 4B are kept constant even when the DC circuit section voltage changes, and as a result, there is an effect that the gain adjustment of the control system can be facilitated.
- the motor rotation speed (indicated as Wrm0 in FIG. 4), which is a reference for designing the control system, may be a value at the start of the motor rapid deceleration control as described above. This is because the motor rotation energy of the motor is large at the start of sudden motor deceleration and the regenerative energy to the inverter is large.If nothing is devised, there is a high possibility of overvoltage and overcurrent. This is because the overvoltage and inverter overcurrent of the DC circuit section can be prevented if designed. For this reason, the maximum rotational speed specification value of the motor may be used as a design criterion, and in that case, more reliable overvoltage and overcurrent can be prevented.
- the motor rotation speed can be substituted by the frequency command 8.
- the voltage Vdc0 of the inverter DC circuit section may be a value at the start of the motor rapid deceleration control.
- the control system design in the motor deceleration control means 14 does not use the moment of inertia value (Jm) that is a parameter of the mechanical torque transmission system. Therefore, there is a merit that adjustment work corresponding to the moment of inertia value which is necessary in the technique shown in Patent Document 3 is not required.
- the inverter determines the voltage command amplification ratio based on the voltage of the inverter DC circuit unit.
- current control is performed so that the motor current amplitude is within the limit value, and in parallel with the above voltage command amplification processing, smooth current amplitude suppression is achieved, and stable motor rapid deceleration There is an effect of realizing processing.
- Embodiment 2 FIG.
- the motor rotation speed at the start of the motor rapid deceleration control and the voltage value of the DC circuit unit are applied to the design, but they are appropriately changed according to the motor rotation speed. It is good also as a structure.
- the product (24) of the torque constant Kt and the motor rotation speed Wrm0 is a direct gain, the gain to be controlled decreases when the motor rotation speed decreases.
- the voltage Vdc0 of the inverter DC circuit section is appropriately changed according to the value at the time of the motor rapid deceleration control, thereby preventing the overvoltage of the DC circuit section of the inverter 3 and the overcurrent of the inverter, and promptly driving the motor suddenly. Deceleration control can be achieved.
- the circuit model 18 of the induction motor has an electrical angular frequency ⁇ as a parameter as shown in the equation (17).
- the electrical angular frequency ⁇ corresponds to an addition value of a value obtained by multiplying the slip frequency ⁇ se and the motor rotation speed by the number of motor pole pairs. Therefore, the value of the electrical angular frequency ⁇ changes according to the motor rotation speed, and the frequency transfer characteristic of the circuit model 18 of the induction motor expressed by the equation (17) changes according to the motor rotation speed. For this reason, by quickly changing the setting of the control system according to the motor rotation speed or frequency command, rapid motor rapid deceleration control can be achieved while preventing overvoltage of the DC circuit portion of the inverter 3 and overcurrent of the inverter. .
- the motor is an induction motor in particular, but the motor deceleration control means 14 according to the present invention can be applied to other types of motors.
- the motor deceleration control means 14 according to the present invention can be applied to other types of motors.
- the secondary magnetic flux is established by the permanent magnet and does not change with time.
- the primary (stator side) circuit model structure of the permanent magnet synchronous motor is the same as that of the induction motor, it is expressed by equation (18) based on equation (17).
- R is the armature resistance of the motor
- L is the armature inductance of the motor.
- Embodiment 4 the operation of increasing the motor loss is performed for the rapid deceleration control of the motor shown in the motor deceleration control means 14, but the following usage method can also be used. That is, the warm-up operation of the motor can be performed by taking advantage of the feature of rapidly increasing the motor loss.
- the induction motor parameter values that vary depending on the motor temperature, such as the primary resistance value and the secondary resistance value of the induction motor, are used for slip frequency calculation and secondary magnetic flux estimation. Also in a permanent magnet synchronous motor or the like, the primary resistance value is a parameter required for construction of a sensorless control system.
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Abstract
Description
また、電圧振幅の増加割合については何ら考慮がなされておらず、インバータ直流回路部の電圧が高く回生エネルギーを受け入れる余地がない場合、モータ損失増加が不十分となり、回生エネルギーが平滑コンデンサに蓄積してインバータ直流回路部の過電圧が発生する場合があった。
インバータを用いてモータを減速制御する減速処理実施指令と前記インバータに指令する電圧指令振幅とを入力して前記モータを減速制御するモータ減速制御手段を有し、
前記モータ減速制御手段は、
前記減速処理実施指令と、前記インバータの直流回路部の電圧信号と、を入力して、モータ急減速のための制御に用いる第一の電圧指令振幅増幅率を計算する励磁制御手段、
前記インバータに印加可能な電流の制限値であるインバータ電流振幅制限値と、モータ電流信号と、を入力して、モータの過電流抑制のための制御に用いる第二の電圧指令振幅増幅率を計算する電流制御手段、
前記第一の電圧指令振幅増幅率と、前記第二の電圧指令振幅増幅率と、を加算して、モータ急減速制御に用いる第三の電圧指令振幅増幅率を出力する加算手段、
前記電圧指令振幅と、前記第三の電圧指令振幅増幅率と、を乗算し出力する乗算手段、
を備え、前記乗算手段により乗算した後の電圧指令振幅に従って前記インバータを制御するものである。
以下、図を用いて本発明の実施の形態1を説明する。説明の都合上、インバータやモータ、電流検出器なども併記する。ここではモータを誘導電動機とし、モータへの周波数指令と電圧指令振幅の比を一定とするV/f制御を例にとり説明するが、他の種類のモータや制御系などでも問題なく適用できる。
ここで、θは電圧指令位相、Vamp*は電圧指令振幅17、Vu*はU相電圧指令、Vv*はV相電圧指令、Vw*はW相電圧指令、Du*はU相デューティ指令、Dv*はV相デューティ指令、Dw*はW相デューティ指令を示す。
また、インバータ3はこのスイッチング指令13に基づいて電力変換動作を行う。以上に示した各構成要素の動作はごく一般的なものであり、詳細な説明は省略する。
ここで、iα、iβ、iampは、各々、2相静止座標(α、β)上の電流のα方向成分、2相静止座標(α、β)上の電流のβ方向成分、電流振幅を示す。
ここで、σはもれ係数、Lsは一次インダクタンス、Rsは一次抵抗、Wrは定格速度、Tqは定格トルク、Jmは機械慣性モーメント値である。なお(12)式の計算において、定格速度は角周波数の単位([rad/sec])に変換している。このため、モータの機械速度や周波数指令は電気回路系から見ると系の時間変化の遅さのため、定数として取り扱うことができる。これを利用することでモータ減速制御手段14やモータや直流回路部電圧などを線形近似してモデリングすることができ、容易に制御系の設計が実現できる。
ここで、電流振幅制限値14iはPI制御器14jにおける目標指令値に相当する。取り扱う主な信号が微小変動量であり、制御フィードバックループ内の各信号がゼロに収束するような制御系の設計を行えば、制御系の安定が確保できる。また目標指令である電流振幅制限値14iは微小変動が発生するような信号ではないため、ここでは単にゼロとしている。なお、この目標指令の設定値は制御系の設計に対して本質的な影響は与えない。
ここで、I、Jは、次式(14)で表される。
また、Rs:1次抵抗、σ:もれ係数、
Ls:1次インダクタンス、M:相互インダクタンス、p:微分演算子
Lr:2次インダクタンス、Rr:2次抵抗、Vs:1次電圧、is:1次電流、
Φr:2次磁束、ω:電気角周波数、ωse:すべり周波数、である。
また、誘導電動機の2次磁束をd軸とすると、誘導電動機の電圧の主成分はd軸と直交するq軸となる場合が多く、2次磁束が確立している状態で電圧振幅信号(微小変動量)17を調整することはq軸方向の電圧を調整することに相当する。これに伴い電流(微小変動量)15もq軸の成分となる。
なお図2において電圧指令振幅増幅率A1(Ga1)は閾値電圧Vthを超えると一次関数的に増加させる構成をとっている。前記したように速やかな電圧指令の増加を行い、モータ損失を増加させて直流回路部の過電圧を抑制する効果があるが、その他に制御系のゲイン設計を容易にする効果を持つ。モータおよび機械負荷のトルク伝達系を示す図4(b)のY点手前には直流回路部電圧の伝達特性を模擬する積分器があるが、ここでは係数として直流回路部電圧Vdc0の逆数が挿入される。すなわち、直流回路部電圧の値により、X点からY点までオープンループ伝達特性が変化することになる。図2に示すように、図4(b)における14a(電圧指令振幅増幅率設定関数)により、電圧指令振幅増幅率A1を直流回路部電圧に応じて上昇させることで、前記積分器におけるVdc0の逆数の特性をキャンセルできる。これにより直流回路部電圧が変化しても図4(b)におけるオープンループ特性は一定に保たれるので、結果として制御系のゲイン調整を容易できる効果がある。
従って特許文献3に示す技術で必要となる、慣性モーメント値に応じた調整作業が不要となるメリットがある。
実施の形態1では、図4(b)に示すようにモータ急減速制御開始時のモータ回転速度や、直流回路部の電圧値を設計に適用したが、モータの回転速度に応じて適宜変更する構成としてもよい。特に図4(b)に示すように、トルク定数Ktとモータ回転速度Wrm0の積(24)が直達ゲインとなるため、モータ回転速度が低下した場合に制御対象のゲインが低下する。インバータ直流回路部の電圧Vdc0についても、同様にモータ急減速制御時の値に応じて適宜変更することで、インバータ3の直流回路部の過電圧やインバータの過電流を防止しつつ、速やかなモータ急減速制御が達成できる。
実施の形態1では特にモータを誘導電動機としたが、他の種類のモータでも本発明によるモータ減速制御手段14は適用できる。ここ永久磁石同期電動機における、図4の誘導電動機の回路モデル18に相当するモデルを考えると、永久磁石同期モータの場合、2次磁束は永久磁石により確立して時間変化しない。また永久磁石同期モータの1次側(固定子側)回路モデル構造は誘導電動機と同じであるため、(17)式をベースに(18)式で表現される。
ここで、R:モータの電機子抵抗、L:モータの電機子インダクタンス、である。
実施の形態1ではモータ減速制御手段14に示したモータの急減速制御のため、モータ損失を増加させる動作を行ったが、次のような使用方法もできる。すなわちモータ損失を急増させるという特徴を生かしてモータの暖機運転を実施することができる。誘導電動機では、すべり周波数計算や2次磁束推定などに、誘導電動機の1次抵抗値や2次抵抗値など、モータ温度によって変化するパラメータ値を用いる。また永久磁石同期モータなどでも、1次抵抗値はセンサレス制御系の構築などに要するパラメータとなる。
なお、本発明は、その発明の範囲内において、各実施の形態を自由に組合わせたり、各実施の形態を適宜、変形、省略することが可能である。
5 モータ、6 モータ制御手段、7 周波数指令発生手段、
8 周波数指令、9 V/f変換手段、10 電圧指令振幅(補償前)、
11 インバータ直流回路部の電圧信号、12 PWM手段、
13 スイッチング指令、14 モータ減速制御手段、
14a 電圧指令振幅増幅率設定関数、
14b フィルター処理前電圧指令振幅増幅率(減速制御時)A1、
14c フィルター処理前電圧指令振幅増幅率(非減速制御時)A2、
14d 選択手段、14e ローパスフィルタ、
14f 第一の電圧指令振幅増幅率、14g 電流振幅演算手段、
14h 電流振幅信号、14i 電流振幅制限値、14j PI制御器、
14k 第二の電圧指令振幅増幅率、14l 加算器、
14m 第三の電圧指令増幅率、14n 乗算器、
14o 励磁制御手段 、14p モータ電流制御手段、
14q 直流回路部電圧信号(微小変動量)指令、
15 検出電流信号、16 減速処理実施指令、
17 電圧指令振幅(補償後)、18 誘導電動機の回路モデル、
19 機械モデル、20 モータ回転速度(微小変動量)、
21 モータ電力(微小変動量)、
22 平滑コンデンサ電流(微小変動量)、23 ゲイン、24 ゲイン、
25 直流回路部の電圧モデル、26 減速処理実施指令出力手段。
Claims (7)
- インバータを用いてモータを減速制御する減速処理実施指令と前記インバータに指令する電圧指令振幅とを入力して前記モータを減速制御するモータ減速制御手段を有し、
前記モータ減速制御手段は、
前記減速処理実施指令と、前記インバータの直流回路部の電圧信号と、を入力して、モータ急減速のための制御に用いる第一の電圧指令振幅増幅率を計算する励磁制御手段、
前記インバータに印加可能な電流の制限値であるインバータ電流振幅制限値と、モータ電流信号と、を入力して、モータの過電流抑制のための制御に用いる第二の電圧指令振幅増幅率を計算する電流制御手段、
前記第一の電圧指令振幅増幅率と、前記第二の電圧指令振幅増幅率と、を加算して、モータ急減速制御に用いる第三の電圧指令振幅増幅率を出力する加算手段、
前記電圧指令振幅と、前記第三の電圧指令振幅増幅率と、を乗算し出力する乗算手段、
を備え、前記乗算手段により乗算した後の電圧指令振幅に従って前記インバータを制御することを特徴とするモータ制御装置。 - 前記励磁制御手段は、
前記減速処理実施指令により減速制御を実施する場合には、前記インバータの直流回路部の電圧信号の関数の出力となる減速用のフィルター処理前電圧指令増幅率を選択し、
減速制御を実施しない場合には、非減速制御時用のフィルター処理前電圧指令増幅率を選択するとともに、
選択後のフィルター処理前電圧指令振幅増幅率にローパスフィルタ処理を行って、前記第一の電圧指令振幅増幅率として出力することを特徴とする請求項1に記載のモータ制御装置。 - 前記電流制御手段は、
モータ電流信号の振幅を計算する電流振幅計算手段、
前記電流振幅計算手段で計算された電流振幅信号と、前記インバータ電流振幅制限値との差分を入力するPI制御手段、を備え、
前記PI制御手段の出力を前記第二の電圧指令振幅増幅率として出力することを特徴とする請求項1に記載のモータ制御装置。 - 前記励磁制御手段、及び前記電流制御手段の制御系の設定は、
モータ減速制御開始時のモータ回転速度または周波数指令に基づいて実施されることを特徴とする請求項2または3に記載のモータ制御装置。 - 前記励磁制御手段、及び前記電流制御手段の制御系の設定は、
モータの最高回転速度仕様値に基づいて実施されることを特徴とする請求項2または3に記載のモータ制御装置。 - 前記励磁制御手段、及び前記電流制御手段の制御系の設定は、
モータ回転速度または周波数指令に基づいて前記モータの減速制御中に逐次実施されることを特徴とする請求項2または3に記載のモータ制御装置。 - モータ減速手段を用いてモータ損失を増加させ前記モータの暖機運転を実施することを特徴とする請求項1~6のいずれか1項に記載のモータ制御装置。
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