JP2008526122A - Ｍｉｍｏ構成のための性能ベースのランク予測方法および装置 - Google Patents

Ｍｉｍｏ構成のための性能ベースのランク予測方法および装置 Download PDF

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JP2008526122A
JP2008526122A JP2007548510A JP2007548510A JP2008526122A JP 2008526122 A JP2008526122 A JP 2008526122A JP 2007548510 A JP2007548510 A JP 2007548510A JP 2007548510 A JP2007548510 A JP 2007548510A JP 2008526122 A JP2008526122 A JP 2008526122A
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サムパス、ヘマンス
カドウス、タマー
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    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B7/00—Radio transmission systems, i.e. using radiation field
    • H04B7/02—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas
    • H04B7/04—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas
    • H04B7/0413—MIMO systems
    • H04B7/0417—Feedback systems
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L1/00—Arrangements for detecting or preventing errors in the information received
    • H04L1/02—Arrangements for detecting or preventing errors in the information received by diversity reception
    • H04L1/06—Arrangements for detecting or preventing errors in the information received by diversity reception using space diversity
    • H04L1/0618—Space-time coding
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B17/00—Monitoring; Testing
    • H04B17/20—Monitoring; Testing of receivers
    • H04B17/24—Monitoring; Testing of receivers with feedback of measurements to the transmitter
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B7/00—Radio transmission systems, i.e. using radiation field
    • H04B7/02—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas
    • H04B7/04—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas
    • H04B7/0413—MIMO systems
    • H04B7/0456—Selection of precoding matrices or codebooks, e.g. using matrices antenna weighting
    • H04B7/0486—Selection of precoding matrices or codebooks, e.g. using matrices antenna weighting taking channel rank into account
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B7/00—Radio transmission systems, i.e. using radiation field
    • H04B7/02—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas
    • H04B7/04—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas
    • H04B7/06—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station
    • H04B7/0613—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station using simultaneous transmission
    • H04B7/0615—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station using simultaneous transmission of weighted versions of same signal
    • H04B7/0619—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station using simultaneous transmission of weighted versions of same signal using feedback from receiving side
    • H04B7/0621—Feedback content
    • H04B7/063—Parameters other than those covered in groups H04B7/0623 - H04B7/0634, e.g. channel matrix rank or transmit mode selection
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B7/00—Radio transmission systems, i.e. using radiation field
    • H04B7/02—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas
    • H04B7/04—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas
    • H04B7/06—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station
    • H04B7/0613—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station using simultaneous transmission
    • H04B7/0615—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station using simultaneous transmission of weighted versions of same signal
    • H04B7/0619—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station using simultaneous transmission of weighted versions of same signal using feedback from receiving side
    • H04B7/0621—Feedback content
    • H04B7/0632—Channel quality parameters, e.g. channel quality indicator [CQI]
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L5/00—Arrangements affording multiple use of the transmission path
    • H04L5/003—Arrangements for allocating sub-channels of the transmission path
    • H04L5/0044—Arrangements for allocating sub-channels of the transmission path allocation of payload

Abstract

【課題】ＭＩＭＯ構成のための性能ベースのランク予測方法および装置。
【解決手段】低複雑性のＭＭＳＥ受信器およびランク予測を有する単一符号語（ＳＣＷ）構成の性能は継続的な干渉相殺（ＳＩＣ）を有する複数符号語構成と同種である。ランク予測の方法は各トーンについてレイヤ伝送に対応するＭＩＭＯチャネルマトリクスを計算し、ＭＩＭＯチャネルマトリクスに基づいて各トーンについて信号対雑音比（ＳＮＲ）を計算し、各レイヤ伝送について効果的なＳＮＲを発生するように各トーンについてＳＮＲをマップし、各レイヤ伝送について効果的なＳＮＲ未満のＳＮＲ閾値を有する最高のパケットフォーマット（ＰＦ）を選択し、各レイヤ伝送について選択された最高のパケットフォーマットに基づいて全体のスペクトル効率を最大化し、そして全体のスペクトル効率を最大化することに基づいてランクを選択することを含む。

Description

本発明は一般に通信に関し、そしてより詳しくはマルチチャネル、例えば、複数入力複数出力（ＭＩＭＯ；multiple-input multiple-output）、直交周波数分割多重化（ＯＦＤＭ；orthogonal frequency division multiplexing）通信システム、を介して伝送されるべきデータストリームの分布を決定するための技術に関する。
無線通信システムでは、送信器からのＲＦ変調信号は多数の伝播パスを介して受信器に到達できる。伝播パスの特性は典型的にフェージングやマルチパスのような多数のファクタによって時間中変化する。有害なパス効果に対してダイバーシティ(diversity)を提供して性能を改善するために、複数の送信および受信アンテナが使用されてもよい。もしも送信および受信アンテナの間の伝播パスがリニアに別々である（即ち、１つのパス上の伝送が他のパス上の伝送の線形結合として形成されない）ならば、それは一般に少なくともある範囲で真実であるが、その時データ伝送を正確に受信する可能性はアンテナ数が増加するほど増加する。一般に、送信および受信アンテナ数が増加するほどダイバーシティは増加し、そして性能はよくなる。
複数入力複数出力（ＭＩＭＯ）通信システムはデータ伝送用の複数の（ＮT）送信アンテナおよび複数の（ＮR）受信アンテナを使用する。ＮT送信およびＮR受信アンテナによって形成されたＭＩＭＯチャネルは、ＮS≦最小{ＮT，ＮR}を有する、ＮS独自チャネルに分解されてもよい。ＮS独自チャネルの各々はまたＭＩＭＯチャネルの空間サブチャネル（または送信チャネル）と呼ばれてもよく、そして単位次元に対応する。ＭＩＭＯシステムは、もしも複数の送受信アンテナによって作り出された追加の次元が使用されれば改善された性能（例えば、増加した送信容量）を提供できる。
フルランク(full-rank)ＭＩＭＯチャネルに関して、独自のデータストリームはＮT送信アンテナ、ここでＮS＝ＮT≦ＮR、の各々から送信される。送信データストリームは種々のチャネル条件（例えば、種々のフェージングやマルチパス効果）を経験でき、そして与えられた量の送信パワーについて種々の信号対雑音および干渉比（signal-to-noise-and-interference ratio）を達成できる。さらに、もしも継続的な干渉相殺処理（interference cancellation processing）が（下記された）送信データストリームを再生するために受信器で使用されれば、その時種々のＳＮＲは、その中でデータストリームが再生される特定の命令次第でこのデータストリームのために達成されることができる。結局、種々のデータレートは、それらの達成されたＳＮＲ次第で、種々のデータストリームによってサポートされることができる。チャネル状態は典型的に時間と共に変化するので、各データストリームによってサポートされたデータレートも時間と共に変化する。
ＭＩＭＯ構成は２つの動作モード−単一符号語（ＳＣＷ;single code word）および複数符号語（ＭＣＷ;multiple-code word）−を有する。
ＭＣＷモードでは、送信器は各空間レイヤ上に別々に、多分種々のレートで、送信されたデータを符号化することができる。受信器は次のように：第１のレイヤを符号化し、そしてその後この符号化された第１のレイヤを再符号化して“推定チャネル”と多重化した後に受信信号からそれの貢献を引き去り、その後第２のレイヤを復号する等の動作をする継続的な干渉相殺（ＳＩＣ;successive interference cancellation）アルゴリズムを使用する。この“オニオンピーリング(onion-peeling)”アプローチは、各継続的に復号されたレイヤが信号対雑音比（ＳＮＲ;signal-to-noise ratio）を調べ、それからより高いレートをサポートできることを意味する。誤り伝搬がない時は、ＳＩＣを有するＭＣＷ構成はキャパシティを達成する。この構成の不便なことは各空間レイヤのレートを“管理すること(managing)”の負担−（ａ）増加したＣＱＩフィードバック（各レイヤごとに１つのＣＱＩ）；（ｂ）増加したＡＣＫ／ＮＡＣＫメッセージング（各レイヤごとに１つ）；（ｃ）各レイヤは種々の伝送で終結することができるのでハイブリッドＡＲＱ（ＨＡＲＱ）内の複雑化；（ｄ）ＳＩＣの性能感度対増加したドップラ、および／または低ＳＮＲを有するチャネル推定エラー；および（ｅ）各継続的なレイヤは前のレイヤが復号されるまで復号されることができないので増加した復号化待ち時間条件−から起こる。
従来のＳＣＷモード構成では、送信器は“同じデータレート”を有する各空間レイヤ上で伝送されたデータを符号化する。受信器は最小２乗平均解法（ＭＭＳＥ;Minimum Mean Square Solution）またはゼロ周波数（ＺＦ;Zero Frequency）受信器のような低複雑性の線形受信器、あるいは各トーン(tone)について、ＱＲＭのような非線形受信器を使用することができる。
ＳＣＷ構成はＭＣＷ構成の上述された実施の形態の混乱に打ち勝つ。欠点はＳＣＷモードが空間的に相関するチャネルまたは高Ｋファクタを有するラインオブサイト（ＬＯＳ;line-of-sight）チャネルにおけるＭＣＷレートをサポートできないことである。これらのシナリオの両者はチャネルランク内のロスまたはチャネル条件数および増加したレイヤ間干渉の増加に導く。これは各空間レイヤについての効果的なＳＮＲを劇的に下げる。よって、各レイヤによってサポートされたデータレートは下げられ、それは全体のデータレートを下げる。
ＫファクタはＬＯＳチャネルパワー対非ＬＯＳチャネルパワーの比である。ランクは非ゼロエネルギーを有するチャネル内の固有モード(eigen-mode)数である。条件数はＭＩＭＯチャネルの最大固有値対最小固有値の比である。
したがってマルチチャネル、例えば、複数入力複数出力（ＭＩＭＯ）、直交周波数分割多重化（ＯＦＤＭ）通信システム、を介して送信されるようにデータストリームをダイナミックに分配するための技術についてこの分野には必要性がある。
[発明の概要]
１つの局面では、ランク予測（rank prediction）の方法は、各トーンについておのおの実行可能な多重化命令を有する伝送に対応するＭＩＭＯチャネルマトリクスを計算すること、ＭＩＭＯチャネルマトリクスに基づいて各トーンについて信号対雑音比（ＳＮＲ）を計算すること、おのおの実行可能な多重化命令について効果的なＳＮＲを発生するように各トーンについてＳＮＲをマップすること、各レイヤ伝送（layer transmission）について効果的なＳＮＲ未満のＳＮＲ閾値を有する最高のパケットフォーマット（ＰＦ;packet format）を選択すること、各レイヤ伝送について選択された最高ＰＦ（highest PF）の絶対的な最高ＰＦを選択すること、および選択された絶対的な最高ＰＦに基づいてランクを選択することを備える。
もう１つの局面では、無線通信装置は、各トーンについてレイヤ伝送に対応するＭＩＭＯチャネルマトリクスを計算するための手段、ＭＩＭＯチャネルマトリクスに基づいて各トーンについて信号対雑音比（ＳＮＲ）を計算するための手段、各レイヤ伝送について効果的なＳＮＲを発生するように各トーンについてＳＮＲをマップするための手段、各レイヤ伝送について効果的なＳＮＲ未満のＳＮＲ閾値を有する最高のパケットフォーマット（ＰＦ）を選択するための手段、各レイヤ伝送について選択された最高ＰＦの絶対的な最高ＰＦを選択するための手段、および選択された絶対的な最高ＰＦに基づいてランクを選択するための手段を備える。
もう１つの局面では、ランク予測の方法を実行するようにプログラムされたプロセッサ、この方法は各トーンについてレイヤ伝送に対応するＭＩＭＯチャネルマトリクスを計算すること、ＭＩＭＯチャネルマトリクスに基づいて各トーンについて信号対雑音比（ＳＮＲ）を計算すること、各レイヤ伝送について効果的なＳＮＲを発生するように各トーンについてＳＮＲをマップすること、各レイヤ伝送について効果的なＳＮＲ未満のＳＮＲ閾値を有する最高のパケットフォーマット（ＰＦ）を選択すること、各レイヤ伝送について選択された最高ＰＦの絶対的な最高ＰＦを選択すること、および選択された絶対的な最高ＰＦに基づいてランクを選択することを備える。
なおもう１つの局面では、ランク予測の方法を具体化するコンピュータ可読媒体、この方法は各トーンについてレイヤ伝送に対応するＭＩＭＯチャネルマトリクスを計算すること、ＭＩＭＯチャネルマトリクスに基づいて各トーンについて信号対雑音比（ＳＮＲ）を計算すること、各レイヤ伝送について効果的なＳＮＲを発生するように各トーンについてＳＮＲをマップすること、各レイヤ伝送について効果的なＳＮＲ未満のＳＮＲ
閾値を有する最高のパケットフォーマット（ＰＦ）を選択すること、各レイヤ伝送について選択された最高ＰＦの絶対的な最高ＰＦを選択すること、および選択された絶対的な最高ＰＦに基づいてランクを選択することを備える。
この発明のいろいろな局面および実施形態が下にさらに詳細に記述される。
発明の詳細な説明
本発明の特徴および性質は全体を通して付記される参照符号を有する図面とともに、下に述べる詳細説明からさらに明白になるであろう。
術語“典型的な”は“一例、事例、または実例として機能すること”を意味すべくこの中で使用されている。この中で“典型的な”として記述された任意の実施形態または構成は必ずしも他の実施形態または構成以上に好ましいとか有利であると解釈されるべきではない。
性能ベースのランク予測についてこの中に記述された技術は、符号分割多重アクセス（ＣＤＭＡ）システム、広帯域ＣＤＭＡ（ＷＣＤＭＡ）システム、ダイレクトシーケンスＣＤＭＡ（ＤＳ−ＣＤＭＡ）システム、時分割多重アクセス（ＴＤＭＡ）システム、周波数分割多重アクセス（ＦＤＭＡ）システム、高速ダウンリンクパケットアクセス（ＨＳＤＰＡ）システム、直交周波数分割多重（ＯＦＤＭ）ベースのシステム、直交周波数分割多重アクセス（ＯＦＤＭＡ）システム、単一入力単一出力（ＳＩＳＯ）システム、複数入力複数出力（ＭＩＭＯ）システム、等のようないろいろな通信システムのために使用されることができる。
ＯＦＤＭは全体のシステム帯域幅を複数の（ＮＦ）直交サブバンドに効果的に区切るマルチキャリア変調技術である。これらのサブバンドはトーン(tone)、サブキャリア(subcarrier)、ビン(bin)、および周波数チャネルとも呼ばれる。ＯＦＤＭで、各サブバンドはデータで変調され得るそれぞれのサブキャリアに関連する。ＮＦ変調記号まで各ＯＦＤＭ記号周期内のＮＦサブバンド上で伝送されることができる。送信に先立って、これらの変調記号は、ＮＦチップを含む“変換された”記号を得るためにＮＦ点逆高速フーリエ変換（ＩＦＦＴ;inverse fast Fourier transform）を使用している時間域に変換される。
ＳＣＷ構成はＭＣＷ構成の欠点に打ち勝つ。しかしながら、ＳＣＷモードは高Ｋファクタと空間的に相関するチャネルまたはラインオブサイト（ＬＯＳ）チャネル内のＭＣＷレートをサポートすることができない。これらのシナリオの両者はチャネルランクにおけるロスまたはチャネル条件数の増加および増加したレイヤ間干渉（inter-layer interference）に導く。これは各空間レイヤについて効果的なＳＮＲを劇的に下げる。よって、各レイヤによってサポートされたデータレートは下げられ、それは全体のデータレートを下げる。
レイヤ間干渉を減らすための１つの方法は低ランクチャネル内に送信される空間レイヤの数、およびトレードオフレイヤ間干渉(trade-off inter-layer interference)およびＭＩＭＯ利得を減らすことである。例えば、送信されたレイヤの数を４から３に下げること、即ち、ランクを４から３に減少させることは、３レイヤについての効果的なＳＮＲを、よって各レイヤによってサポートされたデータレートを劇的に増加させることができる。純効果は実際に３レイヤ伝送が４レイヤ伝送と比較してより高いスペクトル効率を有することである。
１実施形態では、ＳＣＷ構成は全体のスペクトル効率を最大にするようにレイヤ間干渉およびＭＩＭＯ利得を効果的にトレードオフする。これはランク予測により達成され、ここで受信器はチャネルランクとマッチするように干渉に対する搬送波品質（ＣＱＩ;Carrier-Quality-to-Interference）のほかにある伝送のための最適なレイヤ数をフィードバックする。
ＣＱＩと異なる品質表示が使用されてもよいことはこの分野の技術者には明白であるだろう。
従来のＳＣＷ送信器
図１は従来のＳＣＷ送信器１００を示す。ビット１０２はターボ符号化１０４され、そしてレート予測アルゴリズム１１２によって指定されたパケットフォーマット（ＰＦ）１０８，１１０によりＱＡＭマップ１０６される。符号化は単一入力単一出力（ＳＩＳＯ）構成と同じである。符号化された記号はその後ＭTレイヤ１１６にデマルチプレクス１１４され、それはその後ＭT ＯＦＤＭ変調器１２０およびアンテナ１２２に空間的にマップ１１８される。各送信アンテナについてのＯＦＤＭ処理はその後ＳＩＳＯと同じ様式で進み、それの後で信号はＭＩＭＯ無線チャネル内に送り出される。レート予測アルゴリズムは５ミリ秒ごとに受信器１２６からの４ビットＣＱＩフィードバック１２４を使用する。ＣＱＩは、受信器で測定された、効果的なＳＮＲ／空間レイヤの尺度である。空間マッピングは各レイヤについてのＳＮＲが同種であることを確かめるための手法でなされる。前に説明されたように、この構成の性能は低ランクチャネル内で経験する。
ランク予測付きのＳＣＷ送信器
１実施形態に従って、ランク予測付きの単一符号語（ＳＣＷ）構成が記述される。強いランク予測用のアルゴリズムが下に表示される。ＳＮＲ＜１５ｄＢ（ユーザの９０％）について、低複雑性のＭＭＳＥ受信器およびランク予測付きのＳＣＷ構成の性能は、継続的な干渉相殺（ＳＩＣ；successive interference cancellation）を有する複数符号語（ＭＣＷ）構成と同種である。ＨＡＲＱ無しで、ＭＣＱはチャネル推定エラーにより敏感であるので、ＳＣＷはＭＣＷよりよい。これらのファクタは、ＭＣＷと比較してより小さい実施の複雑性およびオーバヘッドのため、ＳＣＷをＭＩＭＯについて魅力的にする。
１５と２０ｄＢとの間のＳＮＲ（ユーザの１０％）について、ＳＣＷとＭＣＷとの間の性能ギャップは低Ｋチャネルについては１．０ｄＢ未満、そして高Ｋチャネルについては２〜５ｄＢである。高Ｋチャネルについて、高ＳＮＲでの性能劣化は、２重偏波アンテナを使用することによって、１〜２ｄＢに下げられる。事実上、ＳＣＷ構成は高ＳＮＲでさえＭＣＷ構成の２ｄＢ以内である。ＨＡＲＱの無い時は、ＭＣＷの性能は、チャネル推定エラーへのＳＩＣの増加した感度のため、ＳＮＲ＜１５ｄＢでＳＣＷより悪い。
図２は１実施形態に従ってランク予測付きのＳＣＷ送信器を示す。ビット２０２はターボ符号化２０４され、そしてレート予測アルゴリズム２１２によって指定された、パケットフォーマット（ＰＦ）２０８，２１０によりＱＡＭマップ２０６される。
１実施形態では、符号化された記号はその後Ｍストリーム２１６またはレイヤ（１≦Ｍ≦ＭT）にデマルチプレクス２１４され、ここでＭ２２８は５ビットＣＱＩ２２４のほかにある、５ミリ秒ごとに受信器２２６フィードバックによって指定された２ビット整数１＜Ｍ＜ＭTである。Ｍストリーム２１６はその後ＭT ＯＦＤＭ変調器２２０およびＭT アンテナ２２２に空間的にマップ２１８される。
空間マッピング(Spatial mapping)
空間マッパ(spatial Mapper)（プリコーダ(precoder)）２１８は、各ＯＦＤＭトーン、ｋについて、Ｍ記号ＭTアンテナにマップオンするＭT ×Ｍマトリクスである。プリコーダについていくつかの選択があり得る。ＭR ×ＭT ＭＩＭＯチャネルＨ（ｋ）を考慮されたい。プリコーダマトリクスは等価なチャネルマトリクスＨ（ｋ）Ｐ（ｋ）がＨ（ｋ）と比較して周波数分離度(selectivity)を改善したように選ばれることができる。増加した周波数分離度は周波数ダイバーシティ利得を得るために復号器によって活用されることができる。
１実施形態では、プリコーダマトリクスは以下の順列マトリクス：
Figure 2008526122
であり、
ここでΠ（０），Π（１），…，Π（ＭT −１）はアイデンティティマトリクスのＭ列から派生したサブ順列的マトリクスであり、
Figure 2008526122
およびＢは等価チャネルの周波数分離度を制御するためのパラメータである。
１実施形態に従って、もしもＭT＝４，Ｍ＝２ならば、その時は
Figure 2008526122
である。
Ｂ＝１について、これは図３に示されたような２つのレイヤを有するサーキュラ多重化戦略に導き、ここにおいて縦線ボックス３０２はレイヤ１からの記号に相当し、そして横線ボックス３０４はレイヤ２からの記号に相当する。図３はＭT＝４，Ｍ＝２，Ｂ＝１を有するサーキュラ多重化を示す。縦軸３０６はアンテナを表す。横軸３０８はトーンを表す。
Ｂ＝４について、これは図４に示されたような２つのレイヤを有するブロックサーキュラ多重化(block-circular multiplexing)戦略に導き、ここで縦線ボックス４０２はレイヤ１からの記号に相当し、そして横線ボックス４０４はレイヤ２からの記号に相当する。図４はＭT＝４，Ｍ＝２，Ｂ＝４を有するブロックサーキュラ多重化を示す。縦軸４０６はアンテナを表す。横軸４０８はトーンを表す。
Ｂにおける増加は等価なチャネルの周波数分離度における減少に導き、それは弱い符号が使用される時に望ましい可能性がある。また、パラメータＢはチャネルインターリーバ選択に敏感であり、したがってパラメータＢは後に最大限に利用されることができる。
サーキュラ多重化はチャネル遅延分散にかかわらず周波数ダイバーシティを改善する。強いターボ符号の存在において、（Ｍ＝１を有する）ＣＭの性能は空間−時間送信ダイバーシティ（ＳＴＴＤ;Space-Time transmit diversity）に近づく。しかしながら、非常に高いＰＦのためにまたは弱い従来の符号を使用している制御チャネルのために、ＳＴＴＤは有意にＣＭより性能が優れることができる。
１実施形態では、プリコーダマトリクスは以下の一般化された遅延ダイバーシティマトリクスである：
Figure 2008526122
ここで
Figure 2008526122
はＭT ×ＭT ＤＦＴマトリクスのＭ列から得られたＭT ×ＭサブＤＦＴマトリクスであり、そして
Figure 2008526122
は
Figure 2008526122
によって与えられた第（ｊ，ｊ）番エントリを有する、ＭT ×ＭT ダイアゴナルマトリクスである。
パラメータδは遅延パラメータであり、それはまたチャネルの周波数分離度を制御し、そしてＮはＯＦＤＭトーンの数である。われわれはＭ＝１について、上記のプリコーディングマトリクスが“純粋な”遅延ダイバーシティを実施することに注目する。遅延ダイバーシティの性能はサーキュラ多重化（およびＳＴＴＤ）より厳密に悪く、そして高ＰＦ用のＬＯＳチャネル条件において不十分な性能を有する。遅延ダイバーシティを使用することの唯一の強みは非常に低いＳＮＲ（ＳＮＲ＜−５ｄＢ）で、そして高い移動性（＞１２０ｋｍｐｈ）について改善されたＳＩＳＯチャネル推定利得の恩恵を被ることである。これらのチャネルシナリオでは、サーキュラ多重化はＳＩＳＯチャネル推定利得の恩恵を被ることはできない。
パケットフォーマット
現在のＳＩＳＯ構成はスペクトル効率[０．５，１，１．５，２．０，２．５，３．０，４．０]ｂｐｓ／Ｈｚを有する７ＰＦを使用する。１レイヤ伝送を使用しているＳＣＷ構成では、スペクトル効率（ＳＥ）内のこのグラニュラリティ(granularity)は十分であろう。しかしながら、全４レイヤが伝送のために使用される時は、これは２〜４ｂｐｓ／ＨｚのようなＳＥグラニュラリティを用いて、[２，４，６，８，１０，１２，１６]ｂｐｓ／Ｈｚのスペクトル効率に翻訳する。これらのユーザはかれらの得られるＳＥよりもずっと低いデータレートで送信することを強いられるので、この粗グラニュラリティの結論はデータレートにおけるロスである。各レイヤ内のレートは別々に調整されることができ、全体のより細かいスペクトル効率のグラニュラリティという結果になるので、ＳＩＣを有するＭＣＷ構成はこのグラニュラリティ問題を持たないことに注目されたい。
Figure 2008526122
表１は１実施形態に従ってランク予測付きのＳＣＷ構成用のパケットフォーマットを示す。表１は第１乃至第６伝送を目標とするＳＥ付きのＰＦを示す。１６ＰＦは第１伝送を目標とする０．２５ｂｐｓ／Ｈｚ／レイヤの増加量で０．５ｂｐｓ／Ｈｚ／レイヤから４．２５ｂｐｓ／Ｈｚ／レイヤまでのＳＥ／レイヤ分布で準備される。第３伝送を目標とする時は、最大到達ＳＥ／レイヤは１．４２ｂｐｓ／Ｈｚ／レイヤである。１．４２ｂｐｓ／Ｈｚ／レイヤと２．１３ｂｐｓ／Ｈｚ／レイヤとの間のＳＥは第２伝送を目標とすることによって達成されることができ、そして２．１３ｂｐｓ／Ｈｚ／レイヤより大きいＳＥは第１伝送を目標とすることによって達成されることができ、ここでＨＡＲＱの恩恵は減少する。
もう１つの実施形態では、より高いＳＥは第３伝送を目標とすることによって達成されることができるように、より多くのＰＦ＃ｓがＳＥ／レイヤ＞４．２５ｂｐｓ／Ｈｚで増加されてもよく、そしてＨＡＲＱ利得の恩恵を被る。そのような場合には、６ビットＣＱＩはＰＦグラニュラリティが得られることを確かめる必要があるかもしれない。
性能ベースのランク予測アルゴリズム
図５は１実施形態に従って性能ベースのランク予測に関するブロック図に示す。第ｋトーンについて、Ｈ（ｋ）Ｐ1 （ｋ）５０２乃至Ｈ（ｋ）Ｐ4 （ｋ）５０８はそれぞれ、ＭＭＳＥ（１）５１２乃至ＭＭＳＥ（４）５１８に入力される。ＭＭＳＥ（１）５１２乃至ＭＭＳＥ（４）５１８はそれぞれ、ＳＮＲ1 （ｋ）５２２乃至ＳＮＲ4 （ｋ）５２８を生成する。ＳＮＲ1 （ｋ）５２２乃至ＳＮＲ4 （ｋ）５２８はそれぞれ、キャップマッパ５３２乃至キャップマッパ５３８に入力される。キャップマッパ５３２乃至キャップマッパ５３８はそれぞれ、ＥｆｆＳＮＲ1 ５４２乃至ＥｆｆＳＮＲ4 ５４８を生成する。ＥｆｆＳＮＲ1 ５４２乃至ＥｆｆＳＮＲ4 ５４８はそれぞれ、ＰＦ選択５２２乃至ＰＦ選択５５８に入力される。１％パケットエラーレート（ＰＥＲ）でのＳＮＲ閾値はＰＦ選択５５２乃至ＰＦ選択５５８に入力される。ＰＦ選択５５２乃至ＰＦ選択５５８はそれぞれ、１×ＰＦ１ ５６２乃至４×ＰＦ４ ５６８を生成する。１×ＰＦ１ ５６２乃至４×ＰＦ４ ５６８は決定ユニット５７０に入力される。決定ユニット５７０はランク５７２を生成する。
ＥｆｆＳＮＲ1 ５４２乃至ＥｆｆＳＮＲ4 ５４８およびランク５７２は選択および量子化ユニット５７４に入力される。選択および量子化ユニット５７４は５ビットＣＱＩ５７６を生成する。
１実施形態に従って、性能ベースのランク予測アルゴリズムは次のとおり機能する：
１．各トーンで、｛１，２，３，４｝レイヤ伝送に対応する、４×４，４×３，４×２，および４×１ＭＩＭＯチャネルマトリクス、Ｈ（ｋ）Ｐ1 （ｋ），Ｈ（ｋ）Ｐ2 （ｋ），Ｈ（ｋ）Ｐ3（ｋ）およびＨ（ｋ）Ｐ4 （ｋ）が計算される。ＭＭＳＥ受信器を想定して、｛１，２，３，４｝レイヤ伝送のための後処理ＳＮＲ、ＳＮＲ1（ｋ），ＳＮＲ2（ｋ），ＳＮＲ3 (ｋ)，ＳＮＲ4 (ｋ）は各トーンについて下記のように計算される：
Figure 2008526122
もしもわれわれがＱＲＭ−ＭＬＤまたはＩＤＤのような他の受信器を想定すれば、後処理ＳＮＲは異なる様式で計算されるであろう。
２．｛１，２，３，４｝レイヤ伝送用の上で計算されたＳＮＲは、ＳＩＳＯ構成用に計算されたパートーン(per-tone)受信器ＳＮＲと等価である。制約されないキャパシティのマッピングはその後、｛１，２，３，４｝レイヤ伝送について、全トーンに亘って平均された効果的なＳＮＲを発生するために（ＳＩＳＯ構成におけるように）使用され、それはＥｆｆＳＮＲ1 ，ＥｆｆＳＮＲ2 ，ＥｆｆＳＮＲ3 ，ＥｆｆＳＮＲ4 として表される。効果的なＳＮＲのためのトーン従属物はない。
３．効果的なＳＮＲは１ＳＩＳＯシステムについて１％ＰＥＲを目標とするＳＮＲ閾値を有するテーブルと比較対照される。測定された効果的なＳＮＲ未満のＳＮＲ閾値を有する最高パケットフォーマット（ＰＦ）は｛１，２，３，４｝レイヤ伝送のために選択される。このＰＦはＰＦ1，ＰＦ2，ＰＦ3，ＰＦ4として表される。
４．最適なランク／レイヤは全体のスペクトル効率を最大化するように選ばれる、即ち、
Figure 2008526122
５．5ビットＣＱＩはその後フィードバックされる、ここで
Figure 2008526122
である。
この中に記述された技術は他のシステムと同様にいろいろなＯＦＤＭベースのシステム用に使用されることができる。この中に記述されたランク予測技術はいろいろな手段によって実施されることができる。例えば、これらの技術はハードウェア、ソフトウェア、またはそれの組合わせで実施されることができる。ハードウェア実施形態に関しては、干渉制御を行うために使用される処理ユニットは１つまたはそれ以上の特定用途向け集積回路（ＡＳＩＣ）、ディジタル信号プロセッサ（ＤＳＰ）、ディジタル信号処理装置（ＤＳＰＤ）、プログラマブル論理装置（ＰＬＤ）、フィールドプログラマブルゲートアレイ（ＦＰＧＡ）、プロセッサ、コントローラ、マイクロコントローラ、マイクロプロセッサ、この中に記述された機能を実行するように設計された他の電子ユニット、あるいはそれの組合わせの内部で実施されることができる。
ソフトウェア実施形態に関しては、干渉制御技術はこの中に記述された機能を実行するモジュール（例えば、手順、機能等）で実施されることができる。ソフトウェア符号はメモリユニット内に蓄積され、そしてプロセッサによって実行されることができる。メモリユニットはプロセッサの内部でまたはプロセッサの外部で実施されることができ、その場合にはそれはこの分野で知られているようないろいろな手段によってプロセッサに通信的に連結されることができる。
開示された実施形態の前の説明はこの分野の任意の技術者が本発明を製作または使用することを可能とするように提供される。これらの実施形態へのいろいろな変更はこの分野の技術者にはたやすく明白であるだろうし、そしてこの中に定義された包括的な原理はこの発明の精神または範囲から逸脱すること無しに他の実施形態に適用されてもよい。従って、本発明はこの中に示された実施形態に制限されるつもりはなく、しかしむしろこの中に開示された原理および新規な特徴と矛盾しない最も広い範囲が許容されるべきである。
従来のＳＣＷ送信器を示す図。 1実施形態に従ってランク予測付きのＳＣＷ送信器を示す図。 １実施形態に従ってＭT ＝４，Ｍ＝２，Ｂ＝１を有するサーキュラ多重化を示す図。 １実施形態に従ってＭT ＝４，Ｍ＝２，Ｂ＝４を有するサーキュラ多重化を示す図。 １実施形態に従って性能ベースのランク予測を示すブロック図。
符号の説明
２０２…ビット、２０４…ターボ符号器、２０６…ＱＡＭマップ、２０８，２１０…ＰＦ、２１２…レート予測、２１４…デマルチプレクサ、２１８…空間マッピング、２２０…ＯＦＤＭ変調器、２２２…アンテナ、２２４…ＣＱＩ（５ビット）、２２６…受信器

Claims (20)

  1. ランク予測の方法であって、
    各トーンについてレイヤ伝送に対応するＭＩＭＯチャネルマトリクスを計算し、
    該ＭＩＭＯチャネルマトリクスに基づいて各トーンについて信号対雑音比（ＳＮＲ）を計算し、
    各レイヤ伝送について効果的なＳＮＲを発生するように各トーンについて該ＳＮＲをマップし、
    各レイヤ伝送について該効果的なＳＮＲ未満のＳＮＲ閾値を有する最高のパケットフォーマット（ＰＦ）を選択し、
    各レイヤ伝送について該選択された最高ＰＦの絶対的な最高ＰＦを選択する、そして
    該選択された絶対的な最高ＰＦに基づいてランクを選択する
    ことを含む方法。
  2. さらに、該選択されたランクに基づいて品質表示を送ることを含む請求項１記載の方法。
  3. 該品質表示が干渉に対する搬送波品質（ＣＱＩ）である請求項２記載の方法。
  4. 該レイヤ伝送の数が４である請求項１記載の方法。
  5. ここにおいて該ＳＮＲは
    Figure 2008526122
     として計算され、ここでｋは{１，２，３，４}レイヤ伝送に対応する、第ｋ番目のトーン、Ｈ（ｋ）Ｐ１（ｋ），Ｈ（ｋ）Ｐ２（ｋ），Ｈ（ｋ）Ｐ３（ｋ）およびＨ（ｋ）Ｐ４（ｋ）である請求項１記載の方法。
  6. マッピングがキャパシテイに関して制約されない請求項１記載の方法。
  7. 該選択されたランク
    Figure 2008526122
     が
    Figure 2008526122
     として計算される請求項１記載の方法。
  8. 該品質表示ＣＱＩが
    Figure 2008526122
     として計算され、ＥｆｆＳＮＲは該選択されたランクの該効果的なＳＮＲである請求項７記載の方法。
  9. 無線通信装置であって、
    各トーンについてレイヤ伝送に対応するＭＩＭＯチャネルマトリクスを計算するための手段、
    該ＭＩＭＯチャネルマトリクスに基づいて各トーンについて信号対雑音比（ＳＮＲ）を計算するための手段、
    各レイヤ伝送について効果的なＳＮＲを発生するように各トーンについて該ＳＮＲをマップするための手段、
    各レイヤ伝送について該効果的なＳＮＲ未満のＳＮＲ閾値を有する最高のパケットフォーマット（ＰＦ）を選択するための手段、
    各レイヤ伝送について該選択された最高ＰＦの絶対的な最高ＰＦを選択するための手段、そして
    該選択された絶対的な最高ＰＦに基づいてランクを選択するための手段、
    とを含む無線通信装置。
  10. 該選択されたランクに基づいて品質表示を送るための手段をさらに含む請求項９記載の無線通信装置。
  11. 該レイヤ伝送の数が少なくとも２である請求項９記載の無線通信装置。
  12. 該品質表示が干渉に対する搬送波品質である請求項１０記載の無線通信装置。
  13. ランク予測の方法を実行するようにプログラムされたプロセッサであって、該方法は
    各トーンについてレイヤ伝送に対応するＭＩＭＯチャネルマトリクスを計算し
    該ＭＩＭＯチャネルマトリクスに基づいて各トーンについて信号対雑音比（ＳＮＲ）を計算し、
    各レイヤ伝送について効果的なＳＮＲを発生するように各トーンについて該ＳＮＲをマップし
    各レイヤ伝送について該効果的なＳＮＲ未満のＳＮＲ閾値を有する最高のパケットフォーマット（ＰＦ）を選択し、
    各レイヤ伝送について該選択された最高ＰＦの絶対的な最高ＰＦを選択し。そして
    該選択された絶対的な最高ＰＦに基づいてランクを選択する
    ことを含むプロセッサ。
  14. 該方法が該選択されたランクに基づいて品質表示を送ることをさらに含む請求項１３記載のプロセッサ。
  15. 該レイヤ伝送の数が少なくとも２である請求項１３記載のプロセッサ。
  16. 該品質表示が干渉に対する搬送波品質である請求項１４記載のプロセッサ。
  17. ランク予測の方法を具体化するコンピュータ可読媒体であって、該方法は、
    各トーンについてレイヤ伝送に対応するＭＩＭＯチャネルマトリクスを計算し、
    該ＭＩＭＯチャネルマトリクスに基づいて各トーンについて信号対雑音比（ＳＮＲ）を計算し、
    各レイヤ伝送について効果的なＳＮＲを発生するように各トーンについて該ＳＮＲをマップし、
    各レイヤ伝送について該効果的なＳＮＲ未満のＳＮＲ閾値を有する最高のパケットフォーマット（ＰＦ）を選択し、
    各レイヤ伝送について該選択された最高ＰＦの絶対的な最高ＰＦを選択し、そして、
    該選択された絶対的な最高ＰＦに基づいてランクを選択することを含む、
    コンピュータ可読媒体。
  18. 該方法は該選択されたランクに基づいて品質表示を送ることをさらに含む請求項１７記載のコンピュータ可読媒体。
  19. 該レイヤ伝送の数が少なくとも２である請求項１７記載のコンピュータ可読媒体。
  20. 該品質表示が干渉に対する搬送波品質である請求項１８記載のコンピュータ可読媒体。
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AU2005319084A1 (en) 2006-06-29
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CN101124760A (zh) 2008-02-13
AR052442A1 (es) 2007-03-21
US9148256B2 (en) 2015-09-29
ZA200705476B (en) 2009-05-27
US20060133521A1 (en) 2006-06-22
KR100933153B1 (ko) 2009-12-21
NZ555996A (en) 2010-05-28
NO20073180L (no) 2007-09-18
RU2406235C2 (ru) 2010-12-10
MX2007007770A (es) 2007-11-09
KR20070087188A (ko) 2007-08-27
TW200637229A (en) 2006-10-16
EP1832031A2 (en) 2007-09-12
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