CN104521204A - 高度容忍非线性地联合顺序估计码元和相位 - Google Patents
高度容忍非线性地联合顺序估计码元和相位 Download PDFInfo
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Abstract
一种顺序估计电路可操作来接收与码元的发送矢量相对应的接收码元间关联(ISC)信号的样本,其中每个码元是特定群集中的多个码元之一。该顺序估计电路可操作来使用减少状态顺序估计(RSSE)过程生成码元的发送矢量的估计值。RSSE过程的每次迭代可以包含生成多个候选者矢量。每个候选者矢量的第一元素可以保存特定群集中的多个码元的相应一个。第一元素可以是除了码元的发送矢量的最近码元之外的码元的发送矢量的其它码元的估计值。每个所述候选者矢量的第二元素保存多个计算填充物值的相应一个。
Description
优先权要求
本专利申请引用如下专利文献,要求其优先权以及要求来自其中的利益:
2012年6月20日提交、和发明名称为“有效利用带宽的装置和方法(Apparatus and Method for Efficient Utilization of Bandwidth)”的美国临时专利申请第61/662,085号;
2012年11月14日提交、和发明名称为“基于部分响应的调制方案(Modulation Scheme Based on Partial Response)”的美国临时专利申请第61/726,099号;
2012年11月26日提交、和发明名称为“基于部分响应的调制方案(Modulation Scheme Based on Partial Response)”的美国临时专利申请第61/729,774号;以及
2012年12月28日提交、和发明名称为“基于部分响应的调制方案(Modulation Scheme Based on Partial Response)”的美国临时专利申请第61/747,132号。
特此通过引用将上述每个申请全文并入本文中。
通过引用并入
本申请引用:
与本申请相同日期提交、和发明名称为“低复杂性、高频谱有效性通信(Low-Complexity,Highly-Spectrally-Efficient Communications)”的美国专利申请第13/754,964号;
与本申请相同日期提交、和发明名称为“部分响应脉冲成形滤波器的设计和优化(Design and Optimization of Partial Response Pulse Shape Filter)”的美国专利申请第13/754,998号;
与本申请相同日期提交、和发明名称为“高频谱有效性通信的群集图优化(Constellation Map Optimization For Highly-Spectrally-Efficient Communi-cations)”的美国专利申请第13/755,001号;
与本申请相同日期提交、和发明名称为“高频谱有效性通信的动态滤波调整(Dynamic Filter Adjustment For Highly-Spectrally-Efficient Communi-cations)”的美国专利申请第13/755,008号;
与本申请相同日期提交、和发明名称为“高频谱有效性通信的接收的定时同步(Timing Synchronization for Reception of Highly-Spectrally-EfficientCommunications)”的美国专利申请第13/755,011号;
与本申请相同日期提交、和发明名称为“高频谱有效性通信的前馈均衡(Feed Forward Equalization for Highly-Spectrally-Efficient Communications)”的美国专利申请第13/755,018号;
与本申请相同日期提交、和发明名称为“高频谱有效性通信的判定反馈均衡器(Decision Feedback Equalizer for Highly-Spectrally-Efficient Communi-cations)”的美国专利申请第13/755,021号;
与本申请相同日期提交、和发明名称为“高频谱有效性通信的具有多个核心的判定反馈均衡器(Decision Feedback Equalizer with Multiple Cores forHighly-Spectrally-Efficient Communications)”的美国专利申请第13/755,025号;
与本申请相同日期提交、和发明名称为“高频谱有效性通信的利用码元出错率偏置自适应函数的判定反馈均衡器(Decision Feedback EqualizerUtilizing Symbol Error Rate Biased Adaptation Function for Highly-Spectrally-Efficient Communications)”的美国专利申请第13/755,026号;
与本申请相同日期提交、和发明名称为“高频谱有效性通信的粗略相位估计(Coarse Phase Estimation for Highly-Spectrally-Efficient Communications)”的美国专利申请第13/755,028号;以及
与本申请相同日期提交、和发明名称为“高频谱有效性通信的细致相位估计(Fine Phase Estimation for Highly-Spectrally-Efficient Communications)”的美国专利申请第13/755,039号。
特此通过引用将上述每个申请全文并入本文中。
技术领域
本申请的各个方面涉及电子通信。更具体地说,本公开的某些实现涉及高度容忍非线性地联合顺序估计码元和相位。
背景技术
现有通信方法和系统是过于耗电的和/或频谱效率低下的。通过将常规的和传统的做法与在本公开的其余部分中参考附图所述的本发明方法和系统的一些方面相比,这样做法的进一步局限性和缺点对于本领域的普通技术人员来说是显而易见的。
发明内容
本发明提供了基本上如至少一个图形所例示和/或结合至少一个图形所述,以及如权利要求书所更全面阐述,高度容忍非线性地联合顺序估计码元和相位的方法和系统。
附图说明
图1是描绘为低复杂性、高频谱有效性通信配置的示范性系统的方块图;
图2是描绘用在为低复杂性、高频谱有效性通信配置的系统中的示范性均衡和顺序估计电路的方块图;
图3是描绘用在为低复杂性、高频谱有效性通信配置的系统中的示范性顺序估计电路的方块图;
图4是描绘用在为低复杂性、高频谱有效性通信配置的系统中的示范性度量计算电路的方块图;
图5A-5E描绘了为高度容忍非线性地联合顺序估计码元和相位配置的系统执行的示范性顺序估计过程的一些部分;以及
图6是例示高度容忍非线性地顺序估计以便接收部分响应信号的示范性过程的流程图。
具体实施方式
如本文所利用,术语“电路”和“线路”指的是物理电子组件(即,硬件)和可以配置硬件,被硬件执行,和/或要不然与硬件相联系的任何软件和/或固件(“代码”)。如本文所使用,举例来说,特定处理器和存储器当执行第一多行代码时可以包含第一“电路”,当执行第二多行代码时可以包含第二“电路”。如本文所利用,“和/或”意味着通过“和/或”联系的列表的一个或多个项目。举一个例子来说,“x和/或y”意味着三元素集{(x),(y),(x,y)}的任何元素。举另一个例子来说,“x,y和/或z”意味着七元素集{(x),(y),(z),(x,y),(x,z),(y,z),(x,y,z)}的任何元素。如本文所利用,术语“方块”和“模块”指的是一个或多个电路可以执行的功能。如本文所利用,术语“示范性”意味着用作非限制性例子、实例、或示例。如本文所利用,术语“举例来说”和“例如”引入一个或多个非限制性例子、实例、或示例的列表。如本文所利用,与是否通过一些用户可配置设置禁用或不启用功能的执行无关,每当线路包含执行功能所需的硬件和代码(如果有必要的话)时,该线路就“可起”执行该功能的“作用”。
图1是描绘为低复杂性、高频谱有效性通信配置的示范性系统的方块图。系统100包含映射器电路102、脉冲成形滤波器电路104、定时导频插入电路105、发送器前端电路106、信道107、接收器前端电路108、滤波器电路109、定时导频移除电路110、均衡和顺序估计电路112、和反映射电路114。组件102,104,105和106可以是发送器(例如,基站或接入点、路由器、网关、移动设备、服务器、计算机、计算机外设、桌子、调制解调器、机顶盒等)的一部分。组件108,109,112和114可以是接收器(例如,基站或接入点、路由器、网关、移动设备、服务器、计算机、计算机外设、桌子、调制解调器、机顶盒等)的一部分,发送器和接收器可以经由信道107通信。
映射器102可操作来按照所选调制方案将要发送的Tx_bitstream的位映射成码元。该码元可以经由信号103输出。举例来说,对于具有N个的码元字母表的正交调幅方案(N-QAM),映射器可以将Tx_bitstream的每个Log2(N)位映射成表示成复数和/或表示成同相(I)和正交相(Q)分量的单个码元。尽管在本公开中将N-QAM用于例示,但本公开的各个方面可应用于任何调制方案(例如,幅移键控(ASK)、相移键控(PSK)、频移键控(FSK)等)。另外,N-QAM群集的点可以规则隔开(“在网格上”)或不规则隔开(“不在网格上”)。更进一步,可以为与对数似然比(LLR)和优化平均互信息位(MMIB)有关的最佳位出错率性能优化映射器使用的码元群集。Tx_bitstream可以是,举例来说,数据位经过前向纠错(FEC)编码器和/或交织器的结果。另外,或可替代地,从映射器102出来的码元可以经过交织器。
脉冲成形器104可操作来调整信号103的波形,以便所得信号113的波形码元发送信号113的信道的频谱要求。频谱要求可以称为“频谱屏蔽”,可以由监管机构(例如,美国联邦通信委员会、或欧洲电信标准协会)和/或支配正在使用的通信信道和/或标准机构(例如,第三代合作伙伴计划)建立。脉冲成形器104可以包含,举例来说,无限脉冲响应(IIR)和/或有限脉冲响应(FIR)滤波器。脉冲成形器104的抽头的数量或“长度”在本文中被表示成整数的LTx。脉冲成形器104的脉冲响应在本文中被表示成hTx。脉冲成形器104可以被配置成其输出信号113故意具有码元间干扰(ISI)的大致数量。于是,脉冲成形器104可以称为部分响应脉冲成形滤波器,信号113可以称为部分响应信号或驻留在部分响应域中,而信号103可以称为驻留在码元域中。可以这样设计脉冲成形器104的抽头的数量和/或抽头系数的值,故意使脉冲成形器104对于加性高斯白噪声(AWGN)是非最佳的,以便提高信号路径中非线性的容忍度。关于这一点,如与,举例来说,常规近零正ISI脉冲成形滤波器(例如,根升余弦(RRC)脉冲成形滤波器)相比,脉冲成形器104在存在非线性的情况下可以提供更优越的性能。脉冲成形器104可以如以下专利文献之一或多个所述设计:如上所述、通过引用将每一个都并入本文中的发明名称为“部分响应脉冲成形滤波器的设计和优化”的美国专利申请、发明名称为“高频谱有效性通信的群集图优化”的美国专利申请、和发明名称为“高频谱有效性通信的动态滤波调整”的美国专利申请。
应当注意到,部分响应信号(或“部分响应域中的信号”)仅仅是在信号的码元之间存在关联的一种信号的一个例子(本文称为“码元间关联(ISC)信号”)。这样的信号与通过,举例来说,升余弦(RC)或根升余弦(RRC)脉冲成形滤波生成的零(或近零)ISI信号相反。为了使例示简单起见,本公开把重点放在经由部分响应滤波生成的部分响应信号上。不过,本公开的各个方面可应用于像,举例来说,经由矩阵相乘(例如,格子编码)生成的信号、和经由奈奎斯特(Nyquist)频率以下的抽选以便使混叠建立码元之间的关联生成的信号那样的其它ISC信号。
定时导频插入电路105可以插入接收器可以用于定时同步的导频信号。定时导频插入电路105的输出信号115因此可以包含加上插入导频信号(例如,在1/4×fbaud上的正弦波,其中fbaud是码元率)的信号113。导频插入电路105的示范性实现描述在以下专利文献中:如上所述、通过引用并入本文中的发明名称为“高频谱有效性通信的接收的定时同步”的美国专利申请。
发送器前端电路106可操作来放大和/或升频转换信号115以生成信号116。因此,发送器前端电路106可以包含,举例来说,功率放大器和/或混合器。该前端可能将非线性失真和/或相位噪声(和/或其它不理想东西)带入信号116中。电路106的非线性可以表示成可能是,举例来说,多项式,或指数(例如,拉普(Rapp)模型)的FnlTx。该非线性可能包含记忆(例如,沃尔泰拉(Volterra)级数)。
信道107可以包含有线、无线、和/或光通信介质。信号116可以通过信道107传播,作为信号118到达接收前端108。信号118可以含有比信号116多的噪声(例如,由于信道中的热噪声的结果)以及可能具有比信号116高的或与其不同的ISI(例如,由于多路径的结果)。
接收器前端电路108可以起放大和/或降频转换信号118以生成信号119的作用。因此,接收器前端可以包含,举例来说,低噪放大器和/或混合器。该接收器前端可能将非线性失真和/或相位噪声带入信号119中。电路108的非线性可以表示成可能是,举例来说,多项式,或指数(例如,拉普模型)的FnlRx。该非线性可能包含记忆(例如,沃尔泰拉级数)。
定时导频恢复和移除电路110可以起锁定导频插入电路105插入的定时导频信号,以便恢复接收信号的码元定时的作用。输出122因此可以包含减去(即,没有)定时导频信号的信号120。定时导频恢复和移除电路110的示范性实现描述在以下专利文献中:如上所述、通过引用并入本文中的发明名称为“高频谱有效性通信的接收的定时同步”的美国专利申请。
输入滤波器109可以起调整部分响应信号119的波形以生成部分响应信号120的作用。输入滤波器109可以包含,举例来说,无限脉冲响应(IIR)和/或有限脉冲响应(FIR)滤波器。输入滤波器109的抽头的数量或“长度”在本文中被表示成整数的LRx。输入滤波器109的脉冲响应在本文中被表示成hRx。输入滤波器109的抽头的数量和/或抽头系数可以根据以下配置:非线性模型信号120的信噪比(SNR)、Tx部分响应滤波器10的抽头的数量和/或抽头系数、和/或其它参数。可以这样设计输入滤波器109的抽头的数量和/或抽头系数的值,使噪声抑制故意受到损害(相对于完美匹配滤光器),以便在存在非线性的情况下提高性能。其结果是,如与,举例来说,常规近零正ISI脉冲成形滤波器(例如,根升余弦(RRC)脉冲成形滤波器)相比,输入滤波器109在存在非线性的情况下可以提供更优越的性能。输入滤波器109可以如以下专利文献之一或多个所述设计:如上所述、通过引用将每一个都并入本文中的发明名称为“部分响应脉冲成形滤波器的设计和优化”的美国专利申请、发明名称为“高频谱有效性通信的群集图优化”的美国专利申请、和发明名称为“高频谱有效性通信的动态滤波调整”的美国专利申请。
如本文所利用,“总部分响应(h)”可以等于hTx和hRx的卷积,因此,“总部分响应长度(L)”可以等于LTx+LRx-1。但是,可以将L选成小于LTx+LRx-1,其中,举例来说,Tx脉冲成形器104和/或Rx输入滤波器109的一个或多个抽头低于预定水平。减小L可以降低顺序估计的解码复杂性。这种权衡可以在设计系统100期间优化。
均衡器和顺序估计器112可操作来执行均衡过程和顺序估计过程。均衡器和顺序估计器112的示范性实现的细节将在下面参照图2来描述。均衡器和顺序估计器112的输出信号132可以处在码元域中,可以携带信号103的相应发送码元的估计值(和/或Tx_bitstream的相应发送信息位的估计值)。尽管未描绘出来,但信号132在到反映射器114的途中可能经过交织器。该估计值可以包含软判定估计值、硬判定估计值、或两者。
反映射器114可操作来按照所选调制方案将码元映射成位序列。举例来说,对于N-QAM调制方案,该反映射器可以将每个码元映射成Rx_bitstream的Log2(N)位。可以将Rx_bitstream输出到,举例来说,去交织器和/或FEC解码器。可替代地,或另外,反映射器114可以生成称为LLR(对数似然比)的每个位的软输出。该软输出位可以供软解码前向纠错器(例如,低密度奇偶校验(LDPC)解码器)使用。该软输出位可以使用,举例来说,软输出维特比(Viterbi)算法(SOVA)或类似算法生成。这样的算法可以将包括丢掉路径的度量水平和/或估计位概率的顺序解码过程的附加信息用于生成LLR,其中其中Pb是位b=1的概率。
在一种示范性实现中,发送器中脉冲成形器104的系统上游和接收器中均衡器和顺序估计器112的下游的组件可以如在常规N-QAM系统中所找到那样。因此,通过修改发送侧物理层和接收侧物理层,可以在另外常规N-QAM系统中实现本发明的各种方面,以便如与,举例来说,使用RRC滤波器和N-QAM限幅器相比,在存在非线性的情况下提高系统的性能。
图2是描绘用在为低复杂性、高频谱有效性通信配置的系统中的示范性均衡和顺序估计电路的方块图。所示的是均衡器电路202、信号组合器电路204、相位调整电路206、顺序估计电路210、和非线性模拟电路236a和236b。
均衡器202可操作来处理信号122以降低信道107引起的ISI。均衡器202的输出222是部分响应域信号。信号222的ISI主要是脉冲成形器104和输入滤波器109的结果(可能存在来自多路径的一些残余ISI,例如,由于在均衡器202中使用了最小均方(LMS)法)。反馈到均衡器202的误差信号201也在部分响应域中。信号201是信号222与非线性模拟电路236a输出的部分响应信号203之间的、由组合器204计算的差值。均衡器的示范性实现描述在以下专利文献中:如上所述、通过引用并入本文中的发明名称为“高频谱有效性通信的前馈均衡”的美国专利申请。
载波恢复电路208可操作来根据信号222与非线性模拟电路236b输出的部分响应信号207之间的相位差生成信号228。载波恢复电路208可以如以下专利文献所述:如上所述、通过引用并入本文中的发明名称为“高频谱有效性通信的粗略相位估计”的美国专利申请。
相位调整电路206可操作来调整信号222的相位以生成信号226。相位调整的数量和方向可以通过载波恢复电路208输出的信号228确定。信号226是近似于(直到由均衡器202的有限长度、未经相位调整电路206校正的残余相位误差、非线性、和/或其它不理想东西引起的均衡误差)从经过脉冲成形器104和输入滤波器109的信号103的相应码元中得出的总部分响应信号的部分响应信号。
缓冲器212缓存信号226的样本,并经由信号232输出信号226的多个样本。信号232被表示成PR1,其中下划线指示它是矢量(在这种情况下,矢量的每个元素对应于部分响应信号的一个样本)。在一种示范性实现中,矢量PR1的长度可以是Q个样本。
顺序估计电路210的输入是信号232、信号228、和响应响应基于h(上面讨论的总部分响应)。举例来说,响应可以代表h(上面所述)与补偿像多路径那样的信道不理想东西的滤波响应之间的折衷。响应可以以从脉冲成形器10的LTx个抽头系数和输入滤波器109的LRx个抽头系数的卷积中得出的LTx+LRx-1个抽头系数的形式传送和/或存储。可替代地,响应可以以少于LTx+LRx-1个的抽头系数—举例来说,由于低于阈值而忽略了LTx和LRx的一个或多个抽头—的形式传送和/或存储。顺序估计电路210可以输出部分响应反馈信号205和209、与信号120的细致确定相位误差相对应的信号234、和信号132(携带发送码元和/或发送位的硬和/或软估计值)。顺序估计电路210的示范性实现将在下面参考图3加以描述。
非线性模拟电路236a可以将非线性函数(在到电路210的途中通过接收信号看到的非线性的模型)应用于信号205得出信号203。类似地,非线性模拟电路236b可以将非线性函数应用于信号209得出信号207。可以是,举例来说,三阶或五阶多项式。将更高阶多项式用于导致的精度的提高可能要权衡实现更高阶多项式的复杂性的提高。在FnlTx是通信系统100的最主要非线性的情况下,只模拟FnlTx可能就足够了。在由于系统中的其它非线性(例如,接收器前端108的非线性)使接收器性能的下降超过阈值的情况下,模型可能要考虑这样的其它非线性。
图3是描绘用在为低复杂性、高频谱有效性通信配置的系统中的示范性顺序估计电路的方块图。所示的是候选者生成电路302、度量计算电路304、候选者选择电路306、组合器电路308、缓冲器电路310、缓冲器电路312、相位调整电路314、和卷积电路316a和316b。参照图3所述的顺序估计过程只是一个例子。也可能存在顺序估计过程的许多变种。举例来说,尽管这里所述的实现每个码元生存者使用一个相位生存者,但另一种实现可能存在共同用于每个码元生存者的PSu(例如,PSu<Su)个相位生存者。
对于在时间n上的每个码元候选者,度量计算电路304可以起根据部分响应信号PR1、传送相位候选者矢量的信号303a、和传送码元候选者矢量的信号303b生成度量矢量的作用。其中下划线指示矢量,下标n指示这是时间n的候选者矢量,M是等于码元字母表的大小的整数(例如,对于N-QAM,M等于N),Su是等于顺序估计过程的每次迭代保留下来的码元生存者矢量的数量的整数,以及P是等于相位字母表的大小的整数。在一种示范性实现中,如下面参照图5A-5E以及在以下专利文献中进一步所述:如上所述、通过引用并入本文中的发明名称为“高频谱有效性通信的细致相位估计”的美国专利申请,相位字母表的大小是三,三个相位的每一个对应于正相移,负相移,或零相位。在一种示范性实现中,每个相位候选者矢量可以包含Q个相位值,每个码元候选者矢量可以包含Q个码元。度量计算方块的示范性实现将在下面参考图4加以描述。
候选者选择电路306可以起根据度量选择码元候选者的Su和相位候选者的Su的作用。所选相位候选者被称为相位生存者每个相位生存者的每个元素可能对应于信号232中的残余相位误差,也就是说,经由相位调整电路206粗略相位误差校正之后保留在信号中的相位误差的估计值。最佳相位生存者经由信号307a传送。为顺序估计过程的下一次迭代保留Su个相位生存者(在该时间上经由信号301b传送它们)。所选码元候选者被称为码元生存者每个码元生存者的每个元素可能包含信号232的码元和/或信息位的软判定估计值和/或硬判定估计值。最佳码元生存者经由信号307b传送给码元缓冲器310。为顺序估计过程的下一次迭代保留Su个码元生存者(在该时间上经由信号301a传送它们)。尽管所述的示范性实现选择了相位生存者和码元生存者的相同数量Su,但未必是这样的情况。示范性候选者选择电路306的操作将在下面参考图5D和6A-6B加以描述。
候选者生成电路302可以起从相位生存者和码元生存者中生成相位候选者和码元候选者的作用,其中索引n-1指示它们是用于生成时间n的候选者的来自时间n-1的生存者。在一种示范性实现中,相位和/或码元候选者的生成可以如,举例来说,下面参考图5A-5C和/或在以下专利文献中所述:如上所述、通过引用并入本文中的发明名称为“低复杂性、高频谱有效性通信”的美国专利申请。
码元缓冲器电路310可以包含可起存储一个或多个码元生存者矢量的一个或多个码元生存者元素作用的多个存储元件。相位缓冲器电路312可以包含可起存储一个或多个相位生存者矢量作用的多个存储元件。缓冲器310和312的示范性实现描述在以下专利文献中:如上所述、通过引用并入本文中的发明名称为“低复杂性、高频谱有效性通信”的美国专利申请。
组合器电路308可以起将经由信号307a传送的最佳相位矢量与载波恢复电路208(图2)生成的信号228组合,以生成与信号222(图2)的细致估计相位误差相对应、经由信号309传送的细致相位误差矢量的作用。在每个时间n上,可以用盖写存储在相位缓冲器312中的
相位调整电路314可以起将信号315a的相位调整通过相位缓冲器312输出的信号234确定的数量,以生成信号205的作用。
进行卷积的电路316a可以包含,举例来说,FIR滤波器或IIR滤波器。电路316a可以起将信号132与响应卷积,得出部分响应信号315a的作用。类似地,卷积电路316b可以起将信号317与响应卷积,得出部分响应信号209的作用。如上所述,响应可以以一个或多个抽头系数的形式由顺序估计电路210存储,和/或传送给顺序估计电路210,该一个或多个抽头系数可以根据脉冲成形器104和/或输入滤波器109的抽头系数和/或根据判定反馈均衡器(DFE)的自适应算法来确定。响应因此可以代表一方面试图完美地重构总部分响应信号(如通过脉冲成形器104和输入滤波器109修改的103)与另一方面补偿信道107的多路径和/或其它不理想东西之间的折衷。关于这一点,系统100可以包含如以下一个或多个专利文献所述的一个或多个DFE:如上所述、通过引用并入本文中的发明名称为“高频谱有效性通信的判定反馈均衡器”的美国专利申请、发明名称为“高频谱有效性通信的具有多个核心的判定反馈均衡器”的美国专利申请、和发明名称为“高频谱有效性通信的利用码元出错率偏置自适应函数的判定反馈均衡器”的美国专利申请。
因此,信号203通过取出发送码元的第一估计值(码元生存者的元素),经由电路316a将发送码元的第一估计值转换到部分响应域,然后经由电路236a(图2)补偿通信系统100中的非线性生成。类似地,信号207从经由电路316b转换到部分响应域以生成信号209,然后将非线性模型应用于信号209b以补偿信号路径中的非线性的发送码元的第二估计值(码元生存者的元素)中生成。
图4是描绘用在为低复杂性、高频谱有效性通信配置的系统中的示范性度量计算电路的方块图。所示的是相位调整电路402、卷积电路404、成本函数计算电路406、和非线性模拟电路408。相位调整电路402可以将矢量PR1(经由信号232传送)的一个或多个元素相移相位候选者矢量的相应一个或多个值。因此相位调整电路402输出的信号403传送每一个包含PR1的多种相移形式的多个部分响应矢量
进行卷积的电路404可以包含,举例来说,FIR滤波器或IIR滤波器。电路404可以起将码元候选者矢量与卷积的作用。因此电路404输出的信号405传送每一个是候选者部分响应矢量的矢量但是,本公开在顺序估计期间不局限于卷积的应用,其(该卷积)只是在为基于部分响应的通信配置系统的情况下使用的特定做法。一般说来,可以在候选者矢量与相应多个线性组合权重之间应用(例如,以矩阵相乘的形式)线性组合。换句话说,线性组合(例如,矩阵相乘)可以总体上与使用ISC信号相联系,而卷积可以特定地与部分响应信号相联系。这种要求覆盖了ISC信号—即,码元与部分响应抽头的卷积可以等效于码元与作为线性组合权重的滤波器抽头的线性组合的应用。
非线性模拟电路408可以将非线性函数(在到电路210的途中通过接收信号看到的非线性的模型)应用于信号405得出信号407。因此电路408输出的信号407传送每一个是非线性调整候选者部分响应矢量的矢量
可以为每个接收样本计算候选者分支分量地在每次迭代时累积与顺序估计有关的度量。在非线性模型包含记忆(例如,模型输出的结果可以是前部分响应样本的函数)的情况下,可以回归地更新该度量。举例来说,假设非线性模型具有1级的记忆(即,非线性模型的输出取决于当前输入和前一级输入),则度量更新可能需要回归地修改前分支度量来反映在1上的记忆深度。换句话说,在非线性模型的记忆深度是m的情况下,在每次迭代时应该连同与新到来样本有关的新度量更新与任何给定候选者相联系的度量以便回归m个前分支度量。
成本函数计算电路406可以起生成指示部分响应矢量的一个或多个与矢量的一个或多个之间的相似性的度量,以便生成误差度量的作用。在一种示范性实现中,误差度量可以是如下面方程1所示计算的欧几里德距离。
对于1≤i≤M×Su×P,
图5A-5E描绘了为高度容忍非线性地联合顺序估计码元和相位配置的系统执行的示范性顺序估计过程的一些部分。在图5A-5E中,为了例示的目的,假设M=4(α,β,χ,δ的码元字母表),Su=3(每次迭代选择三个码元生存者),Psu=Su(每次迭代选择三个相位生存者),p=3(+,-,或0的相位字母表),以及Q(矢量长度)是4。
参照图5A,在图形的左侧示出了来自时间n-1的相位和码元生存者。高度容忍非线性地从生存者中生成码元候选者和相位候选者的第一步骤是复制生存者,移位图5A的右侧上叫做502的每个所得矢量中的内容,以及另外,对于每个码元矢量,将‘0’插入空元素中。在描绘的示范性实施例中,复制生存者M*P-1次并移位一个元素,将‘0’插入码元矢量的最右边元素中。
参照图5B,生成候选者的下一个步骤是插入码元矢量中的码元值和相位矢量中的相位值,得出时间n的矢量和相位候选者(在图5B中叫做405)。关于这一点,对于相位矢量,将相位值插入相位矢量的空元素中。但是,对于码元矢量,将码元值插入码元矢量的[n-1]元素中而不是[n]元素中。
鉴于部分响应脉冲成形的使用,以及鉴于发送器和/或接收器中非线性的存在,将码元值插入码元矢量的[n-1]元素中而不是[n]元素中可以改善估计过程。关于这一点,因为部分响应信号是在部分响应滤波器抽头与映射码元之间应用卷积函数生成的,所以任何码元通常都可能影响数量等于部分响应的长度的样本。但是,可能打算用于估计的(未知)最近码元可能只影响最近接收的样本。如,举例来说,特此通过引用全文并入本文中的“如上所述、通过引用并入本文中的发明名称为‘部分响应脉冲成形滤波器的设计和优化’的美国专利申请”所述,将最近码元的贡献乘以可以配置成具有相对较低幅度的最早部分响应滤波器抽头的因子,以便使脉冲成形最佳。因此,最近码元对接收信号的最近样本的影响可能很小。因此,最近码元的估计可能对甚至低水平的噪声或干扰敏感—例如,甚至低水平的AWGN都可能在估计最近码元时引起误差。估计最近码元的误差又可能影响随后码元的估计以及导致错误猝发。因此,由于估计最近码元的可能低可靠性,以及顺序估计可能局限于状态空间M^(L-1)的非常小子集的M*Su个候选者的事实,生存者选择可能导致要不然对于整个MLSE搜索可能不会出现的错误猝发。于是,为了不增加生存者的数量(要不然使复杂性增加)地提高顺序估计性能,可以对实际上可能是前未知码元的每个码元候选者中的第2元素(即,[n-1]元素)计算分支度量。但是,为了计算这样的度量,可能需要将“填充物”的值填入候选者矢量的第1元素中,以便该度量是候选者之间的公正比较物。于是,填充物的值可以将,逆计算用于每个生存者的候选者以满足成本函数来确定。填充物的值可以由,举例来说,顺序估计电路112计算。逆计算将参照图5C(下面)作更详细描述。因为逆计算可能表现得没有最大似然那么好(因此可能引起总出错率恶化),所以可能有必要使用搜索重复码元的估计(对于第1元素)。换句话说,填充物的值只用于在这次迭代期间计算分支度量,然后在下一次迭代中被放弃和/或盖写。举例来说,在图5A中,的第1元素中的α、的第1元素中的α、和的第1元素中的β每一个都可以是然后在图5B中被放弃的填充物值。
在描绘的示范性实现中,将M个可能码元值的每一个插入码元矢量的元素[n-1]上的Su*P个码元候选者中,以及可以将P个相位值的每一个插入空[n]元素上的M*Su个候选者中。关于这一点,在描绘的示范性实现中,θ5是根据相位生存者计算的参考相位值。举例来说,θ5可以是相位生存者的最后两个或更多个元素的平均值(或加权平均值)(在所示的例子中,最后两个元素的平均值是(θ5+0)/2)。在描绘的示范性实现中,θ4=θ5–Δθ,以及θ6=θ5+Δθ,其中Δθ基于:信号226中的相位噪声的数量、信号226中的相位噪声的斜率(导数)、信号226的信噪比(SNR)、和/或信道107的容量。类似地,在所示的示范性实施例中,θ8是根据相位生存者计算的参考相位值。θ7=θ8–Δθ,θ9=θ8+Δθ,θ11是根据相位生存者计算的参考相位值。θ10=θ11–Δθ,以及θ12=θ11+Δθ。
参照图5C,下一个步骤是生成码元矢量中的第n元素的填充物值(即,以便插入码元矢量中的元素[n]中),得出码元候选者和相位候选者(在图5C中被显示成506)。关于这一点,为了在候选者之间作出公正比较,可以根据与接收信号的最佳匹配计算第n元素的码元估计值。
码元估计值的生成可以使用逆计算(按每个候选者)使成本函数最小地计算。关于这一点,码元估计值计算可以基于,举例来说,码元、部分响应、和噪声。举例来说,当采用线性信道时,可以通过下式表达部分响应接收信号:
其中xn是时刻n接收器上的接收信号,是Tx部分响应的抽头系数的矢量,是转置发送码元矢量(即,得出xn的发送码元)、和wn是噪声(例如,加性高斯白噪声或AWGN)。
对于线性信道情况,可以将顺序估计配置成使平方误差最小:其中是提供最小值的估计码元矢量,以及是顺序估计使用的部分响应滤波函数。当采用将其最近元素设置成零、和将其第2元素设置成要估计的码元的可能值之一的候选者码元矢量(即,采用作为图5B中的码元矢量之一的转置的候选者码元矢量)时,可以将与有关的遗漏贡献参数确定为:
其中对应于用于顺序估计的部分响应的第1抽头的系数。
于是,当采用线性信道时,估计码元矢量的第n元素的逆计算可以通过,举例来说,如方程2(EQ.2)所表达,按照用于发送码元的码元群集限幅贡献参数来确定:
但是,在存在非线性的情况下,码元候选者估计可能需要配置成具体考虑非线性。因此,当假设接收器已知接收信号经历的失真(例如,非线性)时,在顺序估计期间可以使用非线性失真的模型,以便可以几乎没有任何恶化地容忍非线性失真(例如,如通过SER确定)。在存在非线性的情况下,可以将接收信号表达成:
其中是非线性函数。该非线性模型可以,举例来说,表达成:
估计算法可以,举例来说,被配置成使平方距离(欧几里德)成本函数最小。该距离可以在接收(均衡)信号样本与重构信号候选者之间计算。可以便成本函数最小的候选者(最佳度量)成为估计解(即,被选为生存者)。如果码元候选者的生成不考虑信号的实际响应(例如,包括非线性),则顺序估计可以收敛成错误解。于是,在一个示范性实施例中,在应用成本函数计算(如图4所示)之前,可以对每个部分响应重构候选者应用非线性模型。因此,重构候选者可能经历与接收信号相同的响应(例如,包括非线性),以及成本函数最小化可能是精确的,取得与最大似然(ML)解相当的解。
举例来说,假设是候选者码元矢量(例如,码元候选者之一),则将非线性模型应用于那个矢量将得出:即,并入非线性模型的重构部分响应信号(例如,之一的最近样本)。然后可以将平方误差信号(例如,之一)修正成如下形式:
在一种示范性实现中,可以进一步调整上述的修正顺序估计过程的组合和非线性模型的并入。举例来说,因为候选者最初(在图5B的504之后)具有零而不是最近码元,所以与完全码元填充候选者相比,非线性模型的施行可能引入一些错误。假设该误差足够小(原因是,由于在PR实现中主要是ISI,所以最近码元的贡献小),则可以使用,举例来说,线性外推校正该误差:
fNL(y+Δy)≌fNL(y)+f′NL(y)·Δy
其中f′NL(y)是非线性模型fNL(y)的斜率,两者都为接收器所知。
假设作为未知最近码元候选者的贡献的以及是候选者矢量的已知贡献,则可以如方程3(EQ.3)所表达,将非线性模型下的未知最近码元确定为:
因此,如生成用在图5C中的填充物值的方程4(EQ.4)所示,最近码元的值可以是通过(按照正在使用的码元群集)限幅从方程3中获得的值获得的值:
其中:
于是,可以将用于生成度量的第y码元矢量候选者(例如,如506所示)表达成:
其中Symy可以是为搜索插入的M个可能码元值之一(例如,前一次迭代中相同候选者的移位第n元素)。
参照图5D,以及参照图4,然后经由卷积(例如,在电路404中)将码元候选者变换到部分响应域,然后可以将非线性模型应用于所有候选者(例如,在电路408中通过非线性函数),调整参考信号PR1的相位,以及然后根据部分响应信号和计算度量
参照图5E,将在图5D中计算的度量用于选择将在图5C中生成的哪些候选者选成顺序估计过程的下一次迭代的生存者。图5E描绘了通过简单选择与Su个最佳度量相对应的Su个候选者在单个步骤中选择生存者的示范性实现。在描绘的示范性实现中,假设度量是最佳度量,是次最佳度量,以及是第三佳度量。于是,码元候选者被选成最佳码元生存者,被选成最佳相位生存者,码元候选者被选成次最佳码元生存者,被选成次最佳相位生存者,码元候选者被选成第三佳码元生存者,以及被选成第三佳相位生存者。图5E的生存者选择过程可能导致选择了可能非所希望的相同码元候选者。防止冗余码元生存者的生存者选择过程的例子描述在图6以及以下专利文献中:如上所述、通过引用并入本文中的发明名称为“低复杂性、高频谱有效性通信”的美国专利申请。
图6是例示高度容忍非线性地顺序估计以便接收部分响应信号的示范性过程的流程图。该过程从将第一部分响应矢量(例如,PR1)输入矢量计算电路(例如,电路402)中的方块602开始。在方块604中,根据第一部分响应信号和多个相位候选者矢量(例如,)生成多个第二部分响应相位矢量(例如,)。在方块606中,将多个候选码元矢量(例如,)与多个抽头系数(例如,与响应相对应的抽头系数)卷积以生成多个第三部分响应矢量(例如,)。更进一步,在一些情况下,可以将非线性模型应用于多个第三部分响应矢量,以生成多个非线性调整候选者部分响应矢量(例如,)。在方块608中,根据第二部分响应矢量生成度量(例如,矢量之间的欧几里德距离)以及生成第三部分响应矢量(例如,通过电路406)。在方块610中,根据在方块608中生成的度量选择一个或多个候选者矢量。在方块612中,将生存者矢量的最佳一个(例如,与最低度量相对应的生存者矢量)的码元作为估计发送码元输出到反映射器。
在本公开的示范性实现中,接收器可以接收让码元通过非线性电路(例如,电路106和/或电路108)生成的单载波码元间关联(ISC)信号(例如,信号68或信号120)。接收器可以使用顺序估计过程(例如,通过电路62实现)和非线性电路的模型(例如,通过电路236a和/或236b实现)生成发送码元的估计值。ISC信号可以是经由部分响应滤波器(例如,包含滤波器104和/或109的部分响应滤波器)生成的部分响应信号。接收器可以生成ISC反馈信号(例如,信号203),并根据ISC反馈信号控制接收器的均衡器。接收器可以生成ISC反馈信号(例如,信号207),并根据ISC反馈信号控制载波电路。
该顺序估计过程可以包含将多个候选者码元矢量的每一个(例如,矢量的每一个)与多个抽头系数卷积,以生成多个第一ISC矢量的相应一个(例如,矢量之一)。更进一步,在一些情况下,可以将非线性模型应用于多个第一ISC矢量,以生成多个非线性调整ISC矢量(例如,)。该顺序估计过程可以包含生成多个度量(例如,度量),该度量的每一个对应于使用第一ISC矢量(例如,)和第二ISC矢量(例如,)之一计算的成本函数的结果。该多个抽头系数可以基于部分响应滤波器的抽头系数(例如,滤波器104和/或109的抽头系数)。该顺序估计过程可以包含根据多个度量选择候选者码元矢量之一。该顺序估计过程可以包含输出所选候选者码元矢量的码元(例如,码元候选者的索引q2上的码元)作为发送码元的估计值之一。
其它实现可以提供上面存储着机器和/或计算机可执行的机器代码和/或含有至少一个代码段的计算机程序,从而使机器和/或计算机可以执行如本文所述的过程的非短暂计算机可读介质和/或存储介质、和/或非短暂机器可读介质和/或存储介质。
本文公开的方法和系统可以用硬件、软件、或硬件和组合的组合体实现。本文公开的方法和系统可以在至少一个计算系统中以集中方式,或以不同元件分散在几个互连计算系统上的分布方式实现。适用于执行本文所述的方法的任何类型计算系统或其它装置都是合适的。硬件和软件的典型组合体可以是通用计算系统,该通用计算系统带有当被装载和执行时,控制该计算系统,以便其执行本文所述的方法的程序或其它代码。另一种典型实现可以包含专用集成电路(ASIC)或芯片,该ASIC或芯片带有当被装载和执行时,控制该ASIC或芯片,以便其执行本文所述的方法的程序或其它代码。
虽然本文参考某些实现描述了一些方法和系统,但本领域的普通技术人员要明白的是,可以不偏离本发明方法和/或系统的范围地作出各种改变和替代等效物。另外,可以不偏离其范围地作出各种修改以便使特定状况或材料适合本发明方法和/或系统的教导。因此,意图是使本发明方法和/或系统不局限于公开的特定实现,而是使本发明方法和/或系统包括在所附权利要求书的范围之内的所有实现。
Claims (21)
1.一种方法,包含:
在顺序估计电路中接收与码元的发送矢量相对应的接收码元间关联(ISC)信号的样本,其中每个所述码元是特定群集中的多个码元之一;以及
使用减少状态顺序估计(RSSE)过程生成码元的所述发送矢量的估计值,其中:
在所述顺序估计过程期间使用所述ISC信号经历的非线性失真的模型;
所述RSSE过程的每次迭代包含生成多个码元候选者矢量;
每个所述码元候选者矢量的第一元素保存所述特定群集中的所述多个码元的相应一个;以及
所述第一元素是除了码元的所述发送矢量的最近码元之外的码元的所述发送矢量的其它码元的估计值。
2.如权利要求1所述的方法,其中每个所述码元候选者矢量的第二元素保存多个计算填充物值的相应一个。
3.如权利要求2所述的方法,其中所述第二元素是比所述第一元素更近的元素。
4.如权利要求2所述的方法,包含:
计算码元的所述发送矢量的所述最近码元对所述接收ISC信号的所述接收样本的贡献;以及
通过按照所述特定群集限幅所述贡献计算所述填充物值。
5.如权利要求4所述的方法,其中所述计算所述贡献包含生成多个零填充码元候选者矢量,其中每个所述零填充码元候选者矢量的所述第一元素保存所述特定群集中的所述多个码元的相应一个,以及比所述第一元素更近的所述零填充码元候选者矢量的元素保存零。
6.如权利要求1所述的方法,包含当所述接收ISC信号是部分响应信号时,通过将所述多个码元候选者矢量与多个抽头系数卷积,生成多个部分响应码元候选者矢量。
7.如权利要求6所述的方法,包含通过将非线性模型应用于所述多个部分响应码元候选者矢量的每一个,生成多个重构部分响应码元候选者矢量。
8.如权利要求7所述的方法,包含根据所述多个重构部分响应码元候选者和所述接收部分响应信号的所述样本生成所述多个度量。
9.如权利要求1所述的方法,其中:
所述最近码元是码元的所述发送矢量的第一码元;以及
除了所述最近码元之外的所述其它码元是码元的所述发送矢量的第二码元。
10.如权利要求1所述的方法,其中所述RSSE过程的每次迭代包含生成多个相位候选者矢量。
11.一种系统,包含:
顺序估计电路,其可操作来:
接收与码元的发送矢量相对应的接收码元间关联(ISC)信号的样本,其中每个所述码元是特定群集中的多个码元之一;以及
使用减少状态顺序估计(RSSE)过程生成码元的所述发送矢量的估计值,其中:
所述RSSE过程的每次迭代包含生成多个码元候选者矢量;
每个所述码元候选者矢量的第一元素保存所述特定群集中的所述多个码元的相应一个;以及
所述第一元素是除了码元的所述发送矢量的最近码元之外的码元的所述发送矢量的其它码元的估计值。
12.如权利要求11所述的系统,其中每个所述码元候选者矢量的第二元素保存多个计算填充物值的相应一个。
13.如权利要求12所述的系统,其中所述第二元素是比所述第一元素更近的元素。
14.如权利要求12所述的系统,其中所述顺序估计电路可操作来:
计算码元的所述发送矢量的所述最近码元对所述接收ISC信号的所述接收样本的贡献;以及
通过按照所述特定群集限幅所述贡献计算所述填充物值。
15.如权利要求14所述的系统,其中所述贡献的所述计算包含多个零填充码元候选者矢量的生成,其中每个所述零填充码元候选者矢量的所述第一元素保存所述特定群集中的所述多个码元的相应一个,以及比所述第一元素更近的所述零填充码元候选者矢量的元素保存零。
16.如权利要求11所述的系统,其中所述顺序估计电路可操作来:当所述接收ISC信号是部分响应信号时,通过将所述多个码元候选者矢量与多个抽头系数卷积生成多个部分响应码元候选者矢量。
17.如权利要求16所述的系统,其中所述顺序估计电路可操作来:通过将非线性模型应用于所述多个部分响应码元候选者矢量的每一个生成多个重构部分响应码元候选者矢量。
18.如权利要求17所述的系统,其中所述顺序估计电路可操作来:根据所述多个重构部分响应码元候选者和所述接收部分响应信号的所述样本生成所述多个度量。
19.如权利要求11所述的系统,其中:
所述最近码元是码元的所述发送矢量的第一码元;以及
除了所述最近码元之外的所述其它码元是码元的所述发送矢量的第二码元。
20.如权利要求11所述的系统,其中所述RSSE过程的每次迭代包含生成多个相位候选者矢量。
21.一种方法,包含:
在顺序估计电路中:
接收与发送码元的矢量相对应的码元间关联(ISC)信号的样本,码元的所述矢量至少包含在第一码元时间期间发送的第一码元、和在紧接在所述第一码元时间之前的第二码元时间期间发送的第二码元;
根据所述接收样本计算一个或多个分支度量;以及
根据所述一个或多个计算分支度量生成所述第二码元的估计值。
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