WO2023073880A1 - 電力変換装置、モータ駆動装置および冷凍サイクル適用機器 - Google Patents

電力変換装置、モータ駆動装置および冷凍サイクル適用機器 Download PDF

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Publication number
WO2023073880A1
WO2023073880A1 PCT/JP2021/039878 JP2021039878W WO2023073880A1 WO 2023073880 A1 WO2023073880 A1 WO 2023073880A1 JP 2021039878 W JP2021039878 W JP 2021039878W WO 2023073880 A1 WO2023073880 A1 WO 2023073880A1
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WIPO (PCT)
Prior art keywords
frequency
amplitude
component
fourier coefficient
axis current
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PCT/JP2021/039878
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English (en)
French (fr)
Japanese (ja)
Inventor
遥 松尾
知宏 沓木
貴昭 ▲高▼原
浩一 有澤
雄紀 谷山
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Mitsubishi Electric Corp
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Mitsubishi Electric Corp
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Priority to CN202180103598.5A priority Critical patent/CN118160213A/zh
Priority to JP2023555992A priority patent/JP7466794B2/ja
Priority to PCT/JP2021/039878 priority patent/WO2023073880A1/ja
Priority to US18/690,958 priority patent/US20250141340A1/en
Publication of WO2023073880A1 publication Critical patent/WO2023073880A1/ja
Anticipated expiration legal-status Critical
Ceased legal-status Critical Current

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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/12—Arrangements for reducing harmonics from AC input or output
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P27/00—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage
    • H02P27/04—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage
    • H02P27/06—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage using DC to AC converters or inverters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/14—Arrangements for reducing ripples from DC input or output
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/14—Arrangements for reducing ripples from DC input or output
    • H02M1/15—Arrangements for reducing ripples from DC input or output using active elements
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/44—Circuits or arrangements for compensating for electromagnetic interference in converters or inverters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M5/00—Conversion of AC power input into AC power output, e.g. for change of voltage, for change of frequency, for change of number of phases
    • H02M5/40—Conversion of AC power input into AC power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into DC
    • H02M5/42—Conversion of AC power input into AC power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into DC by static converters
    • H02M5/44—Conversion of AC power input into AC power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into DC by static converters using discharge tubes or semiconductor devices to convert the intermediate DC into AC
    • H02M5/453—Conversion of AC power input into AC power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into DC by static converters using discharge tubes or semiconductor devices to convert the intermediate DC into AC using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M5/458—Conversion of AC power input into AC power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into DC by static converters using discharge tubes or semiconductor devices to convert the intermediate DC into AC using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P21/00—Arrangements or methods for the control of electric machines by vector control, e.g. by control of field orientation
    • H02P21/05—Arrangements or methods for the control of electric machines by vector control, e.g. by control of field orientation specially adapted for damping motor oscillations, e.g. for reducing hunting

Definitions

  • the present disclosure relates to a power conversion device, a motor drive device, and a refrigeration cycle application device that convert AC power into desired power.
  • Patent Literature 1 discloses a technique for suppressing vibration by performing compensation by adding a pulsating component for suppressing vibration in a motor drive device to the q-axis current.
  • a typical power conversion device used in a motor drive device as described above rectifies AC power supplied from an AC power supply in a rectifying section, smoothes it in a smoothing capacitor, and converts it into a desired voltage in an inverter composed of a plurality of switching elements. is converted to AC power and output to the motor.
  • aging deterioration of the smoothing capacitor is accelerated when a large current flows through the smoothing capacitor.
  • the AC power rectified by the rectifier pulsates at twice the frequency of the AC power supplied from the AC power supply. to pulsate the q-axis current.
  • the pulsating component of the current flowing through the smoothing capacitor contains a high-frequency component such as a double component or a triple component based on the double frequency of the AC power, the AC power supplied from the AC power supply
  • the effect of the capacitor current suppression control cannot be sufficiently obtained only by the control targeting the double frequency.
  • various control targets are assumed for the compensation control for pulsating the q-axis current.
  • the present disclosure has been made in view of the above, and aims to obtain a power conversion device capable of improving the accuracy of compensation in compensation control for pulsating the q-axis current.
  • a power conversion device includes a rectification unit that rectifies first AC power supplied from a commercial power supply, and a rectification unit that is connected to an output end of the rectification unit.
  • a capacitor, an inverter connected to both ends of the capacitor to generate a second AC power and output it to the motor, and a dq rotation coordinate that rotates in synchronization with the position of the rotor of the motor are used to control the operation of the inverter and the motor. and a control unit for controlling.
  • the control unit extracts a plurality of frequency components from the q-axis current pulsation, which is the pulsation component of the q-axis current, and limits the amplitude value of each extracted frequency component to control the amplitude of the q-axis current pulsation.
  • the power conversion device has the effect of being able to improve the accuracy of compensation in compensation control that pulsates the q-axis current.
  • FIG. 1 is a diagram showing a configuration example of a power converter according to Embodiment 1;
  • FIG. FIG. 2 is a block diagram showing a configuration example of a control unit included in the power converter according to Embodiment 1;
  • FIG. 2 is a block diagram showing a configuration example of a q-axis current pulsation calculator included in the controller of the power converter according to Embodiment 1;
  • 4 is a flow chart showing the operation of the q-axis current pulsation calculator included in the controller of the power converter according to Embodiment 1;
  • FIG. 2 is a diagram showing an example of a hardware configuration that realizes a control unit included in the power converter according to Embodiment 1;
  • FIG. 4 is a block diagram showing a configuration example of a control unit included in a power converter according to Embodiment 2;
  • FIG. 10 is a block diagram showing a configuration example of a q-axis current pulsation calculator included in the controller of the power converter according to Embodiment 2;
  • 8 is a flow chart showing the operation of a q-axis current pulsation calculator included in the controller of the power converter according to Embodiment 2;
  • a first block diagram showing a configuration example of a q-axis current pulsation calculation unit included in a control unit of a power converter according to Embodiment 3.
  • FIG. 10 is a block diagram showing a configuration example of a control unit included in a power converter according to Embodiment 4;
  • FIG. 11 is a block diagram showing a configuration example of a q-axis current pulsation calculator included in a controller of a power converter according to Embodiment 4;
  • 10 is a flow chart showing the operation of a q-axis current pulsation calculator included in the controller of the power converter according to the fourth embodiment;
  • a first block diagram showing a configuration example of a q-axis current pulsation calculator included in a controller of a power converter according to Embodiment 5.
  • FIG. 11 is a block diagram showing a configuration example of a control unit included in a power converter according to a sixth embodiment;
  • 9 is a flow chart showing the operation of a q-axis current pulsation calculator included in the controller of the power converter according to the sixth embodiment;
  • a power conversion device, a motor drive device, and a refrigeration cycle application device will be described below in detail based on the drawings.
  • FIG. 1 is a diagram showing a configuration example of a power conversion device 1 according to Embodiment 1.
  • Power converter 1 is connected to commercial power source 110 and compressor 315 .
  • Power converter 1 converts first AC power having power supply voltage Vs supplied from commercial power supply 110 into second AC power having a desired amplitude and phase, and supplies the second AC power to compressor 315 .
  • the power conversion device 1 includes a reactor 120 , a rectification section 130 , a voltage detection section 501 , a smoothing section 200 , an inverter 310 , current detection sections 313 a and 313 b , and a control section 400 .
  • a motor drive device 2 is configured by the power conversion device 1 and the motor 314 included in the compressor 315 .
  • Reactor 120 is connected between commercial power supply 110 and rectifying section 130 .
  • the rectifying section 130 has a bridge circuit configured by rectifying elements 131 to 134, rectifies the first AC power of the power supply voltage Vs supplied from the commercial power supply 110, and outputs the first AC power.
  • the rectifier 130 performs full-wave rectification.
  • the voltage detection unit 501 detects the DC bus voltage Vdc , which is the voltage across the smoothing unit 200 charged by the current rectified by the rectifying unit 130 and flowing into the smoothing unit 200 from the rectifying unit 130, and detects the detected voltage value. is output to the control unit 400 .
  • Voltage detection unit 501 is a detection unit that detects the power state of capacitor 210 .
  • the smoothing section 200 is connected to the output terminal of the rectifying section 130 .
  • Smoothing section 200 has capacitor 210 as a smoothing element, and smoothes the power rectified by rectifying section 130 .
  • Capacitor 210 is, for example, an electrolytic capacitor, a film capacitor, or the like.
  • Capacitor 210 is connected to the output end of rectifying section 130 and has a capacity to smooth the power rectified by rectifying section 130 . It does not have a waveform shape, but has a waveform shape in which a voltage ripple corresponding to the frequency of the commercial power supply 110 is superimposed on the DC component, and does not pulsate greatly.
  • the frequency of this voltage ripple is a component twice the frequency of the power supply voltage Vs when the commercial power supply 110 is single-phase, and the main component is a frequency component six times the frequency of the power supply voltage Vs when the commercial power supply 110 is three-phase. If the power input from commercial power supply 110 and the power output from inverter 310 do not change, the amplitude of this voltage ripple is determined by the capacitance of capacitor 210 . For example, it pulsates in such a range that the maximum value of the voltage ripple generated in the capacitor 210 is less than twice the minimum value.
  • the inverter 310 is connected to both ends of the smoothing section 200 , that is, the capacitor 210 .
  • Inverter 310 has switching elements 311a-311f and freewheeling diodes 312a-312f.
  • Inverter 310 turns switching elements 311a to 311f on and off under the control of control unit 400, and converts the power output from rectifying unit 130 and smoothing unit 200 into second AC power having a desired amplitude and phase. of AC power is generated and output to the compressor 315 .
  • Current detection units 313 a and 313 b each detect a current value of one phase out of three-phase currents output from inverter 310 and output the detected current value to control unit 400 .
  • Control unit 400 acquires two-phase current values among the three-phase current values output from inverter 310, thereby calculating the remaining one-phase current value output from inverter 310.
  • Compressor 315 is a load having a motor 314 for driving the compressor. Motor 314 rotates according to the amplitude and phase of the second AC power supplied from inverter 310 to perform compression operation.
  • the compressor 315 is a hermetic compressor used in an air conditioner or the like
  • the load torque of the compressor 315 can often be regarded as a constant torque load.
  • FIG. 1 shows a case where the motor windings are Y-connected, but this is only an example and the present invention is not limited to this.
  • the motor windings of the motor 314 may be delta-connection, or may be switchable between Y-connection and delta-connection.
  • reactor 120 may be arranged after rectifying section 130 .
  • the power conversion device 1 may include a booster section, or the rectifier section 130 may have the function of the booster section.
  • the voltage detection section 501 and the current detection sections 313a and 313b may be collectively referred to as detection sections.
  • the voltage value detected by the voltage detection section 501 and the current values detected by the current detection sections 313a and 313b may be referred to as detection values.
  • the control unit 400 acquires the voltage value of the DC bus voltage Vdc of the smoothing unit 200 from the voltage detection unit 501, and obtains the second AC voltage having the desired amplitude and phase converted by the inverter 310 from the current detection units 313a and 313b. Get the current value of power.
  • Control unit 400 controls the operation of inverter 310, specifically, the on/off of switching elements 311a to 311f included in inverter 310, using the detection values detected by the respective detection units. Also, the control unit 400 controls the operation of the motor 314 using the detection values detected by each detection unit.
  • control unit 400 outputs second AC power including pulsation corresponding to the pulsation of power flowing from rectifying unit 130 into capacitor 210 of smoothing unit 200 from inverter 310 to compressor 315 as a load.
  • the operation of the inverter 310 is controlled so as to
  • the pulsation corresponding to the pulsation of the power flowing into the capacitor 210 of the smoothing section 200 is, for example, the pulsation that varies depending on the frequency of the pulsation of the power flowing into the capacitor 210 of the smoothing section 200 .
  • the control unit 400 suppresses the current flowing through the capacitor 210 of the smoothing unit 200 .
  • the control unit 400 does not have to use all the detection values acquired from each detection unit, and may perform control using some of the detection values.
  • the control unit 400 performs control so that any one of the speed, voltage, and current of the motor 314 is in a desired state.
  • the motor 314 is used to drive the compressor 315 and the compressor 315 is a hermetic compressor, attaching a position sensor for detecting the rotor position to the motor 314 is structurally and economically advantageous. Since it is difficult, the control unit 400 controls the motor 314 without a position sensor.
  • control unit 400 controls the operations of inverter 310 and motor 314 using dq rotation coordinates that rotate in synchronization with the rotor position of motor 314, as will be described later.
  • the input current from rectifying section 130 to capacitor 210 of smoothing section 200 is input current I1
  • the output current from capacitor 210 of smoothing section 200 to inverter 310 is output current I2.
  • the charge/discharge current of the capacitor 210 of the smoothing section 200 is assumed to be the charge/discharge current I3.
  • the input current I1 is affected by the power supply phase of the commercial power supply 110 and the characteristics of elements installed before and after the rectifying section 130, but basically has characteristics including a 2n-fold component of the power supply frequency. Note that n is an integer of 1 or more.
  • control unit 400 may control inverter 310 so that input current I1 to capacitor 210 equals output current I2 from capacitor 210. .
  • PWM Pulse Width Modulation
  • the control unit 400 monitors the power state of the smoothing unit 200, that is, the capacitor 210, and provides appropriate pulsation to the motor 314 so that the charging/discharging current I3 decreases. good.
  • the power state of the capacitor 210 means the input current I1 to the capacitor 210, the output current I2 from the capacitor 210, the charging/discharging current I3 of the capacitor 210, the DC bus voltage Vdc of the capacitor 210, and the like.
  • Control unit 400 needs information on at least one of these power states of capacitor 210 for deterioration suppression control.
  • control unit 400 uses DC bus voltage Vdc of capacitor 210 detected by voltage detection unit 501 so that a value obtained by removing PWM ripple from output current I2 matches input current I1.
  • a pulsation is applied to the motor 314 . That is, control unit 400 controls the operation of inverter 310 so that the pulsation corresponding to the detection value of voltage detection unit 501 is superimposed on the drive pattern of motor 314, and suppresses charging/discharging current I3 of capacitor 210.
  • the control unit 400 controls the q-axis current command i q * of the motor 314 based on the input/output power relationship of the motor 314 so that the difference between the input current I1 and the output current I2 becomes small.
  • control unit 400 utilizes the relationship between the input power to inverter 310 and the mechanical output of motor 314 to generate an ideal q-axis current command i q * for reducing charging/discharging current I3. calculate.
  • control unit 400 performs control in rotational coordinates having the d-axis and the q-axis.
  • Power converter 1 is capable of estimating charging/discharging current I3 of capacitor 210 from DC bus voltage Vdc of capacitor 210, and is equipped with a current detection unit that detects charging/discharging current I3 of capacitor 210.
  • the voltage detection unit 501 detects the voltage value of the DC bus voltage Vdc of the capacitor 210 and outputs the voltage value to the control unit 400 .
  • Control unit 400 controls inverter 310 so that the value obtained by removing the PWM ripple from output current I2 from capacitor 210 to inverter 310 matches input current I1, and adds pulsation to the power output to motor 314 .
  • Control unit 400 can reduce charge/discharge current I3 of capacitor 210 by appropriately pulsating output current I2. As described above, since the input current I1 to the capacitor 210 contains 2n times the power supply frequency, the output current I2 and the q-axis current iq of the motor 314 also contain 2n times the power supply frequency. become.
  • control unit 400 controls the rotation speed of the motor 314, the DC bus voltage V dc , and the q-axis current command i q to suppress pulsation that occurs in the current flowing through the motor 314. * can be controlled, and these controls can be performed in parallel.
  • FIG. 2 is a block diagram showing a configuration example of the control unit 400 included in the power converter 1 according to Embodiment 1.
  • the control unit 400 includes a rotor position estimation unit 401, a speed control unit 402, a flux-weakening control unit 403, a current control unit 404, coordinate conversion units 405 and 406, a PWM signal generation unit 407, a q-axis current A pulsation calculator 408 and an adder 409 are provided.
  • the rotor position estimating unit 401 calculates the direction of the rotor magnetic poles on the dq axis for the rotor (not shown) of the motor 314 from the dq-axis voltage command vector V dq * and the dq-axis current vector i dq applied to the motor 314. Estimate an estimated phase angle ⁇ est and an estimated speed ⁇ est , which is the rotor speed.
  • a speed control unit 402 generates a q-axis current command i qDC * from the speed command ⁇ * and the estimated speed ⁇ est . Specifically, the speed control unit 402 automatically adjusts the q-axis current command iqDC * so that the speed command ⁇ * and the estimated speed ⁇ est match.
  • the speed command ⁇ * is, for example, a temperature detected by a temperature sensor (not shown) or a setting indicated by a remote control that is an operation unit (not shown). It is based on information indicating temperature, information on selection of operation mode, instruction information on operation start and operation end, and the like. The operation modes are, for example, heating, cooling, and dehumidification.
  • the q-axis current command iqDC * may be referred to as the first q-axis current command.
  • the flux-weakening control unit 403 automatically adjusts the d-axis current command i d * so that the absolute value of the dq-axis voltage command vector V dq * falls within the limit value of the voltage limit value V lim * . Further, in the present embodiment, the flux-weakening control unit 403 performs flux-weakening control in consideration of the q-axis current ripple command i qrip * calculated by the q-axis current ripple calculation unit 408 .
  • the flux-weakening control can be broadly classified into a method of calculating the d-axis current command id * from the equation of the voltage limit ellipse, and a method in which the deviation of the absolute value between the voltage limit value Vlim * and the dq-axis voltage command vector Vdq * is zero. There are two methods of calculating the d-axis current command i d * so that
  • the current control unit 404 controls the current flowing through the motor 314 using the q-axis current command iq * and the d-axis current command id * to generate the dq-axis voltage command vector Vdq * . Specifically, the current control unit 404 automatically adjusts the dq-axis voltage command vector V dq * so that the dq-axis current vector i dq follows the d-axis current command id * and the q-axis current command i q *. .
  • the dq-axis voltage command vector V dq * may be simply referred to as the dq-axis voltage command.
  • the coordinate conversion unit 405 coordinates-converts the dq-axis voltage command vector V dq * from the dq coordinates into the voltage command V uvw * of the AC quantity according to the estimated phase angle ⁇ est .
  • a coordinate transformation unit 406 coordinates-transforms the current I uvw flowing through the motor 314 from an alternating current quantity to a dq-axis current vector i dq of dq coordinates in accordance with the estimated phase angle ⁇ est .
  • the control unit 400 controls the two-phase current values detected by the current detection units 313a and 313b among the three-phase current values output from the inverter 310, and It can be obtained by calculating the current value of the remaining one phase using the current values of the two phases.
  • PWM signal generation unit 407 generates a PWM signal based on voltage command V uvw * coordinate-transformed by coordinate transformation unit 405 .
  • Control unit 400 applies a voltage to motor 314 by outputting the PWM signal generated by PWM signal generation unit 407 to switching elements 311 a to 311 f of inverter 310 .
  • a q-axis current pulsation calculation unit 408 calculates a q-axis current pulsation i q rip according to some pulsation component x rip generated according to the operation of the power converter 1, and is the pulsation component of the q-axis current command i q * . Generate the aforementioned q-axis current pulsation command i qrip * . Since the pulsation amplitude of the q -axis current iq varies depending on the drive conditions of the motor 314, the q-axis current pulsation calculation unit 408 uses PID (Proportional Integral Differential) control or the like to appropriately consider the drive conditions and determine the amplitude. to decide. The detailed configuration and operation of q-axis current pulsation calculator 408 will be described later.
  • PID Proportional Integral Differential
  • Addition unit 409 adds q-axis current command i qDC * output from speed control unit 402 and q-axis current ripple command i qrip * calculated by q-axis current ripple calculation unit 408 to obtain a q-axis current command.
  • i q * is generated and output to current control section 404 .
  • the q-axis current command iq * may be referred to as a second q-axis current command.
  • FIG. 3 is a block diagram showing a configuration example of the q-axis current pulsation calculator 408 included in the controller 400 of the power converter 1 according to Embodiment 1.
  • the q-axis current ripple calculator 408 includes a subtractor 601 , Fourier coefficient calculators 602 to 605 , an amplitude controller 606 , PID controllers 607 to 610 , and an AC restorer 611 .
  • the q-axis current pulsation calculator 408 is configured as a feedback controller with a command value of zero. Feedback controllers generally have a lower control response than feedforward controllers and are unsuitable for suppressing high-frequency pulsations.
  • a well-known method is a method using Fourier coefficient calculation and PID control.
  • the subtraction unit 601 calculates the deviation between the command value of 0 and the pulsation component x rip which is the input signal.
  • the Fourier coefficient calculators 602 to 605 use the theory of Fourier series expansion to extract the amplitudes of the sine signal component and the cosine signal component of a specific frequency included in the deviation calculated by the subtractor 601. .
  • the Fourier coefficient calculators 602 to 605 calculate the amplitudes of the sin1f component, cos1f component, sin2f component, and cos2f component included in the above deviation, with the specified frequency included in the deviation being 1f. Calculate each.
  • the detected signals multiplied by the deviations in the Fourier coefficient calculators 602 to 605 are sin1 ⁇ int , cos1 ⁇ int , sin2 ⁇ int , and cos2 ⁇ int , respectively.
  • the Fourier coefficient calculator 602 multiplies the deviation by the sin1 ⁇ int detection signal to calculate the amplitude value of the sin1f component of the pulsation included in the pulsation component x rip .
  • a Fourier coefficient calculator 603 multiplies the deviation by the cos1 ⁇ int detection signal to calculate the amplitude value of the cos1f component of the pulsation included in the pulsation component x rip .
  • a Fourier coefficient calculator 604 multiplies the deviation by the detected signal of sin2 ⁇ int to calculate the amplitude value of the sin2f component of the pulsation included in the pulsation component x rip .
  • a Fourier coefficient calculator 605 multiplies the deviation by the cos2 ⁇ int detection signal to calculate the amplitude value of the cos2f component of the pulsation included in the pulsation component x rip .
  • the PID control units 607-610 perform proportional-integral-derivative control, that is, PID control, so that the specific frequency components of the deviations extracted by the Fourier coefficient calculators 602-605 are zero.
  • the PID controller 607 is connected to the Fourier coefficient calculator 602
  • the PID controller 608 is connected to the Fourier coefficient calculator 603
  • the PID controller 609 is connected to the Fourier coefficient calculator 604, and the PID controller 608 is connected to the Fourier coefficient calculator 603.
  • the controller 610 is connected to the Fourier coefficient calculator 605 .
  • the proportional gain and the differential gain may be zero, but the value of the integral gain must be non-zero in order to converge the deviation to zero. . Since the output of the integral control normally changes gently, the output from the PID control units 607 to 610 can also be regarded as substantially constant.
  • AC restorer 611 multiplies sin1 ⁇ int , cos1 ⁇ int , sin2 ⁇ int , and cos2 ⁇ int to restore outputs from PID controllers 607 to 610 to AC, and then sums them up to obtain q-axis current pulsation command i qrip . * is generated.
  • the allowable current value of the inverter 310 may be exceeded.
  • the q-axis current pulsation command i qrip * may become excessive. can be prevented.
  • the q-axis current ripple command i qrip * is limited by the limit value i qriplim of the q-axis current ripple command i qrip * , and as a result, each frequency component included in the q-axis current ripple command i qrip * Although the amplitude value decreases, the amplitude value of each frequency component is determined as a matter of course.
  • amplitude control section 606 adjusts the amplitude values of a plurality of frequency components included in q-axis current ripple command i qrip * for each frequency component so that q-axis current ripple calculation section 408 improve the effectiveness of
  • the amplitude control unit 606 may specifically specify the amplitude value of each frequency component to the PID control units 607 to 610 according to the limit value i qriplim of the q-axis current ripple command i qrip * .
  • a ratio for suppressing the amplitude value of each frequency component extracted by the Fourier coefficient calculators 602 to 605 may be specified.
  • Amplitude control section 606 may specify a limit value for PID control sections 607 to 610 to suppress the amplitude value of each frequency component extracted by Fourier coefficient calculation sections 602 to 605, or PID control section 607 610 may be specified to suppress the amplitude value of each frequency component extracted by the Fourier coefficient calculators 602-605.
  • the amplitude control unit 606 may hold the limit value i qriplim of the q-axis current pulsation command i qrip * in advance, or acquire the q-axis current command i qDC * generated by the speed control unit 402 and obtain q It may be obtained by calculation using the shaft current command i qDC * .
  • the q-axis current pulsation calculator 408 includes four Fourier coefficient calculators 602-605 and four PID controllers 607-610, but this is only an example and the present invention is not limited to this.
  • the q-axis current pulsation calculator 408 may include six Fourier coefficient calculators and six PID controllers, or eight or more Fourier coefficient calculators and eight or more PID controllers.
  • the q-axis current pulsation calculator 408 includes six Fourier coefficient calculators and six PID controllers, it controls the sin3f component and the cos3f component in addition to the four frequency components described above.
  • the target is sin3f component, cos3f component, sin4f component, and cos4f component. to control.
  • the q-axis current ripple calculation unit 408 extracts a plurality of frequency components from the q-axis current ripple iqrip , which is the ripple component of the q -axis current iq, and calculates the amplitude of each extracted frequency component. Limit the value to control the amplitude of the q-axis current ripple i qrip .
  • FIG. 4 is a flowchart showing the operation of the q-axis current pulsation calculator 408 included in the controller 400 of the power converter 1 according to Embodiment 1.
  • the subtractor 601 calculates the deviation between the command value of 0 and the ripple component x rip (step S11).
  • the Fourier coefficient calculators 602 to 605 extract frequency components of a plurality of specific frequencies included in the deviation calculated by the subtractor 601 (step S12).
  • the amplitude control unit 606 determines a limit value for limiting the amplitude value of each frequency component (step S13).
  • the PID controllers 607-610 limit the amplitude values of the frequency components extracted by the Fourier coefficient calculators 602-605 using the limit values determined by the amplitude controller 606 (step S14).
  • the AC restoration unit 611 generates the q-axis current pulsation command i qrip * using each frequency component after the amplitude value limitation obtained by the PID control units 607 to 610 (step S15).
  • FIG. 5 is a diagram showing an example of a hardware configuration that implements the control unit 400 included in the power converter 1 according to Embodiment 1. As shown in FIG. Control unit 400 is implemented by processor 91 and memory 92 .
  • the processor 91 is a CPU (Central Processing Unit, central processing unit, processing unit, arithmetic unit, microprocessor, microcomputer, processor, DSP (Digital Signal Processor)), or a system LSI (Large Scale Integration).
  • the memory 92 includes RAM (Random Access Memory), ROM (Read Only Memory), flash memory, EPROM (Erasable Programmable Read Only Memory), EEPROM (registered trademark) (Electrically Erasable Programmable Read Non-volatile or volatile such as Only Memory)
  • RAM Random Access Memory
  • ROM Read Only Memory
  • flash memory flash memory
  • EPROM Erasable Programmable Read Only Memory
  • EEPROM registered trademark
  • a semiconductor memory can be exemplified.
  • the memory 92 is not limited to these, and may be a magnetic disk, an optical disk, a compact disk, a mini disk, or a DVD (Digital Versatile Disc).
  • q-axis current pulsation calculation unit 408 of control unit 400 generates For the included pulsating component, control is performed to limit the amplitude not only of the frequency of the basic pulsating component but also of positive integer multiples of the frequency of the basic pulsating component.
  • the control unit 400 of the power converter 1 can improve the accuracy of compensation in the compensation control for pulsating the q -axis current iq.
  • the power conversion device 1 can obtain effects such as reduction of copper loss.
  • Embodiment 2 a case where the pulsating component x rip is the DC bus voltage V dc detected by the voltage detection unit 501 will be described specifically for capacitor current suppression control.
  • the DC bus voltage Vdc detected by the voltage detection unit 501 is used for explanation.
  • a detection unit it is also possible to use the charging/discharging current I3 of the capacitor 210 instead of the DC bus voltage Vdc .
  • FIG. 6 is a block diagram showing a configuration example of the control unit 400a included in the power converter 1 according to Embodiment 2.
  • Control unit 400a is obtained by replacing q-axis current ripple calculation unit 408 of control unit 400 of Embodiment 1 shown in FIG. 2 with q-axis current ripple calculation unit 408a.
  • the power conversion device 1 according to Embodiment 2 replaces the control unit 400 with a control unit 400a in the power conversion device 1 according to Embodiment 1 shown in FIG. .
  • FIG. 7 is a block diagram showing a configuration example of the q-axis current pulsation calculator 408a included in the controller 400a of the power converter 1 according to Embodiment 2.
  • the q-axis current pulsation calculator 408a includes a subtractor 601a, Fourier coefficient calculators 602a-605a, an amplitude controller 606a, PID controllers 607a-610a, and an AC restorer 611a.
  • Subtraction section 601 a has the same function as subtraction section 601 .
  • the subtraction unit 601 a calculates the deviation between the command value of 0 and the DC bus voltage Vdc which is the detection value detected by the voltage detection unit 501 for detecting the power state of the capacitor 210 .
  • Vdc DC bus voltage
  • Fourier coefficient calculators 602a-605a have functions similar to those of Fourier coefficient calculators 602-605.
  • the Fourier coefficient calculation units 602a to 605a assume that the power frequency of the first AC power supplied from the commercial power supply 110 is 1f, and the sin 2f component and the cos 2f component included in the deviation calculated by the subtraction unit 601a. , sin4f component, and cos4f component. "f" in the second embodiment and "f" in the first embodiment may be different or the same.
  • the detected signals multiplied by the deviations in the Fourier coefficient calculators 602a to 605a are sin2 ⁇ int , cos2 ⁇ int , sin4 ⁇ int , and cos4 ⁇ int , respectively.
  • the Fourier coefficient calculator 602a multiplies the deviation by the sin2 ⁇ int detection signal to calculate the amplitude value of the sin2f component of the pulsation included in the DC bus voltage Vdc .
  • the Fourier coefficient calculator 603a multiplies the deviation by the cos2 ⁇ int detection signal to calculate the amplitude value of the cos2f component of the pulsation included in the DC bus voltage Vdc .
  • the Fourier coefficient calculator 604a multiplies the deviation by the sin4 ⁇ int detection signal to calculate the amplitude value of the sin4f component of the pulsation included in the DC bus voltage Vdc .
  • the Fourier coefficient calculator 605a multiplies the deviation by the cos4 ⁇ int detection signal to calculate the amplitude value of the cos4f component of the pulsation included in the DC bus voltage Vdc . If the charge/discharge current I3 of the capacitor 210 has a periodic waveform, the output signals from the Fourier coefficient calculators 602a to 605a are substantially constant.
  • each of the Fourier coefficient calculators 602a to 605a which are a plurality of Fourier coefficient calculators, obtains a first frequency that is twice the frequency of the first AC power from the deviation calculated by the subtractor 601a.
  • One of a sine component, a cosine component of the first frequency, a sine component of a second frequency that is an integer multiple of two or more of the first frequency, and a cosine component of the second frequency is extracted.
  • the first frequency is 2f and the second frequency is 4f.
  • Amplitude control section 606 a has the same function as amplitude control section 606 .
  • the amplitude control unit 606a may specifically specify the amplitude value of each frequency component to the PID control units 607a to 610a according to the limit value i qriplim of the q-axis current pulsation command i qrip * , A ratio for suppressing the amplitude value of each frequency component extracted by the Fourier coefficient calculators 602a to 605a may be specified.
  • the amplitude control unit 606a may hold the limit value iqriplim of the q-axis current pulsation command iqrip * in advance, or obtain the q-axis current command iqDC * generated by the speed control unit 402 to obtain q It may be obtained by calculation using the shaft current command i qDC * . In this way, the amplitude control section 606a determines a limit value that limits the amplitude value of each frequency component extracted by the Fourier coefficient calculation sections 602a to 605a.
  • the PID control units 607a-610a have the same functions as the PID control units 607-610.
  • the PID controllers 607a-610a perform proportional-integral-derivative control, that is, PID control, so that the specific frequency components of the deviations extracted by the Fourier coefficient calculators 602a-605a become zero.
  • the PID controller 607a is connected to the Fourier coefficient calculator 602a
  • the PID controller 608a is connected to the Fourier coefficient calculator 603a
  • the PID controller 609a is connected to the Fourier coefficient calculator 604a.
  • the controller 610a is connected to the Fourier coefficient calculator 605a.
  • the PID control units 607a to 610a which are a plurality of integral control units, are each connected to one of the Fourier coefficient calculation units 602a to 605a, and use the limit value determined by the amplitude control unit 606a. , limits the amplitude value of the frequency component extracted by the connected Fourier coefficient calculator.
  • the AC restorer 611 a has the same function as the AC restorer 611 .
  • AC restorer 611a multiplies the outputs from PID controllers 607a to 610a by sin2 ⁇ int , cos2 ⁇ int , sin4 ⁇ int , and cos4 ⁇ int , respectively, and then sums them up to obtain q-axis current pulsation command i qrip . * is generated.
  • the AC restoration unit 611a generates an AC component signal using each frequency component after the amplitude value limitation obtained by the PID control units 607a to 610a, and controls the amplitude of the q-axis current pulsation i qrip . Output as q-axis current pulsation command i qrip * .
  • the q-axis current pulsation calculator 408a includes four Fourier coefficient calculators 602a to 605a and four PID controllers 607a to 610a, but this is only an example and the present invention is not limited to this.
  • the q-axis current pulsation calculator 408a may include six Fourier coefficient calculators and six PID controllers, or eight or more Fourier coefficient calculators and eight or more PID controllers.
  • the q-axis current pulsation calculator 408a includes six Fourier coefficient calculators and six PID controllers, it controls the sin6f component and the cos6f component in addition to the four frequency components described above.
  • the q-axis current pulsation calculation unit 408a includes eight Fourier coefficient calculation units and eight PID control units, in addition to the above four frequency components, the sin6f component, cos6f component, sin8f component, and cos8f component are targeted. to control.
  • FIG. 8 is a flow chart showing the operation of the q-axis current pulsation calculator 408a included in the controller 400a of the power converter 1 according to the second embodiment.
  • the subtractor 601a calculates the deviation between the command value of 0 and the DC bus voltage Vdc (step S21).
  • the Fourier coefficient calculators 602a to 605a extract frequency components of a plurality of specific frequencies included in the deviation calculated by the subtractor 601a (step S22).
  • the amplitude control unit 606a determines a limit value for limiting the amplitude value of each frequency component (step S23).
  • the PID controllers 607a to 610a limit the amplitude values of the frequency components extracted by the Fourier coefficient calculators 602a to 605a using the limit values determined by the amplitude controller 606a (step S24).
  • the AC restoration unit 611a generates the q-axis current pulsation command i qrip * using each frequency component after the amplitude value limitation obtained by the PID control units 607a to 610a (step S25).
  • Control unit 400a included in the power converter 1 will be described.
  • Control unit 400a is implemented by processor 91 and memory 92, similar to control unit 400 of the first embodiment.
  • the q-axis current pulsation calculation unit 408a of the control unit 400a is based on the pulsation component included in the DC bus voltage Vdc .
  • the frequency of positive integral multiples of the frequency of the basic pulsating component is also controlled to limit the amplitude.
  • the control unit 400a of the power converter 1 can improve the accuracy of compensation in the compensation control for pulsating the q -axis current iq.
  • the power conversion device 1 can obtain effects such as reduction of copper loss.
  • Embodiment 3 when the power conversion device 1 is intended for capacitor current suppression control, the amplitude control unit 606a of the q-axis current pulsation calculation unit 408a calculates each frequency component extracted by the Fourier coefficient calculation units 602a to 605a. A method for determining a limit value for limiting the amplitude value of is described.
  • the configuration of control section 400a is the same as the configuration of control section 400a of Embodiment 2 shown in FIG.
  • FIG. 9 is a first block diagram showing a configuration example of the q-axis current pulsation calculator 408a included in the controller 400a of the power converter 1 according to the third embodiment.
  • the q-axis current pulsation calculator 408a includes a subtractor 601a, Fourier coefficient calculators 602a-605a, an amplitude controller 606a, PID controllers 607a-610a, and an AC restorer 611a.
  • the Fourier coefficient calculation units 602a to 605a output the calculation results to the amplitude control unit 606a, and the amplitude control unit 606a calculates the limit value i qriplim of the q-axis current ripple command i qrip * and the Fourier coefficient calculation units 602a to 605a.
  • This embodiment differs from the second embodiment in that the result is used to determine the limit value. That is, the amplitude control section 606a adjusts the amplitude value of each frequency component of the q -axis current iq to be finally output based on the amplitude value of each frequency component of the q -axis current iq.
  • the Fourier coefficient calculator 602a outputs the calculated amplitude value of the sin2f component to the PID controller 607a and the amplitude controller 606a.
  • the amplitude value of the sin2f component is denoted as I q2fs * .
  • the Fourier coefficient calculator 603a outputs the calculated amplitude value of the cos2f component to the PID controller 608a and the amplitude controller 606a.
  • the amplitude value of the cos2f component is denoted as Iq2fc * .
  • the Fourier coefficient calculator 604a outputs the calculated amplitude value of the sin4f component to the PID controller 609a and the amplitude controller 606a.
  • the amplitude value of the sin4f component is denoted as I q4fs * .
  • the Fourier coefficient calculator 605a outputs the calculated amplitude value of the cos4f component to the PID controller 610a and the amplitude controller 606a.
  • the amplitude value of the cos2f component is denoted as Iq4fc * .
  • the amplitude control section 606a calculates the norm of the 2f component of the power supply frequency as shown in Equation (1).
  • the amplitude control section 606a calculates the norm of the 4f component of the power supply frequency as shown in Equation (2).
  • the amplitude control unit 606a adds the norm of the 2f component of the power supply frequency and the norm of the 4f component of the power supply frequency as shown in equation (3).
  • Amplitude control section 606a should ensure that the norm obtained by equation (3) does not exceed limit value i qriplim of q-axis current ripple command i qrip * . Calculate the limit value for
  • Equation (4) expresses the calculations in the PID controllers 607a to 610a. Specifically, the PID control unit 607a multiplies the calculation result Iq2fs * obtained from the Fourier coefficient calculation unit 602a by the limit value obtained from the amplitude control unit 606a to obtain the amplitude value of the sin2f component after the amplitude value limitation. We obtain I q2fs * ( ⁇ ). In addition, in the description of the embodiment, since it is not possible to add “ ⁇ ” above I in Equation (4), it is expressed as I q2fs * ( ⁇ ). The same applies to subsequent similar descriptions.
  • the PID control unit 608a multiplies the calculation result I q2fc * obtained from the Fourier coefficient calculation unit 603a by the limit value obtained from the amplitude control unit 606a to obtain the amplitude value I q2fc * of the cos2f component after the amplitude value limitation. ).
  • the PID control unit 609a multiplies the calculation result I q4fs * obtained from the Fourier coefficient calculation unit 604a by the limit value obtained from the amplitude control unit 606a, thereby obtaining the amplitude value I q4fs * of the sin4f component after the amplitude value limitation. ).
  • the PID control unit 610a multiplies the calculation result I q4fc * obtained from the Fourier coefficient calculation unit 605a by the limit value obtained from the amplitude control unit 606a to obtain the amplitude value I q4fc * of the cos4f component after the amplitude value limitation. ).
  • the Fourier coefficient calculators 602a to 605a which are a plurality of Fourier coefficient calculators, output the amplitude values of the extracted frequency components to the amplitude controller 606a.
  • the amplitude control unit 606a calculates a limit value from the limit value i qriplim for the q-axis current ripple command i qrip * and the amplitude value of each frequency component obtained from the Fourier coefficient calculation units 602a to 605a.
  • the PID controllers 607a to 610a which are a plurality of integral controllers, limit the amplitude values of the frequency components by multiplying the amplitude values of the frequency components extracted by the connected Fourier coefficient calculators by the limit values.
  • the configuration of the q-axis current ripple calculator 408a is the same as the configuration of the q-axis current ripple calculator 408a shown in FIG.
  • the operations of the Fourier coefficient calculation units 602a to 605a are the same as those of the Fourier coefficient calculation units 602a to 605a described above when the amplitude control unit 606a uses the amplitude value.
  • the amplitude control unit 606a calculates the phase of the frequency by using the amplitude value of the sine component and the amplitude value of the cosine component of the same frequency component among the amplitude value information acquired from the Fourier coefficient calculation units 602a to 605a.
  • the amplitude control unit 606a uses I q2fs * , which is the amplitude value of the sin 2f component obtained from the Fourier coefficient calculation unit 602a, and I q2fc * , which is the amplitude value of the cos 2f component obtained from the Fourier coefficient calculation unit 603a, to
  • the phase ⁇ 2f of the frequency 2f component is calculated as shown in equation (5).
  • the amplitude control unit 606a uses the same calculation method to calculate I q4fs * , which is the amplitude value of the sin4f component obtained from the Fourier coefficient calculation unit 604a, and I q4fc * , which is the amplitude value of the cos4f component obtained from the Fourier coefficient calculation unit 605a. is used to calculate the phase ⁇ 4f of the frequency 4f component. Note that the calculation of the phase ⁇ 2f and the phase ⁇ 4f may be performed outside the amplitude control unit 606a by providing a configuration for separate calculation before the amplitude control unit 606a.
  • the amplitude control section 606a determines the limit value of each frequency component from the phase relationship between the phase ⁇ 2f and the phase ⁇ 4f .
  • the reason why the amplitude control unit 606a adjusts the amplitude value of each frequency component of the q-axis current iq that is finally output based on the phase relationship of each frequency component of the q -axis current iq is that a plurality of q-axis current iq This is because the maximum value of the sum of the frequency components differs depending on the phase relationship between the pulsating components of the current iq . For example, if the pulsating component of the q -axis current iq calculated from the 2f frequency component and the pulsating component of the q-axis current iq calculated from the 4f frequency component have the same phase, the current peak value increases.
  • the current peak value may decrease. If the current peak value decreases, the pulsating component of the q-axis current iq will have a margin with respect to the limit value iqriplim of the q-axis current pulsating command iqrip * , so the pulsating component of the q-axis current iq will be reduced accordingly. can be increased and the amount of current flowing into capacitor 210 can be reduced.
  • FIG. 10 is a diagram showing an example of the difference in peak value due to the phase difference when adding two frequency components.
  • FIG. 10(a) shows the case where the phases are the same, and
  • FIG. 10(b) shows the case where the phases are shifted. Note that the amplitudes of sin2f and sin4f are the same in FIGS. 10(a) and 10(b). Also, in FIG. 10B, assume that the phase of sin2f and the phase of sin4 are out of phase by 90°, that is, the initial phase of sin4f is 90°. As shown in FIG.
  • amplitude control section 606a adjusts the limit value of each frequency component according to the phase of each frequency component.
  • the relationship between the phase difference of each frequency component and the peak value when adding each frequency component can be obtained in advance by the designer of the power converter 1 or the like. Moreover, the designer of the power conversion device 1 or the like can obtain in advance how much each frequency component should be restricted based on the peak value when each frequency component is added. Therefore, the amplitude control unit 606a preliminarily holds the relationship between the phase difference of each frequency component, the peak value when the frequency components are added, the limit amount of each frequency component, and the like, thereby adjusting the position of each frequency component. Once the phase difference is determined, the limits for each frequency component can be determined.
  • the Fourier coefficient calculators 602a to 605a which are a plurality of Fourier coefficient calculators, output the amplitude values of the extracted frequency components to the amplitude controller 606a.
  • the amplitude control section 606a calculates the phase of the first frequency and the phase of the second frequency from each frequency component obtained from the Fourier coefficient calculation sections 602a to 605a.
  • Amplitude control section 606a calculates the phase difference between the phase of the first frequency and the phase of the second frequency, and determines the limit value from the limit value i qriplim for the q-axis current pulsation command i qrip * and the phase difference.
  • PID control units 607a to 610a which are a plurality of integral control units, limit the amplitude values of the frequency components extracted by the connected Fourier coefficient calculation units according to the limit values.
  • FIG. 11 is a second block diagram showing a configuration example of the q-axis current pulsation calculator 408a included in the controller 400a of the power converter 1 according to the third embodiment.
  • the q-axis current pulsation calculator 408a includes a subtractor 601a, Fourier coefficient calculators 602a-605a, an amplitude controller 606a, PID controllers 607a-610a, and an AC restorer 611a.
  • the difference from the second embodiment is that the amplitude control unit 606a determines the limit value using the limit value i qriplim of the q-axis current pulsation command i qrip * and the DC component i qDC of the q-axis current command i q * . . That is, the amplitude control unit 606a adjusts the amplitude value of each frequency component of the q-axis current iq to be finally output based on the DC component iqDC of the q-axis current command iq * .
  • the amplitude control unit 606a uses the q-axis current command iqDC * output from the speed control unit 402 as the DC component iqDC of the q-axis current command iq * . may Further, the amplitude control unit 606a may use the detection value of the detection unit when the power conversion device 1 has a detection unit that detects the DC component iqDC of the q-axis current command iq * .
  • the direct-current component iqDC of the q-axis current command iq * is generated by the load torque applied to the motor 314 or the like.
  • the direct current component iqDC of the q-axis current command iq * is positive, and is negative in the opposite direction.
  • the direct-current component i qDC of the q-axis current command i q * is positive, the q-axis current command i q * has a reduced margin with respect to the positive limit value of the q-axis current command i q * .
  • the margin increases with respect to the negative limits.
  • the amplitude control section 606a needs to adjust the magnitude of the amplitude value of each frequency component included in the q -axis current iq from the above relationship.
  • the amplitude controller 606a determines the limit value from the limit value i qriplim for the q-axis current ripple command i qrip * and the DC component i qDC of the q-axis current i q .
  • PID control units 607a to 610a which are a plurality of integral control units, limit the amplitude values of the frequency components extracted by the connected Fourier coefficient calculation units according to the limit values.
  • the amplitude control section 606a may combine the above three techniques for determining the limit value.
  • the q-axis current command for the limit value i qlim of the q-axis current command i q * The margin of i q * changes.
  • the addition of sin2f and sin4f has a phase difference of 90° between the same phase and the phase difference of 90°.
  • Amplitude control section 606a determines the limit value of each frequency component in view of such events.
  • the q-axis current ripple calculation unit 408a of the control unit 400a can determine the limit value by various methods. By combining them, the limit value can be determined with high accuracy.
  • Embodiment 4 a case where the pulsation component x rip is the estimated speed ⁇ est will be described, specifically targeting speed pulsation suppression control of the motor 314 .
  • FIG. 12 is a block diagram showing a configuration example of the control unit 400b included in the power converter 1 according to Embodiment 4.
  • Control unit 400b is obtained by replacing q-axis current ripple calculation unit 408 of control unit 400 of the first embodiment shown in FIG. 2 with q-axis current ripple calculation unit 408b.
  • the power conversion device 1 according to Embodiment 4 replaces the control unit 400 with a control unit 400b in the power conversion device 1 according to Embodiment 1 shown in FIG. .
  • FIG. 13 is a block diagram showing a configuration example of the q-axis current pulsation calculator 408b included in the controller 400b of the power converter 1 according to the fourth embodiment.
  • the q-axis current ripple calculator 408b includes a subtractor 601b, Fourier coefficient calculators 602b-605b, an amplitude controller 606b, PID controllers 607b-610b, and an AC restorer 611b.
  • Subtraction section 601b has the same function as subtraction section 601 .
  • a subtraction unit 601 b calculates a deviation between the speed command ⁇ * and the estimated speed ⁇ est estimated by the rotor position estimation unit 401 .
  • Fourier coefficient calculators 602b-605b have functions similar to those of Fourier coefficient calculators 602-605.
  • the Fourier coefficient calculation units 602b to 605b use the deviation calculated by the subtraction unit 601b as the speed pulsation of the motor 314, the sin1f component, the cos1f component, the sin2f component, and the cos2f component included in the speed pulsation of the motor 314. Calculate the amplitude of each component. "f" in the fourth embodiment, "f” in the second embodiment, and “f” in the first embodiment may be different or the same.
  • the detected signals multiplied by the deviations in the Fourier coefficient calculators 602b to 605b are sin1 ⁇ int , cos1 ⁇ int , sin2 ⁇ int , and cos2 ⁇ int , respectively, and twice the average value of the product of the deviation, which is the input signal, and the detected signal is They are the amplitude values of the sin1f component, cos1f component, sin2f component, and cos2f component included in the deviation, respectively.
  • the Fourier coefficient calculator 602b multiplies the deviation by the sin1 ⁇ int detection signal to calculate the amplitude value of the sin1f component of the pulsation included in the speed pulsation of the motor 314 .
  • the Fourier coefficient calculator 603b multiplies the deviation by the cos1 ⁇ int detection signal, and calculates the amplitude value of the cos1f component of the pulsation included in the speed pulsation of the motor 314 .
  • the Fourier coefficient calculator 604b multiplies the deviation by the detected signal of sin2 ⁇ int to calculate the amplitude value of the sin2f component of the pulsation included in the speed pulsation of the motor 314 .
  • the Fourier coefficient calculator 605b multiplies the deviation by the cos2 ⁇ int detection signal to calculate the amplitude value of the cos2f component of the pulsation included in the speed pulsation of the motor 314 .
  • the Fourier coefficient calculators 602b to 605b which are a plurality of Fourier coefficient calculators, each calculate the sine component of the third frequency included in the velocity pulsation of the motor 314 from the deviation calculated by the subtractor 601b.
  • One of a cosine component of a third frequency, a sine component of a fourth frequency that is an integer multiple of two or more of the third frequency, and a cosine component of the fourth frequency is extracted.
  • the third frequency is 1f and the fourth frequency is 2f.
  • the amplitude control section 606b has the same function as the amplitude control section 606.
  • FIG. The amplitude control unit 606b may specifically specify the amplitude value of each frequency component to the PID control units 607b to 610b according to the limit value i qriplim of the q-axis current ripple command i qrip * , A ratio for suppressing the amplitude value of each frequency component extracted by the Fourier coefficient calculators 602b to 605b may be specified.
  • the amplitude control unit 606b may hold the limit value iqriplim of the q-axis current pulsation command iqrip * in advance, or acquire the q-axis current command iqDC * generated by the speed control unit 402 and obtain q It may be obtained by calculation using the shaft current command i qDC * . In this way, the amplitude control section 606b determines a limit value that limits the amplitude value of each frequency component extracted by the Fourier coefficient calculation sections 602b to 605b.
  • the PID control units 607b-610b have the same functions as the PID control units 607-610.
  • the PID controllers 607b-610b perform proportional-integral-derivative control, that is, PID control, so that the specific frequency components of the deviations extracted by the Fourier coefficient calculators 602b-605b are zero.
  • the PID controller 607b is connected to the Fourier coefficient calculator 602b
  • the PID controller 608b is connected to the Fourier coefficient calculator 603b
  • the PID controller 609b is connected to the Fourier coefficient calculator 604b
  • the PID The controller 610b is connected to the Fourier coefficient calculator 605b.
  • the PID control units 607b to 610b which are a plurality of integral control units, are each connected to one of the Fourier coefficient calculation units 602b to 605b, and use the limit value determined by the amplitude control unit 606b. , limits the amplitude value of the frequency component extracted by the connected Fourier coefficient calculator.
  • the AC restorer 611b has the same function as the AC restorer 611.
  • AC restorer 611b multiplies sin1 ⁇ int , cos1 ⁇ int , sin2 ⁇ int , and cos2 ⁇ int to restore outputs from PID controllers 607b to 610b to AC, and then sums them up to obtain q-axis current pulsation command i qrip . * is generated.
  • the AC restoration unit 611b generates an AC component signal using each frequency component after the amplitude value limitation obtained by the PID control units 607b to 610b, and controls the amplitude of the q-axis current pulsation i qrip . Output as q-axis current pulsation command i qrip * .
  • the q-axis current ripple calculator 408b includes four Fourier coefficient calculators 602b to 605b and four PID controllers 607b to 610b, but this is an example and not limited to this.
  • the q-axis current ripple calculator 408b may include six Fourier coefficient calculators and six PID controllers, or eight or more Fourier coefficient calculators and eight or more PID controllers.
  • the q-axis current pulsation calculator 408b includes six Fourier coefficient calculators and six PID controllers, it controls the sin3f component and the cos3f component in addition to the four frequency components described above.
  • the q-axis current pulsation calculation unit 408b includes eight Fourier coefficient calculation units and eight PID control units, in addition to the above four frequency components, the sin3f component, cos3f component, sin4f component, and cos4f component are targeted. to control.
  • FIG. 14 is a flowchart showing the operation of the q-axis current pulsation calculator 408b included in the controller 400b of the power converter 1 according to the fourth embodiment.
  • the subtractor 601b calculates the deviation between the speed command ⁇ * and the estimated speed ⁇ est (step S31).
  • the Fourier coefficient calculators 602b to 605b extract frequency components of a plurality of specific frequencies included in the deviation calculated by the subtractor 601b (step S32).
  • the amplitude control unit 606b determines a limit value that limits the amplitude value of each frequency component (step S33).
  • the PID controllers 607b-610b limit the amplitude values of the frequency components extracted by the Fourier coefficient calculators 602b-605b using the limit values determined by the amplitude controller 606b (step S34).
  • the AC restoration unit 611b generates the q-axis current pulsation command i qrip * using each frequency component after the amplitude value limitation obtained by the PID control units 607b to 610b (step S35).
  • Control unit 400b is realized by processor 91 and memory 92, similar to control unit 400 of the first embodiment.
  • the q-axis current pulsation calculator 408b of the control unit 400b calculates the basic pulsation In addition to the frequency of the component, control is performed to limit the amplitude of the frequency that is a positive integer multiple of the frequency of the fundamental pulsation component.
  • the control unit 400b of the power converter 1 can improve the accuracy of compensation in the compensation control for pulsating the q -axis current iq.
  • the power conversion device 1 can obtain effects such as reduction of copper loss.
  • Embodiment 5 when the power conversion device 1 is intended for speed pulsation suppression control of the motor 314, the amplitude control unit 606b of the q-axis current pulsation calculation unit 408b is extracted by the Fourier coefficient calculation units 602b to 605b. A method of determining a limit value that limits the amplitude value of each frequency component will be described.
  • the configuration of control section 400b is the same as the configuration of control section 400b of Embodiment 4 shown in FIG.
  • FIG. 15 is a first block diagram showing a configuration example of the q-axis current pulsation calculator 408b included in the controller 400b of the power converter 1 according to the fifth embodiment.
  • the q-axis current ripple calculator 408b includes a subtractor 601b, Fourier coefficient calculators 602b-605b, an amplitude controller 606b, PID controllers 607b-610b, and an AC restorer 611b.
  • the Fourier coefficient calculation units 602b to 605b output the calculation results to the amplitude control unit 606b, and the amplitude control unit 606b calculates the limit value i qriplim of the q-axis current ripple command i qrip * and the Fourier coefficient calculation units 602b to 605b.
  • the result is used to determine the limit value. That is, the amplitude control section 606b adjusts the amplitude value of each frequency component of the q-axis current iq to be finally output based on the amplitude value of each frequency component of the q -axis current iq. Since the specific operation of the q-axis current ripple calculation unit 408b is the same as the operation of the q-axis current ripple calculation unit 408a described as the first method of the third embodiment, detailed description thereof will be omitted.
  • Fourier coefficient calculators 602b to 605b which are a plurality of Fourier coefficient calculators in q-axis current pulsation calculator 408b, output amplitude values of extracted frequency components to amplitude controller 606b.
  • the amplitude control unit 606b calculates a limit value from the limit value i qriplim for the q-axis current ripple command i qrip * and the amplitude value of each frequency component obtained from the Fourier coefficient calculation units 602b to 605b.
  • the PID controllers 607b to 610b which are a plurality of integral controllers, limit the amplitude values of the frequency components by multiplying the amplitude values of the frequency components extracted by the connected Fourier coefficient calculators by the limit values.
  • the configuration of the q-axis current ripple calculation unit 408b is the same as the configuration of the q-axis current ripple calculation unit 408b shown in FIG. 15 described above. Since the specific operation of the q-axis current ripple calculation unit 408b is the same as the operation of the q-axis current ripple calculation unit 408a described as the second method of the third embodiment, detailed description thereof will be omitted.
  • Fourier coefficient calculators 602b to 605b which are a plurality of Fourier coefficient calculators in q-axis current pulsation calculator 408b, output amplitude values of extracted frequency components to amplitude controller 606b.
  • the amplitude control section 606b calculates the phase of the third frequency and the phase of the fourth frequency from each frequency component obtained from the plurality of Fourier coefficient calculation sections 602b to 605b.
  • Amplitude control section 606b calculates the phase difference between the phase of the third frequency and the phase of the fourth frequency, and determines the limit value from the limit value i qriplim for the q-axis current pulsation command i qrip * and the phase difference.
  • PID control units 607b to 610b which are a plurality of integral control units, limit the amplitude values of the frequency components extracted by the connected Fourier coefficient calculation units according to the limit values.
  • FIG. 16 is a second block diagram showing a configuration example of the q-axis current ripple calculator 408b included in the controller 400b of the power converter 1 according to the fifth embodiment.
  • the q-axis current ripple calculator 408b includes a subtractor 601b, Fourier coefficient calculators 602b-605b, an amplitude controller 606b, PID controllers 607b-610b, and an AC restorer 611b.
  • the difference from the fourth embodiment is that the amplitude control unit 606b determines the limit value using the limit value i qriplim of the q-axis current pulsation command i qrip * and the DC component i qDC of the q-axis current command i q * . . That is, the amplitude control section 606b adjusts the amplitude value of each frequency component of the finally output q-axis current iq based on the DC component iqDC of the q-axis current command iq * .
  • the amplitude control unit 606b uses the q-axis current command iqDC * output from the speed control unit 402 as the DC component iqDC of the q-axis current command iq * . may Further, if the power conversion device 1 is provided with a detection unit for detecting the DC component iqDC of the q-axis current command iq * , the amplitude control unit 606b may use the detection value of the detection unit. Since the specific operation of the q-axis current ripple calculation unit 408b is the same as the operation of the q-axis current ripple calculation unit 408a described as the third method of the third embodiment, detailed description thereof will be omitted.
  • the amplitude controller 606b determines the limit value from the limit value iqriplim for the q-axis current ripple command iqrip * and the DC component iqDC of the q -axis current iq.
  • PID control units 607a to 610a which are a plurality of integral control units, limit the amplitude values of the frequency components extracted by the connected Fourier coefficient calculation units according to the limit values.
  • amplitude control section 606b may combine the above three methods of determining the limit value.
  • the q-axis current pulsation calculation unit 408b of the control unit 400b can determine the limit value by various methods. By combining them, the limit value can be determined with high accuracy.
  • Embodiment 6 describes a case where the electric power converter 1 targets the capacitor current suppression control and the speed pulsation suppression control of the motor 314 .
  • FIG. 17 is a block diagram showing a configuration example of the control unit 400c included in the power conversion device 1 according to Embodiment 6.
  • Control unit 400c is obtained by replacing q-axis current ripple calculation unit 408 of control unit 400 of the first embodiment shown in FIG. 2 with q-axis current ripple calculation unit 408c.
  • the power conversion device 1 according to Embodiment 6 replaces the control unit 400 with a control unit 400c in the power conversion device 1 according to Embodiment 1 shown in FIG. .
  • FIG. 18 is a first block diagram showing a configuration example of the q-axis current pulsation calculation section 408c provided in the control section 400c of the power converter 1 according to the sixth embodiment.
  • the q-axis current pulsation calculator 408c includes subtractors 601a and 601b, Fourier coefficient calculators 602a, 603a, 602b and 603b, an amplitude controller 606c, PID controllers 607a, 608a, 607b and 608b, and an AC restorer. 611c.
  • subtraction units 601a and 601b The operations of subtraction units 601a and 601b, Fourier coefficient calculation units 602a, 603a, 602b and 603b, and PID control units 607a, 608a, 607b and 608b are the same as those described above.
  • the amplitude control section 606c has the same function as the amplitude control section 606.
  • the method of determining the limit value in the amplitude control section 606c is the same as the above-described method of the amplitude control section 606a or the amplitude control section 606b.
  • the amplitude control unit 606c may handle the capacitor current suppression control and the speed pulsation suppression control of the motor 314 equally, or increase the limit value of one control and increase the limit value of the other control. It may be weighted by control to make it smaller.
  • the AC restorer 611 c has the same function as the AC restorer 611 .
  • the AC restoration unit 611c synthesizes outputs from the PID control units 607a, 608a, 607b, and 608b to generate a q-axis current pulsation command i qrip * .
  • the subtraction unit 601a which is the first subtraction unit, calculates the difference between the command value that is zero and the detection value detected by the detection unit that detects the power state of the capacitor 210. Compute a deviation of 1.
  • Fourier coefficient calculators 602a and 603a which are a plurality of first Fourier coefficient calculators, each generate a sine component of a first frequency twice the frequency of the first AC power and a first Extract one of the 1 frequency cosine components.
  • a subtraction unit 601b which is a second subtraction unit, calculates a second deviation between the speed command ⁇ * and the estimated speed ⁇ est .
  • Fourier coefficient calculators 602b and 603b which are a plurality of second Fourier coefficient calculators, each generate a third frequency sine component contained in the speed pulsation of motor 314 and a third frequency Extract one of the cosine components of .
  • the amplitude control section 606c determines a limit value for limiting the amplitude value of each frequency component extracted by the Fourier coefficient calculation sections 602a and 603a and the Fourier coefficient calculation sections 602b and 603b.
  • PID controllers 607a and 608a which are a plurality of first integral controllers, are each connected to one of Fourier coefficient calculators 602a and 603a, and using a limit value, the connected Fourier coefficient calculator Limit the amplitude values of the extracted frequency components.
  • PID controllers 607b and 608b which are a plurality of second integral controllers, are each connected to one of Fourier coefficient calculators 602b and 603b, and using a limit value, the connected Fourier coefficient calculator Limit the amplitude values of the extracted frequency components.
  • the AC restoration unit 611c generates an AC component signal using the amplitude-limited frequency components obtained by the PID control units 607a and 608a and the PID control units 607b and 608b, and calculates the amplitude of the q-axis current pulsation i qrip . is output as a q-axis current pulsation command i qrip * that controls
  • the q-axis current ripple calculation unit 408c targets a combination of a sine component and a cosine component of one frequency as the capacitor current suppression control, and the sin Although it was intended for combinations of components and cos components, it is not limited to this.
  • the q-axis current pulsation calculator 408c can also target combinations of sine components and cosine components of a plurality of frequencies in each control, as in the second to fifth embodiments.
  • FIG. 19 is a second block diagram showing a configuration example of the q-axis current pulsation calculation section 408c provided in the control section 400c of the power converter 1 according to Embodiment 6.
  • the q-axis current pulsation calculation unit 408c includes subtraction units 601a and 601b, Fourier coefficient calculation units 602a to 605a and 602b to 605b, an amplitude control unit 606c, PID control units 607a to 610a and 607b to 610b, and an AC restoration unit. 611c.
  • subtraction units 601a and 601b The operations of subtraction units 601a and 601b, Fourier coefficient calculation units 602a-605a and 602b-605b, and PID control units 607a-610a and 607b-610b are the same as those described above.
  • the amplitude control section 606c has the same function as the amplitude control section 606.
  • the method of determining the limit value in the amplitude control section 606c is the same as the above-described method of the amplitude control section 606a or the amplitude control section 606b.
  • the amplitude control unit 606c may handle the capacitor current suppression control and the speed pulsation suppression control of the motor 314 equally, or increase the limit value of one control and increase the limit value of the other control. It may be weighted by control to make it smaller.
  • the AC restorer 611 c has the same function as the AC restorer 611 .
  • the AC restorer 611c synthesizes outputs from the PID controllers 607a to 610a and 607b to 610b to generate a q-axis current pulsation command i qrip * .
  • the subtraction unit 601a which is the first subtraction unit, calculates the difference between the command value that is zero and the detection value detected by the detection unit that detects the power state of the capacitor 210. Compute a deviation of 1.
  • Fourier coefficient calculators 602a to 605a which are a plurality of first Fourier coefficient calculators, each generate a sine component of a first frequency that is twice the frequency of the first AC power and a first One of a cosine component with a frequency of 1, a sine component with a second frequency that is an integer multiple of two or more of the first frequency, and a cosine component with a second frequency is extracted.
  • a subtraction unit 601b which is a second subtraction unit, calculates a second deviation between the speed command ⁇ * and the estimated speed ⁇ est .
  • Fourier coefficient calculators 602b to 605b which are a plurality of second Fourier coefficient calculators, each generate a third frequency sine component contained in the speed pulsation of the motor 314 from the second deviation.
  • One of a cosine component, a sine component at a fourth frequency that is an integer multiple of two or more of the third frequency, and a cosine component at the fourth frequency is extracted.
  • the amplitude control section 606c determines a limit value for limiting the amplitude value of each frequency component extracted by the Fourier coefficient calculation sections 602a to 605a and the Fourier coefficient calculation sections 602b to 605b.
  • PID controllers 607a to 610a which are a plurality of first integral controllers, are each connected to one of Fourier coefficient calculators 602a to 605a, and use a limit value to determine Limit the amplitude values of the extracted frequency components.
  • PID controllers 607b to 610b which are a plurality of second integral controllers, are each connected to one of Fourier coefficient calculators 602b to 605b, and using a limit value, the connected Fourier coefficient calculator Limit the amplitude values of the extracted frequency components.
  • the AC restoration unit 611c generates an AC component signal using the amplitude-limited frequency components obtained by the PID control units 607a to 610a and the PID control units 607b to 610b, and calculates the amplitude of the q-axis current pulsation i qrip . is output as a q-axis current pulsation command i qrip * that controls
  • FIG. 20 is a flow chart showing the operation of the q-axis current pulsation calculator 408c included in the controller 400c of the power conversion device 1 according to the sixth embodiment.
  • the subtractor 601a calculates the deviation between the command value of 0 and the DC bus voltage Vdc (step S41).
  • the subtractor 601b calculates the deviation between the speed command ⁇ * and the estimated speed ⁇ est (step S42).
  • Fourier coefficient calculation units 602a to 605a extract frequency components of a plurality of specific frequencies included in the deviation calculated by subtraction unit 601a
  • Fourier coefficient calculation units 602b to 605b extract frequency components included in the deviation calculated by subtraction unit 601b.
  • a plurality of frequency components of specific frequencies are extracted (step S43).
  • the amplitude control unit 606c determines a limit value that limits the amplitude value of each frequency component (step S44).
  • PID control units 607a to 610a use the limit value determined by amplitude control unit 606c to limit the amplitude value of each frequency component extracted by Fourier coefficient calculation units 602a to 605a, and PID control units 607b to 610b , and the limit value determined by the amplitude control unit 606c is used to limit the amplitude value of each frequency component extracted by the Fourier coefficient calculation units 602b to 605b (step S45).
  • the AC restorer 611c generates a q-axis current pulsation command i qrip * using the amplitude-limited frequency components obtained by the PID controllers 607a to 610a and 607b to 610b (step S46).
  • Control unit 400c included in the power converter 1 will be described.
  • Control unit 400c is realized by processor 91 and memory 92, similar to control unit 400 of the first embodiment.
  • the q-axis current ripple calculator 408c of the controller 400c responds to the ripple components included in the DC bus voltage V dc and the estimated speed ⁇ est . Therefore, it was decided to perform control to limit the amplitude. Thereby, the control unit 400c of the power converter 1 can improve the accuracy of compensation in the compensation control for pulsating the q -axis current iq. As a result, the power conversion device 1 can obtain effects such as reduction of copper loss.
  • the q-axis current pulsation calculator 408c calculates the frequency of the pulsation component that is the basis for the pulsation component included in the DC bus voltage V dc and the estimated speed ⁇ est , as well as the positive integer of the frequency of the pulsation component that is the basis. It was decided to perform control to limit the amplitude of the double frequency as well. Thereby, the control unit 400c of the power conversion device 1 can further improve the accuracy of compensation in the compensation control for pulsating the q -axis current iq. As a result, the power conversion device 1 can obtain the effect of being able to further reduce the copper loss.
  • FIG. 21 is a diagram showing a configuration example of a refrigeration cycle equipment 900 according to Embodiment 7.
  • a refrigerating cycle-applied equipment 900 according to the seventh embodiment includes the power converter 1 described in the first to sixth embodiments.
  • the refrigerating cycle applied equipment 900 according to Embodiment 7 can be applied to products equipped with a refrigerating cycle, such as air conditioners, refrigerators, freezers, and heat pump water heaters.
  • constituent elements having functions similar to those of the first embodiment are assigned the same reference numerals as those of the first embodiment.
  • Refrigerating cycle applied equipment 900 includes compressor 315 incorporating motor 314 according to Embodiment 1, four-way valve 902, indoor heat exchanger 906, expansion valve 908, and outdoor heat exchanger 910 with refrigerant pipe 912. attached through
  • a compression mechanism 904 that compresses the refrigerant and a motor 314 that operates the compression mechanism 904 are provided inside the compressor 315 .
  • the refrigeration cycle applied equipment 900 can perform heating operation or cooling operation by switching operation of the four-way valve 902 .
  • the compression mechanism 904 is driven by a variable speed controlled motor 314 .
  • the refrigerant is pressurized by the compression mechanism 904 and sent out through the four-way valve 902, the indoor heat exchanger 906, the expansion valve 908, the outdoor heat exchanger 910, and the four-way valve 902. Return to compression mechanism 904 .
  • the refrigerant is pressurized by the compression mechanism 904 and sent through the four-way valve 902, the outdoor heat exchanger 910, the expansion valve 908, the indoor heat exchanger 906, and the four-way valve 902. Return to compression mechanism 904 .
  • the indoor heat exchanger 906 acts as a condenser to release heat, and the outdoor heat exchanger 910 acts as an evaporator to absorb heat.
  • the outdoor heat exchanger 910 acts as a condenser to release heat, and the indoor heat exchanger 906 acts as an evaporator to absorb heat.
  • the expansion valve 908 reduces the pressure of the refrigerant to expand it.

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Physics & Mathematics (AREA)
  • Electromagnetism (AREA)
  • Control Of Ac Motors In General (AREA)
  • Inverter Devices (AREA)
PCT/JP2021/039878 2021-10-28 2021-10-28 電力変換装置、モータ駆動装置および冷凍サイクル適用機器 Ceased WO2023073880A1 (ja)

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