WO2013069326A1 - Dispositif de conversion d'énergie électrique - Google Patents

Dispositif de conversion d'énergie électrique Download PDF

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Publication number
WO2013069326A1
WO2013069326A1 PCT/JP2012/064035 JP2012064035W WO2013069326A1 WO 2013069326 A1 WO2013069326 A1 WO 2013069326A1 JP 2012064035 W JP2012064035 W JP 2012064035W WO 2013069326 A1 WO2013069326 A1 WO 2013069326A1
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WIPO (PCT)
Prior art keywords
voltage
control
power
phase inverter
circuit
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Application number
PCT/JP2012/064035
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English (en)
Japanese (ja)
Inventor
健志 網本
奥田　達也
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三菱電機株式会社
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Priority to JP2013542877A priority Critical patent/JP5788017B2/ja
Publication of WO2013069326A1 publication Critical patent/WO2013069326A1/fr

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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
    • H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
    • H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/53—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M7/537—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
    • H02M7/539—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters with automatic control of output wave form or frequency
    • H02M7/5395—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters with automatic control of output wave form or frequency by pulse-width modulation
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J3/00—Circuit arrangements for ac mains or ac distribution networks
    • H02J3/38—Arrangements for parallely feeding a single network by two or more generators, converters or transformers
    • H02J3/40—Synchronising a generator for connection to a network or to another generator
    • H02J3/44—Synchronising a generator for connection to a network or to another generator with means for ensuring correct phase sequence
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J2300/00—Systems for supplying or distributing electric power characterised by decentralized, dispersed, or local generation
    • H02J2300/20—The dispersed energy generation being of renewable origin
    • H02J2300/22—The renewable source being solar energy
    • H02J2300/24—The renewable source being solar energy of photovoltaic origin
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J3/00—Circuit arrangements for ac mains or ac distribution networks
    • H02J3/38—Arrangements for parallely feeding a single network by two or more generators, converters or transformers
    • H02J3/381—Dispersed generators
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0048—Circuits or arrangements for reducing losses
    • H02M1/0054—Transistor switching losses
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0067—Converter structures employing plural converter units, other than for parallel operation of the units on a single load
    • H02M1/007—Plural converter units in cascade
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02E—REDUCTION OF GREENHOUSE GAS [GHG] EMISSIONS, RELATED TO ENERGY GENERATION, TRANSMISSION OR DISTRIBUTION
    • Y02E10/00—Energy generation through renewable energy sources
    • Y02E10/50—Photovoltaic [PV] energy
    • Y02E10/56—Power conversion systems, e.g. maximum power point trackers

Definitions

  • the present invention relates to a power conversion device that converts DC power into AC power, and more particularly to a power conversion device that is used in a power conditioner or the like that links a solar cell voltage to a system.
  • a power conversion device used in a power conditioner for photovoltaic power generation, etc. is a capacitor for boosting a solar cell voltage with a booster circuit and generating a DC voltage sufficient to output AC power to smooth the DC bus voltage. To charge. Then, using it as a DC voltage source, it is converted into AC power by a single-phase inverter composed of power devices consisting of switching elements such as MOSFETs and IGBTs, and then harmonic noise contained in the AC current is removed by a filter to remove noise. It is configured to output the subsequent AC power to an AC system.
  • a booster circuit and a single-phase inverter are interposed between the two.
  • the booster circuit boosts the boosting section so that the boosting section has a partially convex waveform only during the period when the voltage of the intermediate stage capacitor is lower than the absolute value of the system voltage, During that period, a single-phase inverter has been proposed that performs an operation of switching the polarity of the output current in accordance with the polarity of the system voltage (see, for example, Patent Document 1).
  • the booster circuit and the single-phase inverter share the respective AC output waveforms.
  • a dead time is usually provided to prevent an arm short circuit when a bridge-configured power device performs switching, and a voltage drop occurs due to the resistance component of the power device.
  • the output voltage average value (absolute value) on the AC side is slightly lower than the input voltage average value on the DC side. For this reason, during the period when the single-phase inverter generates an AC output waveform without the booster circuit operating, the modulation rate of the power device of the single-phase inverter is maximized and a desired AC voltage cannot be output, resulting in an uncontrollable period. there were.
  • the present invention has been made to solve the above-described problems, and in a power converter that includes a booster circuit and a single-phase inverter and is linked to a system, a loss associated with the switching operation of the power device.
  • the purpose is to reduce the frequency and to generate a high-accuracy AC output waveform with all phases of the system voltage, and to connect to the system with high reliability.
  • a power conversion device includes a booster circuit that boosts the voltage of a DC power source using a power device, a smoothing capacitor that smoothes the voltage boosted by the booster circuit, and the DC power of the smoothing capacitor to the power device.
  • a single-phase inverter that converts to AC power, an output filter connected to the AC side of the single-phase inverter, a control circuit that controls each power device of the booster circuit and the single-phase inverter, and AC power from the phase inverter is output to the system via the output filter.
  • the control circuit performs PWM control on the single-phase inverter without boosting the booster circuit during a period when the system voltage absolute value is less than the voltage value of the DC power supply, and the modulation rate of the single-phase inverter is
  • the booster circuit is boosted by PWM control to adjust the voltage of the smoothing capacitor to PWM control the single-phase inverter, and the system voltage absolute value is greater than or equal to the voltage value of the DC power supply.
  • the voltage of the DC power source is boosted by PWM control of the booster circuit.
  • the loss associated with the switching operation of the power device can be reduced, and a high-accuracy AC output waveform can be generated at all phases of the system voltage without causing control failure. It can be connected to the system well.
  • FIG. 1 is a diagram showing a circuit configuration of a power conversion device according to Embodiment 1 of the present invention.
  • a booster circuit 2 is connected to a DC power source 1 such as a solar battery
  • a smoothing capacitor 3 is connected to the output side of the booster circuit 2
  • a booster circuit 2 is connected to the input side.
  • the bypass power device 7 for directly connecting the DC power source 1 and the smoothing capacitor 3 is connected.
  • a DC input side of the single-phase inverter 4 is connected in parallel with the smoothing capacitor 3, and a filter 5 for removing high-frequency noise is connected to the output side of the single-phase inverter 4.
  • the output side of the filter 5 is connected to the system 6. It is connected.
  • the booster circuit 2 includes a DC reactor 2a, a power device 2b that operates as a rectifying element, and a power device 2c that operates as a boost switch.
  • the single-phase inverter 4 is configured by connecting four power devices 4a to 4d in a full bridge type.
  • the filter 5 includes a reactor 5a and a capacitor 5b.
  • the power devices 2b and 2c constituting the booster circuit 2 and the power devices 4a to 4d constituting the single-phase inverter 4 are switching elements such as MOSFETs and IGBTs and free-wheeling diodes connected in reverse parallel thereto. It is configured.
  • the power device 2b in the booster circuit 2 performs a synchronous rectification operation that is turned on at a timing when a current flows through a diode connected in antiparallel, but may be configured with only a diode.
  • a voltage sensor 9 for detecting the DC power supply voltage Vi and a current sensor 10 for detecting the DC power supply current Ii are installed in the vicinity of the DC power supply 1, and a smoothing capacitor
  • a voltage sensor 11 for detecting the DC bus voltage Vc, which is the voltage of the smoothing capacitor 3 is installed in the vicinity of 3.
  • a current sensor 13 for detecting the filter current If is installed near the reactor 5a of the filter 5, a voltage sensor 14 for detecting the AC output voltage Vo is installed near the capacitor 5b of the filter 5, and A current sensor 15 for detecting an AC output current Io to the grid 6 is installed on the output side of the filter 5.
  • the power conversion apparatus also includes a control circuit 8 as a control means for controlling the power devices 2b, 2c, 4a to 4d of the booster circuit 2 and the single-phase inverter 4 and the bypass power device 7. .
  • the control circuit 8 includes a bypass power device 7, a booster circuit 2, and a single-phase inverter based on the voltages and currents from the voltage sensors 9, 11, 14 and the current sensors 10, 13, 15 and the voltage Vac of the system 6.
  • the control signals S1, S2 and S3a, S3b for switching control of each power device 4 are generated to control the bypass power device 7, the booster circuit 2 and the single-phase inverter 4.
  • the control signal S3a to the single-phase inverter 4 controls switching of the power devices 4a and 4d
  • the control signal S3b to the single-phase inverter 4 controls switching of the power devices 4b and 4c.
  • the voltage Vac of the system 6 may be a reference sine wave voltage of the system voltage Vac.
  • the control operation for the booster circuit 2, the single-phase inverter 4 and the bypass power device 7 by the control circuit 8 will be described with reference to the waveform diagram shown in FIG.
  • FIG. 2 the waveform of the DC power supply voltage Vi, the waveform of the AC output voltage Vo (waveform of AC voltage) output so as to be equal to the system voltage Vac, and the power devices 4a to 4 of the single-phase inverter 4
  • the waveforms of the modulation factor S3D of 4d and the modulation factor S2D of the power device 2c of the booster circuit 2 are shown.
  • control signal S1 given to the bypass power device 7 the control signal S3a given to the power devices 4a and 4d of the single-phase inverter 4, the control signal S3b given to the power devices 4b and 4c of the single-phase inverter 4 and the booster circuit 2
  • the waveform of the applied control signal S2 is shown.
  • the power device is turned on when the signal is high, and the power device is turned off when the signal is low.
  • the control circuit 8 compares the DC power supply voltage Vi detected by the voltage sensor 9 with the absolute value of the system voltage Vac.
  • the control circuit 8 does not cause the booster circuit 2 to perform a boost operation, but makes the bypass power device 7 conductive by the control signal S1, and the DC power supply voltage Vi is applied to the smoothing capacitor 3.
  • the control circuit 8 uses the detected values of the DC bus voltage Vc, the filter current If, the AC output voltage Vo, and the AC output current Io, so that the AC output voltage Vo and the AC output current Io become sine waves, and the AC output voltage Vo is a system.
  • a control command value for the single-phase inverter 4 is generated so as to be equal to the voltage Vac, and control signals S3a and S3b for the power devices 4a to 4d of the single-phase inverter 4 are obtained by comparing this control command value with a carrier wave such as a triangular wave.
  • the single-phase inverter 4 is generated and PWM-controlled.
  • a maximum allowable value is set in advance for the magnitude of the modulation rate S3D of the power devices 4a to 4d, and the modulation rate S3D is generated in the generation of the control signals S3a and S3b.
  • the control is switched.
  • the power devices 4a to 4d are switched with a dead time, so that the maximum value of the modulation rate S3D is smaller than 100%.
  • the control circuit 8 turns off the control signal S1 and shuts off the bypass power device 7, thereby boosting the circuit.
  • the control signal S2 for the second power device 2b, 2c is generated, and the booster circuit 2 is boosted by PWM control.
  • the control circuit 8 generates a command value Vc * of the DC bus voltage Vc so that the AC output voltage Vo equal to the system voltage Vac can be output by the single-phase inverter 4 by PWM control, and the DC power supply voltage Vi, DC power supply
  • a control command value for booster circuit 2 is generated so that DC bus voltage Vc, which is the output voltage of booster circuit 2, becomes command value Vc * .
  • the control signal S2 for the power devices 2b and 2c of the booster circuit 2 is generated by comparing the control command value with the carrier wave to control the booster circuit 2.
  • the control circuit 8 performs PWM control of the single-phase inverter 4 with the control signals S3a and S3b, but it is desirable to perform PWM control while maintaining the modulation rate S3D at the maximum value.
  • the control circuit 8 continues the OFF state of the control signal S1 to shut off the bypass power device 7, generates the control signal S2 for the power devices 2b and 2c of the booster circuit 2, and boosts the booster circuit 2 by PWM control.
  • the control circuit 8 sets the command value Vc * of the DC bus voltage Vc to the system voltage absolute value
  • the control command value of the booster circuit 2 is generated so that the DC bus voltage Vc, which is the output voltage of the booster circuit 2, becomes the command value Vc * .
  • the control signal S2 for the power devices 2b and 2c of the booster circuit 2 is generated by comparing the control command value with the carrier wave, and the booster circuit 2 is PWM-controlled. That is, the DC power supply voltage Vi is boosted to a voltage corresponding to the system voltage absolute value
  • the control circuit 8 controls the single-phase inverter 4 by generating control signals S3a and S3b so that the single-phase inverter 4 only switches the polarity of the AC output. At this time, the modulation rate S3D single-phase inverter 4 is approximately 100%.
  • the single-phase inverter 4 outputs the AC output voltage Vo by PWM control during the period in which the system voltage absolute value
  • the booster circuit 2 does not perform a boost operation, and when the magnitude of the modulation factor S3D reaches the maximum value, the single-phase inverter 4 performs a desired control by PWM control.
  • the booster circuit 2 performs a boost operation by PWM control to adjust the DC bus voltage Vc.
  • the booster circuit 2 outputs a voltage corresponding to the system voltage absolute value
  • the booster circuit 2 does not perform unnecessary boosting, and the single-phase inverter 4 does not perform high-frequency switching of a high voltage, so that loss can be effectively reduced.
  • the step-up circuit 2 does not perform a step-up operation and the magnitude of the modulation factor S3D of the single-phase inverter 4 reaches the maximum value
  • the single-phase inverter 4 can output the desired AC output voltage Vo by PWM control. Since the circuit 2 performs a boost operation by PWM control to adjust the DC bus voltage Vc, the system voltage absolute value
  • the single-phase inverter 4 outputs the AC output voltage Vo by PWM control while the booster circuit 2 performs the boost operation and adjusts the voltage of the smoothing capacitor 3, the magnitude of the modulation factor S3D of the single-phase inverter 4 is maximized.
  • the booster circuit 2 is the minimum booster operation and the DC bus voltage Vc is kept low, and the switching loss of both the booster circuit 2 and the single-phase inverter 4 can be reduced.
  • the booster circuit 2 when the booster circuit 2 does not perform a boost operation, the booster circuit 2 is bypassed by the bypass power device 7, so that the loss can be further reduced.
  • the maximum value of the modulation factor S3D is set to an actual maximum value in consideration of the arm short-circuit prevention time of the single-phase inverter 4 or a small value with some margin.
  • FIG. FIG. 3 is a diagram showing a circuit configuration of the power conversion device according to Embodiment 2 of the present invention
  • FIG. 4 is a waveform diagram for explaining the operation of the power conversion device. 3 and FIG. 4, the same reference numerals are given to the portions corresponding to or corresponding to those of the first embodiment shown in FIG. 1 and FIG.
  • the power converter according to the second embodiment is characterized in that the bypass power device 7 is omitted from the components shown in the first embodiment (FIG. 1) and the power to operate as a rectifying element of the booster circuit 2 is used. A diode 2d is used instead of the device 2b.
  • the control circuit 8a as the control means does not output the control signal S1 to the bypass power device 7, and the control signal S2 to the booster circuit 2 only controls the power device 2c.
  • the booster circuit 2 when the booster circuit 2 does not perform a boost operation, a current flows through a path passing through the DC reactor 2a and the diode 2d. Therefore, the conduction loss is lower than that in the first embodiment using the bypass power device 7. Although slightly increased, it is not necessary to control the bypass power device 7. For this reason, the control operation by the control circuit 8a is facilitated, and the number of parts can be reduced, so that the cost can be reduced.
  • FIG. 5 is a block diagram illustrating control of the booster circuit according to the third embodiment of the present invention.
  • the circuit configuration of the power conversion device according to the third embodiment and the operation waveforms of the respective parts are the same as those shown in FIGS. 1 and 2 of the first embodiment.
  • the single-phase inverter 4 has a polarity from the control in which the modulation rate S3D is PWM controlled at a maximum value, for example, 97%. Only the switching is performed, that is, the control is switched to the modulation rate S3D of 100%.
  • the control of the single-phase inverter 4 is switched at the phase ⁇ 2, and the control of the booster circuit 2 is switched as follows.
  • the control circuit 8 sets the command value Vc * of the DC bus voltage Vc so that the single-phase inverter 4 can output the AC output voltage Vo equal to the system voltage Vac by PWM control.
  • the control command value calculation unit 20 generates the DC bus voltage Vc, which is the output voltage of the booster circuit 2, using the detected values of the DC power supply voltage Vi, the DC power supply current Ii, and the DC bus voltage Vc .
  • the control command value 21 of the booster circuit 2 is generated so that Then, by comparing the control command value 21 with a carrier wave 23 such as a triangular wave, a control signal S2 to the booster circuit 2 is generated to control the booster circuit 2.
  • the command value Vc * of the DC bus voltage Vc is changed to the system voltage absolute value
  • the forward correction amount is added to the control command value 21 for correction, and the control signal S2 to the booster circuit 2 is generated based on the corrected control command value.
  • the control of the single-phase inverter 4 and the booster circuit 2 is switched, and the modulation rate S3D of the single-phase inverter 4 is set to a step of 3%, for example.
  • the booster circuit 2 is controlled by correcting the control command value 21 of the booster circuit 2 with the feedforward correction amount. For this reason, it can suppress that the alternating current output of the single phase inverter 4 becomes large at control switching timing, and distortion of an alternating current output waveform can be suppressed, and the control precision and reliability of a power converter device improve.
  • FIG. 6 is a waveform diagram for explaining the operation of the power conversion apparatus according to embodiment 4 of the present invention.
  • the circuit configuration of the power conversion device according to the fourth embodiment is the same as that shown in FIG. 1 of the first embodiment. Further, parts other than the carrier frequency and the control signal S2 in FIG. 6 are the same as those in the waveform diagram shown in FIG. 2 in the first embodiment.
  • the single-phase inverter 4 When the system voltage absolute value Vac is less than the DC power supply voltage Vi, the single-phase inverter 4 outputs the AC output voltage Vo by PWM control. When the modulation factor S3D of the single-phase inverter 4 is less than the set maximum value ( ⁇ ⁇ 1), the control circuit 8 does not boost the booster circuit 2 and uses the control power signal 7 by the control signal S1. And the DC power supply voltage Vi is applied to the smoothing capacitor 3.
  • the control circuit 8 When the magnitude of the modulation factor S3D reaches the maximum value at the phase ⁇ 1, the control circuit 8 turns off the control signal S1 to shut off the bypass power device 7, generates the control signal S2, and controls the booster circuit 2 to PWM. The control is switched to control for adjusting the DC bus voltage Vc by boosting operation.
  • the control circuit 8 When ⁇ 1 ⁇ ⁇ ⁇ 2, the control circuit 8 generates the command value Vc * of the DC bus voltage Vc so that the single-phase inverter 4 can output the AC output voltage Vo equal to the system voltage Vac by PWM control, and the DC power supply voltage Using the detected values of Vi, DC power supply current Ii, and DC bus voltage Vc, a control command value for booster circuit 2 is generated so that DC bus voltage Vc, which is the output voltage of booster circuit 2, becomes command value Vc *. .
  • the frequency of a carrier wave such as a triangular wave is increased steplessly from a reference frequency, for example, 20 kHz, and the generated control command value and the carrier wave are compared with each other for the power devices 2b and 2c of the booster circuit 2
  • a control signal S2 is generated to control the booster circuit 2.
  • the control circuit 8 performs PWM control on the single-phase inverter 4 while maintaining the modulation rate S3D at the maximum value.
  • the frequency of the carrier wave used to control the single-phase inverter 4 does not vary at a constant.
  • the control circuit 8 switches the single-phase inverter 4 from PWM control to control that only performs polarity switching and raises it.
  • the carrier frequency fa that has been reduced is steplessly lowered to the original reference frequency.
  • the carrier frequency fa rises to, for example, 22 kHz at the phase ⁇ 2, and then falls back to 20kHz. While the value of the carrier frequency fa is higher than the reference frequency, the number of pulses of the control signal S2 increases as the switching frequency increases.
  • the control circuit 8 switches the control of the single-phase inverter 4 and the booster circuit 2, and changes the modulation rate S3D of the single-phase inverter 4 to For example, a step change of 3% is caused.
  • the carrier frequency fa used for the control of the booster circuit 2 is increased at the time of switching the control, the command in the output voltage (DC bus voltage Vc) of the booster circuit 2 is increased.
  • Vc * is improved.
  • the AC output of the single-phase inverter 4 becomes large at the control switching timing, and the distortion of the AC output waveform can be suppressed, and the control accuracy and reliability of the power conversion device are improved.
  • the carrier frequency fa used for control of the booster circuit 2 is increased steplessly from the point of phase ⁇ 1 at which the magnitude of the modulation factor S3D of the single-phase inverter 4 becomes the maximum value. It may be raised from before or may be raised from a point closer to the phase ⁇ 2. It is desirable to change the carrier frequency fa steplessly in order to reduce distortion of the AC output waveform.
  • the carrier frequency fa is set for a predetermined period including the time when the system voltage absolute value
  • FIG. 7 is a waveform diagram for explaining the operation of the power conversion device according to embodiment 5 of the present invention. In FIG. 7, parts corresponding to or corresponding to those of the first embodiment shown in FIG.
  • control circuit 8 does not switch the control at the timing when the magnitude relationship between the DC power supply voltage Vi detected by the voltage sensor 9 and the system voltage absolute value
  • the control operation when 0 ⁇ ⁇ ⁇ / 2 is described below.
  • a symmetrical or positive / negative reversal waveform may be output, and the description is omitted.
  • the control circuit 8 As in the first embodiment, the booster circuit 2 is not boosted, and the bypass power device 7 is turned on by the control signal S1, and the DC power supply voltage Vi is applied to the smoothing capacitor 3. Further, using the detected values of the DC bus voltage Vc, the filter current If, the AC output voltage Vo, and the AC output current Io, the AC output voltage Vo and the AC output current Io become a sine wave, and the AC output voltage Vo becomes the system voltage Vac.
  • a control command value for the single-phase inverter 4 is generated so as to be equal, and control signals S3a and S3b for the power devices 4a to 4d of the single-phase inverter 4 are generated by comparing this control command value with a carrier wave such as a triangular wave,
  • the single phase inverter 4 is PWM controlled.
  • the control circuit 8 When the magnitude of the modulation factor S3D reaches the maximum value at the phase ⁇ 1, the control circuit 8 turns off the control signal S1 to shut off the bypass power device 7, and the control signal for the power devices 2b and 2c of the booster circuit 2 S2 is generated, and the booster circuit 2 is switched to control for boosting operation by PWM control. Then, when ⁇ 1 ⁇ ⁇ ⁇ / 2, the control circuit 8 performs PWM control on the single-phase inverter 4 while maintaining the modulation factor S3D at the maximum value, and an AC output voltage Vo equal to the system voltage Vac is obtained. Thus, the command value Vc * of the DC bus voltage Vc is generated to control the booster circuit 2.
  • the booster circuit 2 is controlled so that the DC bus voltage Vc, which is the output voltage of the booster circuit 2, becomes the command value Vc *.
  • a command value is generated, and a control signal S2 for the power devices 2b and 2c of the booster circuit 2 is generated by comparing the control command value with the carrier wave to control the booster circuit 2. This control is continued even if the system voltage absolute value Vac becomes equal to or higher than the DC power supply voltage Vi through the phase ⁇ 2.
  • the single-phase inverter 4 outputs the AC output voltage Vo equal to the system voltage Vac by PWM control in all phases, so that there is no step change in the modulation factor S3D of the single-phase inverter 4.
  • a low distortion AC output waveform can be generated.
  • the boosting operation period of the booster circuit 2 is limited, and the output voltage (DC bus voltage Vc) is also kept low.
  • the voltage at which the single-phase inverter 4 performs high-frequency switching is also kept low, and loss can be effectively reduced.
  • does not fall out of control with a proximity value less than the DC power supply voltage Vi, and it is possible to generate an AC output waveform with high reliability and high accuracy in all phases of the system voltage.
  • the wide band gap semiconductor include silicon carbide, a gallium nitride-based material, and diamond.
  • Elements formed of such a wide band gap semiconductor have high voltage resistance and high allowable current density, and thus can be miniaturized. By using these miniaturized elements, these elements are incorporated.
  • the semiconductor module can be downsized.
  • the heat resistance is high, the heat dissipating fins of the heat sink can be downsized and the water cooling section can be air cooled, so that the semiconductor module can be further downsized.
  • the power loss is low, it is possible to increase the efficiency of the characteristics of the element itself, and further increase the efficiency of the semiconductor module.

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Dc-Dc Converters (AREA)
  • Inverter Devices (AREA)

Abstract

La présente invention concerne, après qu'un circuit survolteur (2) augmente la tension d'une alimentation en courant continu (1), la conversion par un onduleur monophasé (4) de l'énergie en courant alternatif et la connexion à un circuit (6). Pendant les périodes où la valeur absolue de la tension de circuit (Vac) est inférieure à la tension de l'alimentation en courant continu (Vi), l'onduleur monophasé (4) produit la tension de sortie de courant alternatif (Vo) au moyen d'une commande MLI. Lorsque le facteur de modulation (S3D) est plus petit que la valeur maximale qui a été établie, le circuit survolteur (2) n'augmente pas la tension, et lorsque le facteur de modulation (S3D) atteint la valeur maximale, le circuit survolteur (2) effectue des opérations d'augmentation au moyen d'une commande MLI et ajuste la tension de source de courant continu (Vc) de sorte que l'onduleur monophasé (4) produira la tension de sortie de courant alternatif souhaitée (Vo) au moyen de la commande MLI. Pendant les périodes où la valeur absolue de la tension de circuit (Vac) est supérieure ou égale à la tension de l'alimentation en courant continu (Vi), le circuit survolteur (2) produit une tension équivalente à celle de la valeur absolue de la tension de circuit (Vac) au moyen de la commande par MLI, et l'onduleur monophasé (4) n'exécute que la commutation de polarité du courant de sortie alternatif.
PCT/JP2012/064035 2011-11-07 2012-05-31 Dispositif de conversion d'énergie électrique WO2013069326A1 (fr)

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JP2016163531A (ja) * 2015-03-05 2016-09-05 住友電気工業株式会社 変換装置
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JP2017038496A (ja) * 2015-08-12 2017-02-16 ニチコン株式会社 スイッチング電源装置および電磁石電源システム
JP2017073896A (ja) * 2015-10-07 2017-04-13 住友電気工業株式会社 電力変換装置及びその制御方法
CN106664034A (zh) * 2014-07-08 2017-05-10 住友电气工业株式会社 功率转换装置和三相ac电源装置
JP2017524323A (ja) * 2014-07-15 2017-08-24 ▲陽▼光▲電▼源股▲分▼有限公司Ｓｕｎｇｒｏｗ Ｐｏｗｅｒ Ｓｕｐｐｌｙ Ｃｏ．， Ｌｔｄ． シングルステージ太陽光発電グリッドタイインバータ及びその制御方法、応用
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JP2019004585A (ja) * 2017-06-14 2019-01-10 住友電気工業株式会社 電力変換装置及びその制御方法
CN109639131A (zh) * 2018-12-14 2019-04-16 南方电网科学研究院有限责任公司 一种功率信号输出装置

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KR101830666B1 (ko) * 2013-09-17 2018-02-21 엘에스산전 주식회사 전력 변환 장치
JP2015107027A (ja) * 2013-12-02 2015-06-08 株式会社日本自動車部品総合研究所 電力変換装置
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