EP0059927B1 - Dispositif de réception à micro-ondes - Google Patents

Dispositif de réception à micro-ondes Download PDF

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Publication number
EP0059927B1
EP0059927B1 EP82101608A EP82101608A EP0059927B1 EP 0059927 B1 EP0059927 B1 EP 0059927B1 EP 82101608 A EP82101608 A EP 82101608A EP 82101608 A EP82101608 A EP 82101608A EP 0059927 B1 EP0059927 B1 EP 0059927B1
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EP
European Patent Office
Prior art keywords
waveguide
receiving equipment
feed waveguide
equipment according
feed
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Expired
Application number
EP82101608A
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German (de)
English (en)
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EP0059927A1 (fr
Inventor
Günther Dr.-Ing. Mörz
Wilhelm Dipl.-Ing. Milcz
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Bosch Telecom GmbH
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ANT Nachrichtentechnik GmbH
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Application filed by ANT Nachrichtentechnik GmbH filed Critical ANT Nachrichtentechnik GmbH
Priority to AT82101608T priority Critical patent/ATE15960T1/de
Publication of EP0059927A1 publication Critical patent/EP0059927A1/fr
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Classifications

    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q13/00—Waveguide horns or mouths; Slot antennas; Leaky-waveguide antennas; Equivalent structures causing radiation along the transmission path of a guided wave
    • H01Q13/02—Waveguide horns
    • H01Q13/0208—Corrugated horns
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
    • H01P1/00—Auxiliary devices
    • H01P1/165—Auxiliary devices for rotating the plane of polarisation
    • H01P1/17—Auxiliary devices for rotating the plane of polarisation for producing a continuously rotating polarisation, e.g. circular polarisation
    • H01P1/172—Auxiliary devices for rotating the plane of polarisation for producing a continuously rotating polarisation, e.g. circular polarisation using a dielectric element
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q19/00—Combinations of primary active antenna elements and units with secondary devices, e.g. with quasi-optical devices, for giving the antenna a desired directional characteristic
    • H01Q19/10—Combinations of primary active antenna elements and units with secondary devices, e.g. with quasi-optical devices, for giving the antenna a desired directional characteristic using reflecting surfaces
    • H01Q19/18—Combinations of primary active antenna elements and units with secondary devices, e.g. with quasi-optical devices, for giving the antenna a desired directional characteristic using reflecting surfaces having two or more spaced reflecting surfaces
    • H01Q19/19—Combinations of primary active antenna elements and units with secondary devices, e.g. with quasi-optical devices, for giving the antenna a desired directional characteristic using reflecting surfaces having two or more spaced reflecting surfaces comprising one main concave reflecting surface associated with an auxiliary reflecting surface
    • H01Q19/193—Combinations of primary active antenna elements and units with secondary devices, e.g. with quasi-optical devices, for giving the antenna a desired directional characteristic using reflecting surfaces having two or more spaced reflecting surfaces comprising one main concave reflecting surface associated with an auxiliary reflecting surface with feed supported subreflector

Definitions

  • the present invention relates to a receiving device for left-handed and right-handed circularly polarized microwave signals, consisting of a receiving antenna with a feed system, a polarization converter, a polarization switch and a circuit for converting the microwave signals of both polarization directions from the radio frequency to the intermediate frequency level, part of which for Feed system of the receiving antenna belonging to the receiving waveguide is designed as a bandpass filter acting for both polarization directions and a dielectric insert is inserted into the antenna-side end of the feeding waveguide.
  • Such a receiving device is known from US-A-3001 193.
  • the devices for polarization conversion, for polarization separation and for coupling the received signals to the receiver circuits are implemented using waveguide technology. This results in a complex and very spacious arrangement.
  • Both US-A-3 216 017 and FR-A-1 562 149 are based on a stem radiator, consisting of a dielectric rod inserted into the feed waveguide of the antenna.
  • the part of the dielectric rod which is inserted in the feed waveguide is provided with flats which bring about a polarization conversion of the received signals.
  • the feed waveguide of an antenna can be formed by appropriate dimensioning as a high-pass filter to z. B. to block the oscillator frequency of a frequency converter coupled to the feed waveguide.
  • US Pat. No. 3,778,717 discloses a transmission device in which a waveguide is coupled to a microstrip substrate which carries an oscillator circuit, in that the waveguide is connected to the substrate in a vertical position on the substrate.
  • US-A-3 611 396 discloses an antenna horn which is provided with a groove structure and is formed from a dielectric material and is metallized on its outer surface.
  • the invention has for its object to provide a receiving device for double circularly polarized microwave signals, which is constructed with very simple means and in a very compact form, so that it offers ideal conditions for use as a TV satellite home reception system.
  • the conventional receiving device mentioned at the beginning uses separate components for the polarization conversion, the polarization separation and the waveguide-microstrip line transitions, which leads to a large overall length.
  • FIG. 1 shows the basic structure of a TV satellite home reception system.
  • a Cassegrain antenna with subreflector SR and main reflector HR serves as the receiving antenna.
  • the feed waveguide H of this antenna takes over the function of a high pass HP and a band pass BP for the microwave signals of both polarization directions.
  • a polarization switch OMT Organic Metal-Oxide Transducer
  • a polarization converter POL and a receiving train for each polarization direction are connected directly to the feed waveguide.
  • Each reception train contains an HF preamplifier HFV, a mirror selection filter F 1, a converter consisting of a mixer RF / ZF and an oscillator OSZ, a further mirror selection filter F 2 and an intermediate frequency amplifier ZFV.
  • the receiving device with two receiving trains allows the simultaneous reception of, for example, TV programs which are assigned to both the right-handed and the left-handed circular polarization.
  • FIG 3a shows a perspective view of the feed waveguide H for the receiving antenna constructed according to the Cassegrain principle.
  • the feed waveguide ends with a funnel-like exciter horn E, in which a dielectric, conical insert D is inserted.
  • a dielectric, conical insert D is inserted.
  • the end face of this insert is metallized and thus acts as a sub-reflector SR.
  • the dielectric insert D is provided with two cylindrical J.j 4 transformers T 1 and T 2 protruding into the feed waveguide H for impedance matching.
  • the transformation element T 2 has a reduced cross section compared to the transformation element T 1.
  • a transformation element can be used that tapers continuously towards the inside of the waveguide.
  • the two transformation elements T 1 and T simultaneously fulfill the function of a polarization converter, which converts the received right-handed or left-handed circularly polarized waves into horizontally or vertically linearly polarized waves.
  • the cylindrical transformation elements such as that in FIG. FIG. 3b shows section A-A across the feed waveguide, two opposing flats A 1 and A 1 'or A 2 and A 2' running along the cylinder axis.
  • the flats are arranged in such a way that their normals enclose an angle of 45 ° with the horizontal axis (x-axis) or the vertical axis (y-axis) of the feed steel conductor.
  • the dimensions of the flattenings can influence the intrinsic ellipticity of the polarization converter, whose course plotted against the frequency should be as flat as possible.
  • the dielectric filling degree of the waveguide at the location of the transformation elements must be selected so that an optimal distance between the operating frequency and the cutoff frequency of the waveguide is created. If the distance were too small or too large, the course of the intrinsic ellipticity would become significantly slanted and the polarization decoupling would deteriorate considerably.
  • the transformation elements T 1 and T 2 can also be provided with thickenings and / or indentations, not shown in FIGS. 3a and 3b, in order to reduce self-reflections.
  • the part of the feed waveguide into which the transformation elements of the dielectric insert protrude is dimensioned in such a way that it has the properties of a high-pass filter.
  • this high-pass waveguide piece HP has a cut-off frequency which ensures a sufficiently high blocking attenuation for the oscillator signal (for example 10.8 GHz).
  • the distance between the cut-off frequency (e.g. 11.0 GHz) and the useful signal frequencies must not be too small, otherwise the attenuation would be too high for the useful signals and the electrical parameters, such as cross-polarization decoupling, would be too strong for the mechanical ones Tolerances of the waveguide become dependent.
  • the high-pass waveguide piece HP is followed by a further part of the feed waveguide, which is designed as a bandpass filter BP.
  • a bandpass filter BP for example, this is a three-circuit bandpass filter that has identical transmission properties in the horizontal (x) and vertical (y) direction of oscillation.
  • the four orifices B 1 to B 4 which divide the waveguide into three resonators R 1, R 2 and R 3, have circular coupling openings.
  • the first diaphragm B 1 or the other diaphragms B 2, B 3, B 4 can be provided with a cross-slot-shaped coupling opening.
  • the feed waveguide H is terminated with a substrate MS which carries the microstrip circuit of the receiving train (s); namely, the feed waveguide is perpendicular to the ground surface of the substrate soldered to it.
  • a substrate MS which carries the microstrip circuit of the receiving train (s); namely, the feed waveguide is perpendicular to the ground surface of the substrate soldered to it.
  • four coupling pins K 1 to K 4 are arranged on the substrate MS, which protrude into the feed waveguide. Two of these coupling pins are arranged on the horizontal axis (x-axis) and the other two on the vertical axis (y-axis) of the waveguide.
  • the coupling pins protruding axially into the waveguide each have an end S 1, S 2, S 3 and S 4 that is angled radially to the direction of wave propagation.
  • each coupling pin also has an extension BL 1 BL 2, BL that acts as a dummy line 3 or BL 4, which points in the axial direction into the interior of the feed waveguide.
  • extension BL 1 BL 2 BL that acts as a dummy line 3 or BL 4, which points in the axial direction into the interior of the feed waveguide.
  • These blind lines BL 1 to BL 4 are used for broadband adaptation of the wave type conversion.
  • the overall length of the three-circuit bandpass filter shown in FIG. 3a can be further shortened in that the fourth aperture B 4 is omitted, and the resonator R 3 on the one hand from the Aperture B 3 and on the other hand is limited by the ground surface of the substrate MS, whereby the waveguide space for the shaft coupling simultaneously takes over the function of the third resonator R 3.
  • P 1, P 2, P 3 and P 4 denote the base points of the coupling pins K 1, K 2, K 3 and K 4 projecting through the substrate.
  • the signals at the two base points P 3 and P 4 or P 1 and P 2 each lying on an axis - the vertical (y) or horizontal (x) - have a phase difference of 180 ° with one another. This phase difference must be corrected again when the signals at the base points are combined. In the present exemplary embodiment, this is done, as indicated in FIG. 4, by means of different line lengths of the microstrip lines L 1, L 2, L 3 and L 4 starting from the base points. B. can also be done in a known manner with 180 ° ring hybrids.
  • the branch conductors SL 1, SL 2, SL 3 and SL 4 branching off from the microstrip lines serve to compensate for mismatches.
  • the total energy from the horizontally polarized field becomes the one input and the total energy from the vertically polarized field fed to the other input of a 90 ° ring hybrid RH.
  • the information from the right-handed circularly polarized and the left-handed circularly polarized receive signal are then present separately, provided that no separate polarization converter would be provided in the feed waveguide. Since this is available, the 90 ° hybrid RH could be dispensed with and the oppositely polarized received signals would be available after the conductors L 1, L 2 and L 3, L 4 have been brought into phase.
  • an input of the 90 ° ring hybrid RH or 3dB coupler is preceded by a 180 ° phase switch PS (see FIG. 4). Depending on the switching state (0 ° or 180 °), it enables either the information from the clockwise circularly polarized input signal or the information from the left-handed circularly polarized input signal to be present at an output of the ring hybrid.
  • the second redundant exit of the ring hybrid can be closed with an absorber.
  • the 180 ° phase changeover switch PS has, for example, the shape of a magnetized ferrite body, which is either arranged above the microstrip line leading to the ring hybrid or is attached to a location on the back of the substrate which is etched free from the ground line. With the exception of the separating surface from the substrate, the ferrite body can be metallized, which enables simple soldering onto the substrate. The magnetization of the ferrite body can be switched over by means of a magnetization coil through which a current pulse flows, with one or more turns.
  • the 180 ° phase switch can also be implemented using a switching circulator or a 3dB directional coupler with PIN diodes.
  • FIG. 5 shows another form of the exciter with which the cross-polarization properties of the antenna can be improved.
  • the exciter E shown in FIG. 3a in the form of a smooth-walled funnel is replaced here by a corrugated horn, the advantageous properties of which with regard to cross-polarization should be exploited; namely, the groove exciter is integrated in the dielectric insert D, the end face of which, as described above, is designed as a sub-reflector SR.
  • the groove structure R is applied to the initial area of the dielectric insert D protruding from the high-pass waveguide piece HP. This roller structure can be produced rationally together with the dielectric insert in the injection molding process.
  • the groove structure R perpendicular to the axis of the insert D and also to make the grooves trapezoidal so that the workpiece can be separated more easily from the injection mold.
  • the area provided with the groove structure R and a part TM of the dielectric insert which is inserted in the high-pass waveguide piece HP is coated with a metal layer which is identified in FIG. 5 by a puncturing.
  • the dielectric insert D can be fastened in the high-pass waveguide piece by gluing the metallized part TM, which is cylindrical or slightly conical. No electrical contact between the waveguide and the metallization is required, provided that the adhesive layer is sufficiently thin.
  • the dielectric insert D in turn has two transformation elements T 1 and T 2, the configuration of which is not shown for the purpose of polarization conversion.
  • the insert D can also have a conical cavity which is closed with a half-shell serving as a subreflector.
  • FIG. 6 A further form of excitation is shown in FIG. 6. It was created from the combination of a classic stem radiator with a dielectric holder of the subreflector SR.
  • the stem radiator consists of a dielectric insert DS which is inserted in the high-pass waveguide piece HP and also provided with transformation elements T 1 and T 2 and tapers towards the subreflector SR.
  • a stable dielectric sheath DH is placed on the high-pass waveguide piece, which encloses the metallized subreflector shell SR wearing.
  • the interior of this envelope DH can be filled with a light foam SCH with a low dielectric constant. This exciter achieves very good cross-polarization properties, provided there is a sufficiently large difference between the dielectric constants of the dielectric insert DS and the foam SCH.
  • the receiving device Since the aim is to keep the costs for the receiving device described above as low as possible, simple and quickly implementable methods of electrical balancing, which otherwise takes up a large part of the manufacturing costs, should be discussed in the end.
  • the receiving device should have high electrical qualities, on the other hand, the use of tuning screws should be avoided.
  • the particularly tolerance-sensitive components such.
  • corrections of the intrinsic ellipticity can hereby be brought about, whereby, as can be seen from FIG.
  • the alignment marks M are attached, depending on the cause of the ellipticity, in pairs opposite one another, at a suitable angle to the x or y axis. In the case of interfering couplings of the vibration levels that can be eliminated by adjustment, they must be attached at 45 ° or 135 °.
  • the generation of the alignment marks M can be facilitated by pre-weakening the waveguide wall at the predetermined points.

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  • Waveguide Aerials (AREA)
  • Input Circuits Of Receivers And Coupling Of Receivers And Audio Equipment (AREA)
  • External Artificial Organs (AREA)
  • Pharmaceuticals Containing Other Organic And Inorganic Compounds (AREA)
  • Polyesters Or Polycarbonates (AREA)
  • Waveguide Switches, Polarizers, And Phase Shifters (AREA)
  • Medicines Containing Material From Animals Or Micro-Organisms (AREA)
  • Medicines That Contain Protein Lipid Enzymes And Other Medicines (AREA)
  • Coloring Foods And Improving Nutritive Qualities (AREA)
  • Control Of Motors That Do Not Use Commutators (AREA)
  • Non-Reversible Transmitting Devices (AREA)
  • Threshing Machine Elements (AREA)
  • Measurement Of The Respiration, Hearing Ability, Form, And Blood Characteristics Of Living Organisms (AREA)
  • Micromachines (AREA)
  • Automatic Analysis And Handling Materials Therefor (AREA)

Claims (15)

1. Dispositif de réception de signaux en micro-ondes polarisés circulairement sinistrorsum et dextrorsum, constitué par une antenne réceptrice (HR) avec système d'alimentation, un convertisseur de polarisation (POL), un filtre de polarisation (OMT) et un circuit transposant les signaux en micro-ondes des deux sens de polarisation de la haute fréquence à la fréquence intermédiaire, une partie du guide d'ondes d'alimentation (H) appartenant au système d'alimentation de l'antenne réceptrice étant réalisée sous forme d'un filtre passe-bande (BP) agissant dans les deux sens de polarisation, et une insertion diélectrique (D) étant introduite dans l'extrémité du guide d'ondes d'alimentation (H) située du côté de l'antenne, ledit dispositif étant caractérisé en ce que:
a) la partie (T 1, T 2) de l'insertion diélectrique pénétrant dans le guide d'ondes d'alimentation (H) présente une forme transformant les signaux reçus polarisés circulairement en signaux polarisés rectilignement;
b) le tronçon du guide d'ondes d'alimentation (H) contenant ladite partie (T 1, T2) de l'insertion diélectrique et réalisée sous forme de filtre passe-haut (HP) dont la fréquence de coupure est supérieure à la fréquence de l'oscillateur du circuit de transposition; et
c) le guide d'ondes d'alimentation (H) est perpendiculaire au plan de masse d'un substrat de ligne à ruban (MS) portant le circuit de transposition et connecté audit plan, des broches de couplage (K 1, K 2, K 3, K 4) traversant le substrat de la ligne à ruban (MS) et pénétrant dans le guide d'ondes d'alimentation, les pieds (P 1, P 2, P 3, P 4) desdites broches étant reliés aux conducteurs de la ligne à ruban (L 1, L 2, L 4) sur la face du substrat (MS) opposée au plan de masse; et les broches de couplage (K 1, K 2, K 3, K 4) sont rélisées et positionnées de façon à coupler les signaux des deux sens de polarisation rectiligne.
2. Dispositif de réception selon revendication 1, caractérisé en ce que les conducteurs de la ligne à ruban (L 1, L 2, L 3, L 4) partant des pieds (P 1, P 2, P 3, P 4) des broches ce couplage (K 1, K 2, K 3, K 4) sont réunis par un hybride en anneau (RH) de façon que chacune des deux sorties de ce dernier délivre un signal contenant l'information du signal reçu polarisé circulairement dextrorsum ou sinistrorsum.
3. Dispositif de réception selon revendication 1, caractérisé en ce que deux broches de couplage (K 1, K 2) sont disposées sur un axe horizontal et deux broches de couplage (K 3, K 4) sur un axe vertical; les broches de couplage sont repliées radialement au sens de propagation des ondes dans le guide d'ondes d'alimentation et comportent des prolongements (BL 1, BL 2, BL 3, BL4), dirigés vers l'intérieur du guide d'ondes d'alimentation (H) et agissant comme des bras de réactance.
4. Dispositif de réception selon revendication 2, caractérisé en ce que, lorsqu'un seul changeur est prévu pour les signaux reçus des deux sens de polarisation, un inverseur de phase 180° (PS) est branché en amont d'une entrée de l'hybride en anneau (RH) pour qu'une sortie de ce dernier délivre, selon l'état de commutation de l'inverseur de phase 180°, le signal contenant l'information du signal reçu polarisé circulairement dextrorsum ou sinistrorsum.
5. Dispositif de réception selon revendication 4, caractérisé en ce que l'inverseur de phase 180° (PS) est un coupleur directif 3 dB ou un cir- culateur commutable par des diodes PIN.
6. Dispositif de réception selon revendication 4, caractérisé en ce que l'inverseur de phase 180° (PS) est réalisé par un corps de ferrite disposé au-dessus ou au-dessous du conducteur de la ligne à ruban aboutissant à une entrée de l'hybride en anneau, une impulsion de courant circulant dans une bobine permettant d'inverser l'aimantation dudit corps.
7. Dispositif de réception selon revendication 1, caractérisé en ce que la surface enveloppe de la partie (T 1, T 2) de l'insertion diélectrique (D) pénétrant dans le guide d'ondes d'alimentation (H) présente deux méplats longitudinaux en regard (A 1, A 1' et A 2, A 2'), dont les normales font un angle de 45° avec l'axe horizontal (axe X) ou l'axe vertical (axe Y) du guide d'ondes d'alimentation.
8. Dispositif de réception selon revendication 1, caractérisé en ce que la partie (T 1, T 2) de l'insertion diélectrique (D) pénétrant dans le guide d'ondes d'alimentation (H) présente vers l'intérieur de ce dernier une section à décroissance continue ou étagée.
9. Dispositif de réception selon revendication 1, caractérisé en ce que l'insertion diélectrique (D) s'évase en forme d'entonnoir à l'extérieur du guide d'ondes d'alimentation (H); et la face limite de cet évasement est réalisée en réflecteur auxiliaire (SR).
10. Dispositif de réception selon revendication 9, caractérisé en ce que la partie en entonnoir de l'insertion diélectrique (D) en saillie sur le guide d'ondes d'alimentation (H) est munie sur sa face extérieure d'une structure rainurée (R) métallisée.
11. Dispositif de réception selon revendication 1, caractérisé en ce que l'insertion diélectrique est en saillie sur le guide d'ondes d'alimentation (H), sous forme d'un élément rayonnant tige (DS).
12. Dispositif de réception selon revendication 11, caractérisé en ce que l'extrémité du guide d'ondes d'alimentation (H) porte une gaine diélectrique stable (DH) entourant l'élément rayonnant tige (DS), s'évasant vers le réflecteur auxiliaire (SR) et fermée par une calotte constituant le réflecteur auxiliaire (SR).
13. Dispositif de réception selon revendication 12, caractérisé en ce que la gaine diélectrique (DH) est remplie par une mousse (SCH), dont la constante diélectrique est nettement plus faible que celle de l'élément rayonnant tige (DS).
14. Dispositif de réception selon revendication 1, caractérisé en ce que le guide d'ondes d'alimentation (H) est muni de repères d'équilibrage (M), qui sont formés par une déformation mécanique de la paroi du guide d'ondes et servent à l'accord électrique des paramètres des filtres et de la polarisation croisée du dispositif de réception.
EP82101608A 1981-03-07 1982-03-03 Dispositif de réception à micro-ondes Expired EP0059927B1 (fr)

Priority Applications (1)

Application Number Priority Date Filing Date Title
AT82101608T ATE15960T1 (de) 1981-03-07 1982-03-03 Mikrowellen-empfangseinrichtung.

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
DE3108758 1981-03-07
DE3108758A DE3108758A1 (de) 1981-03-07 1981-03-07 Mikrowellen-empfangseinrichtung

Publications (2)

Publication Number Publication Date
EP0059927A1 EP0059927A1 (fr) 1982-09-15
EP0059927B1 true EP0059927B1 (fr) 1985-10-02

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ID=6126637

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EP82101608A Expired EP0059927B1 (fr) 1981-03-07 1982-03-03 Dispositif de réception à micro-ondes

Country Status (11)

Country Link
US (1) US4498061A (fr)
EP (1) EP0059927B1 (fr)
AT (1) ATE15960T1 (fr)
CA (1) CA1179753A (fr)
DE (2) DE3108758A1 (fr)
DK (1) DK90282A (fr)
ES (1) ES510038A0 (fr)
FI (1) FI820784L (fr)
GR (1) GR76035B (fr)
IE (1) IE53573B1 (fr)
NO (1) NO154510C (fr)

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DE3619220A1 (de) * 1986-06-07 1988-02-18 Kolbe & Co Hans Konvertersystem
DE3822963A1 (de) * 1987-07-06 1989-01-19 Toshiba Kawasaki Kk Mikrowellen-empfangsvorrichtung

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US4596047A (en) * 1981-08-31 1986-06-17 Nippon Electric Co., Ltd. Satellite broadcasting receiver including a parabolic antenna with a feed waveguide having a microstrip down converter circuit
JPS5999801A (ja) * 1982-11-30 1984-06-08 Toshiba Corp マイクロ波受信装置
CA1216907A (fr) * 1983-01-26 1987-01-20 Yoshiaki Kaneko Distributeur-combinateur d'energie du type a couplage par cavite resonante
NL8401335A (nl) * 1984-04-26 1985-11-18 Philips Nv Ontvanginrichting voor toepassing in een tv front end.
WO1986000761A1 (fr) * 1984-07-02 1986-01-30 The Marconi Company Limited Systeme d'antenne du type cassegrain
GB8421102D0 (en) * 1984-08-20 1984-09-26 Marconi Co Ltd Dielectric polariser
CH668507A5 (de) * 1984-10-10 1988-12-30 Huber+Suhner Ag Hohlleiter mit einem strahler.
JPS61198906A (ja) * 1985-02-28 1986-09-03 Mitsubishi Electric Corp 高周波増幅装置
CH667552A5 (de) * 1985-10-11 1988-10-14 Huber+Suhner Ag Hohlleiteranordnung.
FR2591406B1 (fr) * 1985-12-10 1989-01-13 Loire Electronique Dispositif de reception simultanee de deux signaux hyperfrequences a polarisation circulaire de sens inverses
FR2591407B1 (fr) * 1985-12-10 1988-08-05 Loire Electronique Dispositif de reception, a guide d'onde et circuits superheterodynes, de deux signaux hyperfrequences a polarisation de sens inverses
IT1188403B (it) * 1986-03-03 1988-01-14 Gte Telecom Spa Ricevitore a microonde a doppia polarizzazione per ricezione di radiodiffuzione diretta da satellite
DE3622175A1 (de) * 1986-07-02 1988-01-21 Kolbe & Co Hans Anordnung zur auskopplung zweier orthogonal linear polarisierter wellen aus einem hohlleiter
FR2623020B1 (fr) * 1987-11-05 1990-02-16 Alcatel Espace Dispositif d'excitation d'un guide d'onde en polarisation circulaire par une antenne plane
EP0442925A1 (fr) * 1988-11-14 1991-08-28 MOTSON & COMPANY LIMITED Appareil de reception de signaux de micro-ondes
GB2240886A (en) * 1990-02-02 1991-08-14 Racal Mesl Ltd Radio signal polarisation switching arrangement
US5109232A (en) * 1990-02-20 1992-04-28 Andrew Corporation Dual frequency antenna feed with apertured channel
FR2659172B1 (fr) * 1990-03-01 1992-09-04 Europ Agence Spatiale Element rayonnant en guide d'ondes a couplage electromagnetique.
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CA1179753A (fr) 1984-12-18
DE3108758A1 (de) 1982-09-16
IE53573B1 (en) 1988-12-21
DE3266606D1 (en) 1985-11-07
ES8302974A1 (es) 1983-01-16
NO154510B (no) 1986-06-23
US4498061A (en) 1985-02-05
ES510038A0 (es) 1983-01-16
NO154510C (no) 1986-10-01
GR76035B (fr) 1984-08-03
DK90282A (da) 1982-09-08
NO820692L (no) 1982-09-08
IE820498L (en) 1982-09-07
FI820784L (fi) 1982-09-08
EP0059927A1 (fr) 1982-09-15
ATE15960T1 (de) 1985-10-15

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