WO2010113218A1 - 電力変換装置 - Google Patents
電力変換装置 Download PDFInfo
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- WO2010113218A1 WO2010113218A1 PCT/JP2009/001521 JP2009001521W WO2010113218A1 WO 2010113218 A1 WO2010113218 A1 WO 2010113218A1 JP 2009001521 W JP2009001521 W JP 2009001521W WO 2010113218 A1 WO2010113218 A1 WO 2010113218A1
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- smoothing capacitor
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/42—Circuits or arrangements for compensating for or adjusting power factor in converters or inverters
- H02M1/4208—Arrangements for improving power factor of AC input
- H02M1/4225—Arrangements for improving power factor of AC input using a non-isolated boost converter
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/42—Circuits or arrangements for compensating for or adjusting power factor in converters or inverters
- H02M1/4208—Arrangements for improving power factor of AC input
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/0083—Converters characterised by their input or output configuration
- H02M1/0085—Partially controlled bridges
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- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
Definitions
- the present invention relates to a power conversion device that includes a circuit that improves an input power factor and converts AC power into DC power.
- the input AC is full-wave rectified by a diode bridge
- a reactor is connected to one end of the diode bridge
- a switch element is connected to the other output end of the diode bridge in the subsequent stage. Composed.
- the subsequent stage is connected to the output stage via a diode, and by turning on and off the semiconductor switch, the input current control for improving the input power factor and the voltage control of the output stage are performed (for example, see Patent Document 1). ).
- the present invention has been made to solve the above-described problems, and performs input current control for improving the input power factor and voltage control of the output stage to convert AC power into DC power.
- An object of the present invention is to reduce power loss and noise in a power conversion device, and to promote downsizing of the device configuration by eliminating a large current limiting circuit.
- a power conversion device is configured by connecting in series an AC side of one or more single-phase inverters each having a rectifier circuit that rectifies an input from an AC input power source, a plurality of semiconductor switch elements, and a DC voltage source.
- a smoothing capacitor for smoothing the output, and a shorting switch having one end connected to the inverter circuit and the other end connected to one end of the smoothing capacitor.
- the output of the inverter circuit is controlled using a current command so that the voltage of the smoothing capacitor follows the target voltage and the input power factor from the AC input power source is improved.
- the power converter according to the present invention is configured by connecting in series the AC side of one or more single-phase inverters each having a plurality of semiconductor switch elements and a DC voltage source, and the AC side is the first AC input power source.
- An inverter circuit that is connected in series with the terminals of the single-phase inverter and superimposes the sum of the outputs of the single-phase inverters on the AC input, a smoothing capacitor that is arranged downstream of the inverter circuit and smoothes the output, and a short-circuit switch and a rectifier, respectively.
- a first and second series circuit connected in series with a diode and connected between both terminals of the smoothing capacitor; A midpoint of the first series circuit is connected to an AC output line downstream of the inverter circuit, and a midpoint of the second series circuit is connected to a second terminal of the AC input power supply.
- the output of the inverter circuit is controlled using a current command so that the voltage of the smoothing capacitor follows the target voltage and the input power factor from the AC input power source is improved.
- the short-circuit switch does not require high-frequency switching, and the inverter circuit that improves the input power factor and controls the voltage of the output stage can make the voltage handled by switching relatively low. For this reason, switching loss and noise can be reduced without requiring a large current limiting circuit, and a power conversion device in which reduction of power loss and noise and miniaturization of the device configuration are promoted can be realized.
- FIG. 1 is a schematic configuration diagram of a power conversion device according to Embodiment 1 of the present invention.
- an AC voltage power source 1 (hereinafter simply referred to as AC power source 1) as an AC input power source is connected to a diode bridge 2 as a rectifier circuit.
- the output of the diode bridge 2 is connected to the reactor 3 as a current limiting circuit, and the AC side of the inverter circuit 100 constituted by a single-phase inverter is connected in series at the subsequent stage.
- the single-phase inverter that constitutes the inverter circuit 100 includes semiconductor switch elements 4 and 5, diodes 6 and 7, and a DC voltage source 8.
- the semiconductor switch elements 4 and 5 use IGBTs (Insulated Gate Bipolar Transistors) in which diodes are connected in antiparallel, MOSFETs (Metal Oxide Semiconductor Field Effect Transistors) in which diodes are built in between source and drain, etc.
- the diodes 6 and 7 may also be constituted by semiconductor switch elements in the same manner as the semiconductor switch elements 4 and 5.
- the reactor 3 may be connected in series to the subsequent stage of the inverter circuit 100.
- the short-circuit switch 9 and the rectifier diode 10 are connected to the subsequent stage of the inverter circuit 100, and the cathode side of the rectifier diode 10 is connected to the positive electrode of the smoothing capacitor 11 of the output stage.
- the connection point between the short-circuit switch 9 and the anode of the rectifier diode 10 is connected to the AC output line at the subsequent stage of the inverter circuit 100, and the other end of the short-circuit switch 9 is connected to the negative electrode of the smoothing capacitor 11.
- the short-circuit switch 9 is illustrated as a semiconductor switch element in which a diode is connected in reverse parallel, the present invention is not limited to this, and a mechanical switch or the like may be used.
- the operation of the power conversion device configured as described above will be described based on the waveforms of the respective units shown in FIG.
- the input from the AC power supply 1 is full-wave rectified by the diode bridge 2, and the voltage Vin and current Iin in the subsequent stage of the diode bridge 2 have waveforms as shown in FIG. 2.
- Vdc is a DC voltage of the smoothing capacitor 11 controlled to a constant target voltage Vdc *.
- the peak voltage of the voltage Vin is higher than the DC voltage Vdc of the smoothing capacitor 11.
- the inverter circuit 100 controls and outputs the current Iin by PWM control so that the input power factor from the AC power supply 1 becomes approximately 1, and superimposes the generated voltage on the AC side on the voltage Vin at the subsequent stage of the diode bridge 2.
- the current in the inverter circuit 100 charges the DC voltage source 8 through the diode 6 and is output through the diode 7 when the semiconductor switch elements 4 and 5 are off. .
- the current is output through the semiconductor switch element 4 and the diode 7.
- a current is output through the diode 6 and the semiconductor switch element 5.
- the semiconductor switch elements 4 and 5 are simultaneously turned on, the DC voltage source 8 is discharged through the semiconductor switch element 4 and output through the semiconductor switch element 5.
- the semiconductor switch elements 4 and 5 are controlled by such a combination of four types of control, and the inverter circuit 100 is PWM-controlled.
- the input voltage phase from the AC power supply 1 is ⁇
- the phase ⁇ 0 to 0 ⁇
- the shorting switch 9 is turned on until a predetermined phase ⁇ 1 that satisfies ⁇ 1 ⁇ 2.
- the current from the AC power source 1 flows through the path of the AC power source 1 ⁇ the diode bridge 2 ⁇ the reactor 3 ⁇ the inverter circuit 100 ⁇ the short-circuit switch 9 ⁇ the diode bridge 2 ⁇ the AC power source 1.
- the inverter circuit 100 Since the shorting switch 9 is in the ON state, no current flows through the rectifier diode 10 and the smoothing capacitor 11 at the output stage.
- the inverter circuit 100 generates a voltage substantially equal to the reverse polarity of the voltage Vin by combining, for example, a case where the semiconductor switch elements 4 and 5 are off and a case where only the semiconductor switch element 4 is on by PWM control.
- the current Iin is controlled and output so that the input power factor is approximately 1, and during this time, the DC voltage source 8 of the inverter circuit 100 is charged with energy.
- the inverter circuit 100 outputs, for example, a combination of a case where the semiconductor switch elements 4 and 5 are simultaneously turned on and a case where only the semiconductor switch element 4 is turned on by PWM control. To do.
- the current Iin is controlled so that the input power factor becomes approximately 1 while generating a voltage substantially equal to Vdc * ⁇ Vin so that the DC voltage Vdc of the smoothing capacitor 11 can be maintained at the target voltage Vdc *.
- the polarity of the voltage generated by the inverter circuit 100 is equal to the polarity of the current Iin, so that the DC voltage source 8 of the inverter circuit 100 is discharged.
- the shorting switch 9 continues to be turned off, but the operation in the inverter circuit 100 changes. That is, when the phase ⁇ is ⁇ 2 ⁇ ⁇ ⁇ ⁇ / 2, as shown in FIG. 5, the current from the AC power supply 1 is AC power supply 1 ⁇ diode bridge 2 ⁇ reactor 3 ⁇ inverter circuit 100 ⁇ rectifier diode 10 ⁇ It flows through the path of the smoothing capacitor 11 ⁇ the diode bridge 2 ⁇ the AC power supply 1.
- the inverter circuit 100 outputs, for example, a combination of a case where the semiconductor switch elements 4 and 5 are turned off and a case where only the semiconductor switch element 5 is turned on by PWM control.
- the target voltage Vdc * ⁇ voltage Vin of the smoothing capacitor 11 is satisfied, and the inverter circuit 100 sets a voltage approximately equal to Vin ⁇ Vdc * so that the DC voltage Vdc of the smoothing capacitor 11 can be maintained at the target voltage Vdc *.
- the current Iin is controlled and output so that the input power factor becomes approximately 1 while being generated in the opposite polarity to the polarity of.
- the polarity of the voltage generated by the inverter circuit 100 and the polarity of the current Iin are reversed, so that the DC voltage source 8 of the inverter circuit 100 is charged.
- the inverter circuit 100 generates and outputs a voltage substantially equal to the reverse polarity of the voltage Vin, controls and outputs the current Iin so that the input power factor becomes approximately 1, and the DC voltage source 8 is charged.
- the inverter circuit 100 maintains the DC voltage Vdc of the smoothing capacitor 11 at the target voltage Vdc * and controls the current Iin so that the input power factor is approximately 1. Output.
- the DC voltage source 8 is discharged, and when the voltage Vin is equal to or higher than the target voltage Vdc *, the DC voltage source 8 is charged.
- Vdc * Vp ⁇ ⁇ / (4cos ⁇ 1) It becomes.
- the target voltage Vdc * of the smoothing capacitor 11 is determined by ⁇ 1 that determines the short-circuit phase range 20, that is, can be controlled by changing ⁇ 1.
- the DC voltage Vdc of the smoothing capacitor 11 is controlled so as to follow the target voltage Vdc *.
- the voltage of the DC voltage source 8 of the inverter circuit 100 is Vsub
- a desired generated voltage of the inverter circuit 100 in each phase range of 0 ⁇ ⁇ ⁇ ⁇ 1, ⁇ 1 ⁇ ⁇ ⁇ ⁇ 2, and ⁇ 2 ⁇ ⁇ ⁇ ⁇ / 2.
- the above-described desired control can be performed with high reliability. That is, By setting the voltage Vsub to satisfy the three conditions of Vp sin ⁇ 1 ⁇ Vsub, (Vdc * ⁇ Vp sin ⁇ 1) ⁇ Vsub, and (Vp ⁇ Vdc *) ⁇ Vsub, the DC voltage Vdc of the smoothing capacitor 11 becomes the target voltage Vdc *.
- the inverter circuit 100 that controls the current Iin so that the input power factor becomes approximately 1 can be reliably controlled in all phases of the AC power supply 1.
- the voltage Vsub of the DC voltage source 8 is set to be equal to or lower than the Vin peak voltage Vp.
- the inverter circuit 100 is controlled by a control block as shown in FIG. First, the PI-controlled output 22a is calculated using the difference 21a between the DC voltage Vdc of the smoothing capacitor 11 at the output stage and the target voltage Vdc * as a feedback amount.
- the PI-controlled output 22b is calculated using the difference 21b between the voltage Vsub and the target voltage Vsub * as a feedback amount, and both outputs 22a,
- the amplitude target value 23 of the current Iin is determined from the sum of 22b. Based on the amplitude target value 23, a sine wave current command Iin * synchronized with the voltage Vin is generated.
- the difference 24 between the current command Iin * and the detected current Iin is used as a feedback amount, and the PI-controlled output is set as a voltage command 25 that becomes a target value of the generated voltage of the inverter circuit 100.
- the voltage command 25 is corrected by adding the feedforward correction voltage ⁇ V synchronized when the shorting switch 9 is switched on / off. Then, using the corrected voltage command 26 (voltage command 25 before correction except when the shorting switch 9 is switched on / off), a drive signal to each of the semiconductor switch elements 4 and 5 of the inverter circuit 100 is generated by PWM control. And the inverter circuit 100 is operated.
- the control for discharging the DC voltage source 8 is switched to the control for charging.
- the feedforward correction voltage ⁇ V is a positive voltage when the shorting switch 9 is turned off, and is a negative voltage when the shorting switch 9 is turned off.
- the inverter circuit 100 by controlling the inverter circuit 100 using the current command as described above, the DC voltage Vdc of the smoothing capacitor 11 is made to follow the target voltage Vdc *, and the input power factor from the AC power supply 1 is improved. Control to do.
- the short-circuit switch 9 does not require high-frequency switching, and the inverter circuit 100 that improves the input power factor and controls the DC voltage Vdc at the output stage can significantly reduce the voltage handled by switching from the peak voltage of the AC power supply 1. For this reason, switching loss and noise can be reduced without requiring a large reactor 3.
- the DC voltage source 8 of the inverter circuit 100 can be charged by bypassing the smoothing capacitor 11, so that the inverter circuit 100 does not generate a high voltage and the current Iin is supplied to the AC power source 1.
- the charged energy can be used for discharging to the smoothing capacitor 11.
- the reactor 3 does not store energy, but operates as a current limiting circuit that limits current, thereby improving the reliability of current control.
- the voltage Vsub of the direct-current voltage source 8 that is the direct-current voltage of the inverter circuit 100 to be equal to or lower than the peak voltage Vp of Vin, the above-described effects of high efficiency and low noise can be reliably obtained.
- the shorting switch 9 is operated only at a specific phase of the input voltage from the AC power supply 1, the power converter can be controlled stably and there is almost no loss due to switching.
- the target voltage Vdc * of the smoothing capacitor 11 can be controlled by ⁇ 1 in the short-circuit phase range 20, the target voltage Vdc * can be easily controlled, and the degree of freedom in design and control is improved.
- the inverter circuit 100 is controlled to switch the charging / discharging operation of the DC voltage source 8 using the feedforward control when the shorting switch 9 is switched on / off, the response time of the feedback control, It is possible to prevent control delay and realize high speed control.
- the current command is changed so that the voltage Vsub of the DC voltage source 8 is kept constant, the power converter can be controlled stably.
- charging / discharging of the DC voltage source 8 can be balanced, and supply of DC power from the outside is unnecessary, and the apparatus configuration is simplified. Note that voltage control of the DC voltage source 8 may be performed from the outside, and in that case, in the output control of the inverter circuit 100, it is not necessary to perform control to keep the voltage Vsub constant.
- the cathode side of the rectifier diode 10 is connected to the positive electrode of the smoothing capacitor 11 at the output stage.
- the rectifier diode 10 is connected to the negative electrode side of the smoothing capacitor 11 and the negative electrode is connected to the rectifier diode 10. It may be arranged so as to be connected to the anode side, and the same operation as in the above embodiment can be obtained.
- the inverter circuit 100 showed what was comprised by one single phase inverter, as shown in FIG. 7, the alternating current side of several single phase inverter 100a, 100b is connected in series.
- the inverter circuit 200 may be configured.
- the sum total of the outputs of the single-phase inverters 100a and 100b becomes the output of the inverter circuit 200, and the DC voltage of the smoothing capacitor 11 is made to follow the target voltage using the current command in the same manner as in the above embodiment. Control is performed so as to improve the input power factor from the power source 1. Then, the generated voltage on the AC side is superimposed on the voltage Vin after the diode bridge 2.
- the inverter circuit 200 may output by a gradation control that generates a stepped voltage waveform with the sum of the outputs of the plurality of single-phase inverters, or a specific single-phase inverter among the plurality of single-phase inverters Only PWM control may be performed.
- FIG. 1 one end of the shorting switch 9 is connected to the AC output line of the inverter circuit 100.
- one end of the shorting switch 9a is connected to the inverter circuit.
- 100 is connected to the negative electrode side of the DC voltage source 8 constituting 100.
- the other end of the short-circuit switch 9a is connected to the negative electrode side of the smoothing capacitor 11, that is, one end of the diode bridge 2, as in the first embodiment.
- the control of the inverter circuit 100 and the shorting switch 9a is the same as in the first embodiment, but when the shorting switch 9a is in the on state, that is, the input voltage phase ⁇ from the AC power supply 1
- the current from the AC power source 1 is: AC power source 1 ⁇ diode bridge 2 ⁇ reactor 3 ⁇ semiconductor switch element 4 of the inverter circuit 100 ⁇ short circuit switch 9a ⁇ diode bridge 2 ⁇ path of the AC power source 1 or AC power source 1 ⁇ diode
- the current flows through bridge 2 ⁇ reactor 3 ⁇ diode 6 of inverter circuit 100 ⁇ DC voltage source 8 ⁇ shorting switch 9a ⁇ diode bridge 2 ⁇ AC power supply 1.
- the current path is the same as the current path shown in FIGS. 4 and 5 of the first embodiment.
- the same effect as that of the first embodiment is obtained, and since the short-circuit switch 9a is connected to the negative electrode side of the DC voltage source 8, a current passes when the short-circuit switch 9a is turned on.
- the number of elements to be reduced can be reduced, conduction loss can be reduced, and the conversion efficiency of the entire power converter can be improved.
- the inverter circuit 200 when the inverter circuit 200 is configured by connecting the AC sides of the plurality of single-phase inverters 100a and 100b in series, the last stage of the plurality of single-phase inverters 100a and 100b is included.
- the short-circuit switch 9a By connecting the short-circuit switch 9a to the negative electrode side of the DC voltage source 8 in the single-phase inverter 100b connected to, the same operation is performed and the same effect is obtained.
- Embodiment 3 a power converter according to Embodiment 3 of the present invention will be described with reference to FIG.
- the output from the 1st terminal of AC power supply 1 is connected to the reactor 3, and the AC side of the inverter circuit 300 comprised by the single phase inverter in the subsequent stage is connected in series.
- the single-phase inverter in the inverter circuit 300 includes semiconductor switching elements 4, 5, 16, 17 and a DC voltage source 8 including IGBTs having diodes connected in antiparallel, MOSFETs having a diode built in between source and drain, and the like. Composed.
- the midpoint of the first series circuit 15a that constitutes the inverter by connecting the shorting switch 12a made of a semiconductor switch element and the rectifier diode 13a in series is connected to the AC output line at the subsequent stage of the inverter circuit 300
- a midpoint of the second series circuit 15b that constitutes an inverter by connecting a short-circuit switch 12b made of a semiconductor switch element and a rectifier diode 13b in series is connected to a second terminal of the AC power supply 1.
- the first and second series circuits 15a and 15b are connected in parallel and connected between both terminals of the smoothing capacitor 11 of the output stage.
- each of the short-circuit switches 12a and 12b is not limited to a semiconductor switch element, and may be a mechanical switch or the like, but the diodes 14a and 14b are connected in reverse parallel.
- the inverter circuit 300 can maintain the DC voltage Vdc of the smoothing capacitor 11 at a constant target voltage Vdc *, and can also be AC.
- the current Iin is controlled and output by PWM control so that the input power factor from the power supply 1 is approximately 1, and the generated voltage on the AC side is superimposed on the input voltage Vin from the AC power supply 1.
- the short-circuit switches 12a and 12b are turned on when the phase ⁇ of the voltage Vin is, for example, 0 ⁇ ⁇ ⁇ ⁇ 1. Then, the current flows through a path of AC power source 1 ⁇ reactor 3 ⁇ inverter circuit 300 ⁇ short circuit switch 12a ⁇ short circuit switch 12b ⁇ AC power source 1. If the polarity of the AC power supply 1 is negative and the phase Vin of the voltage Vin is, for example, ⁇ ⁇ ⁇ ⁇ + ⁇ 1, and the shorting switches 12a and 12b are turned on, the current flows in the reverse path shown in FIG.
- the current flows through the path of AC power source 1 ⁇ shorting switch 12b ⁇ shorting switch 12a ⁇ inverter circuit 300 ⁇ reactor 3 ⁇ AC power source 1.
- the inverter circuit 300 controls and outputs the current Iin so that the input power factor becomes approximately 1 while generating a voltage substantially equal to the reverse polarity of the voltage Vin by PWM control.
- the inverter circuit 300 The DC voltage source 8 is charged with energy.
- the shorting switches 12a and 12b are simultaneously turned on in the short circuit phase range 20. However, when the polarity of the AC power supply 1 is positive, only the shorting switch 12a is turned on and the polarity of the AC power supply 1 is negative. Only the shorting switch 12b may be turned on. In this case, a current flows through the diodes 14b and 14a connected to the other shorting switches 12b and 12a.
- the current flows as follows. First, when the polarity of the AC power supply 1 is positive, as shown in FIG. 12, the current is supplied from the AC power supply 1 ⁇ the reactor 3 ⁇ the inverter circuit 300 ⁇ the rectifier diode 13a ⁇ the smoothing capacitor 11 ⁇ the diode 14b of the shorting switch 12b ⁇ the AC power supply 1 It flows in the route.
- the inverter circuit 300 maintains the DC voltage Vdc of the smoothing capacitor 11 at the target voltage Vdc * and controls and outputs the current Iin so that the input power factor becomes approximately 1.
- the DC voltage source 8 is discharged.
- the absolute value of the voltage Vin is equal to or higher than the target voltage Vdc *, the DC voltage source 8 is charged. Is done.
- the target voltage Vdc * of the smoothing capacitor 11 is determined by ⁇ 1 that determines the short-circuit phase range 20, that is, it can be controlled by changing ⁇ 1.
- the DC voltage Vdc of the smoothing capacitor 11 is controlled so as to follow the target voltage Vdc *.
- the voltage Vsub of the DC voltage source 8 is set to be equal to or lower than the Vin peak voltage Vp, By setting the voltage Vsub to satisfy the three conditions of Vp sin ⁇ 1 ⁇ Vsub, (Vdc * ⁇ Vp sin ⁇ 1) ⁇ Vsub, and (Vp ⁇ Vdc *) ⁇ Vsub, the DC voltage Vdc of the smoothing capacitor 11 becomes the target voltage Vdc *.
- the inverter circuit 300 that controls the current Iin so that the input power factor becomes approximately 1 can be reliably controlled in all phases of the AC power supply 1.
- the inverter circuit 300 generates a current command as in the first embodiment, and is controlled by a voltage command calculated based on the current command.
- the voltage command is corrected by adding the feedforward correction voltage ⁇ V synchronized when the shorting switches 12a and 12b are switched on / off, and the DC voltage source 8 is charged / discharged. Switch operation. As a result, it is possible to prevent the control from being delayed by the response time of the feedback control, thereby realizing high-speed control.
- the inverter circuit 300 controls the input power factor to control the output stage DC voltage Vdc.
- the switching loss and noise can be reduced without requiring a large reactor 3, which can be significantly lower than the voltage.
- the DC voltage source 8 of the inverter circuit 300 can be charged by bypassing the smoothing capacitor 11, so that the voltage handled by switching can be reduced. Further reduction, higher efficiency and lower noise can be further promoted, and the same effect as in the first embodiment can be obtained.
- the diode bridge 2 used in the first embodiment is not necessary, the number of parts can be reduced and the device configuration is simplified. Moreover, since the number of elements through which current passes can be reduced, conduction loss can be reduced, and the conversion efficiency of the entire power conversion device can be improved.
- the inverter circuit 300 may be configured by connecting the AC sides of a plurality of single-phase inverters in series.
- the rectifier diodes 10, 13a, 13b are connected to the smoothing capacitor 11.
- a semiconductor switch element is connected, and the same is achieved by on / off control. You may make it work.
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Abstract
Description
以下、この発明の実施の形態1による電力変換装置について説明する。図1はこの発明の実施の形態1による電力変換装置の概略構成図である。
図1に示すように、交流入力電源としての交流電圧電源1(以下、単に交流電源1と称す)は整流回路としてのダイオードブリッジ2に接続される。ダイオードブリッジ2の出力は限流回路としてのリアクトル3に接続され、その後段に単相インバータにて構成されたインバータ回路100の交流側が直列接続される。インバータ回路100を構成する単相インバータは半導体スイッチ素子4、5、ダイオード6、7および直流電圧源8から構成される。ここで、半導体スイッチ素子4、5は、ダイオードが逆並列に接続されたIGBT(Insulated Gate Bipolar Transistor)やソース・ドレイン間にダイオードが内蔵されたMOSFET(Metal Oxide Semiconductor Field Effect Transistor)などを用い、またダイオード6、7も、半導体スイッチ素子4、5と同様に半導体スイッチ素子で構成してもよい。また、リアクトル3はインバータ回路100の後段に直列接続しても良い。
交流電源1からの入力はダイオードブリッジ2にて全波整流され、ダイオードブリッジ2の後段の電圧Vin、電流Iinは、図2に示すような波形となる。Vdcは一定の目標電圧Vdc*に制御される平滑コンデンサ11の直流電圧であり、この場合、電圧Vinのピーク電圧が平滑コンデンサ11の直流電圧Vdcより高いものとする。
インバータ回路100は、交流電源1からの入力力率が概1になるようにPWM制御により電流Iinを制御して出力し、交流側の発生電圧をダイオードブリッジ2後段の電圧Vinに重畳する。インバータ回路100内の電流は、図3~図5に示すように、半導体スイッチ素子4、5がオフの時には、ダイオード6を通って直流電圧源8を充電し、ダイオード7を通って出力される。また、半導体スイッチ素子4のみをオンした時には、電流は半導体スイッチ素子4とダイオード7とを通って出力される。また同様に、半導体スイッチ素子5のみをオンした時には、電流はダイオード6と半導体スイッチ素子5を通って出力される。また、半導体スイッチ素子4、5を同時にオンした時には、半導体スイッチ素子4を通って直流電圧源8を放電し、半導体スイッチ素子5を通って出力される。このような4種の制御の組み合わせにて半導体スイッチ素子4、5を制御してインバータ回路100をPWM制御する。
位相θが、θ1≦θ≦θ2である時、インバータ回路100はPWM制御により、例えば、半導体スイッチ素子4、5が同時にオンの場合と、半導体スイッチ素子4のみをオンの場合とを組み合わせて出力する。この時、平滑コンデンサ11の直流電圧Vdcが目標電圧Vdc*に維持できるように、Vdc*-Vinにほぼ等しい電圧を発生させつつ、入力力率が概1になるように電流Iinを制御して出力する。この間、インバータ回路100が発生する電圧極性と電流Iinの極性は等しくなるので、インバータ回路100の直流電圧源8は放電される。
即ち位相θが、θ2≦θ≦π/2である時、図5に示すように、交流電源1からの電流は、交流電源1→ダイオードブリッジ2→リアクトル3→インバータ回路100→整流ダイオード10→平滑コンデンサ11→ダイオードブリッジ2→交流電源1の経路で流れる。また、インバータ回路100はPWM制御により、例えば、半導体スイッチ素子4、5がオフの場合と、半導体スイッチ素子5のみをオンの場合とを組み合わせて出力する。この時、平滑コンデンサ11の目標電圧Vdc*≦電圧Vinであり、インバータ回路100は、平滑コンデンサ11の直流電圧Vdcが目標電圧Vdc*に維持できるように、Vin-Vdc*にほぼ等しい電圧をVinの極性に対して逆極性に発生させつつ、入力力率が概1になるように電流Iinを制御して出力する。この間、インバータ回路100が発生する電圧極性と電流Iinの極性は逆になるので、インバータ回路100の直流電圧源8は充電される。
即ち、交流電源1からの入力電圧の位相θのゼロクロス位相(θ=0、π)±θ1を特定位相として短絡用スイッチ9を切り換え、該ゼロクロス位相を中央として±θ1の位相範囲(以下、短絡位相範囲20と称す)でのみ、短絡用スイッチ9をオン状態として平滑コンデンサ11をバイパスさせる。このとき、インバータ回路100は、電圧Vinの逆極性にほぼ等しい電圧を発生させつつ、入力力率が概1になるように電流Iinを制御して出力し、直流電圧源8は充電される。そして、上記短絡位相範囲20以外の位相では、インバータ回路100は、平滑コンデンサ11の直流電圧Vdcを目標電圧Vdc*に維持し、また入力力率が概1になるように電流Iinを制御して出力する。このとき、電圧Vinが平滑コンデンサ11の目標電圧Vdc*以下の時、直流電圧源8は放電され、電圧Vinが目標電圧Vdc*以上の時は、直流電圧源8は充電される。
0≦θ≦π/2の位相期間では、インバータ回路100の直流電圧源8は、上述したように、0≦θ≦θ1、θ2≦θ≦π/2の期間で充電され、θ1≦θ≦θ2の期間で放電される。インバータ回路100の直流電圧源8の充放電エネルギが等しいとすると、以下の数式が成り立つ。但し、Vpは電圧Vinのピーク電圧、Ipは電流Iinのピーク電流である。
Vdc*=Vp・π/(4cosθ1)
となる。このように、平滑コンデンサ11の目標電圧Vdc*は短絡位相範囲20を決定するθ1により決まり、即ちθ1を変化させて制御できる。そして、平滑コンデンサ11の直流電圧Vdcは該目標電圧Vdc*に追従するように制御される。
Vp sinθ1≦Vsub、(Vdc*-Vp sinθ1)≦Vsub、(Vp-Vdc*)≦Vsub の3条件を満たすように電圧Vsubを設定することで、平滑コンデンサ11の直流電圧Vdcが目標電圧Vdc*に維持でき、また入力力率が概1になるように電流Iinを制御するインバータ回路100の制御が、交流電源1の全位相において信頼性よく行える。なお、直流電圧源8の電圧Vsubは、Vinのピーク電圧Vp以下に設定する。
インバータ回路100は、図6に示すような制御ブロックで制御される。まず、出力段の平滑コンデンサ11の直流電圧Vdcと目標電圧Vdc*との差21aをフィードバック量として、PI制御した出力22aを演算する。また、インバータ回路100の直流電圧源8の電圧Vsubを一定に保つため、該電圧Vsubとその目標電圧Vsub*との差21bをフィードバック量として、PI制御した出力22bを演算し、両出力22a、22bの和から電流Iinの振幅目標値23を決定する。そして、この振幅目標値23に基づいて、電圧Vinに同期した正弦波の電流指令Iin*を生成する。次に、電流指令Iin*と検出された電流Iinとの差24をフィードバック量として、PI制御した出力をインバータ回路100の発生電圧の目標値となる電圧指令25とする。この時、短絡用スイッチ9のオン/オフ切り換え時に同期したフィードフォワード補正電圧ΔVを加算して電圧指令25を補正する。そして、補正後の電圧指令26(短絡用スイッチ9のオン/オフ切り換え時以外は補正前電圧指令25)を用いて、PWM制御によりインバータ回路100の各半導体スイッチ素子4、5への駆動信号を生成し、インバータ回路100を動作させる。
なお、この場合リアクトル3は、エネルギを貯めるものではなく、電流を制限する限流回路として動作し、電流制御の信頼性が向上する。
また、インバータ回路100の直流電圧となる直流電圧源8の電圧Vsubを、Vinのピーク電圧Vp以下に設定することにより、上記高効率化、低ノイズ化の効果を確実に得る。
また、平滑コンデンサ11の目標電圧Vdc*は、短絡位相範囲20のθ1により制御できるため、目標電圧Vdc*を容易に制御でき、設計上および制御上の自由度が向上する。
また、電流指令を変化させて直流電圧源8の電圧Vsubを一定に保つ様に制御するため、電力変換装置を安定に制御することができる。また、直流電圧源8の充放電をバランスさせることができ、外部から直流電力の供給が不要で装置構成が簡便となる。
なお、外部から直流電圧源8の電圧制御をしても良く、その場合、インバータ回路100の出力制御では、電圧Vsubを一定に保つ制御をしなくても良い。
また、θ1=0として短絡用スイッチ9を常時オフ状態とすることも可能で、その場合、0≦θ≦θ2で直流電圧源8は放電、θ2≦θ≦π/2で直流電圧源8は充電する動作をする。
上記実施の形態1では短絡用スイッチ9の一端は、インバータ回路100の交流出力線に接続したが、この実施の形態2では、図8に示すように、短絡用スイッチ9aの一端は、インバータ回路100を構成する直流電圧源8の負極側に接続する。短絡用スイッチ9aの他端は、上記実施の形態1と同様に、平滑コンデンサ11の負極側、即ちダイオードブリッジ2の一端に接続される。
次に、この発明の実施の形態3による電力変換装置について、図10に基づいて説明する。
図10に示すように、交流電源1の第1の端子からの出力は、リアクトル3に接続され、その後段に単相インバータにて構成されたインバータ回路300の交流側が直列接続される。インバータ回路300内の単相インバータは、ダイオードが逆並列に接続されたIGBTやソース・ドレイン間にダイオードが内蔵されたMOSFETなどから成る半導体スイッチ素子4、5、16、17および直流電圧源8から構成される。
また、半導体スイッチ素子から成る短絡用スイッチ12aと整流ダイオード13aとを直列接続してインバータを構成する第1の直列回路15aの中点が、インバータ回路300の後段の交流出力線に接続され、さらに半導体スイッチ素子から成る短絡用スイッチ12bと整流ダイオード13bとを直列接続してインバータを構成する第2の直列回路15bの中点が交流電源1の第2の端子に接続される。そして、第1、第2の直列回路15a、15bは並列接続され、出力段の平滑コンデンサ11の両端子間に接続される。
この場合、各短絡用スイッチ12a、12bは、半導体スイッチ素子に限るものではなく、機械式のスイッチなどでも良いが、ダイオード14a、14bを逆並列接続する。
なお、短絡用スイッチ12a、12bは短絡位相範囲20において同時にオン状態としたが、交流電源1の極性が正の場合に短絡用スイッチ12aのみオン状態とし、交流電源1の極性が負の場合に短絡用スイッチ12bのみオン状態としても良く、その場合、他方の短絡用スイッチ12b、12aに接続されたダイオード14b、14aを経て電流が流れる。
また、直流電圧源8の電圧Vsubは、Vinのピーク電圧Vp以下に設定し、
Vp sinθ1≦Vsub、(Vdc*-Vp sinθ1)≦Vsub、(Vp-Vdc*)≦Vsub の3条件を満たすように電圧Vsubを設定することで、平滑コンデンサ11の直流電圧Vdcが目標電圧Vdc*に維持でき、また入力力率が概1になるように電流Iinを制御するインバータ回路300の制御が、交流電源1の全位相において信頼性よく行える。
さらに、上記実施の形態1で用いたダイオードブリッジ2を不要としているため、部品点数を低減でき装置構成が簡便になる。また、電流が通過する素子数が低減できるため、導通損失を低減でき、電力変換装置全体の変換効率を向上できる。
Claims (20)
- 交流入力電源からの入力を整流する整流回路と、
複数の半導体スイッチ素子と直流電圧源とをそれぞれ有する1以上の単相インバータの交流側を直列接続して構成され、該交流側を上記整流回路の出力に直列接続して上記各単相インバータの出力の総和を上記整流回路の出力に重畳するインバータ回路と、
該インバータ回路の後段に整流ダイオードを介して接続され該出力を平滑する平滑コンデンサと、
上記インバータ回路に一端が接続され、他端が上記平滑コンデンサの一端に接続された短絡用スイッチとを備え、
上記平滑コンデンサの電圧を目標電圧に追従させると共に上記交流入力電源からの入力力率を改善するように、上記インバータ回路を電流指令を用いて出力制御することを特徴とする電力変換装置。 - 上記各単相インバータは、上記半導体スイッチ素子にダイオードを直列接続した2組の直列回路と上記直流電圧源とで構成されることを特徴とする請求項1に記載の電力変換装置。
- 上記短絡用スイッチの一端は、上記インバータ回路の後段の交流出力線に接続されることを特徴とする請求項1または2に記載の電力変換装置。
- 上記短絡用スイッチの一端は、上記インバータ回路を構成する1以上の上記単相インバータの内、最後段に接続された単相インバータにおける上記直流電圧源の一端に接続されることを特徴とする請求項1または2に記載の電力変換装置。
- 上記短絡用スイッチをオン/オフする位相は、上記交流入力電源からの入力電圧の特定位相であることを特徴とする請求項1に記載の電力変換装置。
- 上記交流入力電源からの入力電圧のゼロクロス位相を中央とする所定位相範囲でのみ、上記短絡用スイッチをオン状態として上記平滑コンデンサをバイパスさせることを特徴とする請求項5に記載の電力変換装置。
- 上記短絡用スイッチをオン/オフする上記特定位相を変化させることで、上記平滑コンデンサの目標電圧を調整することを特徴とする請求項5または6に記載の電力変換装置。
- 上記短絡用スイッチのオン/オフ切り換え時に、上記インバータ回路は直流電力の充電/放電動作を切り替えるように制御されることを特徴とする請求項5または6に記載の電力変換装置。
- 上記インバータ回路の交流側に限流回路を直列に接続したことを特徴とする請求項1、2、5または6のいずれか1項に記載の電力変換装置。
- 上記インバータ回路の直流電圧が所定値となるように、上記電流指令を変化させて上記インバータ回路を出力制御することを特徴とする請求項1、2、5または6のいずれか1項に記載の電力変換装置。
- 上記インバータ回路の直流電圧は、上記交流入力電源の電圧ピーク値以下に設定することを特徴とする請求項1、2、5または6のいずれか1項に記載の電力変換装置。
- 複数の半導体スイッチ素子と直流電圧源とをそれぞれ有する1以上の単相インバータの交流側を直列接続して構成され、該交流側を交流入力電源の第1の端子に直列接続して上記各単相インバータの出力の総和を交流入力に重畳するインバータ回路と、
該インバータ回路の後段に配され、該出力を平滑する平滑コンデンサと、
それぞれ短絡用スイッチと整流ダイオードとを直列接続して上記平滑コンデンサの両端子間に接続される第1、第2の直列回路とを備え、
上記第1の直列回路の中点が上記インバータ回路の後段の交流出力線に接続され、上記第2の直列回路の中点が上記交流入力電源の第2の端子に接続され、
上記平滑コンデンサの電圧を目標電圧に追従させると共に上記交流入力電源からの入力力率を改善するように、上記インバータ回路を電流指令を用いて出力制御することを特徴とする電力変換装置。 - 上記短絡用スイッチにダイオードを逆並列接続したことを特徴とする請求項12記載の電力変換装置。
- 上記短絡用スイッチをオン/オフする位相は、上記交流入力電源からの入力電圧の特定位相であることを特徴とする請求項12に記載の電力変換装置。
- 上記交流入力電源からの入力電圧のゼロクロス位相を中央とする所定位相範囲でのみ、上記短絡用スイッチをオン状態として上記平滑コンデンサをバイパスさせることを特徴とする請求項14に記載の電力変換装置。
- 上記短絡用スイッチをオン/オフする上記特定位相を変化させることで、上記平滑コンデンサの目標電圧を調整することを特徴とする請求項14または15に記載の電力変換装置。
- 上記短絡用スイッチのオン/オフ切り換え時に、上記インバータ回路は直流電力の充電/放電動作を切り替えるように制御されることを特徴とする請求項14または15に記載の電力変換装置。
- 上記インバータ回路の交流側に限流回路を直列に接続したことを特徴とする請求項12~15のいずれか1項に記載の電力変換装置。
- 上記インバータ回路の直流電圧が所定値となるように、上記電流指令を変化させて上記インバータ回路を出力制御することを特徴とする請求項12~15のいずれか1項に記載の電力変換装置。
- 上記インバータ回路の直流電圧は、上記交流入力電源の電圧ピーク値以下に設定することを特徴とする請求項12~15のいずれか1項に記載の電力変換装置。
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Also Published As
Publication number | Publication date |
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US20120014139A1 (en) | 2012-01-19 |
DE112009004627T5 (de) | 2012-06-21 |
CN102379081A (zh) | 2012-03-14 |
US9197126B2 (en) | 2015-11-24 |
CN102379081B (zh) | 2014-03-05 |
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