WO2010021103A1 - スイッチング電源回路 - Google Patents

スイッチング電源回路 Download PDF

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Publication number
WO2010021103A1
WO2010021103A1 PCT/JP2009/003840 JP2009003840W WO2010021103A1 WO 2010021103 A1 WO2010021103 A1 WO 2010021103A1 JP 2009003840 W JP2009003840 W JP 2009003840W WO 2010021103 A1 WO2010021103 A1 WO 2010021103A1
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Prior art keywords
voltage
output
circuit
power supply
switching power
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Ceased
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PCT/JP2009/003840
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English (en)
French (fr)
Japanese (ja)
Inventor
崎村紘子
村田一大
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Panasonic Corp
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Panasonic Corp
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Priority to CN200980132267.3A priority Critical patent/CN102144353B/zh
Publication of WO2010021103A1 publication Critical patent/WO2010021103A1/ja
Anticipated expiration legal-status Critical
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of DC power input into DC power output
    • H02M3/02—Conversion of DC power input into DC power output without intermediate conversion into AC
    • H02M3/04—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters
    • H02M3/10—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/145—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M3/155—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/156—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators

Definitions

  • the present invention relates to a switching power supply circuit that stabilizes an output voltage using a three-terminal switching regulator as a non-insulated power supply circuit for stabilizing a DC output voltage.
  • a switching power supply circuit that stabilizes an output voltage using a three-terminal switching regulator has been widely used as a non-insulated power circuit for stabilizing a DC output voltage in a power supply circuit incorporated in an electronic device. ing.
  • an input side and an output side such as a photocoupler are insulated as a transmission circuit that transmits a signal corresponding to an output voltage to a controller that controls a switching operation.
  • the output voltage is fed back using the transmission circuit.
  • the conventional switching power supply circuit as described above is a power supply circuit in which the input side and the output side are non-insulated, but has a circuit configuration that requires an element in which the input side and the output side such as a photocoupler are insulated. ing. Therefore, the cost is increased by an insulating type element such as a photocoupler, which hinders cost reduction.
  • the present invention solves the above-described conventional problems, and can be realized at low cost by using a non-insulated type element as a transmission means as a non-insulated power circuit using a three-terminal switching regulator.
  • An object of the present invention is to provide a switching power supply circuit capable of performing
  • a switching power supply circuit transmits a switch connected to one of two input terminals to which an input voltage is input, and the input voltage switched by the switch as energy.
  • An energy transmission element that performs output between the two output terminals while smoothing energy transmitted from the energy transmission element, and detects an output voltage of the output generation circuit, and according to the output voltage
  • An output voltage detection circuit that generates a detection signal, a transmission circuit that is connected to one of the two output terminals, and that outputs a transmission signal according to the value of the detection signal generated by the output voltage detection circuit;
  • the potential at the connection point between the switch and the energy transfer element is used as an operation reference voltage, and the switch switch is switched according to the transfer signal.
  • a control circuit for generating a drive signal for controlling the quenching is connected between the transmission circuit and the control circuit, and a rectifier to flow only the transmission signal from the transmission circuit in the direction of the control circuit.
  • a non-insulated type rectifier element is used instead of a photocoupler as a non-insulated power circuit using a three-terminal switching regulator. Therefore, it can implement
  • the withstand voltage of the rectifying element may be equal to or greater than the sum of the input voltage and the forward drop voltage of the rectifying element.
  • the switching power supply circuit may further include a conversion circuit inserted between the rectifying element and the control circuit, and the conversion circuit may convert the transmission signal to a constant voltage.
  • the conversion circuit may be configured by a capacitor inserted between a connection point between the rectifying element and the control circuit and a connection point between the switch and the energy transfer element.
  • the transmission circuit may be a bipolar transistor.
  • the transmission circuit may be a MOS transistor.
  • the output voltage detection circuit includes a first resistor and a second resistor inserted in series between the two output terminals, and the first resistor and the second resistor.
  • a current signal output circuit that outputs a current signal corresponding to the divided voltage value at the connection point to the transmission circuit as the detection signal.
  • the current signal output circuit includes a reference terminal using the divided voltage value as a reference voltage, a cathode connected to the transmission circuit, and an anode connected to the other of the two output terminals. May be provided.
  • the output voltage detection circuit is based on a connection point between the third resistor and the Zener diode inserted in series between the two output terminals, and the first resistor and the second resistor. , A collector connected to the transmission circuit, and a transistor having an emitter connected to a connection point of the third resistor and the Zener diode.
  • the output voltage detection circuit has a third resistor and a Zener diode inserted in series between the two output terminals, and the cathode of the Zener diode is connected to the third resistor,
  • the anode of the Zener diode may be connected to the other of the two output terminals, and the detection signal corresponding to the current signal flowing into the cathode of the Zener diode may be output to the transmission circuit.
  • control circuit generates the drive signal for controlling the ON time of the switch so that the output voltage detected by the output voltage detection circuit is constant according to the value of the transmission signal. May be.
  • control circuit flows from the switch to the energy transfer element during the ON period of the switch so that the output voltage detected by the output voltage detection circuit is constant according to the value of the transfer signal.
  • the drive signal for controlling the peak value of the current to be generated may be generated.
  • control circuit generates the drive signal for controlling the switching frequency of the switch so that the output voltage detected by the output voltage detection circuit is constant according to the value of the transmission signal. May be.
  • control circuit controls the switching operation period and the switching stop period of the switch so that the output voltage detected by the output voltage detection circuit becomes constant according to the value of the transmission signal.
  • the drive signal may be generated.
  • the switch is connected to an input terminal on the positive voltage side of the input voltage, and an input terminal on the negative voltage side of the input voltage is connected to an output terminal on the negative voltage side of the two output terminals. It may be a positive voltage output type.
  • the positive voltage side of the input voltage may be connected to the switch, and the negative voltage side of the input voltage may be connected to an output terminal on the positive voltage side of the two output terminals.
  • a non-isolated power supply circuit using a three-terminal switching regulator can be realized at low cost by changing the transmission means from an element with an insulated input side and output side to an inexpensive non-insulated element. Can do.
  • FIG. 1 is a schematic circuit diagram showing a configuration of a switching power supply circuit according to Embodiment 1 of the present invention.
  • FIG. 2 is a waveform diagram showing the operation of the switching power supply circuit according to the first embodiment.
  • FIG. 3 is a schematic circuit diagram showing the configuration of the switching power supply circuit according to Embodiment 2 of the present invention.
  • FIG. 4 is a schematic circuit diagram showing the configuration of the switching power supply circuit according to Embodiment 3 of the present invention.
  • FIG. 5 is a schematic circuit diagram showing the configuration of the switching power supply circuit according to Embodiment 4 of the present invention.
  • FIG. 6 is a waveform diagram showing the operation of the switching power supply circuit according to the fourth embodiment.
  • FIG. 7 is a schematic circuit diagram showing a configuration of a switching power supply circuit as a comparative reference example.
  • FIG. 8 is a waveform diagram showing the operation of a switching power supply circuit as a comparative reference example.
  • FIG. 1 is a schematic circuit diagram showing the configuration of the switching power supply circuit according to the first embodiment.
  • the switching power supply circuit according to the first embodiment includes an input unit 1, an output unit 2, a three-terminal switching regulator 3, a capacitor 4 serving as a conversion circuit, a coil 5 serving as an energy transfer element, and output generation.
  • a capacitor 6 as a circuit, a diode 7, an output voltage detection circuit 8, a PNP transistor 9 as a transmission circuit, and a diode 10 as a rectifying element are provided.
  • the input unit 1 has a positive voltage terminal 11 and a negative voltage terminal 12, and receives an input voltage VIN.
  • the output unit 2 has a positive voltage terminal 21 and a negative voltage terminal 22, and outputs a voltage between the two terminals.
  • the three-terminal switching regulator 3 receives the input voltage VIN from the positive voltage terminal 11 of the input unit 1 and outputs a voltage obtained by switching the input voltage VIN to the coil 5.
  • Capacitance 4 supplies the power supply voltage of the three-terminal switching regulator 3.
  • the capacitor 4 is also a conversion circuit that converts the transmission signal from the diode 10 into a constant current and a constant voltage.
  • the coil 5 is an energy transfer element inserted between the three-terminal switching regulator 3 and the output unit 2.
  • the capacitor 6 is an output generation circuit that smoothes the voltage output from the coil 5 to the output unit 2.
  • the diode 7 has a cathode connected to a connection point between the three-terminal switching regulator 3 and the coil 5, and an anode connected to the negative voltage terminal 22 of the output unit 2.
  • the output voltage detection circuit 8 detects the output voltage VO of the output unit 2.
  • the diode 10 is a rectifying element inserted between the collector of the PNP transistor 9 and the three-terminal switching regulator 3.
  • the output voltage detection circuit 8 includes a first resistor 81 and a second resistor 82 inserted in series between the positive voltage terminal 21 and the negative voltage terminal 22 of the output unit 2, and a reference voltage detection function.
  • a shunt regulator 83 having a terminal connected to the connection point of the first resistor 81 and the second resistor 82, a cathode connected to the base of the PNP transistor 9, and an anode connected to the negative voltage terminal 22 of the output unit 2; Consists of.
  • FIG. 2 is a waveform diagram showing the operation of the switching power supply circuit according to the first embodiment.
  • the transmission circuit PNP transistor 9
  • the rectifier circuit diode 10
  • the capacitor 4 that are different from the comparative reference examples (FIGS. 7 and 8) described later will be described, and the configuration is the same as that of the comparative reference example. A description of the operation of the part is omitted. Since the operations of the three-terminal switching regulator 3 and the coil 5 are the same as those in the comparative reference example, the current IL flowing through the coil shown by the waveform (1) in FIG.
  • the operation waveform is similar to the current IL flowing through the coil indicated by the waveform (1) of the comparative reference example of FIG. 8 and the potential difference VL generated in the coil indicated by the waveform (2).
  • waveform (1) IL is a current flowing through the coil 5
  • waveform (2) VL is a potential difference generated in the coil 5
  • waveform (3) VA is a voltage at the base of the PNP transistor 9 (point A in FIG. 1)
  • waveform (4) VA ′ is a voltage at the collector of the PNP transistor 9 (point A ′ in FIG. 1)
  • a waveform (5) is an image diagram of the control terminal voltage VC.
  • TON is the ON period of the switch 31
  • TOFF is the OFF period of the switch 31
  • VS is the voltage of the source terminal 34
  • VC is the voltage of the control terminal 35
  • VCS is the voltage of the control terminal 35 with respect to the potential of the source terminal 34.
  • waveform (3) VA, waveform (4) VA 'and waveform (5) VC are operation waveforms when the reference voltage GND of the power supply is used as a reference. In the operation waveform of FIG. 2, the direction of the arrow with respect to the current IL of the coil 5 of FIG.
  • the voltage at the connection point C between the first resistor 81 and the second resistor 82 increases or decreases in the same way as the increase or decrease, and the voltage at the connection point C becomes the reference of the shunt regulator 83.
  • the amount of current flowing from the cathode of the shunt regulator 83 to the anode changes in accordance with the error between the voltage at the connection point C and the reference voltage of the shunt regulator 83.
  • the voltage at the base of the PNP transistor 9 (point A in FIG. 1) is lower than the potential at the positive voltage terminal 21 of the output unit 2 by the emitter-base voltage of the PNP transistor 9, and the output unit with respect to GND. Since the potential of the second positive voltage terminal 21 is constant at the output voltage VO, as shown in the waveform (3) in FIG. 2, the operation waveform is constant with respect to GND.
  • the PNP transistor 9 always has a current flowing between the emitter and the base, and the emitter and the collector are conductive. Therefore, considering the reference voltage GND of the power supply as a reference, the collector voltage VA ′ of the PNP transistor 9 is higher than the voltage VO of the positive voltage terminal 21 of the output unit 2 as shown in the waveform (4) of FIG. A constant operating waveform is obtained at a voltage lower by the voltage between the emitter and collector.
  • the voltage VA ′ at the collector of the PNP transistor 9 is higher than the control terminal voltage VC as shown in the waveforms (4) and (5) in FIG. Flowing.
  • the collector voltage VA ′ of the PNP transistor 9 needs to be a value that is higher than the control terminal voltage VC by the forward drop voltage VF of the diode 10.
  • the voltage VO of the positive voltage terminal 21 of the output unit 2 becomes lower than the control terminal voltage VC as shown in the waveforms (4) and (5) of FIG.
  • the voltage at the cathode becomes higher than the above voltage, and no current flows through the diode 10.
  • the diode 10 causes a current transfer signal to flow from the PNP transistor 9 to the controller 32, and a pulsed current transfer signal corresponding to the current signal from the output voltage detection circuit 8 is converted. It is converted into a feedback signal of a constant current / voltage by the capacitor 4 which is also a circuit and flows into the control terminal 35.
  • the current / voltage feedback signal corresponding to the fluctuation of the output voltage VO can be constantly fed back to the controller 32 and the power supply voltage of the controller 32 can be supplied at the same time, and the above power supply control can be realized.
  • the controller 32 controls the switching of the switch 31 in accordance with the amount of current flowing into the control terminal 35, the on-duty of the switch 31 is changed so that the error of the output voltage VO is reduced, whereby the output voltage VO is Kept constant.
  • the voltage difference between the collector voltage of the PNP transistor 9 (waveform (4) in FIG. 2) and the voltage at the control terminal 35 (waveform (5) in FIG. 2) fluctuates with the switching of the switch 31. . Since the voltage difference does not become larger than the fluctuation range of the control terminal voltage VC, the diode 10 inserted between the collector of the PNP transistor 9 and the control terminal 35 has a breakdown voltage equal to or larger than the fluctuation range of the control terminal voltage VC. It is necessary to secure.
  • waveform (4) in FIG. 2 is always constant with respect to GND, and the voltage difference is determined by the voltage characteristics between the emitter and the collector of the PNP transistor 9, so that it does not exceed the breakdown voltage of the PNP transistor. . Therefore, the input side and output side of the transmission means do not need to be insulated.
  • the transmission circuit is neither insulated nor high withstand voltage.
  • a transistor can be used.
  • an element such as a photocoupler in which the input side and the output side are insulated from each other is required in the transmission circuit, but in this embodiment, an element such as a photocoupler in which the input side and the output side are insulated becomes unnecessary, and Since the output side can be constituted by a transmission circuit such as a non-insulated PNP transistor, the cost can be reduced.
  • the diode 10 by using a high-breakdown-voltage diode as the diode 10, it can also be used for a power supply circuit having a high input voltage VIN and a high input voltage.
  • the controller 32 of the three-terminal switching regulator 3 controls the drive signal of the switch 31 according to the current signal flowing into the control terminal 35.
  • the present invention is not limited to this. Absent.
  • the controller 32 of the three-terminal switching regulator 3 can realize the above-described power supply control also by a control method for controlling the drive signal of the switch 31 in accordance with the voltage variation of the control terminal 35 with respect to the source terminal 34.
  • the diode 10 since the current from the diode 10 toward the control terminal 35 flows in a pulsed manner together with the switching of the switch 31, the diode 10 is used as a conversion circuit that converts the current to a constant voltage.
  • the capacitor 4 inserted between the control terminal 35 and the control terminal 35 is used, but is not limited thereto. As long as the circuit converts a pulsed current signal into a constant current / voltage signal, any conversion method may be used, such as averaging of current / voltage and peak hold.
  • the control method of the switch 31 by the controller 32 is described by the PWM control method in which the duty is changed, but is not limited thereto. It can also be realized by a current mode PWM control method for changing the current peak flowing between the drain terminal 33 and the source terminal 34, a PFM control method for changing the oscillation frequency, and an intermittent control method for repeating the oscillation period and the oscillation stop period.
  • the control method does not matter.
  • the output voltage detection circuit 8 is configured by the resistors 81 and 82 and the shunt regulator 83, but is not limited thereto. Any configuration can be used as long as it detects an error in the output voltage VO of the output unit 2, converts the error into a current signal, and allows the current to flow between the emitter and base of the PNP transistor 9.
  • the PNP transistor 9 is constituted by a PNP bipolar transistor, but is not limited thereto.
  • the configuration is not limited as long as the circuit can flow a signal corresponding to the current signal from the output voltage detection circuit 8 into the diode 10 that is a rectifying element.
  • FIG. 3 is a schematic circuit diagram showing the configuration of the switching power supply circuit according to the second embodiment.
  • the first embodiment as a circuit that detects an error of the output voltage VO of the output unit 2, converts the error into a current signal, and allows the current to flow between the emitter and base of the PNP transistor 9, for example, As shown in FIG. 3, a configuration including a first resistor 811, a second resistor 812, a Zener diode 84, and a PNP transistor 85 is also possible.
  • the voltage at the connection point C of the first resistor 81 and the second resistor 82 varies according to the variation of the output voltage VO of the output unit 2, and the connection point C Is applied to the base of the PNP transistor 85.
  • a current flows between the collector and the emitter of the PNP transistor 85 according to the fluctuation of the voltage applied to the base, and the current flows out from the base of the PNP transistor 9, so that it corresponds to the error of the output voltage VO of the output unit 2.
  • FIG. 4 is a schematic circuit diagram showing the configuration of the switching power supply circuit according to the third embodiment.
  • the first embodiment as a circuit that detects an error of the output voltage VO of the output unit 2, converts the error into a current signal, and allows the current to flow between the emitter and base of the PNP transistor 9, for example, A configuration using a Zener diode 86 as shown in FIG. 4 is also possible.
  • a current due to Zener breakdown flows through the Zener diode 86 according to the fluctuation of the output voltage VO of the output unit 2, and the current corresponding to the current flows between the emitter and base of the PNP transistor 9. Therefore, a current flows between the emitter and base of the PNP transistor 9 according to the error of the output voltage VO of the output unit 2.
  • FIG. 5 is a schematic circuit diagram showing the configuration of the switching power supply circuit according to the fourth embodiment.
  • the step-down type in which the positive voltage terminal 11 of the input unit 1 is connected to the three-terminal switching regulator 3 and the negative voltage terminal 12 of the input unit 1 is connected to the negative voltage terminal 22 of the output unit 2.
  • the positive voltage terminal 11 of the input unit 1 is connected to the three-terminal switching regulator 3 and the negative voltage terminal 12 of the input unit 1 is connected to the positive terminal of the output unit 2.
  • a configuration of a polarity inversion type non-insulated power supply circuit connected to the voltage terminal 21 is also possible.
  • TON is the ON period of the switch 31
  • TOFF is the OFF period of the switch 31
  • VS is the voltage of the source terminal 34
  • VC is the voltage of the control terminal 35
  • VCS is the voltage of the control terminal 35 with respect to the potential of the source terminal 34.
  • Waveform (3) VD, waveform (4) VD ′, and waveform (5) VC are operation waveforms when the reference voltage GND of the power supply is used as a reference. In the operation waveform of FIG. 6, the direction of the arrow with respect to the current IL of the coil 5 of FIG.
  • the conduction between the drain terminal 33 and the source terminal 34 is cut off and a current flows through the diode 7, so that the potential VS of the source terminal 34 is equal to the voltage ⁇ of the negative voltage terminal 22 of the output unit 2. Since the potential drops from VO by the forward drop voltage VF of the diode 7 ( ⁇ VO ⁇ VF) and the potential GND of the positive voltage terminal 21 of the output unit 2 becomes higher than the potential VS of the source terminal 34, the potential flows to the coil 5. The value of the current IL decreases, and the energy charged in the coil 5 is output to the output unit 2.
  • the capacitor 6 serving as an output generation circuit smoothes the current IL to generate an output voltage ⁇ VO, and the output current IO becomes an average value of the current IL.
  • the first resistor 81 and the second resistor 82 of the output voltage detection circuit 8 are connected to the first resistor 81 and the second resistor 82 when the output voltage VO of the output unit 2 matches the output voltage of the power supply specification.
  • Each resistance value is set so that the voltage at the connection point C with the resistor 82 matches the reference voltage preset in the shunt regulator 83.
  • the voltage at the connection point C between the first resistor 81 and the second resistor 82 increases or decreases in the same way as the increase or decrease, and the voltage at the connection point C becomes the reference of the shunt regulator 83.
  • the amount of current flowing from the cathode of the shunt regulator 83 to the anode changes in accordance with the error between the voltage at the connection point C and the reference voltage of the shunt regulator 83.
  • the voltage at the base of the PNP transistor 9 (point D in FIG. 5) is lower than the voltage GND at the positive voltage terminal 21 of the output unit 2 by the emitter-base voltage of the PNP transistor 9, and the waveform of FIG. As shown in 3), the operation waveform is constant with respect to GND.
  • the collector voltage VD ′ of the PNP transistor 9 is constant at a voltage lower than the voltage GND of the positive voltage terminal 21 of the output unit 2 by the voltage between the emitter and collector of the PNP transistor 9.
  • the voltage VD ′ at the collector of the PNP transistor 9 is higher than the control terminal voltage VC as shown in the waveforms (4) and (5) in FIG. Flowing.
  • the collector voltage VD ′ of the PNP transistor 9 needs to be a value that is higher than the forward voltage drop VF of the diode 10 than the control terminal voltage VC.
  • the diode 10 causes a current transfer signal to flow from the PNP transistor 9 to the controller 32, and a pulsed current transfer signal corresponding to the current signal from the output voltage detection circuit 8 is converted. It is converted into a feedback signal of a constant current / voltage by the capacitor 4 which is also a circuit and flows into the control terminal 35.
  • the current / voltage feedback signal corresponding to the error of the output voltage VO can be steadily fed back to the controller 32 and the power supply voltage of the controller 32 can be supplied at the same time, so that the above power supply control can be realized.
  • the controller 32 controls the switching of the switch 31 in accordance with the amount of current flowing into the control terminal 35, the on-duty of the switch 31 is changed so that the error of the output voltage VO is reduced, whereby the output voltage VO is Kept constant.
  • the voltage difference between the collector voltage of the PNP transistor 9 (waveform (4) in FIG. 6) and the voltage at the control terminal 35 (waveform (5) in FIG. 6) fluctuates with the switching of the switch 31. . Since the voltage difference does not become larger than the fluctuation range of the control terminal voltage VC, the diode 10 inserted between the collector of the PNP transistor 9 and the control terminal 35 has a breakdown voltage equal to or larger than the fluctuation range of the control terminal voltage VC. It is necessary to secure.
  • a circuit can be constituted by transistors whose transmission circuit is neither non-insulated nor high withstand voltage.
  • the three-terminal switching regulator 3 is composed of a switch 31 and a controller 32 that is a control circuit, and has three terminals 33, 34, and 35.
  • the switch 31 is composed of, for example, a power MOS-FET transistor, and oscillation (switching) of the switch 31 is controlled by a controller 32.
  • a terminal connected to the input unit 1 is a drain terminal 33
  • a terminal connected to the coil 5 is a source terminal 34
  • a terminal connected to the photocoupler 110 is a control terminal 35.
  • the three-terminal switching regulator 3 performs PWM control that changes the on-duty of the switch 31 in accordance with the amount of current flowing from the phototransistor 112 to the control terminal 35.
  • the control terminal voltage VC that is the power supply voltage of the controller 32 is always constant with respect to the source terminal voltage VS that is the reference voltage of the controller 32. It is also a terminal kept at
  • auxiliary power supply circuit 120 that supplies power to the phototransistor 112 in the photocoupler 110 will be described.
  • the auxiliary power supply circuit 120 includes a diode 121 that allows current to flow only from the positive voltage terminal 21 of the output unit 2 to the collector of the phototransistor 112, a connection point between the source terminal 34 of the three-terminal switching regulator 3 and the coil 5, and the diode 121. And a capacitor 122 inserted between the connection point of the collector of the phototransistor 112 and the collector.
  • TON in FIG. 8 indicates the ON period of the switch 31, and TOFF indicates the OFF period of the switch 31.
  • VS represents the voltage at the source terminal 34
  • VC represents the voltage at the control terminal 35.
  • VCS is the voltage of the control terminal 35 with respect to the potential of the source terminal 34, and is always constant.
  • the input voltage VIN is applied to the input unit 1
  • the input voltage VIN is applied to the drain terminal 33 of the three-terminal switching regulator 3.
  • the slope of the time change of the current IL flowing through the coil 5 is proportional to VL / L. Therefore, as shown by the waveform (2) in FIG. 33 is connected between the source terminal 34 and the input voltage VIN is applied to the source terminal 34 side of the coil 5. Therefore, in the ON period TON, a potential difference (VIN ⁇ VO) is generated in the coil 5 from the source terminal 34 side to the output unit 2 side, the value of the forward current IL increases, and the coil 5 is charged with energy.
  • the control terminal voltage VC becomes a potential of (VIN + VCS) with respect to GND as indicated by (4) VB ′.
  • the conduction between the drain terminal 33 and the source terminal 34 is cut off and a current flows through the diode 7, so that the potential of the source terminal 34 decreases from GND to the forward drop voltage VF of the diode 7.
  • a potential difference ( ⁇ VF ⁇ VO) is generated in the coil 5 from the source terminal 34 side to the output unit 2 side, the potential of the positive voltage terminal 21 of the output unit 2 becomes higher than the potential of the source terminal 34 side.
  • the value of the current IL flowing through the coil 5 decreases, and the energy charged in the coil 5 is output to the output unit 2.
  • the capacitor 6 smoothes the output energy to generate the output voltage VO, and the output current IO becomes an average value of the current IL flowing through the coil 5.
  • the control terminal voltage VC becomes a potential of ( ⁇ VF + VCS) with respect to GND.
  • the phototransistor 112 of the photocoupler 110 becomes conductive, and a current corresponding to the error of the output voltage VO flows into the control terminal 35. Since the controller 32 controls the switching of the switch 31 according to the amount of current flowing into the control terminal 35, the output voltage VO is kept constant by changing the on-duty of the switch 31 so that the error of the output voltage VO becomes small. To be kept.
  • the current flowing through the phototransistor 112 charges the capacitor 4 between the control terminal 35 and the source terminal 34, and secures a potential difference between the control terminal 35 and the source terminal 34 to form the power supply voltage of the controller 32. There is also a role to play.
  • an auxiliary power supply circuit 120 that maintains the collector-emitter voltage of the phototransistor 112 and supplies a current flowing through the phototransistor 112 is required.
  • the output voltage VO needs to be a value at which the voltage on the cathode side of the diode 121 becomes higher than the control terminal voltage VC.
  • the voltage VO of the positive voltage terminal 21 of the output unit 2 becomes lower than the control terminal voltage VC, so no current flows through the diode 121, but the collector potential of the phototransistor 112 is higher than the control terminal voltage VC. Is kept by the capacitor 122 so as not to decrease. As a result, the collector voltage of the phototransistor 112 is always higher than the control terminal voltage VC, and the collector-emitter voltage of the phototransistor 112 is ensured.
  • the input side of the transmission circuit that transmits a signal corresponding to the output voltage to the controller 32 is constant with respect to GND, whereas the control on the output side of the transmission circuit is performed. Since the terminal voltage VC fluctuates, a voltage difference is generated between the input side (waveform (3) in FIG. 8) and the output side (waveform (4) in FIG. 8) of the transmission circuit. Since the voltage difference does not become larger than the fluctuation range of the control terminal voltage VC, it is necessary for the transmission circuit to ensure a breakdown voltage that is equal to or greater than the fluctuation width of the control terminal voltage VC between the input side and the output side.
  • the coil 5 is used as the energy transfer element of the non-insulated power supply circuit, but the present invention is not limited to this.
  • the energy transmission element from the three-terminal switching regulator 3 to the output unit 2 may be any means as long as it has an inductor component.
  • the switching power supply circuit of the present invention is a non-isolated power supply circuit using a three-terminal switching regulator, and replaces a photocoupler that has been conventionally used for output voltage control feedback as a transmission circuit with a non-insulated component such as a transistor. And can be realized at a lower cost, and is useful when applied to a technique for reducing the cost of a non-insulated power supply circuit.

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  • Dc-Dc Converters (AREA)
PCT/JP2009/003840 2008-08-18 2009-08-10 スイッチング電源回路 Ceased WO2010021103A1 (ja)

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JP5341627B2 (ja) * 2009-06-11 2013-11-13 パナソニック株式会社 半導体装置およびスイッチング電源装置
JP2011015557A (ja) * 2009-07-02 2011-01-20 Panasonic Corp スイッチング電源装置およびスイッチング電源制御用半導体装置
US8717717B2 (en) * 2011-08-04 2014-05-06 Futurewei Technologies, Inc. High efficiency power regulator and method
CN102324853A (zh) * 2011-09-23 2012-01-18 广州金升阳科技有限公司 一种dc-dc电源变换器的辅助供电方法及辅助电源电路
JP6177813B2 (ja) * 2013-02-08 2017-08-09 株式会社村田製作所 Ｄｃ−ｄｃコンバータ
US8963516B2 (en) * 2013-03-04 2015-02-24 Astec International Limited Precision output control for DC voltage regulators
US9825625B2 (en) 2014-07-09 2017-11-21 CT-Concept Technologie GmbH Multi-stage gate turn-off with dynamic timing
CN105337494B (zh) * 2014-08-11 2019-01-11 邓维增 开关电源隔离电路
JP2017076891A (ja) * 2015-10-15 2017-04-20 株式会社東芝 電源電圧検知回路
JP6641169B2 (ja) * 2015-12-09 2020-02-05 ローム株式会社 スイッチングレギュレータ
JPWO2018168328A1 (ja) * 2017-03-14 2020-01-16 日本電産株式会社 パワー半導体スイッチング素子のダメージ予測装置及びダメージ予測方法、ａｃ−ｄｃコンバータ、ｄｃ−ｄｃコンバータ
CN117519396B (zh) * 2023-12-27 2024-03-22 中国科学院合肥物质科学研究院 一种负载自适应的高效率脉冲恒流源及控制方法

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US20100039087A1 (en) 2010-02-18
CN102144353B (zh) 2016-06-29
JP5513778B2 (ja) 2014-06-04
US8085007B2 (en) 2011-12-27
CN102144353A (zh) 2011-08-03
JP2010075037A (ja) 2010-04-02

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