WO2009090755A1 - 電力変換器の制御装置 - Google Patents
電力変換器の制御装置 Download PDFInfo
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- WO2009090755A1 WO2009090755A1 PCT/JP2008/050638 JP2008050638W WO2009090755A1 WO 2009090755 A1 WO2009090755 A1 WO 2009090755A1 JP 2008050638 W JP2008050638 W JP 2008050638W WO 2009090755 A1 WO2009090755 A1 WO 2009090755A1
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- carrier frequency
- command
- current
- current control
- map
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
- H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
- H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M7/53—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M7/537—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/08—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters
- H02M1/084—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters using a control circuit common to several phases of a multi-phase system
- H02M1/0845—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters using a control circuit common to several phases of a multi-phase system digitally controlled (or with digital control)
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
- H02P27/00—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage
- H02P27/04—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage
- H02P27/06—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage using dc to ac converters or inverters
- H02P27/08—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage using dc to ac converters or inverters with pulse width modulation
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/0003—Details of control, feedback or regulation circuits
- H02M1/0012—Control circuits using digital or numerical techniques
Definitions
- the present invention is applied to a power converter including an inverter composed of a plurality of semiconductor switching elements, and uses a pulse width modulation (hereinafter referred to as “PWM”) to control a switching element of the inverter.
- PWM pulse width modulation
- the present invention relates to a control device.
- a carrier comparison method as one of representative methods for calculating a switching pattern for PWM control of a semiconductor switch element constituting an inverter.
- the voltage command to the inverter is compared with the magnitude of the carrier wave, and an on / off pattern for switching control is determined.
- a triangular wave is often used as the carrier wave.
- the frequency of the carrier wave (hereinafter referred to as “carrier frequency”) is an important parameter that affects the characteristics of the power converter. For example, when the carrier frequency is set high, the accuracy and response characteristics of the inverter output voltage are improved, and electromagnetic noise generated from the load is reduced. On the other hand, when the carrier frequency is set high, the switching loss of the semiconductor switch element increases and the electromagnetic noise increases. For this reason, it is necessary to set an appropriate carrier frequency according to the type of load connected to the inverter and the operating conditions.
- Patent Document 1 As a technique for such a problem, for example, there is a technique disclosed in Patent Document 1 below.
- a technique for changing a carrier frequency according to a deviation (control deviation) between a current command and a detected current is disclosed. Specifically, when the control deviation is large, control for increasing the response frequency by increasing the carrier frequency is performed. Conversely, when the control deviation is small or zero, control for lowering the carrier frequency is performed based on the idea that the control is being performed satisfactorily. That is, it has the technical idea of increasing the carrier frequency only when a control response is required.
- This Patent Document 1 also discloses a technique for changing the carrier frequency in accordance with the change rate of the current deviation based on the change rate of the detected current and the change rate of the current command. It is.
- Patent Document 1 As described above, the technique disclosed in Patent Document 1 (hereinafter referred to as “prior art”) makes it possible to achieve both suppression of inverter loss and current control response.
- this conventional technique has the following problems.
- the conventional technology has a problem that the current control response and the inverter switching loss cannot be sufficiently achieved.
- This problem can be explained as follows. Since the value of the inverter switching loss changes according to the current, if the absolute value of the current is small, the loss becomes small, and the carrier frequency can be increased to improve the current control response.
- the carrier frequency when the carrier frequency is changed according to the current control deviation, the current magnitude information does not exist, and this feature cannot be effectively used.
- the carrier frequency is changed, signals such as the current command, the rate of change thereof, the detected current and the rate of change are referred to.
- the carrier frequency is determined by referring to each signal independently. Since the carrier frequency to be actually used is determined by obtaining and adding them, it cannot be said that the operation status of the power converter is sufficiently considered.
- the current control system in which the timing for sampling the detection current is not synchronized with the peak of the carrier wave (triangular wave) is affected by current ripple and noise, There was a problem that a stable carrier frequency could not be set. As a result, not only the target performance is not achieved, but also the setting of the carrier frequency itself fluctuates, and in the worst case, the current control system becomes unstable.
- the present invention has been made in view of the above, and is a power converter that can stably change a carrier frequency and can achieve further compatibility between current control response and inverter loss suppression.
- An object is to provide a control device.
- a control device for a power converter is applied to a power converter including an inverter composed of a plurality of semiconductor switching elements, and uses pulse width modulation.
- a current command generator for generating a current command, and a voltage for causing a desired current to flow to a load connected to the inverter based on the current command
- a current controller that generates a command
- a carrier frequency setting unit that sets a carrier frequency command used for pulse width modulation of the inverter according to the current command and a rate of change of the current command; and the voltage command and the carrier frequency command.
- the carrier frequency setting unit is configured to map information on a carrier frequency corresponding to the current command represented on one of the orthogonal axes and the rate of change of the current command represented on the other of the orthogonal axes. It has a two-dimensional map, and outputs the input current command and the carrier frequency information on the first two-dimensional map corresponding to the change rate of the input current command to the switching pattern calculation unit.
- the carrier frequency setting unit for setting the carrier frequency command used for the pulse width modulation of the inverter has the current command represented on one of the orthogonal axes and the other of the orthogonal axes.
- a first two-dimensional map is provided in which carrier frequency information corresponding to the rate of change of the current command is mapped, and the carrier frequency setting unit determines the input current command and the rate of change of the input current command.
- the carrier frequency information on the corresponding first two-dimensional map is output to the switching pattern calculation unit, and the switching pattern calculation unit performs pulse width modulation based on the voltage command and the carrier frequency command output from the carrier frequency setting unit. Since the switching pattern command to perform is calculated and output to the inverter, the carrier frequency can be changed stably Ukoto can an effect that it is possible to further achieve both a current control responsiveness improved and inverter loss suppression.
- FIG. 1 is a diagram illustrating a configuration of a control device for a power converter according to a first embodiment of the present invention.
- FIG. 2 is a diagram illustrating an example of the current command change rate calculation unit 11a and its output characteristics.
- FIG. 3 is a diagram showing an example of the current command change rate calculation unit 11a different from FIG. 2 and its output characteristics.
- FIG. 4 is a diagram for explaining the meaning of the carrier frequency map using the relationship with the locus of the current command change rate.
- FIG. 5 is a diagram showing an example different from FIG. 4 of the carrier frequency map.
- FIG. 6 is a diagram illustrating a configuration of a power converter control device according to the second embodiment of the present invention.
- FIG. 1 is a diagram illustrating a configuration of a control device for a power converter according to a first embodiment of the present invention.
- FIG. 2 is a diagram illustrating an example of the current command change rate calculation unit 11a and its output characteristics.
- FIG. 3 is a diagram showing an example
- FIG. 7 is a figure which shows the structure of the control apparatus of the power converter concerning Embodiment 3 of this invention.
- FIG. 8 is a diagram illustrating the configuration of the control device for the power converter according to the fourth embodiment of the present invention.
- FIG. 9 is a figure which shows the structure of the control apparatus of the power converter concerning Embodiment 5 of this invention.
- FIG. 10 is a diagram illustrating an example of a locus recording map.
- FIG. 11 is a diagram illustrating an example of a carrier frequency map generated by adjusting the locus recording map.
- FIG. 12 is a diagram for explaining the operation of the trajectory record map using the current command and the current command change rate.
- Embodiment 1 is a diagram illustrating a configuration of a control device for a power converter according to a first embodiment of the present invention.
- an inverter, a load connected to the inverter, and a current detector are also shown.
- the control device includes a current command generation unit 1, a current control unit 4 and a carrier frequency setting unit 11 that receive an output signal of the current command generation unit 1, and an output of the current control unit 4.
- a switching pattern calculation unit 6 that receives the signal and the output signal of the carrier frequency setting unit 11 is provided.
- the carrier frequency setting unit 11 also receives the current command change rate calculation unit 11a that receives the output signal of the current command generation unit 1, and the output signal of the current command generation unit 1 and the output signal of the current command change rate calculation unit 11a.
- a carrier frequency map 11c serving as each input is provided. Note that the output signal of the switching pattern calculation unit 6 is input to the inverter 8. Further, a current detector 9 is provided between the inverter 8 and a load 10 driven by the inverter 8, and a signal detected by the current detector 9 is fed back to the current control unit 4. It is configured.
- a current command 2 from the current command generator 1 is input to the current controller 4.
- the detected current signal 3 is also input to the current control unit 4, and the current control unit 4 generates a voltage command 5 for flowing a desired current to the load 10 and outputs the voltage command 5 to the switching pattern calculation unit 6.
- the switching pattern calculation unit 6 performs pulse width modulation (PWM) from the input voltage command 5 to generate a switching pattern command 7 and outputs it to the inverter 8.
- PWM pulse width modulation
- the inverter 8 is composed of a plurality of semiconductor switching elements, operates according to the switching pattern command 7, and supplies a desired current to the load 10.
- the current detector 9 detects the current supplied from the inverter 8 to the load 10 and feeds back the detected current to the current control unit 4.
- the carrier frequency setting unit 11 outputs the carrier frequency command 12 generated based on the current command 2 to the switching pattern calculation unit 6.
- the switching pattern calculation unit 6 generates the switching pattern command 7 with a carrier wave according to the input carrier frequency command 12.
- the carrier frequency can be changed based on the current command information.
- the detection current signal 3 since the detection current signal 3 is not used to generate the carrier frequency command 12, it is possible to change the carrier frequency stably even when the current control operation is not synchronized with the carrier wave.
- the configuration in which the detected current signal 3 detected by the current detector 9 is fed back to the current control unit 4 is illustrated. However, for example, when the load current can be estimated in the current control unit 4 The feedback information by the detection current signal 3 is not necessary.
- FIG. 2 is a diagram illustrating an example of the current command change rate calculation unit 11a and output characteristics of the configuration unit as an example.
- FIG. 3 illustrates an example of the current command change rate calculation unit 11a that is different from FIG. It is a figure which shows the output characteristic of the structure part made into the said example.
- the carrier frequency setting unit 11 includes the current command change rate calculation unit 11a and the carrier frequency map 11c.
- the current command change rate calculation unit 11a calculates the change rate of the input current command 2 and outputs it to the carrier frequency map 11c.
- the carrier frequency map 11c generates and outputs a carrier frequency command 12 based on the input current command 2 and the rate of change of the current command 2.
- the carrier frequency map 11c includes a current command represented on one of the orthogonal axes (vertical axis in the example of FIG. 1) and a current command change represented on the other of the orthogonal axes (horizontal axis in the example of FIG. 1).
- a carrier frequency map (A) (first two-dimensional map) that is a two-dimensional map in which carrier frequency information corresponding to the rate is mapped is held.
- a carrier frequency map (A) first two-dimensional map
- carrier frequency map (A) first two-dimensional map
- the control device since the calculation of the current command change rate by the current command change rate calculation unit 11a is a differential operation, sometimes an excessive signal may be generated. Therefore, when the control device is mounted on the power converter, if it is not desirable to generate an excessive signal, it is preferable to use a filter that cuts the gain at a specific frequency or higher.
- a filter having a transfer function represented by the following equation (1-1) can be used.
- G (s) s / (1 + T ⁇ s) (1-1)
- T is a parameter for determining a band
- s is a Laplace variable
- the current command change rate calculation unit 11a includes a change rate calculation filter 112 as shown in FIG. 2A, and the waveform of the current command change rate obtained by the current command change rate calculation unit 11a is as follows.
- the waveform is as shown in FIG.
- the current command change rate calculation unit 11a includes an absolute value calculation unit 113 and a low-pass filter (hereinafter referred to as “LPF”) 114, as shown in FIG. You may comprise.
- the change rate calculation filter 112 calculates the current command change rate
- the absolute value calculation unit 113 calculates the absolute value of the current command change rate
- the LPF 114 executes low-pass filter processing.
- the current command change rate calculation unit 11a for example, even when a vibration-like current command as shown in FIG. 3B is input, a stable current command change rate can be calculated.
- FIG. 4 is a diagram for explaining the meaning of the carrier frequency map using the relationship with the locus of the current command change rate
- FIG. 5 is a diagram showing an example different from FIG. 4 of the carrier frequency map. is there.
- the carrier frequency map 11c outputs a carrier frequency command based on the current command and the rate of change of the current command.
- the carrier frequency on the carrier frequency map shown in FIG. 4 is output as a carrier frequency command.
- two types of carrier frequencies fc1 and fc2 fc1 ⁇ fc2 can be selected according to the current command and the value of the current command change rate.
- FIG. 4 shows a carrier frequency map based on this concept. For example, in the case of a current command as shown in FIG. 2B, the locus shown in FIG. 4 is traced. According to the carrier frequency map shown in FIG. 4, a high carrier frequency fc2 can be set when the current command change rate is large.
- a low carrier frequency fc1 can be set, so that a high current control response and inverter loss suppression can be realized.
- two types of selectable carrier frequencies are used. However, selectable carrier frequencies may be increased.
- a desired one can be selected from three types of carrier frequencies (fc1 ⁇ fc2 ⁇ fc3).
- the carrier frequency map in which the carrier frequency is changed in stages is shown, but the carrier frequency may be controlled to be continuously switched. By this control, it is possible to reduce the disturbance of current and the change in inverter operation sound due to the change of the carrier frequency.
- the power converter control device of the present embodiment it is possible to set the carrier frequency according to the current command information. With this control, both reduction of inverter switching loss and improvement of high current control response can be realized.
- current command information is used and control is performed using a carrier frequency map that correlates the current command and the rate of change of the current command, a stable carrier can be obtained even when the sampling of the detected current is not synchronized with the carrier wave. The frequency can be changed.
- the switching pattern command 7 is described as being applied to the asynchronous PWM method.
- the present invention can also be applied to a synchronous PWM method that performs a switching pattern calculation in synchronization with the voltage command 5. For example, by setting the number of pulses in one cycle of the voltage command 5 instead of the carrier frequency, it can be applied to the synchronous PWM method, and appropriate switching setting can be performed.
- FIG. FIG. 6 is a diagram illustrating a configuration of a power converter control device according to the second embodiment of the present invention.
- the load 10 is assumed to be an AC load such as an AC motor in order to better explain the effects of the present embodiment.
- coordinate conversion units 13 and 15 are further provided in the configuration of the first embodiment shown in FIG.
- the phase / frequency generation unit 17 is provided and the carrier frequency setting unit 11 is provided with a carrier frequency map 11d.
- the detected current signal 3 is converted into a detected current signal 16 on a biaxial orthogonal rotation coordinate by the coordinate conversion unit 15 and used for current control.
- the voltage command 5 is converted into an AC voltage command 14 by the coordinate conversion unit 13 and used for switching pattern calculation.
- the phase / frequency generator 17 outputs a phase signal 18 and a frequency signal 19.
- the phase signal 18 is used for coordinate conversion.
- the frequency signal 19 corresponds to a signal obtained by differentiating the phase signal 18.
- the frequency of the frequency signal 19 output from the phase / frequency generator 17 is set as a fundamental frequency. That is, the frequency of the power supplied from the inverter 8 is this basic frequency.
- the frequency signal 19 is input to the carrier frequency setting unit 11.
- the carrier frequency needs to be set sufficiently higher than the fundamental frequency. If a sufficient carrier frequency cannot be obtained, problems such as the current control system becoming unstable, excessive high-frequency current flowing in the AC load, and the loss of the AC load and the inverter increase. For this reason, when setting a carrier frequency, it becomes a preferable structure to reflect the information of a fundamental frequency.
- FIG. 6 shows a configuration of the carrier frequency setting unit 11 when three types of carrier frequencies can be selected as an example.
- the current command change rate calculation unit 11a and the carrier frequency map 11c having the carrier frequency map (A) are the same as or equivalent to those described in the first embodiment.
- a carrier frequency map 11d is newly added.
- B carrier frequency map
- the carrier frequency map 11d is an operation unit that receives the frequency signal 19 and outputs a carrier frequency update signal 11e.
- the carrier frequency map 11d is a one-dimensional map (first one-dimensional map), and fc1 ⁇ A carrier frequency map (B) in which setting information of fc3 is described is held.
- the carrier frequency update signal 11e is a value of carrier frequency options fc1, fc2, and fc3 (fc1 ⁇ fc2 ⁇ fc3) in the carrier frequency map 11c (carrier frequency map (A)). That is, one carrier frequency is selected from the three types of carrier frequencies on the carrier frequency map (A) based on the current command 2 and the current command change rate 11b, and the value is determined by the carrier frequency map (B). It is determined.
- the control system configured as described above makes it possible to set the carrier frequency reflecting the fundamental frequency. Further, by adopting such a control system, it is possible to ensure the stability of the current control system according to the fundamental frequency, and the carrier frequency that minimizes the loss of the inverter 8, the loss of the load 10, or the total thereof. Can be set.
- the carrier frequency can be set according to the current command information and the fundamental frequency.
- the carrier frequency update signal 11e output from the carrier frequency map 11d has been described as the values of the carrier frequency options fc1, fc2, and fc3 in the carrier frequency map (A). Needless to say, a control system may be used that selects the closest value to the carrier frequency map 11c based on the value indicated as the carrier frequency update signal 11e.
- FIG. FIG. 7 is a figure which shows the structure of the control apparatus of the power converter concerning Embodiment 3 of this invention.
- the switching loss of the inverter is reduced by reducing the carrier frequency while maintaining the response characteristic of the current control system at a predetermined value.
- a current control response setting unit 20 is further provided in addition to the configuration of the first embodiment shown in FIG. 1, and a carrier frequency map 11f and a current control response command correction signal setting are set in the carrier frequency setting unit 11.
- a portion 11g is provided.
- it is the same as that of the structure of FIG. 1, or those components are shown with the same code
- the current control response setting unit 20 sets and outputs an appropriate current control response command 21 according to the operation status of the entire control device.
- the current control response command 21 is input to the carrier frequency setting unit 11 and used for setting the carrier frequency.
- the current control response command 21 is also used as a current control response command for controlling the current control unit 4.
- the current control response command 21 itself is not input to the current control unit 4, but the corrected current control response command 22 corrected according to the carrier frequency command 12 is input to the current control unit 4. It has become.
- a carrier frequency map 11f is a one-dimensional map (second one-dimensional map), for example, a carrier frequency map (C1) in which two types of carrier frequencies fc1 and fc2 (fc1 ⁇ fc2) are described. ).
- a carrier frequency map (C1) in which two types of carrier frequencies fc1 and fc2 (fc1 ⁇ fc2) are described.
- the carrier frequency map (A) and the carrier frequency map (B) when referring to the carrier frequency map itself held in the carrier frequency map 11f, it is described as the carrier frequency map (C).
- the carrier frequency fc2 is set to a carrier frequency that satisfies the original current control response command 21, a predetermined current control response characteristic can be obtained when the current command change rate is high.
- the current command change rate is low, it can be determined that a predetermined current control response characteristic is not required.
- the switching loss of the inverter 8 can be reduced by using the low carrier frequency fc1.
- the current control response command correction signal setting unit 11g that outputs the current control response command correction signal 11h according to the carrier frequency command 12 that is the output of the carrier frequency map 11c is used, and the original current control is performed.
- the current control response command correction signal 11h is subtracted from the response command 21 and output to the current control unit 4 so that an excessive current control response command is not generated when the low carrier frequency fc1 is selected. .
- the switching loss of the inverter is reduced by reducing the carrier frequency while maintaining the response characteristic of the current control system at a predetermined value.
- the current command generator 1 includes a position control system and a speed control system. In this case, if the response characteristics of the current control system that is the lower loop can maintain a predetermined value, the design of the position control system and the speed control system that are the upper loop is facilitated.
- FIG. FIG. 8 is a diagram illustrating the configuration of the control device for the power converter according to the fourth embodiment of the present invention.
- the method of setting the carrier frequency using the basic frequency information based on the current command information has been described.
- the method of setting the carrier frequency using the current control response command information together with the current command information as a basis has been described.
- These basic frequency information and current control response command information can of course be used in combination. Therefore, in the present embodiment, a control system that further uses basic frequency information and current control response command information is configured based on current command information.
- a control system capable of selecting three types of carrier frequencies fc1, fc2, and fc3 (fc1 ⁇ fc2 ⁇ fc3) is configured as an example, and is the same as or equivalent to the configuration illustrated in FIGS. The components are shown with the same reference numerals.
- the carrier frequency setting unit 11 is provided with three carrier frequency maps D (for fc1 setting, fc2 setting, and fc3 setting).
- the carrier frequency map 11i includes a frequency signal 19 represented as a fundamental frequency on one of the orthogonal axes (vertical axis in the example of FIG. 8) and a current control represented on the other of the orthogonal axes (horizontal axis in the example of FIG. 8). It is the two-dimensional map (2nd two-dimensional map) which mapped the response frequency 22 and the carrier frequency information according to.
- the carrier frequency map 11i the frequency signal 19 and the current control response command 21 are input, the carrier frequency map D is referred to, and carrier frequency values assigned to fc1 to fc3 of the carrier frequency map 11c (that is, the carrier frequency map (A)). Is determined.
- the operation of each other block is the same as or equivalent to the operation described in the second and third embodiments, and detailed description thereof is omitted.
- the stability of the current control system is ensured while the response characteristic of the current control system is maintained at a predetermined value, and the carrier frequency is appropriately reduced. Is possible.
- FIG. FIG. 9 is a figure which shows the structure of the control apparatus of the power converter concerning Embodiment 5 of this invention.
- Embodiment 1 shown in FIG. 1 it is necessary to set a carrier frequency map (A) in advance in the carrier frequency map 11 c of the carrier frequency setting unit 11.
- a method for automatically setting and adjusting the carrier frequency map (A) will be described.
- the carrier frequency setting unit 11 shown in FIG. 9 is further provided with a locus recording map 11j and a locus information analysis unit 11k.
- FIG. 10 is a diagram illustrating an example of a trajectory record map
- FIG. 11 is a diagram illustrating an example of a carrier frequency map generated by adjusting the trajectory record map
- FIG. 12 is a diagram for explaining the operation of the locus record map using the current command and the current command change rate.
- the trajectory record map 11j includes a current command represented on one of the orthogonal axes (vertical axis in the example of FIG. 10), a current command change rate represented on the other of the orthogonal axes (horizontal axis in the example of FIG. 10), 2 is a two-dimensional map in which the transition of the trajectory representing the relationship and the number of passages (synonymous with dwell time) of the trajectory in a predetermined region are recorded (mapped).
- the predetermined region here is an area determined by a predetermined width on one side of the orthogonal axis and a predetermined width on the other side as surrounded by a broken line portion in FIG.
- the transition of the trajectory in the trajectory record map is as shown in FIG. It becomes.
- the trajectory recording map 11j counts the number of times (corresponding to the residence time) that has passed through the region (region surrounded by the broken line) on the trajectory recording map every predetermined period ⁇ t after the start of current control.
- the locus record map generated at this time is as shown in FIG.
- the number of passes through the region R1 where both the current command and the current command change rate are small is 3, and the number of passes through the region R2 where the current command is low and the current command change rate is high is 2.
- the number of passes through the region R4 where the current command is large and the current command change rate is small is 11. This count value is obtained by counting the locations (circles) corresponding to the respective areas shown in FIG.
- the region is a region suitable for carrier frequency adjustment.
- a region R4 illustrated in FIG. 10B is a region suitable for carrier frequency adjustment.
- the trajectory information analysis unit 11k extracts the aforementioned count value from the trajectory record map 11j, and changes the carrier frequency information of the carrier frequency map (A) provided in the carrier frequency map 11c according to the count value.
- FIG. 11A is a carrier frequency map (A) before adjustment (before change), and is set to a predetermined carrier frequency (5 [kHz] in the example in the figure) in all regions. Yes.
- a predetermined carrier frequency (example in the figure) that is smaller than the carrier frequency before adjustment. Then, it is changed to 4 [kHz].
- the carrier frequency setting the carrier frequency may be reset by resetting the carrier frequency once set in a predetermined period longer than ⁇ t and calculating the count value again. By doing so, it is possible to set an appropriate carrier frequency that flexibly corresponds to the operating condition of the load.
- the carrier frequency map reflecting the actual operation can be set, and the carrier frequency map once set is automatically set. Therefore, the labor required for setting and adjusting the carrier frequency map can be reduced. For example, when performing the current control, the locus of the current command and the current command change rate is recorded, and the region where the current command is large and the current command change rate is small is extracted for a long time, Adjustment to lower the carrier frequency can be performed automatically.
- the adjustment method for reducing the carrier frequency in the region where the current command is large and the current command change rate is small is shown, but the present invention is not limited to this adjustment method. On the contrary, an adjustment for increasing the carrier frequency may be performed for a region requiring a current control response.
- the configuration for automatically adjusting the carrier frequency map (A) is shown in the embodiment in which the configuration is applied to the carrier frequency setting unit of the first embodiment.
- the configuration may be applied to the carrier frequency setting unit shown in FIG.
- control device for a power converter according to the present invention is useful as an invention that enables stable carrier frequency change and can achieve both current control response and inverter loss suppression. is there.
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Abstract
Description
2 電流指令
3 検出電流信号
4 電流制御部
5 電圧指令
6 スイッチングパターン演算部
7 スイッチングパターン指令
8 電力変換器(インバータ)
9 電流検出器
10 負荷
11 キャリア周波数設定部
11a 電流指令変化率演算部
11b 電流指令変化率
11c キャリア周波数マップ(A)
11d キャリア周波数マップ(B)
11e キャリア周波数更新信号
11f キャリア周波数マップ(C)
11g 電流制御応答指令補正信号設定部
11h 電流制御応答指令補正信号
11i キャリア周波数マップ(D)
11j 軌跡記録マップ
11k 軌跡情報解析部
12 キャリア周波数指令
13 座標変換部(回転座標から静止座標への変換)
14 電圧指令(交流)
15 座標変換部(静止座標から回転座標への変換)
16 検出電流信号(座標変換後)
17 位相・周波数発生部
18 位相信号
19 周波数信号
20 電流制御応答設定部
21 電流制御応答指令
22 電流制御応答指令(補正後)
112 変化率演算フィルタ
113 絶対値演算部
115 ローパスフィルタ(LPF)
(制御装置の構成)
まず、実施の形態1にかかる電力変換器の制御装置の構成、すなわち電力変換器を制御するための実施の形態1にかかる制御装置の構成について説明する。図1は、本発明の実施の形態1にかかる電力変換器の制御装置の構成を示す図である。なお、同図では、説明のため、インバータならびに、インバータに接続される負荷および電流検出器を併記している。
つぎに、実施の形態1にかかる制御装置の動作について、図1の図面を参照して説明する。電流指令発生部1による電流指令2は、電流制御部4に入力される。また、電流制御部4には、検出電流信号3も入力され、電流制御部4は、所望の電流を負荷10に流すための電圧指令5を生成してスイッチングパターン演算部6に出力する。スイッチングパターン演算部6は、入力された電圧指令5からパルス幅変調(PWM)を行いスイッチングパターン指令7を生成してインバータ8に出力する。なお、本項で説明するスイッチングパターン指令7は、電圧指令とキャリア波との大小比較によってパターン生成を行う非同期PWM方式を用いるものとする。インバータ8は、複数の半導体スイッチング素子で構成され、スイッチングパターン指令7に従って動作し、所望の電流を負荷10に供給する。電流検出器9は、インバータ8から負荷10に供給される電流を検出するとともに、検出した電流を電流制御部4にフィードバックする。キャリア周波数設定部11は、電流指令2に基づき生成したキャリア周波数指令12をスイッチングパターン演算部6に出力する。
つぎに、キャリア周波数設定部11の動作について図1~図3の各図面を参照して説明する。なお、図2は、電流指令変化率演算部11aの一例および当該一例とする構成部の出力特性を示す図であり、図3は、電流指令変化率演算部11aの図2とは異なる一例および当該一例とする構成部の出力特性を示す図である。
なお、上式における「T」は帯域を決定するパラメータであり、「s」はラプラス変数である。
つぎにキャリア周波数マップについて図4および図5を用いて説明する。ここで、図4は、キャリア周波数マップの持つ意味を電流指令変化率の軌跡との関係を用いて説明する図であり、図5は、キャリア周波数マップの図4とは異なる例を示す図である。
図6は、本発明の実施の形態2にかかる電力変換器の制御装置の構成を示す図である。特に、本実施の形態では、本実施の形態の効果をよりよく説明するため、負荷10は、例えば交流モータなどの交流負荷を想定する。また、負荷10を交流負荷としているため、本実施の形態では、図1に示す実施の形態1の構成において、さらに座標変換部13,15を設けるようにしている。その他、位相・周波数発生部17を設けている点、およびキャリア周波数設定部11にキャリア周波数マップ11dを設けている点についても実施の形態1との相違点である。なお、その他の構成については、図1の構成と同一または同等であり、それらの構成部には同一の符号を付して示している。
つぎに、実施の形態2にかかるキャリア周波数設定部11の動作について図6を参照して説明する。実施の形態2にかかる制御装置では、図1に示す実施の形態1とは異なり、キャリア周波数設定部11に周波数信号19が入力される構成となっている。一般的に、交流負荷に電力を供給する場合、キャリア周波数は基本周波数より十分高く設定する必要があることが知られている。もし、十分なキャリア周波数が得られない場合、電流制御系が不安定化したり、交流負荷に余分な高周波電流が流れ交流負荷の損失やインバータの損失が増加したりするといった問題が発生する。このため、キャリア周波数を設定する際に、基本周波数の情報を反映させることが好ましい構成となる。
図7は、本発明の実施の形態3にかかる電力変換器の制御装置の構成を示す図である。本実施の形態は、電流制御系の応答特性を所定値に保持しつつ、キャリア周波数を低減することでインバータのスイッチング損失を削減する実施の形態を示すものである。
つぎに、実施の形態3にかかるキャリア周波数設定部11の動作について、図7を参照して説明する。図7において、キャリア周波数マップ11fは、一次元のマップ(第2の一次元のマップ)であり、例えばfc1,fc2(fc1<fc2)の2種類のキャリア周波数が記載されたキャリア周波数マップ(C)を保持している。なお、キャリア周波数マップ(A)およびキャリア周波数マップ(B)のときと同様に、キャリア周波数マップ11fに保持されたキャリア周波数マップ自身に言及する場合には、キャリア周波数マップ(C)として記述する。
図8は、本発明の実施の形態4にかかる電力変換器の制御装置の構成を示す図である。図6に示す実施の形態2では、電流指令情報を基本として、基本周波数情報を用いてキャリア周波数を設定する手法について説明した。また、図7に示す実施の形態3では、電流指令情報を基本として、電流制御応答指令情報を併せて用いてキャリア周波数を設定する手法について説明した。これらの基本周波数情報および電流制御応答指令情報は、無論併用して用いることも可能である。そこで、本実施の形態では、電流指令情報を基本として、基本周波数情報および電流制御応答指令情報をさらに用いる制御系を構成している。なお、図8では、3種類のキャリア周波数fc1,fc2,fc3(fc1<fc2<fc3)が選択できる制御系を一例として構成しており、図6および図7に示す構成と同一または同等である構成部には同一の符号を付して示している。
図9は、本発明の実施の形態5にかかる電力変換器の制御装置の構成を示す図である。図1に示す実施の形態1では、キャリア周波数設定部11のキャリア周波数マップ11cに、予めキャリア周波数マップ(A)を設定する必要がある。実施の形態5では、このキャリア周波数マップ(A)を自動的に設定・調整する手法について説明する。図9に示すキャリア周波数設定部11では、図1に示す実施の形態1の構成に加えて、さらに軌跡記録マップ11jおよび軌跡情報解析部11kを設けるようにしている。なお、その他の構成については、図1の構成と同一または同等であり、それらの構成部には同一の符号を付して示している。
Claims (5)
- 複数の半導体スイッチング素子で構成されたインバータを具備する電力変換器に適用され、パルス幅変調を用いて前記インバータのスイッチング素子を制御する電力変換器の制御装置において、
電流指令を発生する電流指令発生部と、
前記電流指令に基づいて前記インバータに接続される負荷に所望の電流を流すための電圧指令を生成する電流制御器と、
前記電流指令および前記電流指令の変化率に応じて前記インバータのパルス幅変調に用いるキャリア周波数指令を設定するキャリア周波数設定部と、
前記電圧指令および前記キャリア周波数指令に基づいて前記パルス幅変調を行いスイッチングパターン指令を演算するスイッチングパターン演算部と、
を備え、
前記キャリア周波数設定部は、直交軸の一方に表される前記電流指令と直交軸の他方に表される前記電流指令の変化率とに応ずるキャリア周波数の情報をマッピングした第1の二次元マップを有し、入力された電流指令および当該入力された電流指令の変化率に対応する前記第1の二次元マップ上のキャリア周波数の情報を前記スイッチングパターン演算部に出力する
ことを特徴とする電力変換器の制御装置。 - 請求項1に記載のキャリア周波数設定部は、前記インバータの出力電力の周波数に応ずるキャリア周波数の情報をマッピングした第1の一次元マップを有し、前期第1の一次元マップから出力されるキャリア周波数情報を用いて前記第1の二次元マップから出力されるキャリア周波数の値を調整することを特徴とする請求項1に記載の電力変換器の制御装置。
- 請求項1に記載のキャリア周波数設定部は、
電流制御応答指令に応ずるキャリア周波数の情報をマッピングした第2の一次元マップと、
前記第1の二次元マップから出力されるキャリア周波数指令に対応する電流制御応答指令補正信号に基づいて前記電流制御応答指令を補正するための電流制御応答指令補正信号を設定する電流制御応答指令補正信号設定部と、
を有し、
前記キャリア周波数設定部は、前記第2の一次元マップから出力されるキャリア周波数の情報を用いて前記第1の二次元マップから出力されるキャリア周波数の値を調整するとともに、前記電流制御応答指令補正信号を前記電流制御部に出力し、
前記電流制御部は、前記電流制御応答指令補正信号を用いて補正された電流制御応答指令に従って電流制御動作を行う
ことを特徴とする請求項1に記載の電力変換器の制御装置。 - 請求項1に記載のキャリア周波数設定部は、
直交軸の一方に表される電流制御応答指令と直交軸の他方に表される前記インバータの出力電力の周波数とに応ずるキャリア周波数の情報をマッピングした第2の二次元マップと、
前記第1の二次元マップから出力されるキャリア周波数指令に対応する電流制御応答指令補正信号に基づいて前記電流制御応答指令を補正するための電流制御応答指令補正信号を設定する電流制御応答指令補正信号設定部と、
を有し、
前記キャリア周波数設定部は、前記第2の二次元マップから出力されるキャリア周波数の情報を用いて前記第1の二次元マップから出力されるキャリア周波数の値を調整するとともに、前記電流制御応答指令補正信号を前記電流制御部に出力し、
前記電流制御部は、前記電流制御応答指令補正信号を用いて補正された電流制御応答指令に従って電流制御動作を行う
ことを特徴とする請求項1に記載の電力変換器の制御装置。 - 請求項1~4に記載のキャリア周波数設定部は、
直交軸の一方に表される前記電流指令と直交軸の他方に表される前記電流指令の変化率との関係を表す軌跡を記録し、かつ、直交軸の前記一方における所定幅と前記他方における所定幅とによって決定される各領域内を前記軌跡が通過した回数をカウントし、当該カウントされたカウント値を記録した軌跡記録マップと、
前記軌跡記録マップから抽出されたカウント値に応じて前記第1の二次元マップにおけるキャリア周波数情報を変更する軌跡情報解析部と、
を備えたことを特徴とする請求項1~4のいずれか1項に記載の電力変換器の制御装置。
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US12/811,742 US8537580B2 (en) | 2008-01-18 | 2008-01-18 | Controller of power converter |
PCT/JP2008/050638 WO2009090755A1 (ja) | 2008-01-18 | 2008-01-18 | 電力変換器の制御装置 |
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- 2008-01-18 US US12/811,742 patent/US8537580B2/en not_active Expired - Fee Related
- 2008-01-18 JP JP2009549945A patent/JP5188511B2/ja not_active Expired - Fee Related
- 2008-01-18 CN CN2008801249885A patent/CN101919151B/zh not_active Expired - Fee Related
- 2008-01-18 EP EP08703488.0A patent/EP2237401B1/en not_active Not-in-force
- 2008-07-22 TW TW097127750A patent/TW200934072A/zh not_active IP Right Cessation
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Cited By (11)
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JP2012235619A (ja) * | 2011-05-02 | 2012-11-29 | Toyota Motor Corp | 回転電機の制御装置 |
WO2015059784A1 (ja) * | 2013-10-23 | 2015-04-30 | 三菱電機株式会社 | モータ制御装置およびモータ制御方法 |
JP6037364B2 (ja) * | 2013-10-23 | 2016-12-07 | 三菱電機株式会社 | モータ制御装置およびモータ制御方法 |
US10116241B2 (en) | 2013-10-23 | 2018-10-30 | Mitsubishi Electric Corporation | Motor control device and motor control method |
WO2017183243A1 (ja) * | 2016-04-22 | 2017-10-26 | 株式会社オートネットワーク技術研究所 | 電源装置 |
JPWO2017183243A1 (ja) * | 2016-04-22 | 2018-08-16 | 株式会社オートネットワーク技術研究所 | 電源装置 |
US10326368B2 (en) | 2016-04-22 | 2019-06-18 | Autonetworks Technologies, Ltd. | Power supply device |
JP2021182832A (ja) * | 2020-05-20 | 2021-11-25 | 三菱電機株式会社 | 回転機駆動制御装置 |
JP7109500B2 (ja) | 2020-05-20 | 2022-07-29 | 三菱電機株式会社 | 回転機駆動制御装置 |
CN112630821A (zh) * | 2020-12-30 | 2021-04-09 | 核工业北京地质研究院 | 一种应用于地震数据采集的变频控制装置及其控制方法 |
CN112630821B (zh) * | 2020-12-30 | 2024-01-12 | 核工业北京地质研究院 | 一种应用于地震数据采集的变频控制装置及其控制方法 |
Also Published As
Publication number | Publication date |
---|---|
TWI371155B (ja) | 2012-08-21 |
CN101919151A (zh) | 2010-12-15 |
US20100277149A1 (en) | 2010-11-04 |
JPWO2009090755A1 (ja) | 2011-05-26 |
JP5188511B2 (ja) | 2013-04-24 |
TW200934072A (en) | 2009-08-01 |
EP2237401A1 (en) | 2010-10-06 |
EP2237401A4 (en) | 2013-06-19 |
CN101919151B (zh) | 2013-04-17 |
EP2237401B1 (en) | 2014-09-10 |
US8537580B2 (en) | 2013-09-17 |
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