US10326205B2 - Multi-layered software defined antenna and method of manufacture - Google Patents

Multi-layered software defined antenna and method of manufacture Download PDF

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Publication number
US10326205B2
US10326205B2 US15/654,643 US201715654643A US10326205B2 US 10326205 B2 US10326205 B2 US 10326205B2 US 201715654643 A US201715654643 A US 201715654643A US 10326205 B2 US10326205 B2 US 10326205B2
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antenna
patch
conductive
delay line
feed
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US15/654,643
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US20180062266A1 (en
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Dedi David HAZIZA
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Sderotech Inc
Wafer LLC
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Wafer LLC
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Priority to US15/654,643 priority Critical patent/US10326205B2/en
Priority to EP17847175.1A priority patent/EP3507856B1/en
Priority to CN201780061159.6A priority patent/CN109937511B/zh
Priority to JP2019511937A priority patent/JP2019537850A/ja
Priority to KR1020197007515A priority patent/KR102479625B1/ko
Priority to PCT/US2017/045186 priority patent/WO2018044488A1/en
Priority to TW106126192A priority patent/TWI691116B/zh
Priority to CN201780020915.0A priority patent/CN109075443B/zh
Priority to KR1020187028100A priority patent/KR102072934B1/ko
Priority to PCT/US2017/049962 priority patent/WO2018045350A1/en
Priority to EP17847661.0A priority patent/EP3507864B1/en
Priority to JP2018548180A priority patent/JP6591088B2/ja
Priority to KR1020197018418A priority patent/KR102364013B1/ko
Priority to JP2019531126A priority patent/JP7061810B2/ja
Priority to EP17877580.5A priority patent/EP3552217A4/en
Priority to CN201780082269.0A priority patent/CN110140184A/zh
Priority to PCT/US2017/063539 priority patent/WO2018106485A1/en
Assigned to WAFER LLC reassignment WAFER LLC ASSIGNMENT OF ASSIGNORS INTEREST (SEE DOCUMENT FOR DETAILS). Assignors: HAZIZA, DEDI DAVID
Priority to US15/885,680 priority patent/US10320070B2/en
Priority to EP18836169.5A priority patent/EP3656020B1/en
Priority to CA3070353A priority patent/CA3070353A1/en
Priority to KR1020207004088A priority patent/KR20200090142A/ko
Priority to JP2020502472A priority patent/JP7002630B2/ja
Priority to PCT/US2018/016872 priority patent/WO2019018005A1/en
Priority to KR1020237003522A priority patent/KR20230028805A/ko
Priority to CN201880057552.2A priority patent/CN111095676B/zh
Priority to TW107104565A priority patent/TWI672859B/zh
Publication of US20180062266A1 publication Critical patent/US20180062266A1/en
Priority to IL261863A priority patent/IL261863B/en
Priority to IL265113A priority patent/IL265113B2/en
Priority to IL266906A priority patent/IL266906B2/en
Priority to US16/436,807 priority patent/US10505273B2/en
Priority to US16/438,303 priority patent/US10505280B2/en
Application granted granted Critical
Publication of US10326205B2 publication Critical patent/US10326205B2/en
Priority to JP2019168502A priority patent/JP7045080B2/ja
Priority to US16/708,354 priority patent/US10741921B2/en
Assigned to WAFER LLC, SDEROTECH, INC. reassignment WAFER LLC ASSIGNMENT OF ASSIGNORS INTEREST (SEE DOCUMENT FOR DETAILS). Assignors: WAFER LLC
Priority to JP2022096587A priority patent/JP7442850B2/ja
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    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q9/00—Electrically-short antennas having dimensions not more than twice the operating wavelength and consisting of conductive active radiating elements
    • H01Q9/04—Resonant antennas
    • H01Q9/0407—Substantially flat resonant element parallel to ground plane, e.g. patch antenna
    • H01Q9/045—Substantially flat resonant element parallel to ground plane, e.g. patch antenna with particular feeding means
    • H01Q9/0457—Substantially flat resonant element parallel to ground plane, e.g. patch antenna with particular feeding means electromagnetically coupled to the feed line
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01L—SEMICONDUCTOR DEVICES NOT COVERED BY CLASS H10
    • H01L23/00—Details of semiconductor or other solid state devices
    • H01L23/58—Structural electrical arrangements for semiconductor devices not otherwise provided for, e.g. in combination with batteries
    • H01L23/64—Impedance arrangements
    • H01L23/66—High-frequency adaptations
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q1/00—Details of, or arrangements associated with, antennas
    • H01Q1/48—Earthing means; Earth screens; Counterpoises
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q1/00—Details of, or arrangements associated with, antennas
    • H01Q1/50—Structural association of antennas with earthing switches, lead-in devices or lightning protectors
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q21/00—Antenna arrays or systems
    • H01Q21/0087—Apparatus or processes specially adapted for manufacturing antenna arrays
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q21/00—Antenna arrays or systems
    • H01Q21/06—Arrays of individually energised antenna units similarly polarised and spaced apart
    • H01Q21/061—Two dimensional planar arrays
    • H01Q21/065—Patch antenna array
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q21/00—Antenna arrays or systems
    • H01Q21/24—Combinations of antenna units polarised in different directions for transmitting or receiving circularly and elliptically polarised waves or waves linearly polarised in any direction
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q21/00—Antenna arrays or systems
    • H01Q21/24—Combinations of antenna units polarised in different directions for transmitting or receiving circularly and elliptically polarised waves or waves linearly polarised in any direction
    • H01Q21/245—Combinations of antenna units polarised in different directions for transmitting or receiving circularly and elliptically polarised waves or waves linearly polarised in any direction provided with means for varying the polarisation 
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q21/00—Antenna arrays or systems
    • H01Q21/28—Combinations of substantially independent non-interacting antenna units or systems
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q3/00—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system
    • H01Q3/24—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system varying the orientation by switching energy from one active radiating element to another, e.g. for beam switching
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q3/00—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system
    • H01Q3/26—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system varying the relative phase or relative amplitude of energisation between two or more active radiating elements; varying the distribution of energy across a radiating aperture
    • H01Q3/30—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system varying the relative phase or relative amplitude of energisation between two or more active radiating elements; varying the distribution of energy across a radiating aperture varying the relative phase between the radiating elements of an array
    • H01Q3/34—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system varying the relative phase or relative amplitude of energisation between two or more active radiating elements; varying the distribution of energy across a radiating aperture varying the relative phase between the radiating elements of an array by electrical means
    • H01Q3/36—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system varying the relative phase or relative amplitude of energisation between two or more active radiating elements; varying the distribution of energy across a radiating aperture varying the relative phase between the radiating elements of an array by electrical means with variable phase-shifters
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q3/00—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system
    • H01Q3/44—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system varying the electric or magnetic characteristics of reflecting, refracting, or diffracting devices associated with the radiating element
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q9/00—Electrically-short antennas having dimensions not more than twice the operating wavelength and consisting of conductive active radiating elements
    • H01Q9/04—Resonant antennas
    • H01Q9/0407—Substantially flat resonant element parallel to ground plane, e.g. patch antenna
    • H01Q9/0414—Substantially flat resonant element parallel to ground plane, e.g. patch antenna in a stacked or folded configuration
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q9/00—Electrically-short antennas having dimensions not more than twice the operating wavelength and consisting of conductive active radiating elements
    • H01Q9/04—Resonant antennas
    • H01Q9/0407—Substantially flat resonant element parallel to ground plane, e.g. patch antenna
    • H01Q9/0442—Substantially flat resonant element parallel to ground plane, e.g. patch antenna with particular tuning means
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q9/00—Electrically-short antennas having dimensions not more than twice the operating wavelength and consisting of conductive active radiating elements
    • H01Q9/04—Resonant antennas
    • H01Q9/06—Details
    • H01Q9/14—Length of element or elements adjustable
    • H01Q9/145—Length of element or elements adjustable by varying the electrical length
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B7/00—Radio transmission systems, i.e. using radiation field
    • H04B7/02—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas
    • H04B7/04—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas
    • H04B7/0413—MIMO systems
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B7/00—Radio transmission systems, i.e. using radiation field
    • H04B7/02—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas
    • H04B7/04—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas
    • H04B7/08—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the receiving station
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/18—Phase-modulated carrier systems, i.e. using phase-shift keying

Definitions

  • the disclosed invention relates to radio-transmission and/or reception antennas and methods for manufacturing such antennas and its associated feeding networks, be it microstrip, stripline or other.
  • the subject inventor has disclosed an antenna that utilizes variable dielectric constant to control the characteristics of the antenna, thereby forming a software defined antenna. Details about that antenna can be found in U.S. Pat. No. 7,466,269, the entire disclosure of which is incorporated herein by reference.
  • the antenna disclosed in the '269 patent proved to be operational and easy to manufactured by simply forming the radiating elements and feeding lines on top of an LCD screen. Therefore, further research has been done to further investigate different possibilities of fabricating software defined antennas, as disclosed herein.
  • Embodiments disclosed herein provide an improved antenna array and method for manufacturing such an antenna array.
  • Various disclosed embodiments provide an antenna having capacitively coupled feed line and other means to connect the feeding network to the radiating elements, such as vias and proximity coupling.
  • the antenna comprises an insulating substrate; a conductive patch provided on top surface of the insulating substrate; a ground plane provided on bottom surface of the insulating substrate, the ground plane comprising an aperture therein, the aperture being registered to be aligned below the conductive patch; a feed line having terminative end thereof registered to be aligned below the aperture, so as to capacitively transmit RF signal to the conductive patch through the aperture.
  • Other configurations are feasible as well and the following example is set to provide an optional solution and provide an insight on how to implement the system most effectively.
  • Embodiments of the invention provide a software defined antenna by using a variable dielectric to control a delay line, thereby generating a phase and/or frequency shift.
  • the phase shift may be used, e.g., for spatial orientation of the antenna or for polarization control.
  • Disclosed embodiments decouple the antenna and the corporate feed design so as to avoid signal interference between them.
  • Disclosed embodiments further decouple the RF and DC potentials.
  • the various elements of the antenna, such as the radiator, the corporate feed, the variable dielectric, the phase shift control lines, etc., are provided in different layers of a multi-layered antenna design, thus decoupling the design and avoiding cross-talk.
  • Various disclosed features include a novel arrangement for coupling the RF signal between the radiating element and the feed line; an arrangement for controlling frequency and phase of the signal; a multi-layered antenna; and methods of manufacturing the antenna.
  • FIG. 1 illustrates a top view of an antenna according to one embodiment
  • FIG. 2 illustrates a top view of an antenna according to another embodiment, wherein each radiating element can be fed by two orthogonal feed lines;
  • FIG. 3A illustrates a top view of a single radiating element
  • FIG. 3B illustrates a cross section of relevant sections of the antenna at the location of the radiating element of FIG. 3A , according to one embodiment
  • FIG. 4 illustrates a cross section of relevant sections of the antenna at the location of the radiating element according to another embodiment
  • FIG. 5 illustrates a cross section of relevant sections of the antenna at the location of the radiating element according to another embodiment designed to provide enhanced bandwidth
  • FIG. 6A illustrates a top view of a single radiating element
  • FIG. 6B illustrates a cross section of relevant sections of the antenna at the location of the radiating element of FIG. 6A , according to an embodiment having two delay lines connected to each patch, similar to what is shown in FIG. 2
  • FIGS. 6C and 6D describe embodiments that have the variable dielectric layer directly beneath the RF line and that the RF line is activated by an AC voltage through a BiasT, that is to provide a strong impact line as well as two layers for two different corporate feeding networks.
  • FIG. 6E illustrates a rectangular patch that can be used to operate in two different frequencies
  • FIG. 6F illustrates a standard Bias-T circuit.
  • FIG. 7 illustrates an embodiment wherein the DC potential for controlling the variable dielectric constant material is applied to the delay line itself, such that no electrodes are needed;
  • FIG. 8 illustrates an embodiment with two delay lines connected to a single patch, such that each delay line may carry a different polarization; while FIG. 8A illustrates a variation of the embodiment shown in FIG. 8 .
  • FIG. 9 illustrates an embodiment wherein the VDC plate includes only defined area of VDC material; while FIG. 9A illustrates a variation of the embodiment shown in FIG. 9 .
  • FIG. 10 illustrates an embodiment wherein no VDC plate is used.
  • FIG. 1 illustrates a top view of an antenna 100 , according to one embodiment.
  • the antenna is a multi-layer antenna that includes the patch layers, the true time delay layer, the slotted ground layer and the corporate feed layer, as will be described in more details below. In some instances, additional layers are added, providing multiple polarization, wider bandwidth, etc.
  • the various elements of the antenna may be printed or deposited on the insulating substrates.
  • the antenna in this particular example comprises a 4 ⁇ 4 array of radiators 110 , although any number of radiators in various geometries and arrangements may be used, and a square arrangement of 4 ⁇ 4 elements is chosen only as one example.
  • each radiator 110 is a conductive patch provided (e.g., deposited, adhered to, or printed) on top of an insulation layer 105 and has a delay feed line 115 coupled to it, either physically or capacitively, as will be explained further below.
  • Each delay feed line 115 is a conductor that provides the RF signal to its corresponding patch 110 .
  • the RF signal can be manipulated, e.g., delayed, change frequency, change phase, by controlling a variable dielectric layer positioned under the delay line. By controlling all of the delay lines, the array can be made to point to different directions, as needed, thus providing a scanning array.
  • each element is fed from only one feed line.
  • each radiating element 210 can be fed by two orthogonal feed lines, 215 and 217 , for example, each having different polarization.
  • the description provided herein is applicable to both and any similar, architectures.
  • FIG. 3A illustrates a top view of a single radiating element 310
  • FIG. 3B illustrates a cross section of relevant sections of the antenna at the location of the radiating element 310 of FIG. 3A
  • FIG. 8 provides a top “transparent” view that is applicable to all of the embodiments described herein, including the embodiment of FIGS. 3A and 3B . Thus, in studying any of the embodiments disclosed herein, the reader should also refer to FIG. 8 for a better understanding.
  • a top dielectric spacer 305 is generally in the form of a dielectric (insulating) plate or a dielectric sheet, and may be made of, e.g., glass, PET, etc.
  • the radiating patch 310 is formed over the spacer by, e.g., adhering a conductive film, sputtering, printing, etc.
  • a via is formed in the dielectric spacer 305 and is filled with conductive material, e.g., copper, to form contact 325 , which connects physically and electrically to radiating patch 310 .
  • a delay line 315 is formed on the bottom surface of dielectric spacer 305 (or on top surface of upper binder 342 ), and is connected physically and electrically to contact 325 .
  • the delay line 315 is a meandering conductive line and may take on any shape so as to have sufficient length to generate the desired delay, thereby causing the desired phase shift in the RF signal.
  • variable dielectric constant (VDC) plate 340 having variable dielectric constant material 344 .
  • VDC plate 340 is shown consisting of upper binder 342 , (e.g., glass PET, etc.) variable dielectric constant material 344 (e.g., twisted nematic liquid crystal layer), and bottom binder 346 .
  • binder layers 342 and 344 may be omitted.
  • adhesive such as epoxy or glass beads may be used instead of the binder layers 342 and/or 344 .
  • the VDC plate 340 when using twisted nematic liquid crystal layer, also includes an alignment layer that may be deposited and/or glued onto the bottom of spacer 305 , or be formed on the upper binder 342 .
  • the alignment layer may be a thin layer of material, such as polyimide-based PVA, that is being rubbed or cured with UV in order to align the molecules of the LC at the edges of confining substrates.
  • the effective dielectric constant of VDC plate 340 can be controlled by applying DC potential across the VDC plate 340 .
  • electrodes are formed and are connected to controllable voltage potential.
  • electrode 347 is shown connected to variable voltage potential 341
  • electrode 343 is connected to ground.
  • electrode 343 may also be connected to a variable potential 349 .
  • variable potential 341 and/or variable potential 349 by changing the output voltage of variable potential 341 and/or variable potential 349 , one can change the dielectric constant of the VDC material in the vicinity of the electrodes 343 and 347 , and thereby change the RF signal traveling over delay line 315 .
  • Changing the output voltage of variable potential 341 and/or variable potential 349 can be done using a controller, Ctl, running software that causes the controller to output the appropriate control signal to set the appropriate output voltage of variable potential 341 and/or variable potential 349 .
  • the antenna's performance and characteristics can be controlled using software—hence software controlled antenna.
  • ground refers to both the generally acceptable ground potential, i.e., earth potential, and also to a common or reference potential, which may be a set potential or a floating potential.
  • ground is used as shorthand to signify either an earth or a common potential, interchangeably.
  • common or reference potential which may be set or floating potential, is included therein.
  • reception and transmission are symmetrical, such that a description of one equally applies to the other. In this description it may be easier to explain transmission, but reception would be the same, just in the opposite direction.
  • a back plane conductive ground (or common) 355 is formed on the top surface of back plane insulator (or dielectric) 350 or the bottom surface of bottom binder 346 .
  • the back plane conductive ground 355 is generally a layer of conductor covering the entire area of the antenna array.
  • a window (DC break) 353 is provided in the back plane conductive ground 355 .
  • the RF signal travels from the feed patch 360 , via the window 353 , and is coupled to the delay line 315 .
  • a DC open and an RF short are formed between delay line 315 and feed patch 360 .
  • the back plane insulator 350 is made of a Rogers® (FR-4 printed circuit board) and the feed patch 360 may be a conductive line formed on the Rogers.
  • a PTFE Polytetrafluoroethylene or Teflon®
  • other low loss material may be used.
  • FIG. 8 illustrates an embodiment with two delay lines connected to a single patch 810 , such that each delay line may carry a different signal, e.g., at different polarization.
  • the following explanation is made with respect to one of the delay lines, as the other may have similar construction.
  • the radiating patch 810 is electrically DC connected to the delay line 815 by contact 825 (the delay line for the other feed is referenced as 817 ). So, in this embodiment the RF signal is transmitted from the delay line 815 to the radiating patch 810 directly via the contact 825 . However, no DC connection is made between the feed patch 860 and the delay line 815 ; rather, the RF signal is capacitively coupled between the feed patch 860 and the delay line 815 . This is done through an aperture in the ground plane 850 . As shown in FIG. 3B , the VDC plate 340 is positioned below the delay line 315 , but in FIG. 8 it is not shown, so as to simplify the drawing for better understanding of the RF short feature.
  • the back ground plane 850 is partially represented by the hatch marks, also showing the window (DC break) 853 .
  • the RF path is radiating patch 810 , to contact 825 , to delay line 815 , capacitively through window 850 to feed patch 860 .
  • the length of the window 853 should be set to about half the wavelength of the RF signal traveling in the feed patch 860 , i.e., ⁇ /2.
  • the width of the window, indicated as “W”, should be set to about a tenth of the wavelength, i.e., ⁇ /10.
  • the feed patch 860 extends about a quarter wave, ⁇ /4, beyond the edge of the window 853 , as indicated by D.
  • the terminus end (the end opposite contact 825 ) of delay line 815 extends a quarter wave, ⁇ /4, beyond the edge of the window 853 , as indicated by E. Note that distance D is shown longer than distance E, since the RF signal traveling in feed patch 860 has a longer wavelength than the signal traveling in delay line 815 .
  • every reference to wavelength, ⁇ indicates the wavelength traveling in the related medium, as the wavelength may change as it travels in the various media of the antenna according to its design and the DC potential applied to variable dielectric matter within the antenna.
  • FIG. 8A illustrates a variation wherein the RF signal path between the delay line and the radiating patch is capacitive, i.e., there's no physical conductive contact between them.
  • a coupling patch 810 ′ is fabricated nest to the radiating patch 810 .
  • the contact 825 forms physical conductive contact between the delay line 815 and coupling patch 810 ′.
  • the coupling of the RF signal between the radiating patch 810 and the coupling patch 810 ′ is capacitive across the short dielectric space S.
  • the space S may be simply air or filled with other dielectric material. While in FIG. 8A only delay line 815 is shown capacitively coupled to the radiating patch 810 , this is done for illustration only, and it should be appreciated that both delay lines 815 and 817 may be capacitively coupled to the radiating patch 810 .
  • FIG. 4 illustrates another embodiment having similar construction to that of FIG. 3B , except for the arrangement for applying DC potential to the variable dielectric constant material 444 .
  • the two electrodes 443 and 447 are provided side by side, rather than across the layer 444 .
  • the electrodes 443 and 447 can be formed on the top surface of bottom binder 446 . Otherwise the structure and operation of the antenna shown in FIG. 4 is similar to that shown in FIG. 3B .
  • FIG. 5 illustrates another example designed to provide enhanced bandwidth.
  • the general structure of the antenna of FIG. 5 can be according to any of the embodiments provided herein, except that another dielectric layer in the form of spacer 514 is provided over the radiating patch 510 .
  • a resonant path, 512 is formed on top of the spacer 514 .
  • Resonant patch 512 has the same shape as radiating patch 510 , except that it is larger, i.e., has larger width and larger length, if it is a rectangle, or larger sides if it is a square.
  • the RF signal is coupled between radiating patch 510 and resonant patch 512 capacitively across spacer 514 . This arrangement provides a larger bandwidth than using just radiating patch 510 .
  • FIGS. 6A and 6B illustrate an embodiment having two delay lines connected to each patch, similar to what is shown in FIG. 2 .
  • each delay line may transmit in different polarization.
  • a bottom dielectric 652 separates the two feed patches 660 and 662 , each coupling signal to a respective one of the delay lines 615 and 617 .
  • the two feed patches 660 and 662 are oriented orthogonally to each other.
  • the signal coupling is done capacitively through a window 653 in the conductive ground 655 , as illustrated in the previous examples.
  • FIG. 6B only one window 653 is illustrated, since the other window is provided in another plane not shown in this cross section. However, the arrangement of two windows can be seen in FIG. 8 .
  • FIG. 6C illustrates another example of two orthogonal feed lines.
  • one feed line is used for transmission while the other is used for reception. While this embodiment is illustrated in conjunction with radiating patch 610 and resonant patch 612 , this is not necessary and is used only for consistency of illustration with FIG. 6B .
  • feed patch 660 is provided on the bottom of back plane dielectric 650 and is coupled to a transmission line via connector 665 .
  • the signal from the transmission line 665 is coupled from feed patch 660 capacitively through the window 653 in conductive ground 655 to the radiating patch 610 .
  • a second conductive ground 655 ′ with window 653 ′ is provided on the bottom of bottom plane dielectric 652 .
  • a second bottom plane dielectric 652 ′ is provided below the second conductive ground 655 ′, and feed patch 662 is provided on the bottom of the second bottom plane dielectric 652 ′.
  • feed patch dielectric 662 is used for reception.
  • radiating patch 610 is square, so that the transmission and reception are performed at the same frequency, but may be at different polarization and/or phase.
  • the radiating patch 610 is rectangle (see FIG. 6E ), in which case the transmission and reception may be done at different frequencies, which may be at the same and different polarization and/or phase.
  • FIG. 6D illustrates another example where one feed patch is used for transmission and the other for reception.
  • the control of the VDC material is done by feeding the DC potential to the delay line 615 .
  • This can be done, e.g., using a modified Bias-T arrangement.
  • FIG. 6F illustrates a standard Bias-T circuit.
  • the RF+DC node corresponds to the delay line 615 .
  • the DC node corresponds to the output of the variable voltage potential 641 .
  • the RF node corresponds to feed patches 660 and 662 .
  • the RF node is coupled to the circuit via capacitor C.
  • the RF signal in the disclosed embodiments is already coupled to the delay line capacitively, such that capacitor C may be omitted.
  • inductor I into the DC side of the antenna, a modified Bias-T circuitry is created.
  • FIG. 6D Another variation illustrated in FIG. 6D , but which can be implemented in any of the other embodiments, is the elimination of the binder layers.
  • the VDC material is sandwiched between the spacer 605 and the back plane dielectric 650 with the conductive ground 655 .
  • glass beads shown in broken line
  • glass beads can be interspersed within VDC material 644 so as to maintain the proper separation between the spacer 605 and the back plane dielectric 650 with the conductive ground 655 .
  • glass beads can also be used when using the bider layers.
  • FIG. 7 illustrates an embodiment wherein the DC potential for controlling the variable dielectric constant material is applied to the delay line itself, such that no electrodes are needed.
  • a bias-t may be used to separate the RF and DC signals. That is, the two electrodes, e.g., electrodes 343 and 347 , are omitted. Instead, the output of variable voltage potential supplier 741 is DC connected directly to the delay line 715 , establishing a DC potential between delay line 715 and back plane conductive ground 755 .
  • delay line has two functions: it accepts the DC voltage potential to thereby change the dielectric constant of the VDC material 744 , and it capacitively couples RF signal to the feed patches 760 and 762 .
  • various antennas may be constructed having the common elements comprising: an insulating spacer; at least one radiating arrangement provided on the insulating spacer, wherein each radiating arrangement comprises a conductive patch provided on the top surface of the insulating spacer, a delay line provided on the bottom surface of the insulating spacer, and a contact made of conductive material and providing electrical DC connection between the conductive patch and the delay line via a window in the insulating spacer; a variable dielectric constant (VDC) plate; a back plane insulator; a back plane conductive ground provided over the top surface of the back plane insulator; and an RF coupling arrangement for each of the at least one radiating arrangement, the RF coupling arrangement comprising a window formed in the back plane conductive ground and a conductive RF feed patch provided over the bottom surface of the back plane insulator in an overlapping orientation to the window.
  • VDC variable dielectric constant
  • electrodes are provided in order to control the dielectric constant at selected areas of the VDC plate, while in others the delay line is used for this purpose.
  • the conductive patch is used to couple RF signal from the air, while in others it is used to couple RF energy to another, larger, patch which is used to couple RF signal from the air.
  • the size of the patch is configured according to the desired RF wavelength. The RF wavelength can also be used to optimize the RF coupling by properly sizing the window, the delay line, and the feed patch.
  • the VDC plate may be segmented into individual pixels of VDC material.
  • An LCD panel of a flat panel screen may be used for the VDC plate.
  • VDC pixels may be grouped according to the area coverage of the electrodes or the delay lines. In other embodiments the VDC material is provided only in areas controlled by the electrodes or delay line.
  • FIG. 9 illustrates an example wherein the VDC plate 940 includes only defined area of VDC material.
  • VDC area 942 is shown under delay line 915 and VDC area 944 is shown under delay line 917 .
  • Each of VDC areas may be one continuous area of VDC material or may be divided into pixels. For ease of production the entire area of VDC plate 940 may include pixels of VDC material.
  • FIG. 9A illustrates capacitive coupling of the delay line 915 to the radiating patch 910 through coupling patch 910 ′, similar to that shown in FIG. 8A , but otherwise it is the same as shown in FIG. 9 .
  • FIG. 10 illustrates an embodiment wherein no VDC plate is used.
  • the antenna comprises an insulating substrate 1080 and the conductive patch 1010 is provided on the top surface of the insulating substrate 1080 .
  • a ground plane 1055 provided on the bottom surface of the insulating substrate 1080 , the ground plane comprising an aperture 1053 therein. The aperture is registered to be aligned below the conductive patch 1010 .
  • a feed line 1060 has its terminative end thereof registered to be aligned below the aperture 1053 , so as to capacitively transmit RF signal to the conductive patch 1010 through the aperture 1053 .
  • a back plane dielectric is provided between the ground plane 1055 and the feed line 1060 .
  • a connector 1065 is used to transmit/receive RF signal to/from the feed line 1060 .
  • a multi-layer, software controlled antenna comprises a radiating patch over an insulator plate.
  • a delay line is provided on the bottom of the insulator plate and has one end thereof RF coupled to the radiating patch.
  • the electrical coupling may be by physical conductive contact or by proximity coupling without physical conductive connection therebetween.
  • a variable dielectric constant (VDC) plate is provided below the delay line.
  • a ground plane is provided on bottom of VDC plate, the ground plane comprising an aperture therein, the aperture being registered to be aligned below the radiating patch.
  • a feed line having terminative end thereof registered to be aligned below the aperture is provided below the ground plane, so as to capacitively transmit RF signal to the conductive patch through the aperture.
  • An electrical isolation is provided between the feed line and the ground plane.
  • a back plane dielectric plate may be provided between the feed line and the ground plane.
  • a second feed line is provided, which may coupled RF signal to the delay line through another aperture provided in the ground plane, or through a second, separate ground plane.
  • a resonant patch may be provided over the radiating patch, wherein in some embodiments an insulating spacer may be provided between the radiating patch and the resonant patch.
  • electrodes are provided in the VDC plate. The electrodes are coupled to variable voltage potential source, which may be connected to a controller. In other embodiments the VDC plate is controlled by applying DC potential to the delay line. Applying a DC potential to the delay line may be implemented using a modified Biat-T, wherein the feed line, ground plate, VDC plate, and delay line form the RF leg of the Bias-T circuitry. The DC leg may be coupled to the delay line through an intermediate inductor (see FIG. 6D ).

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US15/654,643 US10326205B2 (en) 2016-09-01 2017-07-19 Multi-layered software defined antenna and method of manufacture
EP17847175.1A EP3507856B1 (en) 2016-09-01 2017-08-02 Software controlled antenna
CN201780061159.6A CN109937511B (zh) 2016-09-01 2017-08-02 软件控制的天线
JP2019511937A JP2019537850A (ja) 2016-09-01 2017-08-02 ソフトウェア制御のアンテナ
KR1020197007515A KR102479625B1 (ko) 2016-09-01 2017-08-02 소프트웨어 제어된 안테나
PCT/US2017/045186 WO2018044488A1 (en) 2016-09-01 2017-08-02 Software controlled antenna
TW106126192A TWI691116B (zh) 2016-09-01 2017-08-03 以軟體控制的天線
KR1020187028100A KR102072934B1 (ko) 2016-09-01 2017-09-01 소프트웨어 제어 안테나를 제조하는 방법
CN201780020915.0A CN109075443B (zh) 2016-09-01 2017-09-01 制造软件控制的天线的方法
PCT/US2017/049962 WO2018045350A1 (en) 2016-09-01 2017-09-01 Method of manufacturing software controlled antenna
EP17847661.0A EP3507864B1 (en) 2016-09-01 2017-09-01 Method of manufacturing software controlled antenna
JP2018548180A JP6591088B2 (ja) 2016-09-01 2017-09-01 ソフトウェア制御アンテナの作製方法
KR1020197018418A KR102364013B1 (ko) 2016-12-07 2017-11-28 저손실 전기 전송 메커니즘과 이를 이용한 안테나
JP2019531126A JP7061810B2 (ja) 2016-12-07 2017-11-28 低損失電送機構及びそれを使用するアンテナ
EP17877580.5A EP3552217A4 (en) 2016-12-07 2017-11-28 LOW LOSS ELECTRICAL TRANSMISSION MECHANISM AND USER ANTENNA
CN201780082269.0A CN110140184A (zh) 2016-12-07 2017-11-28 低损耗电传输机构和使用其的天线
PCT/US2017/063539 WO2018106485A1 (en) 2016-12-07 2017-11-28 Low loss electrical transmission mechanism and antenna using same
US15/885,680 US10320070B2 (en) 2016-09-01 2018-01-31 Variable dielectric constant antenna having split ground electrode
EP18836169.5A EP3656020B1 (en) 2016-09-01 2018-02-05 Variable dielectric constant antenna having split ground electrode
CA3070353A CA3070353A1 (en) 2016-09-01 2018-02-05 Variable dielectric constant antenna having split ground electrode
KR1020207004088A KR20200090142A (ko) 2016-09-01 2018-02-05 분할된 접지 전극을 갖는 가변 유전 상수 안테나
JP2020502472A JP7002630B2 (ja) 2016-09-01 2018-02-05 スプリット型接地電極を有する可変誘電率アンテナ
PCT/US2018/016872 WO2019018005A1 (en) 2016-09-01 2018-02-05 VARIABLE DIELECTRIC CONSTANT ANTENNA HAVING DIVIDED MASS ELECTRODE
KR1020237003522A KR20230028805A (ko) 2016-09-01 2018-02-05 분할된 접지 전극을 갖는 가변 유전 상수 안테나
CN201880057552.2A CN111095676B (zh) 2016-09-01 2018-02-05 具有分体式接地电极的可变介电常数天线
TW107104565A TWI672859B (zh) 2016-09-01 2018-02-08 具有分離的接地電極的可變介電常數天線
IL261863A IL261863B (en) 2016-09-01 2018-09-20 A method for producing a software controlled antenna
IL265113A IL265113B2 (en) 2016-09-01 2019-02-28 Software controlled antenna
IL266906A IL266906B2 (en) 2016-12-07 2019-05-27 A low-loss electrical transmission mechanism and an antenna using it
US16/436,807 US10505273B2 (en) 2016-09-01 2019-06-10 Variable dielectric constant antenna having split ground electrode
US16/438,303 US10505280B2 (en) 2016-09-01 2019-06-11 Multi-layered software defined antenna and method of manufacture
JP2019168502A JP7045080B2 (ja) 2016-09-01 2019-09-17 ソフトウェア制御アンテナの作製方法
US16/708,354 US10741921B2 (en) 2016-09-01 2019-12-09 Multi-layered software defined antenna and method of manufacture
JP2022096587A JP7442850B2 (ja) 2016-09-01 2022-06-15 ソフトウェア制御のアンテナ

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US16/438,303 Active US10505280B2 (en) 2016-09-01 2019-06-11 Multi-layered software defined antenna and method of manufacture
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