CN111146948A - 耐辐射有源驱动同步电力转换器的磁峰值电流模式控制 - Google Patents
耐辐射有源驱动同步电力转换器的磁峰值电流模式控制 Download PDFInfo
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- H02M3/00—Conversion of dc power input into dc power output
- H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
- H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
- H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
- H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
- H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/33569—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements
- H02M3/33576—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements having at least one active switching element at the secondary side of an isolation transformer
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- H02M1/00—Details of apparatus for conversion
- H02M1/14—Arrangements for reducing ripples from dc input or output
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- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
- H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
- H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
- H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
- H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/33507—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of the output voltage or current, e.g. flyback converters
- H02M3/33515—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of the output voltage or current, e.g. flyback converters with digital control
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- H02M3/00—Conversion of dc power input into dc power output
- H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
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- H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
- H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
- H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/33507—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of the output voltage or current, e.g. flyback converters
- H02M3/33523—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of the output voltage or current, e.g. flyback converters with galvanic isolation between input and output of both the power stage and the feedback loop
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- H02M3/00—Conversion of dc power input into dc power output
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- H02M3/33592—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements having at least one active switching element at the secondary side of an isolation transformer having a synchronous rectifier circuit or a synchronous freewheeling circuit at the secondary side of an isolation transformer
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- H02M1/00—Details of apparatus for conversion
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Abstract
用于使用分立模拟部件为电力转换器提供峰值电流模式控制(PCMC)的系统和方法。可使用一对互补双极结型晶体管来设置电力转换器的最大占空比。PCMC可使用比较器来实现,该比较器将峰值输入电流与误差反馈信号进行比较,并且当峰值输入电流超过误差反馈信号时终止脉冲宽度调制(PWM)脉冲。磁信号变压器可用于建立次级侧偏置电压源以返回误差信号,并驱动同步栅极驱动的AC联接信号。可以通过反激变压器的输出绕组在主开关断开时使同步开关接通,并且可在主开关接通之前通过来自磁信号变压器的时钟脉冲的后沿使同步开关断开。
Description
技术领域
本公开总体涉及用于电力转换器的控制器。
背景技术
DC/DC转换器是一种将输入DC电压转换为不同输出DC电压的电源。这种转换器通常包括变压器,所述变压器经由电压源与负载之间的开关电路进行电联接。称为正向转换器的转换器包括至少一个主开关,该至少一个主开关连接在变压器的初级绕组与电压源之间,从而在开关接通和导通时向变压器的次级绕组提供正向电力传输。金属氧化物半导体场效应晶体管(MOSFET)装置通常用于一个或多个主开关。
电力转换器设计通常受到各种要求的限制,诸如效率、输入电压范围、输出电压、电力密度和占地面积。这些约束需要某些性能权衡。例如,实现较高的效率可需要更窄的输入电压范围。为了进一步提高效率,通常采用有源复位方案和同步整流。这些同步整流方案可以是有源控制或自驱动。
具有高水平电离辐射的环境带来特殊的设计挑战。单个带电粒子可使数千个电子自由,从而导致电子噪声和信号尖峰。在数字电路的情况下,这可导致不准确或难以理解的结果。在用于卫星、航天器、飞机、发电站等的部件的设计中,这可能是特别严重的问题。
发明内容
一种用于电力转换器的峰值电流模式控制(PCMC)控制器可概括为包括峰值电流检测器电路、磁隔离器电路和同步栅极驱动电路,其中:所述电力转换器包括具有初级绕组和次级绕组的主变压器,初级绕组能够电联接至输入电压节点并且电联接至主开关,次级绕组能够电联接至输出电压节点并且电联接至同步整流器开关;所述峰值电流检测器电路具有第一输入节点、第二输入节点和输出节点,其中第一输入节点可操作地联接至在操作中感测电力转换器的电流的电流传感器电路,第二输入节点可操作地联接至误差控制信号电路,输出节点提供能够至少部分地用于控制主开关的操作的峰值电流检测器输出信号,在操作中,峰值电流检测器电路将从电流传感器电路接收到的电流传感器信号与从误差控制信号电路接收的误差控制信号进行比较,并且响应于检测到电流传感器信号超过误差控制信号,改变峰值电流检测器输出信号的状态;所述磁隔离器电路包括隔离变压器,隔离变压器包括初级绕组和次级绕组,磁隔离器电路包括第一输入节点、第二输入节点、第一输出节点和第二输出节点,第一输入节点可操作地联接至误差控制信号电路,第二输入节点可操作地联接至时钟电路以从时钟电路接收时钟信号,第一输出节点电联接至峰值电流检测器电路的第二输入节点以向峰值电流检测器电路提供误差控制信号,第二输出节点电联接至隔离变压器的次级绕组;所述同步栅极驱动电路包括第一输入节点、第二输入节点和输出节点,第一输入节点可操作地联接至主变压器的次级绕组,第二输入节点可操作地联接至磁隔离器电路的第二输出节点,输出节点可操作地进行联接,以控制同步整流器开关的操作。
峰值电流检测器电路可包括比较器,以及同步栅极驱动电路可包括MOSFET驱动器。磁隔离器电路可包括为PCMC控制器的次级侧电路提供电压源的电路。PCMC控制器还可包括延时栅极驱动电路,其包括第一输入节点、第二输入节点和输出节点,第一输入节点可操作地联接至时钟电路,以从时钟电路接收时钟信号;第二输入节点可操作地联接至峰值电流检测器电路的输出节点;延时栅极驱动电路的输出节点可操作地进行联接,以至少部分地基于时钟信号和峰值电流检测器输出信号来控制主开关的操作,在操作中,所述延时栅极驱动电路可以使得在切换周期期间主开关仅在同步整流器开关断开之后接通。延时栅极驱动电路可包括电阻器-电容器(RC)电路。延时栅极驱动电路可包括MOSFET栅极驱动器。PCMC控制器还可包括预设最大占空比电路,其包括可操作地联接至时钟电路以从时钟电路接收时钟信号的输入节点,以及可操作地联接至延时栅极驱动电路的第二输入节点的输出节点,在操作中,预设最大占空比电路可以设置用于电力转换器的主开关的最大占空比。预设最大占空比电路可以包括第一互补双极结型晶体管和第二互补双极结型晶体管。磁隔离器电路可以包括可操作地联接至隔离变压器的初级绕组的磁隔离器电路开关,以及其中,磁隔离器电路的第二输入节点可以可操作地进行联接,以控制同步整流器开关的操作。同步栅极驱动电路可以操作成在每个周期使同步整流器开关在主开关断开之后接通,以及在后续周期期间使同步整流器开关在主开关接通之前断开。PCMC控制器还可包括所述电流传感器电路,其包括电流变送器,所述电流变送器在操作中感测电力转换器的电流。电流变送器可以包括变压器或电阻器。
电力转换器可概括为包括变压器、初级电路、次级电路以及峰值电流模式控制(PCMC)控制器,其中:变压器具有初级绕组和次级绕组,初级绕组能够电联接至输入电压节点,以及次级绕组能够电联接至输出电压节点;初级电路电联接至初级绕组,初级电路包括主开关;次级电路,电联接至次级绕组,初级电路包括同步整流器开关;峰值电流模式控制(PCMC)控制器包括峰值电流检测器电路、磁隔离器电路以及同步栅极驱动电路,其中,峰值电流检测器电路具有第一输入节点、第二输入节点和输出节点,其中第一输入节点可操作地联接至在操作中感测电力转换器的电流的电流传感器电路,第二输入节点可操作地联接至误差控制信号电路,输出节点提供能够至少部分地用于控制主开关的操作的峰值电流检测器输出信号,在操作中,峰值电流检测器电路将从电流传感器电路接收到的电流传感器信号与从误差控制信号电路接收的误差控制信号进行比较,并且响应于检测到电流传感器信号超过误差控制信号,改变峰值电流检测器输出信号的状态;磁隔离器电路包括隔离变压器,隔离变压器包括初级绕组和次级绕组,磁隔离器电路包括第一输入节点、第二输入节点、第一输出节点和第二输出节点,第一输入节点可操作地联接至误差控制信号电路,第二输入节点可操作地联接至时钟电路以从时钟电路接收时钟信号,第一输出节点电联接至峰值电流检测器电路的第二输入节点以向峰值电流检测器电路提供误差控制信号,第二输出节点电联接至隔离变压器的次级绕组;同步栅极驱动电路包括第一输入节点、第二输入节点和输出节点,第一输入节点可操作地联接至主变压器的次级绕组,第二输入节点可操作地联接至磁隔离器电路的第二输出节点,输出节点可操作地进行联接以控制同步整流器开关的操作。
峰值电流检测器电路可以包括比较器,以及同步栅极驱动电路可以包括MOSFET驱动器。磁隔离器电路可以包括为PCMC控制器的次级侧提供电压源的电路。电力转换器还可包括延时栅极驱动电路,其包括第一输入节点、第二输入节点和输出节点,第一输入节点可操作地联接至时钟电路,以从时钟电路接收时钟信号;第二输入节点可操作地联接至峰值电流检测器电路的输出节点;延时栅极驱动电路的输出节点可操作地进行联接,以至少部分地基于时钟信号和峰值电流检测器输出信号来控制主开关的操作,在操作中,延时栅极驱动电路可以使得在切换周期期间主开关仅在同步整流器开关断开之后接通。延时栅极驱动电路可以包括电阻器-电容器(RC)电路。电力转换器还可包括预设最大占空比电路,其包括可操作地联接至时钟电路以从时钟电路接收时钟信号的输入节点,以及可操作地联接至延时栅极驱动电路的第二输入节点的输出节点,在操作中,预设最大占空比电路可以设置用于电力转换器的主开关的最大占空比。预设最大占空比电路可包括第一互补双极结型晶体管和第二互补双极结型晶体管。磁隔离器电路可包括可操作地联接至隔离变压器的初级绕组的磁隔离器电路开关,以及其中,磁隔离器电路的第二输入节点可操作地进行联接,以控制同步整流器开关的操作。同步栅极驱动电路可以操作成在每个周期使同步整流器开关在主开关断开之后接通,以及在后续周期期间,可以使同步整流器开关在主开关接通之前断开。电力转换器还可包括所述电流传感器电路,其包括电流变送器,所述电流变送器在操作中感测电力转换器的电流。电流变送器可包括变压器或电阻器。
用于电力转换器的峰值电流模式控制(PCMC)控制器可概括为包括磁隔离器电路,其中:所述电力转换器包括具有初级绕组和次级绕组的主变压器,初级绕组能够电联接至输入电压节点并且电联接至主开关,次级绕组能够电联接至输出电压节点并且电联接至同步整流器开关;所述磁隔离器电路包括隔离变压器,隔离变压器包括电联接至初级侧电路的初级绕组和电联接至次级侧电路的次级绕组,磁隔离器电路包括这样的电路:所述电路在操作中向次级侧电路提供电压源,将来自次级侧电路的误差控制信号提供给初级侧电路,并提供能够由同步栅极驱动电路使用的输出信号以控制同步整流器开关的操作。
附图说明
在附图中,相同的附图标记表示相似的元件或动作。附图中元件的尺寸和相对位置不一定按比例绘制。例如,各种元件的形状和角度不一定按比例绘制,以及这些元件中的一些可被任意放大和定位,从而提高附图的易读性。另外,所绘制的元件的特定形状不一定旨在传达与特定元件的实际形状有关的任何信息,而是可能仅为了便于在附图中识别而被选择。
图1A至图1B是根据一个示出的实施方式的包括磁峰值电流控制模式(PCMC)控制器的电力转换器的示意性电路图。
图2是根据一个示出的非限制性实施方式的图1A至图1B的PCMC控制器的各种MOSFET驱动器(U2和U3)的真值表。
图3是示出根据一个示出的实施方式的在启动操作期间图1A至图1B的电力转换器的各种波形的曲线图。
图4是示出根据一个示出的非限制性实施方式的针对输入电压为16伏的误差控制信号、峰值电流信号、主开关栅极信号和同步整流器开关栅极信号的放大视图的曲线图。
图5是示出根据一个示出的实施方式的针对输入电压为42伏的误差控制信号、峰值电流信号、主开关栅极信号和同步整流器开关栅极信号的放大视图的曲线图。
图6是示出根据一个示出的非限制性实施方式的主开关栅极信号和同步整流器开关栅极信号的曲线图。
图7是示出根据一个示出的非限制性实施方式的针对输入电压为28伏的主开关栅极信号、时钟信号、用于延时栅极驱动电路的比较器的非反相输入信号、以及用于延时栅极驱动电路的反相输入信号的曲线图。
图8是示出根据一个示出的非限制性实施方式的峰值电流模式PWM终端电路的比较器的输出信号、误差控制信号、峰值电流信号和时钟信号的曲线图。
图9是示出根据一个示出的非限制性实施方式的同步整流器开关栅极信号、时钟信号、同步栅极驱动电路的比较器的反相输入信号、以及同步栅极驱动电路的比较器的非反相输入信号的曲线图。
具体实施方式
在以下描述中,阐述了某些具体细节,以便提供对所公开的各种实施方式的透彻理解。然而,相关领域的技术人员应认识到的是,可以在没有这些具体细节中的一个或多个的情况下或者在利用其他方法、部件、材料等的情况下来实践实施方式。在其他实例中,没有详细示出或描述与计算机系统、服务器计算机和/或通信网络相关联的公知结构,以避免不必要地模糊对实施方式的描述。
除非在上下文中另有要求,否则在整个说明书和所附权利要求中,词语“包含(comprising)”与“包括(including)”同义,并且是包含性的或开放式的(即,不排除另外的、未列举的要素或方法行为)。
在本说明书全文中,“一个实施方式”或“实施方式”的引用意为在至少一个实施方式中包括结合该实施方式描述的特定特征、结构或特性。因而,在本说明书全文中的各个地方出现的短语“在一个实施方式中”或“在实施方式中”不一定都指代相同的实施方式。另外,特定特征、结构或特性可在一个或多个实施方式中以任何合适的方式组合。
如在本说明书和所附权利要求中所使用的,除非在上下文中另有明确规定,否则单数形式“一”、“一个”和“该”包括复数指示物。还应注意的是,除非在上下文中另有明确规定,否则术语“或”通常以其包括“和/或”的含义使用。
本文提供的公开内容的标题和摘要仅是为了方便,并不解释实施方式的范围或含义。
本公开的一个或多个实施方式提供用于使用分立模拟部件的电力转换器的峰值电流模式控制(PCMC)电路。如下面参考附图进一步讨论的,本公开的一个或多个实施方式为多种应用(例如,空间应用)提供耐辐射、高效、超宽输入DC-DC转换器。在至少一些实施方式中,控制电路使得能够实现至少6:1输入范围比率的超宽输入范围转换器,并且提供例如90%或更高的效率。在至少一些实施方式中,提供脉冲宽度调制(PWM)控制器,其经由两个磁性部件(例如,反激式(flyback)变压器、多功能隔离器或隔离变压器)实施同步整流时序控制,且使用分立模拟部件来模拟锁存器峰值电流模式控制,这提供具有更高效率和更宽输入电压范围的同步反激式转换器。
图1A至图1B示出了根据本公开的示例性实施方式的、利用PCMC控制器102的电力转换器100的示意性电路图。在所示实施方式中,电力转换器100是利用同步整流的同步反激式转换器。然而,应理解的是,PCMC控制器102也可与其他类型的电力转换器一起使用。通常,电力转换器100包括PCMC控制器或控制电路102、电力训练电路104以及隔离开的次级控制或反馈电路106,次级控制或反馈电路在本文中也称为误差控制信号电路。首先,提供对电力转换器100的整体操作的讨论。然后,更详细地描述PCMC控制器102。
在采用同步整流器的开关电源电路中,通过电力晶体管来代替二极管,以获得较低的导通状态电压降。同步整流器通常使用n沟道MOSFET而非二极管,从而避免二极管的导通电压降,这可能对于低输出电压电源而言很重要。当二极管从阳极到阴极导通时,晶体管被偏置成导通,并且相反地,当二极管从阴极到阳极不导通时,晶体管截止以阻断电流。虽然MOSFET通常用于此目的,但双极晶体管和其他有源半导体开关也可能是合适的。
在图1A至图1B的示例性电力转换器100中,经由输入电感器L1提供输入电压VIN的DC电压输入V1通过初级开关M1或主开关M1连接至变压器T1的初级绕组L2。在输入电压VIN和参考节点(例如,地)之间提供输入电容器C2。在所示的实施方式中,开关M1是NMOS装置。内部初级侧电压源V2用于向电力转换器100的初级侧的各种部件提供电压VCCP。
变压器T1的次级绕组L3通过包括MOSFET整流装置或开关M4的同步整流器连接至输出端VOUT。整流装置M4包括体二极管。在主电源开关M1导通的情况下,输入电压VIN施加在初级绕组L2上。次级绕组L3的极性定向为响应于初级电压,且电流IoutLOAD通过连接至输出端VOUT的负载RLOAD,并通过MOSFET整流装置M4返回到次级绕组L3。输出滤波电容器C1使转换器100的输出分流。
整流装置M4的电导率由栅极驱动逻辑控制,该栅极驱动逻辑可是PCMC控制器102的部分,或者可以从PCMC控制器102接收信号,这将在下面进行进一步讨论。如图1A和图1B所示,PCMC控制器102可包括输出控制节点VGATE_MAIN和控制信号VGATE_SYNC,其中,输出控制节点VGATE_MAIN向主开关M1提供具有占空比D的PWM驱动信号,控制信号VGATE_SYNC向同步整流装置M4提供控制信号。
隔离开的次级控制或反馈电路106包括电流传感器电路108,其可操作成感测电力转换器100的负载电流IoutLOAD。次级控制电路106另外地或替代地包括电压传感器电路110,其可操作成感测电力转换器100的输出电压VOUT。电流传感器电路108和电压传感器电路110可分别经由误差放大器112和114向PCMC控制器102提供反馈信号VFB(或误差控制信号),如下面进一步讨论。电流传感器电路108和电压传感器电路110可以是可操作成分别感测电流和电压的任何合适的电路,并且可包括一个或多个变压器、一个或多个电阻器等。
PCMC控制器102包括延时栅极驱动电路116、预设最大占空比电路118、峰值电流模式PWM终端电路120(本文中也称为峰值电流模式检测器电路)、多功能磁隔离器电路122和同步栅极驱动电路124。下面提供对每个部件的讨论。
预设最大占空比电路118可操作成设置用于控制器102的最大允许占空比。预设最大占空比电路118包括互补双极结型晶体管(BJT)Q8和Q9、电阻器R24和R25以及电容器C16、C17和C18。来自时钟电路的固定时钟信号输入CLOCK(参见图7)通过一对BJT Q8和Q9进行补充,该固定时钟信号输入设置最大占空比Dmax。在应用中,固定时钟输入信号CLOCK具有低占空比d(例如,20%占空比)。在BJT Q8和Q9的各个集电极处的电力转换器100的最大可允许占空比Dmax是:Dmax=1-d。主开关M1的占空比D由延时栅极驱动电路116输出的VGATE_MAIN信号提供。
延时栅极驱动电路116包括主开关栅极驱动器U2,主开关栅极驱动器具有非反相输入NINV1、反相输入INV1和输出VGATE_MAIN。延时栅极驱动电路116还包括电阻器R33以及电容器C25,其中,电阻器R33联接至时钟信号CLOCK和主开关栅极驱动器U2的反相输入INV1,电容器C25联接在主开关栅极驱动器U2的反相输入INV1与地之间。延时栅极驱动电路116的电阻器R33和电容器C25包括电阻器-电容器(RC)电路,其调节时钟信号CLOCK进入主开关栅极驱动器U2的延时。对延时进行调整来改变主开关M1与同步整流器开关M4之间的停滞时间(dead time),以防止击穿。该延时设置成使得同步整流器开关M4在主开关M1接通之前断开。在图2的表200中示出了用于延时栅极驱动电路116的主开关驱动器U2的真值表。
峰值电流模式PWM终端电路120操作成调整栅极驱动器U2的占空比D。峰值电流模式PWM终端电路120包括峰值电流传感器电路121(例如,变压器、电阻器),其向比较器U1的非反相输入提供代表峰值电流Ipeak的电压信号V_IPEAK。峰值电流模式PWM终端电路120还包括电容器C7和齐纳二极管D9,电容器C7和齐纳二极管D9联接至比较器U1的反相输入。比较器U1的输出U1_OUT联接至BJT Q10的基极。BJT Q10的集电极与地联接,并且BJT Q10的发射极联接至Dmax节点,其中,Dmax节点联接至延时栅极驱动电路116的栅极驱动器U2的非反相输入NINV1。比较器U1的反相输入处的节点标记为V_FB_SLOPE_COMP。
在操作中,比较器U1感测电平移位的峰值输入电流,并通过接通BJT Q10来终止PWM信号。图2的表200是驱动器U2的真值表。当主开关M1导通时,经由峰值电流传感器电路121感测的电流的幅值增加。当感测到的电流达到电压V_FB_SLOPE_COMP时,栅极信号VGATE_MAIN终止于该周期。峰值电流受齐纳二极管D9处的电压限制。
多功能磁隔离器电路122可操作成执行多种功能,下面将进一步对这些功能进行讨论。多功能磁隔离器电路122包括隔离变压器T2,其具有联接至初级侧电路的初级侧绕组L4和联接至次级侧电路的次级侧绕组L5。多功能磁隔离器电路122包括BJT Q11、MOSFET开关M3、电阻器R7、R9、R28和R31、电容器C3、C5、C6、C19和C20、二极管D1、D6、D7、D8、D11以及齐纳二极管D5。
多功能磁隔离器电路122磁性地提供次级偏置电压源VCCS,经由隔离变压器T2将来自电力转换器100的次级侧电路的电压和/或电流误差信号VFB返回到初级侧电路,并将用于同步栅极驱动器U3的计时信号从电力转换器100的初级侧电路驱动到次级侧电路。
同步栅极驱动电路124操作成驱动同步整流器开关M4。同步栅极驱动电路124包括驱动器U3、电阻器R1和R2、二极管D3和D4、电容器C4和齐纳二极管D2。
如上所述,在主开关M1断开后,在FET体二极管使反激电流传导通过变压器T1的次级绕组L3之后,同步整流器开关M4便立即接通。当FET体二极管正向偏置时且在主开关M1接通之前,同步整流器开关M4通过从磁隔离变压器T2接收的时钟信号CLOCK的后沿(trailingedge)而断开。该方案有利地实现了零电压切换,并且使同步整流器开关M4的开关损耗最小化。齐纳二极管D2处的齐纳电压确保同步整流器开关M4在主开关M1接通时保持断开,并且因此不受来自驱动脉冲的任何电压毛刺的影响。同步驱动器U3具有由图2的表200指示的逻辑的反相输入INV2、非反相输入NINV2和输出VGATE_SYNC。
图3包括多个曲线图300,其示出了根据一个示出的实施方式的、图1A至图1B的电力转换器在启动操作并且调节到15伏输出期间的各种波形。具体地,图3示出了误差控制信号V_FB_SLOPE_COMP、峰值电流信号V_IPEAK、主开关栅极信号VGATE_MAIN、同步整流器开关栅极信号VGATE_SYNC和输出电压信号VOUT。
图4是曲线图400,其示出了误差控制信号V_FB_SLOPE_COMP、峰值电流信号V_IPEAK、主开关栅极信号VGATE_MAIN和同步整流器开关栅极信号VGATE_SYNC的放大视图,曲线图400示出了选通控制。对于图4的曲线图400,输入电压为16V。当峰值电流信号V_IPEAK与误差控制信号V_FB_SLOPE_COMP交叉时,主开关栅极信号VGATE_MAIN立即终止。为了防止次谐波振荡超过50%占空比,误差控制或反馈信号V_FB_SLOPE_COMP包括用于通过电阻器R9对电容器C7放电进行斜率补偿的内置斜度。
图5是曲线图500,其示出了针对输入电压为42V的误差控制信号V_FB_SLOPE_COMP、峰值电流信号V_IPEAK、主开关栅极信号VGATE_MAIN和同步整流器开关栅极信号VGATE_SYNC的放大视图。
图6是曲线图600,其示出了主开关栅极信号VGATE_MAIN和同步整流器开关栅极信号VGATE_SYNC。曲线图600示出了同步整流器开关M4的断开与主开关M1接通之前之间的停滞时间。同样,在同步整流器开关M4接通之前,主开关M1断开。这通过上面讨论的延时栅极驱动电路116来实现。如上所述,该特征防止了由开关M1和开关M4二者同时导通引起的击穿。
图7是曲线图700,其示出了针对输入电压为28V的主开关栅极信号VGATE_MAIN、时钟信号CLOCK、用于延时栅极驱动电路116的栅极驱动器U2的非反相输入信号NINV1以及用于栅极驱动器U2的反相输入信号INV1。图8是曲线图800,其示出了峰值电流检测器电路120的比较器U1的输出信号U1_OUT、误差控制信号V_FB_SLOPE_COMP、峰值电流信号V_IPEAK和时钟信号CLOCK。图9是曲线图900,其示出了同步整流器开关栅极信号VGATE_SYNC、时钟信号CLOCK、同步栅极驱动电路124的栅极驱动器U3的反相输入信号INV2以及栅极驱动器U3的非反相输入信号NINV2。从曲线图700、800和900可看出的是,时钟信号CLOCK为转换器100提供工作频率,并提供所有的时序参考。主开关M1仅在时钟信号CLOCK的下降沿期间通过主开关栅极信号VGATE_MAIN导通,并且在峰值电流信号V_IPEAK与误差控制信号V_FB_SLOPE_COMP交叉时终止。
有利地,本文中讨论的一个或多个实施方式通过使用模拟装置和最小集成电路来实现同步反激。这提供了对设计的完全控制和所有权并提供了允许多种配置的部件选择,所述多种配置包括提供多种输出电力范围和多种水平的耐辐射性的配置。
在至少一些实施方式中,提供了使用分立部件来控制反激技术中的同步整流的时序。如上所述,主开关与同步整流器开关之间的延迟可通过时钟脉冲的后沿提供,以在接通主开关之前断开同步整流器开关。在至少一些实施方式中,具有同步驱动能力的PWM控制器可在8伏的输入电压或甚至更低电压下操作。另外,在至少一些实施方式中,在不使用数字触发器的情况下实现模拟锁存器峰值电流模式控制。如上所述,通过使用具有由模拟部件设定的预设最大占空比的单个比较器,可进一步增强这一点。另外,在至少一些实施方式中,电力转换器100可在高频(例如,400kHz或更高)下操作。
前面的详细描述通过使用框图、示意图和示例阐述了装置和/或过程的各种实施方式。在这样的框图、示意图和示例包括一个或多个功能和/或操作的情况下,本领域技术人员将理解的是,可通过各种硬件、软件、固件或其实际上任何组合来单独地和/或共同地实现这样的框图、流程图或示例内的每个功能和/或操作。在一个实施方式中,本主题可通过专用集成电路(ASIC)来实现。然而,本领域技术人员将认识到的是,本文中所公开的实施方式可以全部或部分等效地在标准集成电路中实现,实现为在一个或多个计算机上运行的一个或多个计算机程序,实现为固件或者实际上实现为其任何组合,并且根据本公开内容,设计电路和/或编写用于软件和/或固件的代码将完全在本领域普通技术人员的技能范围内。
本领域技术人员应认识到的是,本文中阐述的许多方法或算法可采用附加动作,可省略某些动作,和/或可以以于所指定的顺序不同的顺序来执行动作。
另外,本领域技术人员应理解的是,本文中所教导的机构能够分配为具有多种形式的程序产品,并且不管用于实际执行该分配的特定类型的信号承载介质如何,说明性实施方式均同样适用。信号承载介质的示例包括但不限于以下:可记录型介质,诸如软盘、硬盘驱动器、CD ROM、数字磁带和计算机存储器。
可组合上文所描述的各种实施方式来提供进一步的实施方式。可以根据以上详细描述对实施方式作出这些和其他改变。通常,在所附权利要求中,所使用的术语不应被解释为将权利要求限制于说明书和权利要求中公开的具体实施方式,而是应解释为包括所有可能的实施方式以及这些权利要求的全部等同物。因此,权利要求不受公开内容的限制。
Claims (24)
1.一种用于电力转换器的峰值电流模式控制(PCMC)控制器,所述电力转换器包括具有初级绕组和次级绕组的主变压器,所述初级绕组能够电联接至输入电压节点并且电联接至主开关,所述次级绕组能够电联接至输出电压节点并且电联接至同步整流器开关,所述PCMC包括:
峰值电流检测器电路,其具有第一输入节点、第二输入节点和输出节点,其中所述第一输入节点可操作地联接至在操作中感测所述电力转换器的电流的电流传感器电路,所述第二输入节点可操作地联接至误差控制信号电路,所述输出节点提供能够至少部分地用于控制所述主开关的操作的峰值电流检测器输出信号,在操作中,所述峰值电流检测器电路将从所述电流传感器电路接收的电流传感器信号与从所述误差控制信号电路接收的误差控制信号进行比较,并且响应于检测到所述电流传感器信号超过所述误差控制信号,改变所述峰值电流检测器输出信号的状态;
磁隔离器电路,包括隔离变压器,所述隔离变压器包括初级绕组和次级绕组,所述磁隔离器电路包括第一输入节点、第二输入节点、第一输出节点和第二输出节点,所述磁隔离器电路的第一输入节点可操作地联接至所述误差控制信号电路,所述磁隔离器电路的第二输入节点可操作地联接至时钟电路以从所述时钟电路接收时钟信号,所述第一输出节点电联接至所述峰值电流检测器电路的第二输入节点以向所述峰值电流检测器电路提供所述误差控制信号,所述第二输出节点电联接至所述隔离变压器的次级绕组;以及
同步栅极驱动电路,包括第一输入节点、第二输入节点和输出节点,所述同步栅极驱动电路的第一输入节点可操作地联接至所述主变压器的次级绕组,所述同步栅极驱动电路的第二输入节点可操作地联接至所述磁隔离器电路的第二输出节点,所述同步栅极驱动电路的输出节点可操作地进行联接,以控制所述同步整流器开关的操作。
2.如权利要求1所述的PCMC控制器,其中,所述峰值电流检测器电路包括比较器,以及所述同步栅极驱动电路包括MOSFET驱动器。
3.如权利要求1所述的PCMC控制器,其中,所述磁隔离器电路包括为所述PCMC控制器的次级侧电路提供电压源的电路。
4.如权利要求1所述的PCMC控制器,还包括:
延时栅极驱动电路,其包括第一输入节点、第二输入节点和输出节点,所述延时栅极驱动电路的第一输入节点可操作地联接至所述时钟电路,以从所述时钟电路接收所述时钟信号;所述延时栅极驱动电路的第二输入节点可操作地联接至所述峰值电流检测器电路的输出节点;所述延时栅极驱动电路的输出节点可操作地进行联接,以至少部分地基于所述时钟信号和所述峰值电流检测器输出信号来控制所述主开关的操作,在操作中,所述延时栅极驱动电路使得在切换周期期间所述主开关仅在所述同步整流器开关断开之后接通。
5.如权利要求4所述的PCMC控制器,其中,所述延时栅极驱动电路包括电阻器-电容器(RC)电路。
6.如权利要求4所述的PCMC控制器,其中,所述延时栅极驱动电路包括MOSFET栅极驱动器。
7.如权利要求4所述的PCMC控制器,还包括:
预设最大占空比电路,其包括可操作地联接至所述时钟电路以从所述时钟电路接收所述时钟信号的输入节点,以及可操作地联接至所述延时栅极驱动电路的第二输入节点的输出节点,在操作中,所述预设最大占空比电路设置用于所述电力转换器的主开关的最大占空比。
8.如权利要求7所述的PCMC控制器,其中,所述预设最大占空比电路包括第一互补双极结型晶体管和第二互补双极结型晶体管。
9.如权利要求1所述的PCMC控制器,其中,所述磁隔离器电路包括可操作地联接至所述隔离变压器的初级绕组的磁隔离器电路开关,以及其中,所述磁隔离器电路的第二输入节点可操作地进行联接,以控制所述同步整流器开关的操作。
10.根据权利要求1所述的PCMC控制器,其中,所述同步栅极驱动电路可操作成在每个周期使所述同步整流器开关在所述主开关断开之后接通,以及在后续周期期间使所述同步整流器开关在所述主开关接通之前断开。
11.如权利要求1所述的PCMC控制器,还包括:
所述电流传感器电路,所述电流传感器电路包括在操作中感测所述电力转换器的电流的电流变送器。
12.如权利要求11所述的PCMC控制器,其中,所述电流变送器包括变压器或电阻器。
13.一种电力转换器,包括:
变压器,具有初级绕组和次级绕组,所述初级绕组能够电联接至输入电压节点,以及所述次级绕组能够电联接至输出电压节点;
初级电路,电联接至所述初级绕组,所述初级电路包括主开关;
次级电路,电联接至所述次级绕组,所述初级电路包括同步整流器开关;以及
峰值电流模式控制(PCMC)控制器,包括:
峰值电流检测器电路,其具有第一输入节点、第二输入节点和输出节点,其中所述第一输入节点可操作地联接至在操作中感测所述电力转换器的电流的电流传感器电路,所述第二输入节点可操作地联接至误差控制信号电路,所述输出节点提供能够至少部分地用于控制所述主开关的操作的峰值电流检测器输出信号,在操作中,所述峰值电流检测器电路将从所述电流传感器电路接收的电流传感器信号与从所述误差控制信号电路接收的误差控制信号进行比较,并且响应于检测到所述电流传感器信号超过所述误差控制信号,改变所述峰值电流检测器输出信号的状态;
磁隔离器电路,包括隔离变压器,所述隔离变压器包括初级绕组和次级绕组,所述磁隔离器电路包括第一输入节点、第二输入节点、第一输出节点和第二输出节点,所述磁隔离器电路的第一输入节点可操作地联接至所述误差控制信号电路,所述磁隔离器电路的第二输入节点可操作地联接至时钟电路以从所述时钟电路接收时钟信号,所述第一输出节点电联接至所述峰值电流检测器电路的第二输入节点以向所述峰值电流检测器电路提供所述误差控制信号,所述第二输出节点电联接至所述隔离变压器的次级绕组;以及
同步栅极驱动电路,包括第一输入节点、第二输入节点和输出节点,所述同步栅极驱动电路的第一输入节点可操作地联接至所述主变压器的次级绕组,所述同步栅极驱动电路的第二输入节点可操作地联接至所述磁隔离器电路的第二输出节点,所述同步栅极驱动电路的输出节点可操作地进行联接,以控制所述同步整流器开关的操作。
14.如权利要求13所述的电力转换器,其中,所述峰值电流检测器电路包括比较器,以及所述同步栅极驱动电路包括MOSFET驱动器。
15.如权利要求13所述的电力转换器,其中,所述磁隔离器电路包括为所述PCMC控制器的次级侧提供电压源的电路。
16.如权利要求13所述的电力转换器,还包括:
延时栅极驱动电路,其包括第一输入节点、第二输入节点和输出节点,所述延时栅极驱动电路的第一输入节点可操作地联接至所述时钟电路,以从所述时钟电路接收所述时钟信号;所述延时栅极驱动电路的第二输入节点可操作地联接至所述峰值电流检测器电路的输出节点;所述延时栅极驱动电路的输出节点可操作地进行联接,以至少部分地基于所述时钟信号和所述峰值电流检测器输出信号来控制所述主开关的操作,在操作中,所述延时栅极驱动电路使得在切换周期期间所述主开关仅在所述同步整流器开关断开之后接通。
17.根据权利要求16所述的电力转换器,其中,所述延时栅极驱动电路包括电阻器-电容器(RC)电路。
18.如权利要求16所述的电力转换器,还包括:
预设最大占空比电路,其包括可操作地联接至所述时钟电路以从所述时钟电路接收所述时钟信号的输入节点,以及可操作地联接至所述延时栅极驱动电路的第二输入节点的输出节点,在操作中,所述预设最大占空比电路设置用于所述电力转换器的主开关的最大占空比。
19.如权利要求18所述的电力转换器,其中,所述预设最大占空比电路包括第一互补双极结型晶体管和第二互补双极结型晶体管。
20.如权利要求13所述的电力转换器,其中,所述磁隔离器电路包括可操作地联接至所述隔离变压器的初级绕组的磁隔离器电路开关,以及其中,所述磁隔离器电路的第二输入节点可操作地进行联接,以控制所述同步整流器开关的操作。
21.根据权利要求13所述的电力转换器,其中,所述同步栅极驱动电路可操作成在每个周期使所述同步整流器开关在所述主开关断开之后接通,以及在后续周期期间,使所述同步整流器开关在所述主开关接通之前断开。
22.如权利要求13所述的电力转换器,还包括:
所述电流传感器电路,所述电流传感器电路包括在操作中感测所述电力转换器的电流的电流变送器。
23.如权利要求22所述的电力转换器,其中,所述电流变送器包括变压器或电阻器。
24.一种用于电力转换器的峰值电流模式控制(PCMC)控制器,所述电力转换器包括具有初级绕组和次级绕组的主变压器,所述初级绕组能够电联接至输入电压节点并且电联接至主开关,所述次级绕组能够电联接至输出电压节点并且电联接至同步整流器开关,所述PCMC控制器包括:
磁隔离器电路,包括隔离变压器,所述隔离变压器包括电联接至初级侧电路的初级绕组和电联接至次级侧电路的次级绕组,所述磁隔离器电路包括这样的电路:所述电路在操作中向所述次级侧电路提供电压源,将来自所述次级侧电路的误差控制信号提供给所述初级侧电路,并提供能够由同步栅极驱动电路使用的输出信号,以控制所述同步整流器开关的操作。
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TWI733198B (zh) | 2021-07-11 |
US10425080B1 (en) | 2019-09-24 |
CN111146948B (zh) | 2023-12-01 |
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