WO2003007656A1 - Efficient and scalable parametric stereo coding for low bitrate applications - Google Patents

Efficient and scalable parametric stereo coding for low bitrate applications Download PDF

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Publication number
WO2003007656A1
WO2003007656A1 PCT/SE2002/001372 SE0201372W WO03007656A1 WO 2003007656 A1 WO2003007656 A1 WO 2003007656A1 SE 0201372 W SE0201372 W SE 0201372W WO 03007656 A1 WO03007656 A1 WO 03007656A1
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Prior art keywords
stereo
balance
signal
parameter
width
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PCT/SE2002/001372
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English (en)
French (fr)
Inventor
Fredrik Henn
Kristofer KJÖRLING
Lars Gustaf Liljeryd
Jonas Rödén
Jonas ENGDEGÅRD
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Coding Technologies Sweden AB
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Coding Technologies Sweden AB
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Priority claimed from SE0102481A external-priority patent/SE0102481D0/xx
Priority claimed from SE0200796A external-priority patent/SE0200796D0/xx
Priority to CN2005101099602A priority Critical patent/CN1758338B/zh
Priority to JP2003513284A priority patent/JP4447317B2/ja
Priority to DK08016926T priority patent/DK2015292T3/da
Priority to CN200510109959XA priority patent/CN1758337B/zh
Priority to AT02741611T priority patent/ATE305715T1/de
Priority to KR1020047000072A priority patent/KR100649299B1/ko
Priority to EP16181505.5A priority patent/EP3104367B1/en
Priority to HK04105508.0A priority patent/HK1062624B/en
Priority to CN2005101099570A priority patent/CN1758335B/zh
Priority to DE60206390T priority patent/DE60206390T2/de
Priority to CN2005101099585A priority patent/CN1758336B/zh
Priority to US10/483,453 priority patent/US7382886B2/en
Priority to EP18212610.2A priority patent/EP3477640B1/en
Priority to CNB028136462A priority patent/CN1279790C/zh
Priority to EP02741611A priority patent/EP1410687B1/en
Application filed by Coding Technologies Sweden AB filed Critical Coding Technologies Sweden AB
Publication of WO2003007656A1 publication Critical patent/WO2003007656A1/en
Anticipated expiration legal-status Critical
Priority to US11/237,127 priority patent/US8059826B2/en
Priority to US11/237,133 priority patent/US8073144B2/en
Priority to US11/237,174 priority patent/US8014534B2/en
Priority to US11/238,982 priority patent/US8116460B2/en
Priority to US12/496,926 priority patent/US8081763B2/en
Priority to US12/610,193 priority patent/US8243936B2/en
Priority to US12/610,186 priority patent/US8605911B2/en
Priority to US13/458,492 priority patent/US9218818B2/en
Priority to US14/078,456 priority patent/US20140074485A1/en
Priority to US15/458,135 priority patent/US9799340B2/en
Priority to US15/458,126 priority patent/US9792919B2/en
Priority to US15/458,143 priority patent/US9865271B2/en
Priority to US15/458,150 priority patent/US9799341B2/en
Priority to US16/157,899 priority patent/US10297261B2/en
Priority to US16/399,705 priority patent/US10540982B2/en
Priority to US16/744,586 priority patent/US10902859B2/en
Priority to US17/155,372 priority patent/US20210217425A1/en
Ceased legal-status Critical Current

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Classifications

    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04S—STEREOPHONIC SYSTEMS 
    • H04S5/00—Pseudo-stereo systems, e.g. in which additional channel signals are derived from monophonic signals by means of phase shifting, time delay or reverberation 
    • G—PHYSICS
    • G10—MUSICAL INSTRUMENTS; ACOUSTICS
    • G10L—SPEECH ANALYSIS TECHNIQUES OR SPEECH SYNTHESIS; SPEECH RECOGNITION; SPEECH OR VOICE PROCESSING TECHNIQUES; SPEECH OR AUDIO CODING OR DECODING
    • G10L19/00—Speech or audio signals analysis-synthesis techniques for redundancy reduction, e.g. in vocoders; Coding or decoding of speech or audio signals, using source filter models or psychoacoustic analysis
    • G10L19/04—Speech or audio signals analysis-synthesis techniques for redundancy reduction, e.g. in vocoders; Coding or decoding of speech or audio signals, using source filter models or psychoacoustic analysis using predictive techniques
    • G10L19/16—Vocoder architecture
    • G10L19/18—Vocoders using multiple modes
    • G10L19/24—Variable rate codecs, e.g. for generating different qualities using a scalable representation such as hierarchical encoding or layered encoding
    • G—PHYSICS
    • G10—MUSICAL INSTRUMENTS; ACOUSTICS
    • G10L—SPEECH ANALYSIS TECHNIQUES OR SPEECH SYNTHESIS; SPEECH RECOGNITION; SPEECH OR VOICE PROCESSING TECHNIQUES; SPEECH OR AUDIO CODING OR DECODING
    • G10L19/00—Speech or audio signals analysis-synthesis techniques for redundancy reduction, e.g. in vocoders; Coding or decoding of speech or audio signals, using source filter models or psychoacoustic analysis
    • G10L19/008—Multichannel audio signal coding or decoding using interchannel correlation to reduce redundancy, e.g. joint-stereo, intensity-coding or matrixing
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04S—STEREOPHONIC SYSTEMS 
    • H04S1/00—Two-channel systems
    • H04S1/007—Two-channel systems in which the audio signals are in digital form
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04S—STEREOPHONIC SYSTEMS 
    • H04S3/00—Systems employing more than two channels, e.g. quadraphonic
    • H04S3/002—Non-adaptive circuits, e.g. manually adjustable or static, for enhancing the sound image or the spatial distribution
    • G—PHYSICS
    • G10—MUSICAL INSTRUMENTS; ACOUSTICS
    • G10L—SPEECH ANALYSIS TECHNIQUES OR SPEECH SYNTHESIS; SPEECH RECOGNITION; SPEECH OR VOICE PROCESSING TECHNIQUES; SPEECH OR AUDIO CODING OR DECODING
    • G10L19/00—Speech or audio signals analysis-synthesis techniques for redundancy reduction, e.g. in vocoders; Coding or decoding of speech or audio signals, using source filter models or psychoacoustic analysis
    • G10L19/02—Speech or audio signals analysis-synthesis techniques for redundancy reduction, e.g. in vocoders; Coding or decoding of speech or audio signals, using source filter models or psychoacoustic analysis using spectral analysis, e.g. transform vocoders or subband vocoders
    • G10L19/0204—Speech or audio signals analysis-synthesis techniques for redundancy reduction, e.g. in vocoders; Coding or decoding of speech or audio signals, using source filter models or psychoacoustic analysis using spectral analysis, e.g. transform vocoders or subband vocoders using subband decomposition

Definitions

  • the present invention relates to low bitrate audio source coding systems. Different parametric representations of stereo properties of an input signal are introduced, and the application thereof at the decoder side is explained, ranging from pseudo-stereo to full stereo coding of spectral envelopes, the latter of which is especially suited for HFR based codecs.
  • Audio source coding techniques can be divided into two classes: natural audio coding and speech coding.
  • natural audio coding is commonly used for speech and music signals, and stereo transmission and reproduction is possible.
  • mono coding of the audio program material is unavoidable.
  • a stereo impression is still desirable, in particular when listening with headphones, in which case a pure mono signal is perceived as originating from "within the head", which can be an unpleasant experience.
  • Prior art methods have in common that they are applied as pure post-processes. In other words, no information on the degree of stereo-width, let alone position in the stereo sound stage, is available to the decoder. Thus, the pseudo-stereo signal may or may not have a resemblance of the stereo character of the original signal.
  • a particular situation where prior art systems fall short, is when the original signal is a pure mono signal, which often is the case for speech recordings. This mono signal is blindly converted to a synthetic stereo signal at the decoder, which in the speech case often causes annoying artifacts, and may reduce the clarity and speech intelligibility.
  • Other prior art systems aiming at true stereo transmission at low bitrates, typically employ a sum and difference coding scheme.
  • L and R are identical.
  • a traditional L/R-codec encodes this mono signal twice, whereas a S/D codec detects this redundancy, and the D signal does (ideally) not require any bits at all.
  • the present invention employs detection of signal stereo properties prior to coding and transmission.
  • a detector measures the amount of stereo perspective that is present in the input stereo signal. This amount is then transmitted as a stereo width parameter, together with an encoded mono sum of the original signal.
  • the receiver decodes the mono signal, and applies the proper amount of stereo- width, using a pseudo-stereo generator, which is controlled by said parameter.
  • a mono input signal is signaled as zero stereo width, and correspondingly no stereo synthesis is applied in the decoder.
  • useful measures of the stereo-width can be derived e.g. from the difference signal or from the cross-correlation of the original left and right channel.
  • the value of such computations can be mapped to a small number of states, which are transmitted at an appropriate fixed rate in time, or on an as-needed basis.
  • the invention also teaches how to filter the synthesized stereo components, in order to reduce the risk of unmasking coding artifacts which typically are associated with low bitrate coded signals.
  • the overall stereo-balance or localization in the stereo field is detected in the encoder. This information, optionally together with the above width-parameter, is efficiently transmitted as a balance- parameter, along with the encoded mono signal.
  • this stereo-balance parameter can be derived from the quotient of the left and right signal powers.
  • the transmission of both types of parameters requires very few bits compared to full stereo coding, whereby the total bitrate demand is kept low.
  • several balance and stereo-width parameters are used, each one representing separate frequency bands.
  • the balance-parameter generalized to a per frequency-band operation, together with a corresponding per band operation of a level-parameter, calculated as the sum of the left and right signal powers, enables a new, arbitrary detailed, representation of the power spectral density of a stereo signal.
  • the balance-signal can be quantized with less precision than the level ditto, since the quantization error, when converting back to a stereo spectral envelope, causes an "error in space", i.e. perceived localization in the stereo panorama, rather than an error in level.
  • the level/balance-scheme can be adaptively switched off, in favor of a levelL/levelR-signal, which is more efficient when the overall signal is heavily offset towards either channel.
  • the above spectral envelope coding scheme can be used whenever an efficient coding of power spectral envelopes is required, and can be incorporated as a tool in new stereo source codecs.
  • a particularly interesting application is in HFR systems that are guided by information about the original signal highband envelope.
  • the lowband is coded and decoded by means of an arbitrary codec, and the highband is regenerated at the decoder using the decoded lowband signal and the transmitted highband envelope information [PCT WO 98/57436].
  • the possibility to build a scalable HFR-based stereo codec is offered, by locking the envelope coding to level/balance operation.
  • the level values are fed into the primary bitstream, which, depending on the implementation, typically decodes to a mono signal.
  • the balance values are fed into the secondary bitstream, which in addition to the primary bitstream is available to receivers close to the transmitter, taking an IBOC (In-Band On-Channel) digital AM-broadcasting system as an example.
  • IBOC In-Band On-Channel
  • the decoder produces a stereo output signal.
  • the primary bitstream can contain stereo parameters, e.g. a width parameter.
  • Fig. 1 illustrates a source coding system containing an encoder enhanced by a parametric stereo encoder module, and a decoder enhanced by a parametric stereo decoder module.
  • Fig. 2a is a block schematic of a parametric stereo decoder module
  • Fig. 2b is a block schematic of a pseudo-stereo generator with control parameter inputs
  • Fig. 2c is a block schematic of a balance adjuster with control parameter inputs
  • Fig. 3 is a block schematic of a parametric stereo decoder module using multiband pseudo-stereo generation combined with multiband balance adjustment
  • Fig. 4a is a block schematic of the encoder side of a scalable HFR-based stereo codec, employing level/balance-coding of the spectral envelope
  • Fig. 4b is a block schematic of the corresponding decoder side.
  • Fig. 1 shows how an arbitrary source coding system comprising of an encoder, 107, and a decoder, 115, where encoder and decoder operate in monaural mode, can be enhanced by parametric stereo coding according to the invention.
  • L and R denote the left and right analog input signals, which are fed to an AD-converter, 101.
  • the output from the AD-converter is converted to mono, 105, and the mono signal is encoded, 107.
  • the stereo signal is routed to a parametric stereo encoder, 103, which calculates one or several stereo parameters to be described below. Those parameters are combined with the encoded mono signal by means of a multiplexer, 109, forming a bitstream, 111.
  • the bitstream is stored or transmitted, and subsequently extracted at the decoder side by means of a demultiplexer, 113.
  • the mono signal is decoded, 115, and converted to a stereo signal by a parametric stereo decoder, 119, which uses the stereo parameter(s), 117, as control signal(s).
  • the stereo signal is routed to the DA-converter, 121, which feeds the analog outputs, L' and R' .
  • the topology according to Fig.1 is common to a set of parametric stereo coding methods which will be described in detail, starting with the less complex versions.
  • One method of parameterization of stereo properties according to the present invention is to determine the original signal stereo-width at the encoder side.
  • a first approximation of the stereo-width is the difference signal, D — L - R, since, roughly put, a high degree of similarity between L and R computes to a small value of D, and vice versa.
  • D the difference signal
  • a mono signal that is fed to L and R at different levels does not yield a zero D signal, even though the perceived width is zero.
  • more elaborate detectors might be required, employing for example cross-correlation methods.
  • a problem with the aforementioned detector is the case when mono speech is mixed with a much weaker stereo signal e.g. stereo noise or background music during speech-to-music/music-to-speech transitions. At the speech pauses the detector will then indicate a wide stereo signal. This is solved by normalizing the stereo-width value with a signal containing information of previous total energy level e.g., a peak decay signal of the total energy.
  • the detector signals should be pre-filtered by a low- pass filter, typically with a cutoff frequency somewhere above a voice's second formant, and optionally also by a high-pass filter to avoid unbalanced signal-offsets or hum.
  • a low- pass filter typically with a cutoff frequency somewhere above a voice's second formant, and optionally also by a high-pass filter to avoid unbalanced signal-offsets or hum.
  • Fig 2a gives an example of the contents of the parametric stereo decoder introduced in Fig 1.
  • the block denoted 'balance', 211, controlled by parameter B, will be described later, and should be regarded as bypassed for now.
  • the block denoted 'width', 205 takes a mono input signal, and synthetically recreates the impression of stereo width, where the amount of width is controlled by the parameter W.
  • the optional parameters S and D will be described later.
  • a subjectively better sound quality can often be achieved by incorporating a crossover filter comprising of a low-pass filter, 203, and a high- pass filter, 201, in order to keep the low frequency range "tight" and unaffected.
  • the stereo output from the width block is added to the mono output from the low-pass filter by means of 207 and 209, forming the stereo output signal.
  • Any prior art pseudo-stereo generator can be used for the width block, such as those mentioned in the background section, or a Schroeder-type early reflection simulating unit (multitap delay) or reverberator.
  • Fig. 2b gives an example of a pseudo-stereo generator, fed by a mono signal M.
  • the amount of stereo- width is determined by the gain of 215, and this gain is a function of the stereo-width parameter, W. The higher the gain, the wider the stereo-impression, a zero gain corresponds to pure mono reproduction.
  • the output from 215 is delayed, 221, and added, 223 and 225, to the two direct signal instances, using opposite signs.
  • a compensating attenuation of the direct signal can be incorporated, 213.
  • the gain of the delayed signal is G
  • the gain of the direct signal can be selected as sqrt(l - G 2 ).
  • a high frequency roll-off can be incorporated in the delay signal path, 217, which helps avoiding pseudo-stereo caused unmasking of coding artifacts.
  • crossover filter, roll-off filter and delay parameters can be sent in the bitstream, offering more possibilities to mimic the stereo properties of the original signal, as also shown in Figs.
  • a reverberation unit is used for generating a stereo signal, the reverberation decay might sometimes be unwanted after the very end of a sound. These unwanted reverb-tails can however easily be attenuated or completely removed by just altering the gain of the reverb signal.
  • a detector designed for finding sound endings can be used for that purpose. If the reverberation unit generates artifacts at some specific signals e.g., transients, a detector for those signals can also be used for attenuating the same.
  • IP R correspond to balance values of +10 dB, OdB, and -10 dB respectively. Clearly, those values map to the locations "left”, “center”, and “right”.
  • the span of the balance parameter can be limited to for example +/- 40 dB, since those extreme values are already perceived as if the sound originates entirely from one of the two loudspeakers or headphone drivers. This limitation reduces the signal space to cover in the transmission, thus offering bitrate reduction.
  • a progressive quantization scheme can be used, whereby smaller quantization steps are used around zero, and larger steps towards the outer limits, which further reduces the bitrate. Often the balance is constant over time for extended passages.
  • the most rudimental decoder usage of the balance parameter is simply to offset the mono signal towards either of the two reproduction channels, by feeding the mono signal to both outputs and adjusting the gains correspondingly, as illustrated in Fig. 2c, blocks 227 and 229, with the control signal B.
  • This is analogous to turning the "panorama” knob on a mixing desk, synthetically “moving” a mono signal between the two stereo speakers.
  • the balance parameter can be sent in addition to the above described width parameter, offering the possibility to both position and spread the sound image in the sound-stage in a controlled manner, offering flexibility when mimicking the original stereo impression.
  • Fig. 3 shows an example of a parametric stereo decoder using a set of N pseudo-stereo generators according to Fig. 2b, represented by blocks 307, 317 and 327, combined with multiband balance adjustment, represented by blocks 309, 319 and 329, as described in Fig. 2c.
  • the individual passbands are obtained by feeding the mono input signal, M, to a set of bandpass filters, 305, 315 and 325.
  • the bandpass stereo outputs from the balance adjusters are added, 311, 321, 313, 323, forming the stereo output signal, L and R.
  • the formerly scalar width- and balance parameters are now replaced by the arrays W(k) and B(k).
  • every pseudo-stereo generator and balance adjuster has unique stereo parameters.
  • parameters from several frequency bands can be averaged in groups at the encoder, and this smaller number of parameters be mapped to the corresponding groups of width and balance blocks at the decoder.
  • S(k) represents the gains of the delay signal paths in the width blocks
  • D(Ic) represents the delay parameters.
  • S(k) and D(k) are optional in the bitstream.
  • the parametric balance coding method can, especially for lower frequency bands, give a somewhat unstable behavior, due to lack of frequency resolution, or due to too many sound events occurring in one frequency band at the same time but at different balance positions.
  • Those balance-glitches are usually characterized by a deviant balance value during just a short period of time, typically one or a few consecutive values calculated, dependent on the update rate. In order to avoid disturbing balance-glitches, a stabilization process can be applied on the balance data.
  • This process may use a number of balance values before and after current time position, to calculate the median value of those.
  • the median value can subsequently be used as a limiter value for the current balance value i.e., the current balance value should not be allowed to go beyond the median value.
  • the current value is then limited by the range between the last value and the median value.
  • the current balance value can be allowed to pass the limited values by a certain overshoot factor.
  • the overshoot factor, as well as the number of balance values used for calculating the median should be seen as frequency dependent properties and hence be individual for each frequency band.
  • Interpolation refers to interpolations between two, in time consecutive balance values. By studying the mono signal at the receiver side, information about beginnings and ends of different sound events can be obtained. One way is to detect a sudden increase or decrease of signal energy in a particular frequency band. The interpolation should after guidance from that energy envelope in time make sure that the changes in balance position should be performed preferably during time segments containing little signal energy.
  • the interpolation scheme benefits from finding the beginning of a sound by e.g., applying peak-hold to the energy and then let the balance value increments be a function of the peak-holded energy, where a small energy value gives a large increment and vice versa.
  • this interpolation method equals linear interpolation between the two balance values. If the balance values are quotients of left and right energies, logarithmic balance values are preferred, for left - right symmetry reasons.
  • Another advantage of applying the whole interpolation algorithm in the logarithmic domain is the human ear's tendency of relating levels to a logarithmic scale.
  • interpolation can be applied to the same.
  • a simple way is to interpolate linearly between two in time consecutive stereo-width values. More stable behavior of the stereo-width can be achieved by smoothing the stereo-width gain values over a longer time segment containing several stereo-width parameters.
  • smoothing with different attack and release time constants, a system well suited for program material containing mixed or interleaved speech and music is achieved.
  • An appropriate design of such smoothing filter is made using a short attack time constant, to get a short rise-time and hence an immediate response to music entries in stereo, and a long release time, to get a long fall-time.
  • attack time constants, release time constants and other smoothing filter characteristics can also be signaled by an encoder.
  • stereo-unmasking is the result of non-centered sounds that do not fulfill the masking criterion.
  • the problem with stereo-unmasking might be solved or partly solved by, at the decoder side, introducing a detector aimed for such situations.
  • Known technologies for measuring signal to mask ratios can be used to detect potential stereo-unmasking. Once detected, it can be explicitly signaled or the stereo parameters can just simply be decreased.
  • one option is to employ a Hubert transformer to the input signal, i.e. a 90 degree phase shift between the two channels is introduced.
  • a Hubert transformer to the input signal, i.e. a 90 degree phase shift between the two channels is introduced.
  • a better balance between a center-panned mono signal and "true" stereo signals is achieved, since the Hubert transformation introduces a 3 dB attenuation for center information.
  • this improves mono coding of e.g. contemporary pop music, where for instance the lead vocals and the bass guitar commonly is recorded using a single mono source.
  • the multiband balance-parameter method is not limited to the type of application described in Fig. 1. It can be advantageously used whenever the objective is to efficiently encode the power spectral envelope of a stereo signal. Thus, it can be used as tool in stereo codecs, where in addition to the stereo spectral envelope a corresponding stereo residual is coded.
  • P P L + P R , where i and P R are signal powers as described above. Note that this definition does not take left to right phase relations into account. (E.g.
  • P and B are calculated for a set of frequency bands, typically, but not necessarily, with bandwidths that are related to the critical bands of human hearing.
  • those bands may be formed by grouping of channels in a constant bandwidth filterbank, whereby P L and P R are calculated as the time and frequency averages of the squares of the subband samples corresponding to respective band and period in time.
  • the sets P 0 , Pi, P 2 , ⁇ , P N - I and B 0 , B 2 , ..., B N ⁇ , where the subscripts denote the frequency band in an Nband representation, are delta and Huffman coded, transmitted or stored, and finally decoded into the quantized values that were calculated in the encoder.
  • the last step is to convert P and B back to P L and P R .
  • P L BP/(B + 1)
  • P R PI(B + 1).
  • resolution and range of the quantization method can advantageously be selected to match the properties of a perceptual scale. If such scale is made frequency dependent, different quantization methods, or so called quantization classes, can be chosen for the different frequency bands.
  • quantization methods or so called quantization classes, can be chosen for the different frequency bands.
  • the encoded parameter values representing the different frequency bands should then in some cases, even if having identical values, be interpreted in different ways i.e., be decoded into different values.
  • the P and B signals may be adaptively substituted by the P L and P R signals, in order to better cope with extreme signals.
  • delta coding of envelope samples can be switched from delta-in-time to delta-in-frequency, depending on what direction is most efficient in terms of number of bits at a particular moment.
  • the balance parameter can also take advantage of this scheme: Consider for example a source that moves in stereo field over time. Clearly, this corresponds to a successive change of balance values over time, which depending on the speed of the source versus the update rate of the parameters, may correspond to large delta-in-time values, corresponding to large codewords when employing entropy coding.
  • the delta-in-frequency values of the balance parameter are zero at every point in time, again corresponding to small codewords.
  • a lower bitrate is achieved in this case, when using the frequency delta coding direction.
  • Another example is a source that is stationary in the room, but has a non-uniform radiation. Now the delta-in-frequency values are large, and delta-in-time is the preferred choice.
  • the P/B-coding scheme offers the possibility to build a scalable HFR-codec, see Fig. 4.
  • a scalable codec is characterized in that the bitstream is split into two or more parts, where the reception and decoding of higher order parts is optional.
  • the example assumes two bitstream parts, hereinafter referred to as primary, 419, and secondary, 417,, but extension to a higher number of parts is clearly possible.
  • 4a comprises of an arbitrary stereo lowband encoder, 403, which operates on the stereo input signal, IN (the trivial steps of AD- respective DA-conversion are not shown in the figure), a parametric stereo encoder, which estimates the highband spectral envelope, and optionally additional stereo parameters, 401, which also operates on the stereo input signal, and two multiplexers, 415 and 413, for the primary and secondary bitstreams respectively.
  • the highband envelope coding is locked to P/B-operation, and the P signal, 407, is sent to the primary bitstream by means of 415, whereas the B signal, 405, is sent to the secondary bitstream, by means of 413.
  • the lowband codec different possibilities exist: It may constantly operate in S/D-mode, and the S and D signals be sent to primary and secondary bitstreams respectively. In this case, a decoding of the primary bitstream results in a full band mono signal. Of course, this mono signal can be enhanced by parametric stereo methods according to the invention, in which case the stereo-parameter(s) also must be located in the primary bitstream. Another possibility is to feed a stereo coded lowband signal to the primary bitstream, optionally together with highband width- and balance-parameters. Now decoding of the primary bitstream results in true stereo for the lowband, and very realistic pseudo-stereo for the highband, since the stereo properties of the lowband are reflected in the high frequency reconstruction.
  • the secondary bitstream may contain more lowband information, which when combined with that of the primary bitstream, yields a higher quality lowband reproduction.
  • the topology of Fig. 4 illustrates both cases, since the primary and secondary lowband encoder output signals, 411, and 409, connected to 415 and 417 respectively, may contain either of the above described signal types.
  • the bitstreams are transmitted or stored, and either only 419 or both 419 and 417 are fed to the decoder, Fig. 4b.
  • the primary bitstream is demultiplexed by 423, into the lowband core decoder primary signal, 429 and the P signal, 431.
  • the secondary bitstream is demultiplexed by 421 , into the lowband core decoder secondary signal, 427, and the B signal, 425.
  • the lowband signal(s) is(are) routed to the lowband decoder, 433, which produces an output, 435, which again, in case of decoding of the primary bitstream only, may be of either type described above (mono or stereo).
  • the signal 435 feeds the HFR- unit, 437, wherein a synthetic highband is generated, and adjusted according to P, which also is connected to the HFR-unit.
  • the decoded lowband is combined with the highband in the HFR-unit, and the lowband and/or highband is optionally enhanced by a pseudo-stereo generator (also situated in the HFR-unit), before finally being fed to the system outputs, forming the output signal, OUT.
  • the HFR-unit also gets the B signal as an input signal, 425, and 435 is in stereo, whereby the system produces a full stereo output signal, and pseudo-stereo generators if any, are bypassed.

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PCT/SE2002/001372 2001-07-10 2002-07-10 Efficient and scalable parametric stereo coding for low bitrate applications Ceased WO2003007656A1 (en)

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HK04105508.0A HK1062624B (en) 2001-07-10 2002-07-10 Efficient and scalable parametric stereo coding for low bitrate applications
CNB028136462A CN1279790C (zh) 2001-07-10 2002-07-10 用于低比特率音频编码应用的高效可标度参数立体声编码
EP02741611A EP1410687B1 (en) 2001-07-10 2002-07-10 Efficient and scalable parametric stereo coding for low bitrate applications
DE60206390T DE60206390T2 (de) 2001-07-10 2002-07-10 Effiziente und skalierbare parametrische stereocodierung für anwendungen mit niedriger bitrate
DK08016926T DK2015292T3 (da) 2001-07-10 2002-07-10 Effektiv og skalerbar parametrisk stereokodning til audiokodningsapplikationer med lav bithastighed
CN200510109959XA CN1758337B (zh) 2001-07-10 2002-07-10 用于低比特率音频编码应用的高效可标度参数立体声编码
AT02741611T ATE305715T1 (de) 2001-07-10 2002-07-10 Effiziente und skalierbare parametrische stereocodierung für anwendungen mit niedriger bitrate
KR1020047000072A KR100649299B1 (ko) 2001-07-10 2002-07-10 저 비트레이트 오디오 코딩 적용을 위한 효율적인스케일러블 파라미터 스테레오 코딩 방법 및 장치
EP16181505.5A EP3104367B1 (en) 2001-07-10 2002-07-10 Parametric stereo audio decoding
CN2005101099602A CN1758338B (zh) 2001-07-10 2002-07-10 用于低比特率音频编码应用的高效可标度参数立体声编码
CN2005101099570A CN1758335B (zh) 2001-07-10 2002-07-10 用于低比特率音频编码应用的高效可标度参数立体声编码
JP2003513284A JP4447317B2 (ja) 2001-07-10 2002-07-10 低ビットレートオーディオ符号化用の効率的かつスケーラブルなパラメトリックステレオ符号化
CN2005101099585A CN1758336B (zh) 2001-07-10 2002-07-10 用于低比特率音频编码应用的高效可标度参数立体声编码
US10/483,453 US7382886B2 (en) 2001-07-10 2002-07-10 Efficient and scalable parametric stereo coding for low bitrate audio coding applications
EP18212610.2A EP3477640B1 (en) 2001-07-10 2002-07-10 Parametric stereo audio decoding
US11/237,133 US8073144B2 (en) 2001-07-10 2005-09-27 Stereo balance interpolation
US11/237,174 US8014534B2 (en) 2001-07-10 2005-09-27 Efficient and scalable parametric stereo coding for low bitrate audio coding applications
US11/237,127 US8059826B2 (en) 2001-07-10 2005-09-27 Efficient and scalable parametric stereo coding for low bitrate audio coding applications
US11/238,982 US8116460B2 (en) 2001-07-10 2005-09-28 Efficient and scalable parametric stereo coding for low bitrate audio coding applications
US12/496,926 US8081763B2 (en) 2001-07-10 2009-07-02 Efficient and scalable parametric stereo coding for low bitrate audio coding applications
US12/610,193 US8243936B2 (en) 2001-07-10 2009-10-30 Efficient and scalable parametric stereo coding for low bitrate audio coding applications
US12/610,186 US8605911B2 (en) 2001-07-10 2009-10-30 Efficient and scalable parametric stereo coding for low bitrate audio coding applications
US13/458,492 US9218818B2 (en) 2001-07-10 2012-04-27 Efficient and scalable parametric stereo coding for low bitrate audio coding applications
US14/078,456 US20140074485A1 (en) 2001-07-10 2013-11-12 Efficient and scalable parametric stereo coding for low bitrate audio coding applications
US15/458,150 US9799341B2 (en) 2001-07-10 2017-03-14 Efficient and scalable parametric stereo coding for low bitrate applications
US15/458,135 US9799340B2 (en) 2001-07-10 2017-03-14 Efficient and scalable parametric stereo coding for low bitrate audio coding applications
US15/458,143 US9865271B2 (en) 2001-07-10 2017-03-14 Efficient and scalable parametric stereo coding for low bitrate applications
US15/458,126 US9792919B2 (en) 2001-07-10 2017-03-14 Efficient and scalable parametric stereo coding for low bitrate applications
US16/157,899 US10297261B2 (en) 2001-07-10 2018-10-11 Efficient and scalable parametric stereo coding for low bitrate audio coding applications
US16/399,705 US10540982B2 (en) 2001-07-10 2019-04-30 Efficient and scalable parametric stereo coding for low bitrate audio coding applications
US16/744,586 US10902859B2 (en) 2001-07-10 2020-01-16 Efficient and scalable parametric stereo coding for low bitrate audio coding applications
US17/155,372 US20210217425A1 (en) 2001-07-10 2021-01-22 Efficient and scalable parametric stereo coding for low bitrate audio coding applications

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SE0102481A SE0102481D0 (sv) 2001-07-10 2001-07-10 Parametric stereo coding for low bitrate applications
SE0200796A SE0200796D0 (sv) 2002-03-15 2002-03-15 Parametic Stereo Coding for Low Bitrate Applications
SE0200796-1 2002-03-15
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US11/237,133 Division US8073144B2 (en) 2001-07-10 2005-09-27 Stereo balance interpolation
US11/237,174 Division US8014534B2 (en) 2001-07-10 2005-09-27 Efficient and scalable parametric stereo coding for low bitrate audio coding applications
US11/237,127 Division US8059826B2 (en) 2001-07-10 2005-09-27 Efficient and scalable parametric stereo coding for low bitrate audio coding applications
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JP2009217290A (ja) 2009-09-24
JP2006085183A (ja) 2006-03-30
EP2015292B1 (en) 2009-09-23
CN1758338A (zh) 2006-04-12
JP4447317B2 (ja) 2010-04-07
CN101887724B (zh) 2012-05-30
EP1603118A3 (en) 2008-02-20
DE60236028D1 (de) 2010-05-27
ES2650715T3 (es) 2018-01-22
US8059826B2 (en) 2011-11-15
DE60206390D1 (de) 2005-11-03
US20060023891A1 (en) 2006-02-02
HK1080206A1 (en) 2006-04-21
JP2006074818A (ja) 2006-03-16
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EP1603118B1 (en) 2017-09-20
KR100666813B1 (ko) 2007-01-09
HK1080979A1 (en) 2006-05-04
PT1603118T (pt) 2017-12-22
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PT3104367T (pt) 2019-03-14

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