CN101039103A - 高效率功率调制器 - Google Patents

高效率功率调制器 Download PDF

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CN101039103A
CN101039103A CNA2007100858614A CN200710085861A CN101039103A CN 101039103 A CN101039103 A CN 101039103A CN A2007100858614 A CNA2007100858614 A CN A2007100858614A CN 200710085861 A CN200710085861 A CN 200710085861A CN 101039103 A CN101039103 A CN 101039103A
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signal
power
amount
modulators
input
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小伊尔·W·迈克库恩
温德尔·B·桑德尔
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Panasonic Holdings Corp
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Matsushita Electric Industrial Co Ltd
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    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03F—AMPLIFIERS
    • H03F1/00—Details of amplifiers with only discharge tubes, only semiconductor devices or only unspecified devices as amplifying elements
    • H03F1/32—Modifications of amplifiers to reduce non-linear distortion
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03F—AMPLIFIERS
    • H03F1/00—Details of amplifiers with only discharge tubes, only semiconductor devices or only unspecified devices as amplifying elements
    • H03F1/02—Modifications of amplifiers to raise the efficiency, e.g. gliding Class A stages, use of an auxiliary oscillation
    • H03F1/0205—Modifications of amplifiers to raise the efficiency, e.g. gliding Class A stages, use of an auxiliary oscillation in transistor amplifiers
    • H03F1/0211—Modifications of amplifiers to raise the efficiency, e.g. gliding Class A stages, use of an auxiliary oscillation in transistor amplifiers with control of the supply voltage or current
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03C—MODULATION
    • H03C5/00—Amplitude modulation and angle modulation produced simultaneously or at will by the same modulating signal
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03F—AMPLIFIERS
    • H03F1/00—Details of amplifiers with only discharge tubes, only semiconductor devices or only unspecified devices as amplifying elements
    • H03F1/32—Modifications of amplifiers to reduce non-linear distortion
    • H03F1/3241—Modifications of amplifiers to reduce non-linear distortion using predistortion circuits
    • H03F1/3247—Modifications of amplifiers to reduce non-linear distortion using predistortion circuits using feedback acting on predistortion circuits
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03F—AMPLIFIERS
    • H03F1/00—Details of amplifiers with only discharge tubes, only semiconductor devices or only unspecified devices as amplifying elements
    • H03F1/32—Modifications of amplifiers to reduce non-linear distortion
    • H03F1/3241—Modifications of amplifiers to reduce non-linear distortion using predistortion circuits
    • H03F1/3282—Acting on the phase and the amplitude of the input signal
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03F—AMPLIFIERS
    • H03F1/00—Details of amplifiers with only discharge tubes, only semiconductor devices or only unspecified devices as amplifying elements
    • H03F1/32—Modifications of amplifiers to reduce non-linear distortion
    • H03F1/3241—Modifications of amplifiers to reduce non-linear distortion using predistortion circuits
    • H03F1/3282—Acting on the phase and the amplitude of the input signal
    • H03F1/3288—Acting on the phase and the amplitude of the input signal to compensate phase shift as a function of the amplitude
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03F—AMPLIFIERS
    • H03F2200/00—Indexing scheme relating to amplifiers
    • H03F2200/207—A hybrid coupler being used as power measuring circuit at the output of an amplifier circuit
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03F—AMPLIFIERS
    • H03F2200/00—Indexing scheme relating to amplifiers
    • H03F2200/324—An amplitude modulator or demodulator being used in the amplifier circuit
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03F—AMPLIFIERS
    • H03F2200/00—Indexing scheme relating to amplifiers
    • H03F2200/451—Indexing scheme relating to amplifiers the amplifier being a radio frequency amplifier
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03F—AMPLIFIERS
    • H03F2200/00—Indexing scheme relating to amplifiers
    • H03F2200/504—Indexing scheme relating to amplifiers the supply voltage or current being continuously controlled by a controlling signal, e.g. the controlling signal of a transistor implemented as variable resistor in a supply path for, an IC-block showed amplifier

Abstract

本发明，一般地说，与作为用极性调制技术的调制器的基本组成部分的功率放大器相结合。这样，可以达到精确的信号产生(包括包络变化)和高能量效率的组合，这种组合以前是不可能的。根据本发明的一个实施例，被调制的无线电(带通)信号发生器产生一般类型的高质量的信号，这些高质量信号特别包括具有可变包络的信号。在将所加的DC功率变换成RF信号功率时以高能量效率产生信号。结果导致对于产品如移动电话手机具有较长的电池寿命。极大地改善了的效率也允许极大地减小(10到1或更多)无线电发射机需要的任何散热片的尺寸，这又极大地降低了价格和尺寸。而且，这些无线电发射机可以在用小的散热片或者甚至没有任何散热片元件，温度上升很小的情况下连续工作。由于允许较长的工作时间，这提供了高的工作可靠性以及较大的总处理能力。本发明的另一个方面允许产生具有宽频带的高质量信号，而不需要工作时的连续反馈。由于极大地简化了发射机电路的设计，制造和复杂性，这进一步降低了成本。

Description

高效率功率调制器
技术领域
本发明涉及无线电频率(RF)的功率放大器。
背景技术
在RF通信领域中，随着对更大的传输的总处理能力的希望和要求的不断增加，优先的信号必须显示出高的数据效率。一般地说，高数据效率的信号显示出包络变化的特性。这种包络变化信号一般需要线性电路工作。
在常规的无线电发射机中，调制器和功率放大器(PA)是分开工作的，如图1所示。调制器101将输入发射机的信息输入信号103变换成通常在无线电频率的带通信号105，该信号能够具有或者恒定的包络(平均信号功率等于峰值信号功率)或者变化的包络(平均信号功率小于峰值信号功率)。将带通信号105加到功率放大器(PA)107，功率放大器107产生输出信号109，它具有足够的功率以便辐射希望的距离。在无线电技术中一般我们知道只支持恒定包络信号的电路比支持包络变化信号的电路固有地具有较高的能量效率，这是因为包络变化信号需要线性电路性能。因为包络变化信号是更普遍的，所以本揭示集中在这些信号的产生上。
我们广泛地认识到希望的联合线性工作和高能量效率的目的是相互排斥的，即，具有高能量效率的放大器不以线性方式工作，而类似地以线性方式工作的放大器不显示出高的能量效率。
因为历史上已经证明改善线性放大器的能量效率(到50％或更高)基本上不可能的，所以最大的努力集中在用较高效率的非线性放大器并改善它的线性。这些方法包括前馈线性化，预畸变，反馈预畸变和调制器反馈。我们简略地将这些方法总结如下。
在图2表示的前馈线性化方法中，首先使PA207特征化以便使它将产生的信号发生某些畸变。由前馈块211外部地产生这些畸变的逆，然后与来自PA的输出209相加，以便形成线性化的输出信号215。这应该消除来自PA本身的畸变，导致改善的线性工作。
在图3表示的预畸变方法中，再次首先使PA307特征化以便使它将产生的信号发生某些畸变。由预畸变块310产生这些畸变的逆，以便产生改变的带通信号305′，将该信号加到PA的输入端。PA应该消除来自预畸变器的畸变，导致改善的线性工作。
在图4表示的反馈预畸变方法中，再次首先使PA特征化以便使它将产生的信号发生某些畸变。从外部产生这些畸变的逆，然后加到PA的输入端。PA应该消除来自预畸变器的畸变，导致改善的线性工作。在PA的输出端读出在预畸变中的任何误差，以信号412的形式反馈并用于校正预畸变器。用在这中技术中的预畸变块410′通常称为自适应预畸变器。
近来开始对将PA周围连续的反馈送回到调制器，使得能够连续地校正PA误差的研究投入一些努力。如图5所示，这是自适应预畸变器方法的延伸，其中在调制器501′内包括预畸变器功能。因为这是反馈技术，所以特别关心反馈环(它包括反馈信号512′)的稳定性。通过在反馈环中包括已知的非线性部件(PA)更加促使要保持反馈环的稳定性。此外，信号调制的可允许带宽受到反馈环动力学的限制。这种技术的一个例子是组合模拟锁定环通用调制器(CALLUM)，在D.J.Jennings，J.P.McGeehan，“A high-efficiency RF transmitter using VCO derived synthesis：CALLUM”，Proceedings of the 1998IEEE Radio and Wireless Conference(RAWCON)，August 1998，pp.137-140中对它作了描述。
LINC技术(D.C.Cox，“Linear Amplification with NonlinearComponents”，IEEE Transactions on Communications，vol.COM-23，Dec.1974，pp.1942-5)是一种放大器方法，它用一个由用于放大包络变化信号的多个非放大器组合构成的LINC放大器607′，如图6所示。关键是将一个任意的带通(无线电)信号表示为2个恒定包络相位调制信号的矢量和。在高效率非线性放大器中放大这2个恒定包络信号，将这2个放大器中的每一个都设计成能够提供所要的输出峰值功率的一半，然后将它们组合起来(通常在一个无源网络中)以便产生最后的输出信号。当输出信号的值低时，这个组合器必须内部地消耗来自这2个非线性PA的输出功率。于是，LINC技术失去了单个非线性放大器的固有效率中的大部分。
现有的另一个放大包络变化信号同时具有高能量效率的方法是包络消除和恢复(EER)，在D.K.Su，W.J.McFarland，“An IC for LinearingRF Power Amplifiers Using Envelope Elimination and Restoration”，IEEEJournal of Solid-State Circuits，Vol.33，Dec.1998，pp.2252-2258中对它进行了描述。EER技术与LINC技术相似，是在调制器后用一个分开的放大器，如图7所示。EER放大器709″必须首先从所加的输入信号对振幅变化进行解调，然后对输入信号进行限幅以便在非线性(优先地开关模式)放大器中放大。在最后输出级实现包络恢复。在围绕包络恢复过程经常使用一个反馈环以便使输出信号包络与来自输入信号的被测量的包络更紧密地匹配。当用任何反馈控制环时，环动力学限制了可以达到的调制带宽。
还有一个需要是为了能够产生具有适合于传输而同时显示出高的DC到RF变换效率的无线电通信信号。进一步，如此产生的信号质量必须总是满足严格的性能技术要求，如GSM-EDGE技术要求。
发明内容
本发明，一般地说，与作为用极性调制技术的调制器的基本组成部分的功率放大器相结合。这样，可以达到精确的信号产生(包括包络变化)和高能量效率的组合，这种组合以前是不可能的。根据本发明的一个实施例，被调制的无线电(带通)信号发生器产生一般类型的高质量的信号，这些高质量信号特别包括具有可变包络的信号。在将所加的DC功率变换成输出RF信号功率时以高能量效率产生信号。结果导致对于产品如移动电话手机具有较长的电池寿命。极大地改善了的效率也允许极大地减小(10到1或更多)无线电发射机需要的任何散热片的尺寸，这又极大地降低了价格和尺寸。而且，这些无线电发射机可以在用小的散热片或者甚至没有任何散热片元件，温度上升很小的情况下连续工作。由于允许较长的工作时间，这提供了高的工作可靠性以及较大的总处理能力。本发明的另一个方面允许产生具有宽频带的高质量信号，而不需要工作时的连续反馈。由于极大地简化了发射机电路的设计，制造和复杂性，这进一步降低了成本。
具体来说，本发明提供了一种RF功率调制器，包括：一个三端口功率放大器，它具有1个信号输入端，1个信号输出端和1个能够以被控制的方式进行变化的电源输入端；一个对信息输入作出响应的调制器驱动器，用于产生加到三端口功率放大器的信号输入端的输入信号和一个加到电源输入端的被控制的电源；其中在2个状态，即硬接通状态和硬断开状态之间重复驱动三端口功率放大器，同时使功率放大器在相当大的百分数的时间中不在线性工作区域内工作。
本发明还提供了一种RF功率调制器包括：一个具有一级或多级的功率放大器；一个调制器驱动器，用于接收信息信号并相应驱动功率放大器以便产生经过调制的RF输出信号；其中经过调制的RF输出信号首先存在于功率放大器的一级的输出端。
附图说明
我们从下面的描述结合所附诸图可以进一步了解本发明。其中：
图1是表示无线电发射机的标准结构的方框图。
图2是表示用于已知功率放大器(PA)的前馈线性器的方框图。
图3是表示用于使功率放大器线性化的常规的输入预畸变器的方框图。
图4是表示用于使功率放大器线性化的已知的反馈预畸变器的方框图。
图5是已知的用调制器反馈的功率放大器的方框图。
图6是用已知的LINC技术的放大器的方框图。
图7是用已知的EER放大器技术的放大器的方框图。
图8是表示功率放大器的三端口模式的方框图。
图9是根据本发明的一个实施例的具有PA校正测量的功率调制器的方框图。
图10是表示功率调制器的一个实施例的更多详细情况的方框图。
图11是用正交调制测绘仪的功率调制器的方框图。
图12是用正交调制测绘仪的功率调制器的另一个方框图。
具体实施方式
本发明的基础是满足所述目的的线性化，图1的标准结构是不够的。宁可需要包括PA作为调制器的基本部分。这意味着不仅是被调制的信号以所要的全传输功率存在于PA输出端的第1个位置，而且PA实际上必须实施部分调制。
为了达到这一点，重要的是知道任何PA实际上都是一个三端口器件，具有2个输入端口和1个输出端口。在表示放大器800的图8中画出了这个新的PA工作模式。每个输入端口都具有自己的到输出端口305的传递函数。进一步，2个传递函数可以是相关的或独立的，与功率放大器的设计等级有关。
例如，用线性等级A的PA，在电源端口和输出信号端口之间具有非常弱的关系，而在输入信号端口的数值和相位与输出信号端口的数值和相位(设计出的放大器的特征)之间具有很强的关系。在另一个极端，对于开关模式的PA如登等级E在输入信号端口的数值与输出信号端口的数值之间具有非常弱的关系。在输入信号端口的相位与输出信号端口的相位之间具有很强的关系，并在电源端口和输出信号端口的数值之间具有另一个很强的关系。
我们也注意到处于接近饱和或饱和的过激励线性放大器如等级A显示出非常类似于开关模式放大器的传递关系。本发明利用在电源端口和输出信号端口的数值之间的很强的关系，所以它优先地用非线性PA(开关模式或饱和的PA放大器优先，等级C到某种程度)工作。这自然地增加了整个系统的能量效率，其中这些非线性放大器是最大地能量有效的。
在电源端口和输出信号端口的数值之间的这种很强的关系被用于控制输出信号的数值。具有这种直接和独立地控制输出信号数值的能力，所以在极座标中考虑总的调制工作是自然的事。从广泛采用的笛卡尔座标的常规使用到正交调制器的使用，这是非常不同的。
本发明的一个优先实施例如图9所示。将信息输入903加到调制器驱动器901，调制器驱动器901驱动功率放大器907的2个输入端口(902，904)，使它产生希望的输出信号。选择地，可以测量输出信号以便从校正因子的表911恢复一个适当的校正因子。将校正因子加到调制器驱动器，校正信号输出。在实施了一次校正过程，其中观察了功率放大器的性能，并计算和存储了适当的校正因子后，每当用控制值控制功率放大器时，能够将相同的校正因子用于产生一个适当的控制值。
对于许多应用来说，因为振幅压缩(AM-AM)和交叉调制(AM-PM)的扰动很小，所以这个功率极性调制系统能够直接工作在前馈模式中。对于需要较大精度的应用，能够自动和独立地测量和存储这些小的扰动作为校正因子。然后将这些校正因子加到适当的直接的调制路径上，极性功率调制器连续工作在前馈方式中。
对这个校正方法有2个特别的贡献。第一，它不是一个闭环反馈系统，使得功率调制器能够达到的调制带宽不受这种反馈系统的环路动力学的限制。第二，系统的复杂性从现有的系统如CALLUM中所用的复杂性极大地减少了。这是由于在本发明中校正的独立性质：校正相位不影响输出信号数值，校正数值不影响输出信号相位。校正是一组2个一维过程。当信号数值和相位误差影响I和Q调制信号两者，它是二维过程时，这个情况与笛卡尔系统不同。我们清楚地懂得完成2个独立的一维过程要比完成1个二维经过校正的过程简单得多。
图10表示功率调制器的一个优先实施例。它应用极座标信号图(PSM)1021将信息输入变换成信号数值和相位。用于方形16QAM信号的PSM的一个例子如表1所示。使这些数值和相位通过时间对准(TA)块1023，使得在功率放大器(PA)中相位调制信号和数值控制信号的对准是精确的(考虑到在2条路径之间的延迟差)。使这些信号通过限带滤波器(BLF)1025a，1025b，以便控制输出信号的占有带宽。使数值BLF1025a的输出通过数值控制器1027以便设定输出信号的数值。这个方法类似于在WO00/48307中揭示的方法，这里通过参考将它结合进来。需要时，这里也能够包括对AM-AM畸变的校正。相位角BLF1025b的输出用于控制相位调制信号发生器1029(如在US5,952,895中所说的，这里通过参考将它结合进来)。将PM信号发生器的输出加到PA的RF输入端1002，以便设定输出信号的相位。需要时，这里也能够包括对AM-PM畸变的校正。
为了产生精确的信号，需要校正PA中的交叉调制(AM-PM畸变)和数值压缩(AM-AM畸变)。因为这些两个影响都与实际输出信号的数值有关，所以一个推荐的校正过程应是：1)用固定(恒定)相位调制产生加到PA输入端的信号，2)将这个信号加到PA上，3)将输出数值设定在它的最大值，4)用相位角测量块1031测量PA输出信号的实际相位，相位角测量块1031优先地是一个简单的如WO99/18691揭示的装置，这里通过参考将它结合进来，5)用数值测量块1033如探测器二极管或探测对数放大器，测量PA输出信号的实际数值，6)将测得的相位角和数值存储在存储器1011中，7)降低数值控制，和8)重复测量和存储过程。
表1：对于方形16QAM的极座标信号图
标号     数值     相位(度)        标号     数值     相位(度)
0        0.333    45.0            8        0.333    135
1        0.745    71.6            9        0.745    108.4
2        0.333    -45.0           A        0.333    -135.0
3        0.745    -71.6           B        0.745    -108.4
4        0.745    18.4            C        0.745    161.6
5        1.000    45.0            D        1.000    135.0
6        0.745    -18.4           E        0.745    -161.6
7        1.000    -45.0           F        1.000    -135.0
虽然用极性技术是优先实施例，但是本发明与常规的信号图是兼容的。这表示在图11中，用正交座标的与表1等效的信号图表示在表2中。代替极座标信号图，用直角座标信号图1122。直角座标到极座标的变换器1126用于将最后得到的I，Q信号变换成极座标形式。
表2：对于方形16QAM的笛卡尔信号图
标号     x        y            标号     x         y
0        0.236    0.236        8        -0.236    0.236
1        0.236    0.707        9        -0.236    0.707
2        0.236    -0.236       A        -0.236    -0.236
3        0.236    -0.707       B        -0.236    -0.707
4        0.707    0.236        C        -0.707    0.236
5        0.707    0.707        D        -0.707    0.707
6        0.707    -0.236       E        -0.707    -0.236
7        0.707    -0.707       F        -0.707    -0.707
进一步，能够用正交调制器产生相位调制信号。这如图12所示。代替直角座标到极座标的变换器，用直角座标到数值的变换器1227产生用于数值控器1227的数值信号。正交相位调制信号发生器1229直接用I，Q信号。尽管可以用数值测量块1233和校正表1211实施幅度校正，但是用了正交相位调制信号发生器1229，图11的直接的相位校正特性不再可能了。由于在正交调制器中精确的相位控制是困难的，以及正交调制器独立调整它的输出信号的相位时经常出现不稳定性，当需要AM-PM校正时通常不用这个选择。
那些普通的熟练的技术人员将估计到本发明能够以其它的特别形式体现出来，而没有偏离它的精神和基本特征。所以从所有方面来说我们认为现在揭示的实施例是说明性的和不是限制性的。由所附权利要求书而不是由上面的描述指定本发明的范围，我们有意将在本发明的等效物的意义和范围内发生的所有变化都包括在本发明中。

Claims (9)

1、一种RF功率调制器，包括：
三端口功率放大器，具有信号输入端、信号输出端以及电源输入端；
调制器驱动器，其响应于信息输入，产生施加给所述三端口功率放大器的信号输入端的输入信号以及施加给所述电源输入端的受控电源，其中所述调制器驱动器包括：信号图，其响应于信息信号，产生至少第一量与第二量；相位调制信号发生器，其响应上述量中的至少一个，产生所述三端口功率放大器的输入信号；以及幅度控制器，其响应于上述量中的至少一个，产生所述受控电源；
校准电路，用于产生从对所述三端口功率放大器的输出信号的至少一个特性的测量中导出的校正因子，该校正因子施加给所述调制器驱动器，从而引起所述输入信号与所述受控电源中的至少一个改变；
其中所述调制器驱动器与所述校准电路针对RF输出信号以开环方式运行。
2、如权利要求1所述的功率调制器，其中所述信号图是极坐标信号图，并且所述量包括幅度量和角度量。
3、如权利要求1所述的功率调制器，其中所述信号图是直角坐标信号图，进一步包括执行直角坐标至极坐标变换的装置，由此产生幅度量和角度量。
4、如权利要求1所述的功率调制器，其中所述第一量与第二量是I和Q信号，并且所述相位调制信号发生器响应于所述I、Q信号产生所述输入信号。
5、如权利要求2所述的功率调制器，进一步包括时间调校装置，用于使所述幅度量和角度量彼此按规定的时间调校发生。
6、如权利要求2所述的功率调制器，进一步包括处于所述幅度量的信号路径中的第一限带滤波器和处于所述角度量的信号路径中的第二限带滤波器。
7、如权利要求1所述的功率调制器，进一步包括第一与第二校准环路，每个环路包括用于测量所述三端口功率放大器的输出信号的至少一个特性的装置。
8、如权利要求7所述的功率调制器，其中一个校准环路执行角度校准，而另一个校准环路执行幅度校准。
9、如权利要求8所述的功率调制器，其中用于执行角度校准的校准环路包括直接数字相位量化器。
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