WO2018167981A1 - Dispositif de commande d'onduleur et procédé de commande d'onduleur - Google Patents

Dispositif de commande d'onduleur et procédé de commande d'onduleur Download PDF

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Publication number
WO2018167981A1
WO2018167981A1 PCT/JP2017/011056 JP2017011056W WO2018167981A1 WO 2018167981 A1 WO2018167981 A1 WO 2018167981A1 JP 2017011056 W JP2017011056 W JP 2017011056W WO 2018167981 A1 WO2018167981 A1 WO 2018167981A1
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Prior art keywords
output
phase
output voltage
inverter
time correction
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PCT/JP2017/011056
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English (en)
Japanese (ja)
Inventor
照佳 村松
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三菱電機株式会社
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Priority to PCT/JP2017/011056 priority Critical patent/WO2018167981A1/fr
Priority to JP2019505676A priority patent/JP6647448B2/ja
Publication of WO2018167981A1 publication Critical patent/WO2018167981A1/fr

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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
    • H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
    • H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P27/00—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage
    • H02P27/04—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage
    • H02P27/06—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage using dc to ac converters or inverters
    • H02P27/08—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage using dc to ac converters or inverters with pulse width modulation

Definitions

  • the present invention relates to a pulse width modulation type inverter control device and an inverter control method for driving a synchronous motor.
  • PWM pulse width modulation
  • the output time of each phase may be smaller than the minimum output time that allows current detection. In this case, it is not possible to detect a phase current whose output time is shorter than the minimum output time during which current can be detected. As a result, the current can be detected only for one phase or the current cannot be detected for one phase, and the PWM inverter control cannot be performed.
  • the present invention has been made in view of the above, and an object of the present invention is to obtain an inverter control device that enables stable inverter control regardless of the combination of the motor speed and the carrier frequency.
  • the present invention provides a direct current that supplies direct current power to an inverter in an inverter control device that controls an inverter that drives a motor based on a carrier signal and a timer value of each phase.
  • the phase current calculation means for calculating the AC current of each phase
  • the motor rotation speed calculation means for calculating the motor rotation speed from the AC current of each phase
  • the output time Ti per half of the pulse width modulation period of two basic voltage vectors of non-zero magnitude adjacent to the sector of Vs and the output voltage vector Vs.
  • Vs calculating means for calculating Tk and Tk, and an average vector of the output voltage vectors Vs ′ and Vs ′′ is equal to the output voltage vector Vs, and half the pulse width modulation period of two basic voltage vectors adjacent to the output voltage vector Vs ′ Vs ′ and Vs ′′ calculating means for calculating the output voltage vectors Vs ′ and Vs ′′ so that each of the hit output times is equal to or longer than the required output time.
  • the present invention includes the frequency of the carrier signal and the motor rotation.
  • Output time correction control execution determining means for determining whether or not to execute output time correction control based on the number and output times Ti and Tk, and determining that the output time correction control execution determination means executes the output time correction control
  • the first half of the pulse width modulation period is the output voltage vector Vs ′
  • the second half of the pulse width modulation period is the output voltage vector Vs ′′.
  • the output time correction control execution determination means determines that the output time correction control is not executed, the output voltage vector Vs is set to both in the first half and the second half of the pulse width modulation period.
  • Timer value calculating means for obtaining a timer value of each phase is further provided.
  • the inverter control device has an effect that stable inverter control is possible regardless of the combination of the motor speed and the carrier frequency.
  • FIG. 3 is a diagram for explaining a relationship between a basic voltage vector and a sector according to the first embodiment; 6 is a flowchart for explaining the operation of the output time correction control execution determination unit according to the first embodiment.
  • Vector diagram of output voltage vector in the case of FIG. The figure which shows the motor current waveform of the U phase when output time correction control is performed even if it is a case where the inverter control apparatus concerning Embodiment 1 satisfy
  • FIG. 1 is a block diagram showing a configuration of a microcomputer according to a first embodiment.
  • FIG. 1 is a diagram illustrating a configuration of an inverter control device 100 according to the first embodiment of the present invention.
  • the inverter control device 100 controls the inverter 1 that drives the motor 2 that is a synchronous motor.
  • Motor 2 is a three-phase motor.
  • the inverter control device 100 includes a phase current calculation unit 4, a motor rotation number calculation unit 5, a ⁇ - ⁇ axis voltage calculation unit 6, a Vs calculation unit 7, a carrier frequency setting unit 8, and an output time correction control execution determination.
  • Vs ′ and Vs ′′ calculating means 10 Means 9, Vs ′ and Vs ′′ calculating means 10, timer value calculating means 11, and drive signal generating means 12, and DC bus 13 for supplying DC power from power supply 14 to inverter 1
  • Current detection means 3 is provided, and the current detection means 3 detects a direct current for each of a plurality of phases flowing through the motor 2.
  • FIG. 2 is a diagram illustrating a configuration of the inverter 1 and the motor 2 according to the first embodiment.
  • the inverter 1 is a three-phase inverter.
  • the inverter 1 includes switching elements SW1 and SW4 corresponding to the U phase, switching elements SW2 and SW5 corresponding to the V phase, and switching elements SW3 and SW6 corresponding to the W phase.
  • Switching elements SW1 to SW3 are upper arm side switching elements, and switching elements SW4 to SW6 are lower arm side switching elements.
  • Switching elements SW1 and SW4 are connected via terminal 101, switching elements SW2 and SW5 are connected via terminal 102, and switching elements SW3 and SW6 are connected via terminal 103.
  • the terminal connected to the coil corresponding to the U phase of the motor 2 is connected to the terminal 101 of the inverter 1, and the terminal connected to the coil corresponding to the V phase of the motor 2 is connected to the terminal 102 of the inverter 1, The terminal connected to the coil corresponding to the W phase of the motor 2 is connected to the terminal 103 of the inverter 1.
  • the phase current calculation unit 4 calculates three-phase AC currents Iu, Iv, and Iw that are AC currents of the respective phases from the DC current Idc detected by the current detection unit 3.
  • the motor rotation speed calculation means 5 calculates a q-axis current by dq conversion from the three-phase AC currents Iu, Iv, and Iw obtained by the phase current calculation means 4, and calculates the motor from the calculated q-axis current AC component.
  • the rotational speed f is calculated.
  • the ⁇ - ⁇ -axis voltage calculation means 6 is a ⁇ -axis voltage command V ⁇ and a ⁇ -axis voltage command V ⁇ that are voltage command values for the ⁇ - ⁇ axes from the three-phase alternating currents Iu, Iv, Iw obtained by the phase current calculation means 4. And the phase ⁇ are calculated.
  • the ⁇ - ⁇ axis is a rotational coordinate system assumed on the stator of the motor 2.
  • the phase ⁇ is an angle in the rotational coordinate system from the U phase of the stator of the motor 2 to the ⁇ axis.
  • the U phase of the stator of the motor 2 corresponds to a basic voltage vector V1 described later.
  • the Vs calculation means 7 is adjacent to the sector SCT_Vs of the output voltage vector Vs and the output voltage vector Vs based on the ⁇ -axis voltage command V ⁇ , the ⁇ -axis voltage command V ⁇ and the phase ⁇ calculated by the ⁇ - ⁇ -axis voltage calculation means 6.
  • the output times Ti and Tk per 1/2 PWM period of two basic voltage vectors whose magnitudes are non-zero are calculated.
  • Perfect 1/2 PWM cycle means a value in units of 1/2 PWM cycle, which is half of the pulse width modulation cycle. SCT_Vs, output times Ti and Tk will be described below with reference to FIG.
  • FIG. 3 is a diagram for explaining the relationship between the basic voltage vector and the sector according to the first embodiment.
  • the basic voltage vectors V1 to V6 correspond to the switching states of the switching elements SW1 to SW6 of the inverter 1.
  • (1, 0, 0) indicating the basic voltage vector V1 indicates that the switching elements SW1, SW5, and SW6 of the inverter 1 are in the ON state and the switching elements SW2, SW3, and SW4 are in the OFF state. That is, “1” when the upper arm side switching element is ON and the lower arm side switching element is OFF in each of the U phase, V phase, and W phase, and the upper arm side switching element is OFF.
  • “0” is shown in order. Therefore, (1, 1, 0) indicating the basic voltage vector V2 indicates that the switching elements SW1, SW2, and SW6 of the inverter 1 are in the ON state and the switching elements SW3, SW4, and SW5 are in the OFF state.
  • the carrier frequency setting means 8 outputs the carrier frequency fc, which is a preset frequency of the carrier signal, to the output time correction control execution determination means 9 and the drive signal generation means 12.
  • the output time correction control execution determination means 9 outputs the output time from the motor rotation speed f calculated by the motor rotation speed calculation means 5, Ti and Tk calculated by the Vs calculation means 7, and a preset carrier frequency fc. It is determined whether or not correction control is executed.
  • the Vs ′ and Vs ′′ calculation means 10 is based on the required output time TMIN which is the minimum output time required for the current detection means 3 to detect any of the Ti and Tk calculated by the Vs calculation means 7.
  • TMIN the required output time required for the current detection means 3 to detect any of the Ti and Tk calculated by the Vs calculation means 7.
  • the output time correction control is executed so that phase current information for two phases can be detected from the DC bus current during one PWM cycle.
  • Vs ′ and Vs ′′ calculating means 10 executes the output time correction control.
  • the output time correction control is executed based on the sector SCT_Vs, the output times Ti and Tk given from the Vs calculating means 7 via the determination means 9.
  • Vs ′ and Vs ′′ calculation means 10 calculates two basic voltages whose average vectors of output voltage vectors Vs ′ and Vs ′′ are equal to output voltage vector Vs and whose magnitude is adjacent to output voltage vector Vs ′.
  • the output voltage vectors Vs ′ and Vs ′′ are calculated so that each of the output times per 1/2 PWM period of the vector is equal to or greater than a predetermined required output time TMIN.
  • the output voltage vector Vs ′ is calculated in the first half of the PWM period.
  • the output voltage vector Vs ′′ is applied in the second half of the PWM period.
  • the Vs ′ and Vs ′′ calculating means 10 per sector SCT_Vs ′ of the output voltage vector Vs ′ satisfying the above conditions and the 1 ⁇ 2 PWM period of the basic voltage vector adjacent to the output voltage vector Vs ′.
  • a specific example of a detailed calculation method of the Vs ′ and Vs ′′ calculation means 10 may be a known method such as the method described in Patent Document 1.
  • the timer value calculation means 11 When the output time correction control is executed, the timer value calculation means 11 outputs the sector SCT_Vs ′ calculated by the calculation means 10, the output times Ti ′ and Tk ′, the sector SCT_Vs ′′, and the output time. Timer values U_TIM, V_TIM, and W_TIM for each of the U phase, V phase, and W phase are calculated so as to satisfy Ti ′′ and Tk ′′. Specifically, the sector SCT_Vs ′, the output times Ti ′ and Tk ′, and the sector SCT_Vs ′′ are set such that the first half of the PWM cycle is the output voltage vector Vs ′ and the second half of the PWM cycle is the output voltage vector Vs ′′. Based on the output times Ti ′′ and Tk ′′, the timer value calculation means 11 calculates the timer values U_TIM, V_TIM, W_TIM of each phase.
  • the timer value calculation unit 11 When the output time correction control is not executed, the timer value calculation unit 11 satisfies the sector SCT_Vs and the output times Ti and Tk given from the Vs calculation unit 7 via the output time correction control execution determination unit 9. In addition, timer values U_TIM, V_TIM, and W_TIM for each phase are calculated. Specifically, the timer value calculation means 11 calculates the timer values U_TIM, V_TIM, W_TIM of each phase based on the sector SCT_Vs and the output times Ti and Tk so that both the first half and the second half of the PWM cycle become the output voltage vector Vs. Is calculated.
  • a specific method for calculating the timer values U_TIM, V_TIM, and W_TIM of each phase by the timer value calculation unit 11 is a known method such as the method described in Patent Document 1. It doesn't matter.
  • the drive signal generation unit 12 generates a PWM drive signal by comparing the carrier signal of the carrier frequency fc and the timer values U_TIM, V_TIM, and W_TIM calculated by the timer value calculation unit 11 and outputs them to the inverter 1. To do.
  • a specific example of a method for generating a PWM drive signal using the timer values U_TIM, V_TIM, and W_TIM of each phase may be a known method such as the method described in Patent Document 1.
  • FIG. 4 is a flowchart for explaining the operation of the output time correction control execution determination unit 9 according to the first embodiment.
  • the output times Ti and Tk calculated by the Vs calculating means 7 and the required output times TMIN and TMIN which are half the minimum output times required for detecting the direct current are obtained.
  • the output time correction control execution determination means 9 executes case classification in 11 cases of case 0 to case 10 as follows (step S1).
  • the output time correction control execution determination means 9 determines whether or not the output times Ti and Tk correspond to case 0 (step S2). When the output times Ti and Tk correspond to case 0 (step S2: Yes), the output time correction control execution determination unit 9 determines that the current for two phases can be detected, and the inverter control device 100 corrects the output time. Control is not executed (step S5). That is, the timer value calculator 11 calculates the timer values U_TIM, V_TIM, and W_TIM of each phase so that the sector SCT_Vs and the output times Ti and Tk calculated by the Vs calculator 7 are satisfied. When the output times Ti and Tk do not correspond to case 0 (step S2: No), the output time correction control execution determination unit 9 proceeds to step S3.
  • step S3 the output time correction control execution determination unit 9 determines whether or not the combination of the carrier frequency fc and the motor rotation speed f satisfying the conditions in which case1, case2, case3, and case7 exist.
  • FIG. 5 is a diagram illustrating a relationship between the motor current and the carrier signal according to the first embodiment.
  • FIG. 6 is a vector diagram of an output voltage vector in the case of FIG.
  • the number of carrier periods included in one electrical angle period is obtained by fc ⁇ (f ⁇ number of pole pairs).
  • the carrier period is the period of the carrier signal.
  • the above combination is applied in the case of a three-phase inverter.
  • the combination of the carrier frequency fc that satisfies the condition and the motor rotation speed f may be any combination that synchronizes with the common divisor of 60 deg whose carrier cycle is an electrical angle.
  • the inverter 1 is a three-phase inverter
  • the number of phases of inverter 1 may be different from 3. If the combination of the motor rotation speed f and the carrier frequency fc is such that the carrier period is synchronized with the common divisor of the electrical angle (360 ⁇ inverter phase ⁇ 2) deg, case 1 can only detect current for one phase.
  • the state can be any of case2, case3, and case7. Therefore, in step S3, it is determined whether or not the motor rotation speed f and the carrier frequency fc satisfy the condition that the carrier period is synchronized with the common divisor of the electrical angle (360 ⁇ inverter phase ⁇ 2) deg. What is necessary is just to judge.
  • the inverter control device 100 executes the output time correction control (step S3). S6). That is, the timer value calculation unit 11 satisfies the sector SCT_Vs ′ calculated by the Vs ′ and Vs ′′ calculation unit 10, the output times Ti ′ and Tk ′, the sector SCT_Vs ′′, and the output times Ti ′′ and Tk ′′. As described above, the timer value calculation means 11 calculates the timer values U_TIM, V_TIM, and W_TIM of the U phase, V phase, and W phase.
  • step S3 If the output time correction control execution determination unit 9 determines that the combination of the carrier frequency fc and the motor speed f satisfies the conditions (step S3: Yes), the process proceeds to step S4.
  • step S4 the output time correction control execution determination means 9 determines whether or not the output times Ti and Tk calculated by the Vs calculation means 7 satisfy a predetermined condition.
  • the predetermined condition may be case1, case2, case3, and case7 in which only one phase of current can be detected in a 1/2 PWM cycle.
  • the predetermined conditions for the output times Ti and Tk in step S4 may be limited to case 2 and case 7 in which the output voltage phase is greatly shaken when the output time correction control is executed.
  • a plurality of states may be selected from case1, case2, case3, and case7, and the predetermined conditions for the output times Ti and Tk may be set.
  • step S4 If the output time correction control execution determination means 9 determines that the output times Ti and Tk satisfy the predetermined conditions (step S4: Yes), the inverter control device 100 does not execute the output time correction control (step S5). Further, when the output time correction control execution determining means 9 determines that the output times Ti and Tk do not satisfy the predetermined condition (step S4: No), the inverter control device 100 executes the output time correction control (step S4). S6).
  • FIG. 7 is a diagram illustrating a U-phase motor current waveform when the output time correction control is executed even when the inverter control device 100 according to the first embodiment satisfies a predetermined condition.
  • FIG. 8 is a diagram illustrating a U-phase motor current waveform when the output time correction control is not executed when the inverter control device 100 according to the first embodiment satisfies a predetermined condition. 7 and 8, the horizontal axis is time, and the vertical axis is motor current. FIG.
  • Fig. 5 shows a U-phase motor current waveform when the output time correction control is executed. That is, FIG. 7 differs from FIG. 4 in the case where it is determined in step S4 of FIG. 4 that the output times Ti and Tk satisfy predetermined conditions (step S4: Yes). The situation when time correction control is executed is shown.
  • FIG. 8 shows a case where the inverter control device 100 does not execute the output time correction control according to the flowchart of FIG. 4 in the case 2 or case 7 (step S4: Yes) under the same conditions as FIG.
  • the U-phase motor current waveform in step S5) is shown.
  • the inverter 1 is a three-phase inverter
  • the number of poles of the motor 2 is 6
  • the carrier frequency fc 4.5 kHz
  • the motor rotation speed f 125 rp
  • the total number of times of current detection per one electrical angle cycle is 12 times.
  • six times is a state in which current can be detected only for one phase. In all of these cases, if correction control is executed for the output time, the voltage phase may increase and control may become unstable.
  • the inverter control device 100 has the carrier frequency fc and the motor rotation that satisfy the condition that the current can be detected only in one phase regardless of the modulation rate in the 1/2 PWM period. In the case of a combination with the number f, control instability can be suppressed by not correcting the output time. Furthermore, the inverter control device 100 according to the first embodiment is a combination of the carrier frequency fc and the motor rotation speed f that satisfy the above conditions, and the output times Ti and Tk satisfy further predetermined conditions. In addition, the output time may not be corrected.
  • An example of a device on which the inverter control device 100 according to the first embodiment is mounted is an air conditioner or a refrigerator.
  • the inverter control device 100 can control an inverter control board that drives a compressor motor or a fan motor mounted thereon.
  • the inverter control device 100 By installing the inverter control device 100 in an air conditioner or refrigerator, it is possible to expand the operating range, improve the operation quality, and prevent the noise or vibration of the compressor motor or fan motor due to current pulsation. A high air conditioner or refrigerator can be realized.
  • the inverter control device 100 is specifically realized by a microcomputer or the like.
  • FIG. 9 is a block diagram of the configuration of the microcomputer 200 according to the first embodiment.
  • the function of each means of the inverter control device 100 is realized by the microcomputer 200 having the configuration as shown in FIG.
  • the microcomputer 200 includes a CPU (Central Processing Unit) 201 that executes calculation and control, a RAM (Random Access Memory) 202 that the CPU 201 uses as a work area, a ROM (Read Only Memory) 203 that stores programs and data, It includes an I / O (Input / Output) 204 that is hardware for exchanging signals with the outside, and a peripheral device 205 including an oscillator that generates a clock.
  • the inverter control method described above performed by the inverter control device 100 is realized by the CPU 201 executing a program stored in the ROM 203.
  • the configuration described in the above embodiment shows an example of the contents of the present invention, and can be combined with another known technique, and can be combined with other configurations without departing from the gist of the present invention. It is also possible to omit or change the part.

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Inverter Devices (AREA)
  • Control Of Ac Motors In General (AREA)

Abstract

Cette invention concerne un dispositif de commande d'onduleur (100) pour commander un onduleur (1) pour entraîner un moteur (2), comprenant : des moyens de calcul de vitesse de rotation de moteur (5) pour calculer une vitesse de rotation de moteur ; des moyens de calcul de Vs (7) pour calculer le secteur d'un vecteur de tension de sortie Vs et des temps de sortie Ti et Tk par demi-cycle de modulation de largeur d'impulsion de deux vecteurs de tension fondamentaux adjacents au vecteur de tension de sortie Vs et ayant une grandeur non nulle ; des moyens de calcul de Vs' et Vs" (10) pour calculer des vecteurs de tension de sortie Vs' et Vs" ; des moyens de détermination d'exécution de commande de correction de temps de sortie (9) pour déterminer, sur la base de la fréquence d'un signal de porteuse, de la vitesse de rotation de moteur et des temps de sortie Ti et Tk, si une commande de correction de temps de sortie est exécutée ou non ; et des moyens de calcul de valeur de temporisateur (11) pour, lorsque les moyens de détermination d'exécution de commande de correction de temps de sortie (9) déterminent que la commande de correction de temps de sortie n'est pas exécutée, obtenir la valeur de temporisateur de chaque phase de telle sorte que le vecteur de tension de sortie Vs soit appliqué à la fois à la première et à la seconde moitié du cycle de modulation de largeur d'impulsion.
PCT/JP2017/011056 2017-03-17 2017-03-17 Dispositif de commande d'onduleur et procédé de commande d'onduleur WO2018167981A1 (fr)

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PCT/JP2017/011056 WO2018167981A1 (fr) 2017-03-17 2017-03-17 Dispositif de commande d'onduleur et procédé de commande d'onduleur
JP2019505676A JP6647448B2 (ja) 2017-03-17 2017-03-17 インバーター制御装置およびインバーター制御方法

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Cited By (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN114400911A (zh) * 2022-01-25 2022-04-26 燕山大学 三相电流源型变换器直流侧电流纹波抑制细分调制方法

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Publication number Priority date Publication date Assignee Title
JPH114594A (ja) * 1996-03-28 1999-01-06 Schneider Electric Sa 交流電動機用周波数変換器
JP2003209976A (ja) * 2002-01-11 2003-07-25 Matsushita Electric Ind Co Ltd Ｐｗｍインバータ装置及びその電流検出方法
JP2011234428A (ja) * 2010-04-23 2011-11-17 Mitsubishi Electric Corp ３相電圧型ｐｗｍインバータ制御装置
JP2012157103A (ja) * 2011-01-24 2012-08-16 Mitsubishi Electric Corp インバータ装置、ファン駆動装置、圧縮機駆動装置および空気調和機
WO2017022084A1 (fr) * 2015-08-04 2017-02-09 三菱電機株式会社 Dispositif de commande d'onduleur et climatiseur
JP2017050974A (ja) * 2015-09-01 2017-03-09 株式会社安川電機 電力変換装置、制御装置および制御方法

Patent Citations (6)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JPH114594A (ja) * 1996-03-28 1999-01-06 Schneider Electric Sa 交流電動機用周波数変換器
JP2003209976A (ja) * 2002-01-11 2003-07-25 Matsushita Electric Ind Co Ltd Ｐｗｍインバータ装置及びその電流検出方法
JP2011234428A (ja) * 2010-04-23 2011-11-17 Mitsubishi Electric Corp ３相電圧型ｐｗｍインバータ制御装置
JP2012157103A (ja) * 2011-01-24 2012-08-16 Mitsubishi Electric Corp インバータ装置、ファン駆動装置、圧縮機駆動装置および空気調和機
WO2017022084A1 (fr) * 2015-08-04 2017-02-09 三菱電機株式会社 Dispositif de commande d'onduleur et climatiseur
JP2017050974A (ja) * 2015-09-01 2017-03-09 株式会社安川電機 電力変換装置、制御装置および制御方法

Cited By (2)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN114400911A (zh) * 2022-01-25 2022-04-26 燕山大学 三相电流源型变换器直流侧电流纹波抑制细分调制方法
CN114400911B (zh) * 2022-01-25 2022-08-16 燕山大学 三相电流源型变换器直流侧电流纹波抑制细分调制方法

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