WO2011086804A1 - 電力変換装置 - Google Patents
電力変換装置 Download PDFInfo
- Publication number
- WO2011086804A1 WO2011086804A1 PCT/JP2010/072545 JP2010072545W WO2011086804A1 WO 2011086804 A1 WO2011086804 A1 WO 2011086804A1 JP 2010072545 W JP2010072545 W JP 2010072545W WO 2011086804 A1 WO2011086804 A1 WO 2011086804A1
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- WIPO (PCT)
- Prior art keywords
- switching element
- power supply
- boot capacitor
- diode
- power
- Prior art date
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Classifications
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M5/00—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases
- H02M5/40—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc
- H02M5/42—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters
- H02M5/44—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters using discharge tubes or semiconductor devices to convert the intermediate dc into ac
- H02M5/453—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters using discharge tubes or semiconductor devices to convert the intermediate dc into ac using devices of a triode or transistor type requiring continuous application of a control signal
- H02M5/458—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters using discharge tubes or semiconductor devices to convert the intermediate dc into ac using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M5/4585—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters using discharge tubes or semiconductor devices to convert the intermediate dc into ac using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only having a rectifier with controlled elements
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/08—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters
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- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03K—PULSE TECHNIQUE
- H03K17/00—Electronic switching or gating, i.e. not by contact-making and –breaking
- H03K17/51—Electronic switching or gating, i.e. not by contact-making and –breaking characterised by the components used
- H03K17/56—Electronic switching or gating, i.e. not by contact-making and –breaking characterised by the components used by the use, as active elements, of semiconductor devices
- H03K17/687—Electronic switching or gating, i.e. not by contact-making and –breaking characterised by the components used by the use, as active elements, of semiconductor devices the devices being field-effect transistors
- H03K17/6871—Electronic switching or gating, i.e. not by contact-making and –breaking characterised by the components used by the use, as active elements, of semiconductor devices the devices being field-effect transistors the output circuit comprising more than one controlled field-effect transistor
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- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03K—PULSE TECHNIQUE
- H03K2217/00—Indexing scheme related to electronic switching or gating, i.e. not by contact-making or -breaking covered by H03K17/00
- H03K2217/0009—AC switches, i.e. delivering AC power to a load
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- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03K—PULSE TECHNIQUE
- H03K2217/00—Indexing scheme related to electronic switching or gating, i.e. not by contact-making or -breaking covered by H03K17/00
- H03K2217/0081—Power supply means, e.g. to the switch driver
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- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03K—PULSE TECHNIQUE
- H03K2217/00—Indexing scheme related to electronic switching or gating, i.e. not by contact-making or -breaking covered by H03K17/00
- H03K2217/009—Resonant driver circuits
Definitions
- the present invention relates to a power converter, and more particularly to an operating power supply for outputting a switch signal to a switching element.
- Patent Document 1 describes an inverter.
- the inverter has an upper switching element and a lower switching element connected in series between two DC power supply lines.
- a first internal control circuit for supplying a switch signal is connected to the upper switching element, and a second internal control circuit for supplying a switch signal is connected to the lower switching element.
- DC power is supplied to the second internal control circuit as operating power.
- a voltage across the capacitor is supplied to the first internal control circuit as an operating power source.
- a diode is connected between one end on the high potential side of the capacitor and one end on the high potential side of the DC power supply. The diode is placed with its anode facing the DC power supply.
- the capacitor is charged using a DC power source as a power source by conduction of the lower switching element.
- Patent Documents 2 and 3 are disclosed as techniques related to the present invention.
- Patent Document 1 does not consider the operating power supply of switching elements other than the switching elements of the inverter.
- the present invention provides a power conversion device that can obtain an operating power supply for a switching element other than an inverter from an operating power supply for the switching element of the inverter.
- a first aspect of a power conversion device includes a first power supply line (LH), a second power supply line (LL) to which a potential lower than that of the first power supply line is applied, and an output terminal.
- a first switching element (Ty1) provided between the output terminal and the first power supply line, and both ends for supporting a DC voltage between them, Power having one end on the potential side connected to the first switching element on the second power supply line side and a power supply unit (Cby1) serving as an operation power supply for outputting a switch signal to the first switching element A converter, a second switching element (Tx1, Tx2, S1) provided between the first and second power lines, and one end connected to the second switching element on the first power line side And the other end electrically connected to the other end of the power supply unit.
- the second switch is charged and charged.
- a boot capacitor (Cbx1, Cbx2, Cb1, Cbx) serving as an operation power supply for outputting a switch signal to the switching element, and the first power supply line from the other end of the power supply unit via the boot capacitor And diodes (Dbx1, Dbx2, Db1, Dbx) that flow current only in the direction from the power supply unit toward the boot capacitor.
- a second aspect of the power conversion device is the power conversion device according to the first aspect, in which the second power supply line (LH, LL) is connected between the first power supply line (LH, LL).
- a third switching element (Tx2) connected in series to the second switching element (Tx1) on the power supply line side; one end connected to the third switching element on the first power supply line side;
- a second boot capacitor (Cbx2) that is charged and serves as an operating power for outputting a switch signal to the third switching element, and the other end of the boot capacitor (Cbx1) or a power supply unit (Cby1 ) And the other end of the second boot capacitor, and further includes a second diode (Dbx2) provided with a cathode facing the second boot capacitor.
- a third aspect of the power conversion device according to the present invention is the power conversion device according to the first or second aspect, wherein the second switching element has a reverse blocking structure.
- a fourth aspect of the power converter according to the present invention is the power converter according to the first aspect, and is connected in series with the second switching element (Tx1) on the second power line (LL) side.
- the second diode (Dx1) provided with the anode directed toward the second power supply line is connected in series on the second power supply line side with respect to the series body of the second switching element and the second diode.
- An operating power supply having one end connected to the third switching element and the other end connected to the other end of the boot capacitor, and being charged and outputting a switch signal to the third switching element;
- the second boot capacitor (Cbx2) Provided.
- a fifth aspect of the power conversion device according to the present invention is the power conversion device according to the fourth aspect, wherein the third diode (Dx2) is connected to the third switching element (Tx2). Located on the power line (LL) side.
- a sixth aspect of the power conversion device according to the present invention is the power conversion device according to the first aspect, wherein the diode (Dx1) includes the second switching element (Tx) and the first power supply line (LH). ).
- a seventh aspect of the power conversion device is the power conversion device according to the first aspect, wherein a connection point between the second switching element (Tx1) and the boot capacitor (Cbx1) and the first A second diode (Dx1) provided between the power supply line, and the diode (Dbx1) is provided between the power supply unit (Cby1) and the connection point.
- An eighth aspect of the power converter according to the present invention is the power converter according to the first aspect, wherein the power converter is connected in series with the second switching element (Tx11), and the cathode is connected to the first power line.
- a second diode (Dx11) arranged toward (LH), a third switching element (Tx12), connected in series with the third switching element, and a cathode connected to the second power line (LL).
- a third diode (Dx12) arranged in parallel and connected in parallel with the series body of the second switching element and the second diode, and the second power line side And having one end connected to the third switching element and the other end connected to the other end of the boot capacitor (Cbx11) for charging and outputting a switch signal to the third switching element.
- the second boot controller that serves as the operating power for Further comprising a capacitor (Cbx12), between the boot capacitor and the second boot capacitor, a fourth diode which is disposed toward the cathode into the second boot capacitor and (D
- a ninth aspect of the power converter according to the present invention is the power converter according to the first aspect, wherein the power converter is connected in series with the second switching element (Tx11), and the cathode is connected to the first power line.
- a second power supply unit (Ed) serving as an operating power supply for outputting a switch signal to the four switching elements, one end connected to the third switching
- a power converter according to a tenth aspect of the present invention is the power converter according to the first aspect, wherein the power converter is connected to the second switching element (Tx11) on the first power line (LH) side.
- a third diode (Dx12) connected in parallel with the second switching element, and the boot capacitor is connected in common to a connection point of the second switching element and the third switching element, It functions as an operation power source for outputting a switch signal to the second switching element and the third switching element.
- An eleventh aspect of the power converter according to the present invention is the power converter according to any one of the first to fifth, eighth and ninth aspects, wherein the second switching elements (Tr1, Ts1, Tt1) A plurality of the second switching elements are directly connected to the first power supply line (LH), and the boot capacitor (Cbx1) includes at least two second switching elements of the plurality of second switching elements. It functions as an operation power source for outputting a switch signal to the switching element.
- a twelfth aspect of the power conversion device according to the present invention is the power conversion device according to any one of the first to eleventh aspects, wherein the power conversion unit converts the voltage of the power supply unit (Cby1).
- a voltage adjusting unit (VAy1) is further provided for reducing the voltage and functioning as an operation power supply for the first switching element (Ty1).
- a thirteenth aspect of a power conversion device is the power conversion device according to any one of the first to twelfth aspects, wherein the first switching element (Tu1, Tv1, Tw1) and the power supply There are a plurality of parts (Cbu1, Cbv1, Cbw1), and one ends of the plurality of power supply parts are respectively connected to the plurality of first switching elements on the second power supply line (LL) side, and the diodes (Dbx11 ) Is provided between the other end of one of the plurality of power supply units (Cbu1) and the other end of the boot capacitor (Cbx1), and the other end of the other one of the plurality of power supply units (Cbv1)
- a boot diode (Dbx12) provided with a cathode facing the boot capacitor is further provided between the other end of the boot capacitor.
- a fourteenth aspect of a power conversion device is the power conversion device according to any one of the first to twelfth aspects, wherein the first switching element (Tu1, Tv1, Tw1) and the power supply are provided.
- the first switching element (Tu1, Tv1, Tw1) and the power supply are provided.
- a fifteenth aspect of the power converter according to the present invention is the power converter according to any one of the first to fourteenth aspects, wherein the power supply unit is a third boot capacitor (Cby1), A fourth switching element (Ty2) provided between the output terminal and the second power supply line; one end connected to the fourth switching element on the second power supply line (LL) side; And a DC power supply (Ed) serving as an operation power supply for outputting a switch signal to the fourth switching element, and between the other end of the third boot capacitor and the other end of the DC power supply. And a diode (Dby1) provided with the anode facing the DC power supply side and the cathode facing the third boot capacitor side, respectively.
- the power supply unit is a third boot capacitor (Cby1), A fourth switching element (Ty2) provided between the output terminal and the second power supply line; one end connected to the fourth switching element on the second power supply line (LL) side;
- a DC power supply (Ed) serving as an operation power supply for outputting a switch signal to the fourth
- the boot capacitor is charged using the power supply unit as a power source.
- the operating power supply of the third switching element can be obtained from the operating power supply of the first switching element of the inverter.
- the third and fourth switching elements can be used as components of the current source converter.
- the second switching capacitor is charged by turning on the third switching element as compared with the case where the reverse blocking diode is connected in series with the third switching element.
- the voltage drop at the reverse blocking diode can be avoided.
- the second and third diodes exhibit reverse blocking capability for the third and fourth switching elements, respectively. Therefore, the third and fourth switching elements and the second and third diodes can function as components of the current source converter.
- the third switching element is made conductive, a current flows from the boot capacitor to the second boot capacitor via the second diode and the third switching element, so that the second boot capacitor can be charged.
- the second diode inhibits the second boot capacitor from discharging through the above path.
- the second diode can prevent the second boot capacitor from being discharged while exhibiting the reverse blocking ability as the current source converter. Therefore, the manufacturing cost can be reduced as compared with the case of providing individual diodes.
- the voltage across the second boot capacitor can be increased.
- the diode exhibits reverse blocking capability for the third switching element. Therefore, the diode and the third switching element can function as components of the current source converter. In addition, the diode inhibits the boot capacitor from discharging to the power supply unit side.
- the discharge of the boot capacitor can be prevented while the diode exhibits the reverse blocking ability as the current source converter. Therefore, the manufacturing cost can be reduced as compared with the case of providing individual diodes.
- the second and third switching elements and the second and third diodes constitute a bidirectional switching element.
- the second boot capacitor can be charged by turning on the second switching element. Since the boot capacitor and the second boot capacitor are respectively employed as the operation power sources for the second and third switching elements, the manufacturing cost can be reduced.
- the second and third switching elements and the second and third diodes constitute a bidirectional switching element.
- the second boot capacitor can be charged by conducting the bidirectional switching element. Since the boot capacitor and the second boot capacitor are respectively employed as the operation power sources for the second and third switching elements, the manufacturing cost can be reduced.
- the second and third switching elements and the second and third diodes constitute a bidirectional switching element.
- the manufacturing cost can be reduced as compared with the case where each is provided with a boot capacitor.
- the eleventh aspect of the power conversion device of the present invention since the first power supply line functions as a common potential line for the plurality of third switching elements, one boot capacitor serves as the operating power supply for the plurality of third switching elements. Even if it functions as, the variation in the potential of the operating voltage among the plurality of third switching elements can be reduced.
- the voltage across the boot capacitor is determined by the voltage of the power supply unit. Is also low.
- the voltage adjustment unit steps down the voltage of the power supply unit, the difference between the operating power supply of the first switching element and the operating power supply of the third switching element can be reduced.
- the voltage across the boot capacitor can be stabilized during normal operation.
- the boot capacitor is employed as the operation power supply for outputting the switch signal to the first switching element, so that compared to the case where the DC power supply is employed. Manufacturing cost can be reduced.
- FIG. 1 It is a figure which shows another example of a notional structure of a power converter device. It is a figure which shows another example of a notional structure of a converter and an inverter. It is a figure which shows another example of a notional structure of a converter and an inverter. It is a figure which shows another example of a notional structure of a converter and an inverter. It is a figure which shows another example of a notional structure of a converter and an inverter. It is a figure which shows another example of a notional structure of a converter and an inverter. It is a figure which shows another example of a notional structure of a converter and an inverter. It is a figure which shows another example of a notional structure of a converter and an inverter. It is a figure which shows another example of a notional structure of a converter and an inverter.
- the power conversion apparatus includes a converter 1, a clamp circuit 2, and an inverter 3 that are power conversion units as components thereof.
- the converter 1 is connected to input terminals Pr, Ps, and Pt.
- the converter 1 converts the three-phase AC voltage applied to the input terminals Pr, Ps, and Pt into a DC voltage and applies it to the DC power supply lines LH and LL.
- the converter 1 has switching legs for three r, s, and t phases.
- the r-phase switching leg has switching elements Tr1 and Tr2 and diodes Dr1 and Dr2.
- the s-phase switching leg includes switching elements Ts1 and Ts2 and diodes Ds1 and Ds2.
- the t-phase switching leg includes switching elements Tt1 and Tt2 and diodes Dt1 and Dt2. These three switching legs are connected in parallel between the DC power supply lines LH and LL.
- Switching elements Tx1, Tx2 are, for example, insulated gate bipolar transistors.
- the switching elements Tx1 and Tx2 have first to third electrodes.
- the switching elements Tx1 and Tx2 conduct / non-conduct a current flowing between the first electrode and the second electrode.
- a switch signal (voltage signal or current signal) for controlling conduction / non-conduction of the switching elements Tx1, Tx2 is applied to the third electrode.
- the first electrode also functions as a control reference electrode that serves as a reference for the switch signal (for example, a reference potential for a voltage signal).
- the first to third electrodes are an emitter electrode, a collector electrode, and a gate electrode, respectively. This point is also applied to other switching elements described later.
- the switching element Tx1 and the diode Dx1 are connected in series between the DC power supply line LH and the input terminal Px.
- the switching element Tx1 is disposed with its emitter electrode facing the DC power supply line LH, and the diode Dx1 is disposed with its anode facing the input terminal Px.
- the switching element Tx2 and the diode Dx2 are connected in series between the DC power supply line LL and the input terminal Px.
- the switching element Tx2 is arranged with its emitter electrode facing the input end Px, and the diode Dx2 is arranged with its anode facing the DC power supply line LL.
- a switching signal is given to the switching elements Tx1 and Tx2, and the converter 1 converts the three-phase AC voltage into a DC voltage. Thereby, a higher potential than the DC power supply line LL is applied to the DC power supply line LH.
- the diodes Dx1 and Dx2 exhibit reverse blocking ability as a converter. In other words, the converter 1 functions as a current source converter.
- the inverter 3 converts the DC voltage between the DC power supply lines LH and LL into an AC voltage and applies it to the load 4 (for example, a motor).
- the load 4 is drawn as an inductive load having a series body of a resistor and a reactor.
- the inverter 3 has switching legs for three u, v, and w phases.
- the u-phase switching leg includes switching elements Tu1 and Tu2 and diodes Du1 and Du2.
- the v-phase switching leg has switching elements Tv1, Tv2 and diodes Dv1, Dv2.
- the w-phase switching leg includes switching elements Tw1 and Tw2 and diodes Dw1 and Dw2. These three switching legs are connected in parallel between the DC power supply lines LH and LL.
- Switching elements Ty1, Ty2 are, for example, insulated gate bipolar transistors. Switching elements Ty1, Ty2 are connected in series between DC power supply lines LH, LL. All of the switching elements Ty1, Ty2 are arranged with the emitter electrode directed toward the DC power supply line LL. The diodes Dy1 and Dy2 are connected in parallel to the switching elements Ty1 and Ty2, respectively. All of the diodes Dy1 and Dy2 are arranged with the anode directed toward the DC power supply line LL.
- the output terminal Py provided between the switching elements Ty1 and Ty2 is connected to the load 4.
- a switching signal is given to the switching elements Ty1 and Ty2, and the inverter 3 converts a DC voltage into an AC voltage.
- Diodes Dy1 and Dy2 prevent reverse current from flowing to switching elements Ty1 and Ty2, respectively, and prevent reverse voltage from being applied to switching elements Ty1 and Ty2, respectively.
- the clamp circuit 2 includes a switching element S1, a diode D1, and a capacitor C1.
- the diode D1 and the capacitor C1 are connected in series between the DC power supply lines LH and LL.
- the diode D1 is arranged with its anode directed toward the DC power supply line LH.
- the switching element S1 is an insulated gate bipolar transistor, for example, and is connected in parallel to the diode D1.
- Switching element S1 is arranged with its emitter electrode facing DC power supply line LH.
- the regenerative energy from the inverter 3 can be absorbed by the capacitor C1.
- the clamp circuit 2 also has the effect of a snubber circuit that absorbs a voltage increase between the DC power supply lines LH and LL due to switching.
- the capacitor C1 is clamped to the maximum value of the voltage between the DC power supply lines LH and LL by the rectifying function of the diode D1, and if the switching element S1 is non-conductive, the voltage is supplied from the capacitor C1 to the inverter 3. None happen. Therefore, when the capacitor C1 is charged and the switching element S1 is non-conductive, the snubber clamp circuit 2 can be ignored equivalently. Therefore, the converter 1 and the inverter 3 can be made to function as a direct power conversion device in which the DC power supply lines LH and LL do not have power storage means such as a smoothing capacitor.
- the clamp circuit 2 is not an indispensable requirement, but an actual power converter has an inductance in the wiring, and is preferably provided.
- the converter 1 has drive circuits Drx1 and Drx2 that drive the switching elements Tx1 and Tx2, respectively, and the inverter 3 has drive circuits Dry1 and Dry2 that drive the switching elements Ty1 and Ty2, respectively.
- Drive circuits Drx1, Drx2, Dry1, Dry2 are connected to the gate electrodes of switching elements Tx1, Tx2, Ty1, Ty2, respectively.
- the drive circuit Dry2 is supplied with operating power from the DC power supply Ed.
- One end on the low potential side of the DC power supply Ed is connected to the emitter electrode of the switching element Ty2 and the drive circuit Dry2.
- One end on the high potential side of the DC power supply Ed is connected to the drive circuit Dry2.
- the voltage across the boot capacitor Cby1 is supplied to the drive circuit Dry1 as an operating power source.
- One end of the boot capacitor Cby1 is connected to the emitter electrode of the switching element Ty1 and the drive circuit Dry1.
- the other end of the boot capacitor Cby1 is connected to the drive circuit Dry1.
- This content can be grasped as that the boot capacitor Cby1 supports a DC voltage between the one end and the other end and functions as an operation power supply for outputting a switch signal to the switching element Ty1. This also applies to other boot capacitors.
- the other end of the boot capacitor Cby1 is connected to one end on the high potential side of the DC power supply Ed via the diode Dby1.
- the diode Dby1 is arranged with the anode directed toward the DC power supply Ed.
- the diode Dby1 prevents the boot capacitor Cby1 from being discharged to the DC power supply Ed side.
- the level shift circuit LSy1 is connected to the drive circuit Dry1 on the side opposite to the switching element Ty1.
- the level shift circuit LSy1 appropriately shifts the potential level of the switch signal generated by a common control circuit (not shown) in accordance with the potential of the drive circuit Dry1, and supplies this to the drive circuit Dry1.
- a common control circuit not shown
- level shift circuits connected to other drive circuits described later, and therefore detailed description thereof will be omitted below.
- Boot capacitor Cby1 is charged prior to normal operation of the power converter. Specifically, the boot capacitor Cby1 is charged by turning on the switching element Ty2. This is because the current flows through the series circuit A1 including the DC power supply Ed, the diode Dby1, the boot capacitor Cby1, and the switching element Ty2 by the conduction of the switching element Ty2.
- the boot capacitor Cby1 is used instead of the DC power supply as the operation power supply of the drive circuit Dry1, the manufacturing cost can be reduced.
- the voltage across the boot capacitor Cbx1 is supplied to the drive circuit Drx1 as an operating power source.
- One end of the boot capacitor Cbx1 is connected to the emitter electrode of the switching element Tx1 and the drive circuit Drx1.
- the other end of the boot capacitor Cbx1 is connected to one end on the high potential side of the boot capacitor Cby1 via the drive circuit Drx1 and the diode Dbx1.
- the diode Dbx1 is arranged with the anode directed toward the boot capacitor Cby1.
- the diode Dbx1 prevents the boot capacitor Cbx1 from discharging toward the boot capacitor Cby1.
- the level shift circuit LSx1 is connected to the drive circuit Drx1.
- Boot capacitor Cbx1 is also charged prior to normal operation of the power converter. Specifically, the boot capacitor Cbx1 can be charged using the charge stored in the boot capacitor Cby1 by turning on the switching element Ty1. This is because the current flows through the series circuit A2 including the boot capacitor Cby1, the diode Dbx1, the boot capacitor Cbx1, and the switching element Ty1 by the conduction of the switching element Ty1.
- the boot capacitor Cby1 is employed as the operation power supply of the switching element Ty1
- the boot capacitor Cbx1 is charged after the boot capacitor Cby1 is charged. This is because the operating power cannot be supplied to the switching element Ty1 (more specifically, the drive circuit Dry1) before the boot capacitor Cby1 is charged, and the switching element Ty1 cannot be made conductive. This also applies to other boot capacitors described later.
- the boot capacitor Cbx1 is charged and functions as an operation power source for outputting a switch signal to the switching element Tx1. Therefore, it is not necessary to provide a DC power source for the switching element Tx1, and the manufacturing cost can be reduced.
- the boot capacitor Cbx1 is charged using the boot capacitor Cby1 for the switching element Ty1 disposed on the upper side of the inverter 3 as a power source.
- the following effects are brought about as compared with the case where the boot capacitor Cbx1 is charged using the DC power supply Ed for the switching element Ty2 disposed below the inverter 3 as a power supply.
- the diode Dbx1 is connected between one end on the high potential side of the DC power supply Ed and the high potential end of the boot capacitor Cbx1 as illustrated in FIG. May be. That is, the anode of the diode Dbx1 may be connected between the anode of the diode Dby1 and the DC power supply Ed.
- the switching elements Ty1 and Ty2 need to be turned on simultaneously. This is because the conduction causes a current to flow to the series circuit A4 including the DC power supply Ed, the diode Dbx1, the boot capacitor Cbx1, and the switching elements Ty1 and Ty2, and the boot capacitor Cbx1 is charged.
- the switching elements Ty1 and Ty2 are conducted exclusively with each other, and these are not conducted simultaneously. This is to prevent a large current from flowing from the input terminal Px to the DC power supply lines LH and LL via the converter 1 by short-circuiting the DC power supply lines LH and LL. Therefore, in the power conversion device of FIG. 3, the boot capacitor Cbx1 is not charged in the normal operation of the inverter 3.
- the voltage across the boot capacitor Cbx2 is supplied to the drive circuit Drx2 as an operating power source.
- One end of the boot capacitor Cbx2 is connected to the emitter electrode of the switching element Tx2 and the drive circuit Drx2.
- the other end of the boot capacitor Cbx2 is connected to the drive circuit Drx2 and one end on the high potential side of the boot capacitor Cbx1 via the diode Dbx2.
- the diode Dbx2 is arranged with its cathode facing the boot capacitor Cbx2. The diode Dbx2 prevents the boot capacitor Cbx2 from discharging toward the boot capacitor Cbx1 side.
- the level shift circuit LSx2 is connected to the drive circuit Drx2.
- This boot capacitor Cbx2 is also charged prior to normal operation of the power converter.
- the boot capacitor Cbx2 is charged after the boot capacitor Cbx1 is charged.
- the boot capacitor Cbx2 can be charged by turning on the switching element Tx1. This is because the current flows through the series circuit A3 including the boot capacitor Cbx1, the diode Dbx2, the boot capacitor Cbx2, and the switching element Tx1 by the conduction of the switching element Tx1.
- the boot capacitor Cbx1 is charged with the boot capacitor Cby1 as a power source, so that the voltage across the boot capacitor Cby1 decreases at this time.
- the boot capacitor Cbx2 is charged, the voltage across the boot capacitor Cbx1 decreases. Therefore, in the charging operation prior to the normal operation, it is desirable to repeatedly perform the charging operation of each of the boot capacitors Cbx1, Cbx2, and Cby1 described above. As a result, the voltage drop of the boot capacitors Cbx1 and Cby1 due to the current consumption of each drive circuit Drx1 and Dry1 can be recovered, and the voltage drop of the boot capacitor Cbx1 due to the charge of the boot capacitor Cbx2 can be recovered. Similarly, the boot capacitor Cbx1 It is possible to recover the voltage drop of the boot capacitor Cby1 due to the charging.
- the switching elements Ty1 and Ty2 may be simultaneously turned on before normal operation. Thereby, the boot capacitor Cbx1 can be charged while suppressing the voltage drop of the boot capacitor Cby1.
- the switching elements Tx1 and Tx2 are normally-off switching elements. Thereby, it is possible to prevent a large current from flowing through converter 1 due to a short circuit of DC power supply lines LH and LL.
- the switching elements Tx1, Ty1 and Ty2 may be simultaneously turned on before normal operation. Thereby, the boot capacitor Cbx2 can be charged while suppressing the voltage drop of the boot capacitors Cby1, Cbx1.
- the boot capacitor Cbx2 is charged with the boot capacitor Cbx1 as a power source, but may be charged with the boot capacitor Cby1 as a power source. That is, as illustrated in FIG. 4, the anode of the diode Dbx2 may be connected to one end on the high potential side of the boot capacitor Cby1. In this case, the boot capacitor Cbx2 can be charged by turning on the switching elements Tx1 and Ty1 simultaneously. This is because such conduction causes a current to flow through the series circuit A5 including the boot capacitor Cby1, the diode Dbx2, the boot capacitor Cbx2, and the switching elements Tx1 and Ty1.
- the manufacturing cost can be reduced. Further, since the switching elements Tx1 and Ty1 can be simultaneously conducted in the normal operation, the boot capacitor Cbx2 can be charged even during the normal operation.
- the switching power supply Ty1 is also obtained from the boot capacitor Cby1, but may be obtained from a DC power supply.
- each of the switching elements Tx1 and Tx2 obtains the operating power supply from the boot capacitors Cbx1 and Cbx2, but the present invention is not limited to this.
- the manufacturing cost can be reduced, and the boot capacitor can be charged during normal operation, so that a capacitor with a small capacitance can be adopted.
- the converter 1 has been described as a three-phase converter and the inverter 3 has been described as a three-phase inverter, it is not limited thereto.
- the inverter 3 is not an essential requirement.
- a switching element and a power supply unit connected to the switching element on the side of the DC power supply line and functioning as an operation power supply may be provided between the DC power supply line LH and the output terminal. This also applies to other embodiments described later.
- the step-down chopper circuit 30 shown in FIG. 5 may be used.
- the chopper circuit 30 is connected to the output of the converter 1, for example, and can step down the DC voltage between the DC power supply lines LH and LL and output it from the output terminals P1 and P2.
- the converter 1 for example, the DC power supply lines LH and LL and output it from the output terminals P1 and P2.
- the chopper circuit 30 includes a switching element S30 provided between the DC power supply line LH and the output terminal P1.
- the switching element S30 is, for example, an insulated gate bipolar transistor, and is arranged with the emitter electrode facing the output terminal P1.
- the switching element S30 is supplied with a DC power supply Ed as an operating power supply.
- One end on the low potential side of the DC power supply Ed is connected to the switching element S30 on the DC power supply line LL side. Since the drive circuit Dr30 and the level shift circuit LS30 are the same as the other drive circuits and the level shift circuit, description thereof will be omitted.
- One end on the high potential side of the DC power supply Ed is connected to one end on the high potential side of the boot capacitor Cbx1 via the diode Dbx1.
- the diode Dbx1 is provided with its anode facing the DC power supply Ed. In such a power converter, when the switching element S30 is turned on, a current flows through the series circuit A30 including the DC power supply Ed, the diode Dbx1, the boot capacitor Cbx1, and the switching element S30. Therefore, the boot capacitor Cbx1 is charged.
- the clamp circuit 2 has a drive circuit Drs1 that drives the switching element S1.
- Drive circuit Drs1 is connected to the gate electrode of switching element S1.
- a level shift circuit LS1 is connected to the drive circuit Drs1.
- the voltage across the boot capacitor Cb1 is supplied to the drive circuit Drs1 as an operating power source.
- One end of the boot capacitor Cb1 is connected to the emitter electrode of the switching element S1 and the drive circuit Drs1.
- the other end of the boot capacitor Cb1 is connected to the drive circuit Drs1 and one end on the high potential side of the boot capacitor Cby1 via a diode Db1.
- the diode Db1 is arranged with the anode directed toward the boot capacitor Cby1.
- the diode Db1 prevents the boot capacitor Cb1 from discharging to the boot capacitor Cby1 side.
- the boot capacitor Cb1 is charged prior to the normal operation of the power converter, for example. Specifically, the boot capacitor Cb1 can be charged using the electric charge stored in the boot capacitor Cby1 by turning on the switching element Ty1. This is because the conduction of the switching element Ty1 causes a current to flow through the series circuit A6 including the boot capacitor Cby1, the diode Db1, the boot capacitor Cb1, and the switching element Ty1. The switching element S1 is turned on after regenerative energy from the inverter 3 side accumulates in the capacitor C1. Therefore, the boot capacitor Cb1 does not necessarily need to be charged prior to normal operation, and may be charged during normal operation.
- the boot capacitor Cb1 is charged and functions as an operation power supply for outputting a switch signal to the switching element S1. Therefore, it is not necessary to provide a DC power source for the switching element S1, and the manufacturing cost can be reduced.
- the boot capacitor Cb1 can be charged by conducting only the switching element Ty1. Therefore, the boot capacitor Cb1 can be charged even in the normal operation of the inverter 3, and thus the capacitance required for the boot capacitor Cb1 can be reduced.
- the clamp circuit 2 may include capacitors C1 and C2, switching elements S1 and S2, and diodes D1 to D3.
- Capacitors C1 and C2 and diode D1 are connected in series between DC power supply lines LH and LL.
- the diode D1 is provided between the capacitors C1 and C2 with its anode directed toward the DC power supply line LH.
- the switching elements S1 and S2 are, for example, insulated gate bipolar transistors. Switching element S1 and diode D2 are connected in series with each other. A series body of the switching element S1 and the diode D2 is provided between the DC power supply line LH and the cathode of the diode D1.
- Switching element S1 is arranged with its emitter electrode facing DC power supply line LH, and diode D2 is arranged with its cathode facing DC power supply line LH.
- Switching element S2 and diode D3 are connected in series with each other.
- a series body of the switching element S2 and the diode D3 is connected between the DC power supply line LL and the anode of the diode D1.
- Switching element S2 is arranged with its collector electrode facing DC power supply line LL, and diode D3 is arranged with its anode facing DC power supply line LL.
- the capacitors C1 and C2 are charged in series with each other when the switching elements S1 and S2 are non-conductive. Therefore, the breakdown voltage of the capacitors C1 and C2 can be reduced as compared with the case where one capacitor C1 is charged. If the switching elements S1 and S2 are turned on, the capacitors C1 and C2 are discharged in parallel with each other.
- the clamp circuit 2 includes drive circuits Drs1 and Drs2 that drive the switching elements S1 and S2, respectively.
- Drive circuits Drs1 and Drs2 are connected to the gate electrodes of switching elements S1 and S2, respectively.
- Level shift circuits LS1 and LS2 are connected to the drive circuits Drs1 and Drs2, respectively.
- the operating power supply of the drive circuit Drs1 is the same as that of the clamp circuit 2 of FIG. Therefore, it is not necessary to employ a direct current power source as the operating power source for the switching element S1, and the manufacturing cost can be reduced. Further, the boot capacitor Cb1 is charged even during normal operation.
- the drive circuit Dr2 is supplied with operating power from the DC power supply Ed2.
- the DC power supply Ed2 has one end on the low potential side connected to the emitter electrode of the switching element S2.
- a boot capacitor is not employed as the operating power supply of the drive circuit Drs2. This is due to the following reason. That is, a circuit is assumed in which the DC power supply Ed2 is replaced with a boot capacitor Cb2, and the boot capacitor Cb2 and the boot capacitor Cb1 are connected by a diode. Then, the boot capacitors Cb1, Cb2 and the capacitor C1 are always short-circuited. Due to such a short circuit, an excessive voltage is divided into one or both of the boot capacitors Cb1 and Cb2, and the boot capacitors Cb1 and Cb2 are prevented from obtaining a desired voltage.
- the converter 1 is not an essential requirement when a boot capacitor is provided for the switching element of the clamp circuit 2. If the converter 1 and the clamp circuit 2 are provided and the emitters of the switching element S1 and the switching element Tx1 are connected to a common potential (for example, the DC power supply line LH), any of the switching elements included in the converter 1 and the clamp circuit 2 It is only necessary to provide a boot capacitor for one of them.
- the power converter of FIG. 8 differs from the power converter of FIG. 1 in the configuration of the converter 1.
- the clamp circuit 2 of FIG. 1 is employed as the clamp circuit 2.
- the present invention is not limited to this configuration.
- the clamp circuit 2 of FIG. 7 may be employed. Further, the clamp circuit 2 may not be provided.
- the converter 1 has r, s, and t phase switching legs.
- the r-phase switching leg includes a switching element Tr and diodes Dr1 to Dr4.
- the s-phase switching leg includes a switching element Ts and diodes Ds1 to Ds4.
- the t-phase switching leg includes a switching element Tt and diodes Dt1 to Dt4.
- the r, s, and t-phase switching legs are connected in parallel between the DC power supply lines LH and LL.
- Switching element Tx (where x represents r, s, t) is, for example, an insulated gate bipolar transistor.
- the switching element Tx and the diodes Dx1 and Dx2 are connected in series between the DC power supply lines LH and LL.
- the diode Dx1 is disposed on the DC power supply line LH side with respect to the switching element Tx, and the diode Dx2 is disposed on the DC power supply line LL side with respect to the switching element Tx.
- the switching element Tx is arranged with the emitter electrode facing the DC power supply line LH, and the diodes Dx1 and Dx2 are arranged with the cathode facing the DC power supply line LH.
- the diodes Dx1 and Dx2 exhibit reverse blocking capability as the converter 1.
- the anode of the diode Dx3 is connected to a point between the switching element Tx and the diode Dx1, and its cathode is connected to the input terminal Px.
- the anode of the diode Dx4 is connected to the input terminal Px, and the cathode thereof is connected to a point between the switching element Tx and the diode Dx2.
- the number of switching elements can be reduced, so that the manufacturing cost can be reduced.
- the converter 1 has a drive circuit Drx that drives the switching element Tx.
- the drive circuit Drx is connected to the gate electrode of the switching element Tx.
- a level shift circuit LSx is connected to the drive circuit Drx.
- the voltage across the boot capacitor Cbx is supplied to the drive circuit Drx as an operating power source.
- One end of the boot capacitor Cbx is connected to the emitter electrode of the switching element Tx and the drive circuit Drx.
- the other end of the boot capacitor Cbx is connected to one end on the high potential side of the boot capacitor Cby1 via the drive circuit Drx and the diode Dbx.
- the diode Dbx is arranged with its cathode facing the boot capacitor Cbx. The diode Dbx prevents the boot capacitor Cbx from discharging to the boot capacitor Cby1 side.
- Boot capacitor Cbx is charged prior to normal operation of the power converter. Specifically, the boot capacitor Cbx can be charged by turning on the switching element Ty1. This is because the conduction of the switching element Ty1 causes a current to flow through the series circuit A7 including the boot capacitors Cby1, Cbx, the diodes Dbx, Dx1, and the switching element Ty1. As described above, since it is not necessary to use a DC power source for the switching element Tx, the manufacturing cost can be reduced. Moreover, since the boot capacitor Cbx can be charged every time the switching element Ty1 is conducted even during normal operation, the capacitance required by the boot capacitor Cbx can be reduced.
- the operation power supply voltage of each switching element may vary.
- the voltage becomes lower as the operation power supply in the subsequent stage.
- the boot capacitor Cby1 is charged via the diode Dby1 and the switching element Ty2 using the DC power supply Ed as a power supply. Therefore, the voltage across the boot capacitor Cby1 is smaller than the voltage of the DC power supply Ed by the sum of the forward voltage of the diode Dby1 and the voltage between the emitter and collector of the switching element Ty2. Similarly, the voltage across boot capacitor Cbx1 is smaller than the voltage across boot capacitor Cby1 by the sum of the forward voltage of diode Dbx1 and the voltage between the emitter and collector of switching element Ty1. Similarly, the voltage across the boot capacitor Cbx2 is smaller than the voltage across the boot capacitor Cbx1 by the sum of the forward voltage of the diodes Dbx2 and Dx1 and the voltage between the emitter and collector of the switching element Tx1.
- each terminal voltage is expressed by the following equation.
- Vcby1 Ved ⁇ Vf ⁇ Vce (1)
- Ved, Vcbx1, Vcbx2, and Vcby1 are voltages across the DC power supply Ed and the boot capacitors Cbx1, Cbx2, and Cby1, respectively.
- Vf is the forward voltage of the diodes Dby1, Dbx1, Dbx2, Dx1.
- Vce is a voltage between the emitter and collector of the switching elements Tx1, Ty1, Ty2.
- the same switching element can be adopted if the variation in voltage with respect to the operating power source can be eliminated, and the variation in switching characteristics of each switching element can be reduced. Therefore, in the second embodiment, variation in the operating voltage of each switching element is reduced.
- the power conversion apparatus further includes voltage adjustment circuits VAy1, VAy2, and VAx1.
- VAy1, VAy2, and VAx1 In the illustration of FIG. 10, only one switching leg of the converter 1 and one switching leg of the inverter 3 are typically illustrated.
- the voltage adjustment circuit VAx1 is connected between, for example, one end of the boot capacitor Cbx1 on the high potential side and the drive circuit Drx1.
- the voltage adjustment circuit VAx1 is a resistor, for example, and steps down the voltage across the boot capacitor Cbx1 and supplies it to the drive circuit Drx1 as an operation power supply.
- the voltage across the boot capacitor Cbx1 is stepped down by the sum of twice the voltage Vf and the voltage Vce and supplied as an operating power supply.
- the operating power supplied to the drive circuits Drx1 and Drx2 can be made equal (see Expression (2) and Expression (3)).
- the voltage adjustment circuit VAy1 is connected between one end on the low potential side or the high potential side of the boot capacitor Cby1 and the drive circuit Dry1.
- the voltage adjustment circuit VAy1 is a resistor, for example, and steps down the voltage across the boot capacitor Cby1 and supplies it to the drive circuit Dry1 as an operating power supply. More specifically, the voltage across the boot capacitor Cby1 is stepped down by the sum of 3 times the voltage Vf and 2 times the voltage Vce, and supplied as an operating power supply.
- the voltage adjustment circuit VAy2 is connected between one end on the high potential side of the DC power supply Ed and the drive circuit Dry2.
- the voltage adjustment circuit VAy2 is a resistor, for example, and steps down the voltage of the DC power supply Ed and supplies it to the drive circuit Dry2 as an operation power supply. More specifically, the voltage of the DC power supply Ed is stepped down by the sum of four times the voltage Vf and three times the voltage Vce and supplied as the operating power.
- the operating voltages of the drive circuits Drx1, Drx2, Dry1, Dry2 can be made equal to each other by the voltage adjustment circuits VAx1, VAy1, VAy2.
- Vcby1, Vcbx1, and Vcbx2 across the boot capacitors Cby1, Cbx1, and Cbx2 are expressed by the following equations.
- Vcby1 Ved ⁇ Vf ⁇ Vce (4)
- the operating voltages of the drive circuits Drx1, Drx2, Dry1, Dry2 can be made equal to each other.
- the voltage dropped by the voltage adjustment circuit VAx1 is smaller than that of the power conversion device of FIG. 10, the power consumption generated in the voltage adjustment circuit VAx1 can be reduced.
- voltage adjustment circuits VAy1 and VAy2 may be provided for the boot capacitor Cby1 and the DC power supply Ed, respectively, as illustrated in FIG.
- the voltage drop of the voltage adjustment circuit VAy2 may be the sum of three times the voltage Vf and twice the voltage Vce
- the voltage drop of the voltage adjustment circuit VAy1 may be the sum of the voltage Vf twice and the voltage Vce.
- this voltage adjustment circuit is not limited to the form presented here.
- a form in which the voltage of the boot capacitor is divided or a form in which a constant voltage is obtained by a Zener diode may be used.
- it may be configured such that the input of the regulator is connected to both ends of the boot capacitor, and the output of the regulator is connected to the drive circuit.
- switching elements Tr1, Ts1, and Tt1 are directly connected to a DC power supply line LH.
- the diodes Dr1, Ds1, and Dt1 are positioned closer to the input terminals Pr, Ps, and Pt than the switching elements Tr1, Ts1, and Tt1, respectively.
- the DC power supply line LH functions as a common potential for the switching elements Tr1, Ts1, and Tt1. Therefore, one boot capacitor can function as an operation power source for outputting a switch signal to the three switching elements Tx1. That is, the voltage across one boot capacitor is supplied to the three drive circuits Drx1 that respectively drive the three switching elements Tx1 as an operation power supply. Thereby, the number of boot capacitors can be reduced.
- one such boot capacitor may function as an operation power supply for outputting a switch signal to the switching element S1 of the clamp circuit 2 of FIGS. If the switching element S1 is directly connected to the DC power supply line LH in the clamp circuit 2 of FIG. 7, the above-described one boot capacitor is used as an operating power supply for outputting a switch signal to the switching element S1. Can function as.
- the diode Dx1 may be provided on the DC power supply line LH side with respect to the switching element Tx1, as exemplified in FIG. More specifically, the diode Dx1 may be provided closer to the DC power supply line LH than the connection point of the switching element Tx1, the boot capacitor Cbx1, and the drive circuit Drx1.
- the switching element Tx1 and the diode Dx1 are connected in series to each other, but these functions may be realized by a single switching element.
- a mesa type or separation blocking type reverse blocking insulated gate bipolar transistor may be employed. It can be understood that such a switching element has a reverse blocking structure.
- the diode Dbx2 may not be provided. Since the diode Dx1 is provided on the charging path (series circuits A3, A5) of the boot capacitor Cbx2, the diode Dx1 can prevent the boot capacitor Cbx2 from discharging toward the boot capacitor Cbx1. In other words, the diode Dx1 exhibits reverse blocking capability as a converter and can prevent discharge through the charging path of the boot capacitor Cbx2. Therefore, the number of diodes can be reduced and the manufacturing cost can be reduced as compared with the case where the diodes Dx1 and Dbx2 are individually provided.
- a diode Dx1 is interposed on the charging path of the boot capacitor Cbx1 (series circuit A2 in FIG. 13). Therefore, the diode Dx1 functions as the diode Dbx1 on the series circuit A2.
- the diode Dbx1 is preferably provided. This is because in normal operation, the boot capacitor Cbx1 can be discharged to the boot capacitor Cby1 side through a path that does not pass through the diode Dx1. Details will be described below.
- boot capacitors Cbx1 and Cby1 are charged with the voltage Vc, and the voltage drop of each switching element and each diode is zero. Further, it is assumed that the potential applied to the DC power supply line LL is zero.
- phase voltage Vr applied to the input terminal Pr is larger than the phase voltage Vs applied to the input terminal Ps and the switching elements Tr1 and Ts2 are conducting
- FIG. 1 the arrangement of the switching elements Tr1, Ts1, Tt1 and the diodes Dr1, Ds1, Dt1 is reversed.
- the input terminal Ps is connected to the power supply line LL by the conduction of the switching element Ts2.
- the input terminal Pr is connected to the power supply line LH by the conduction of the switching element Tr1.
- the potential difference between the DC power supply line LH and the DC power supply line LL becomes the difference between the phase voltages Vr and Vs, that is, the line voltage Vrs (> 0).
- the code x is replaced with the code r in FIG. Since the switching element Tr1 is conductive, the potentials of the emitter electrode and the collector electrode are equal to each other. Therefore, the potential on the low potential side of the boot capacitor Cbr1 is the line voltage Vrs. Considering the voltage Vc of the boot capacitor Cbr1, the high potential side potential of the boot capacitor Cbr1 is the sum of the line voltage Vrs and the voltage Vc.
- the switching element Ty2 when the switching element Ty2 is turned on, the potential on the low potential side of the boot capacitor Cby1 is zero, and the potential on the high potential side is the voltage Vc. Accordingly, the high potential side potential (Vc + Vrs) of the boot capacitor Cbr1 is higher than the high potential side potential (Vc) of the boot capacitor Cby1. Accordingly, at this time, the boot capacitor Cbr1 can be discharged to the boot capacitor Cby1 through a path not passing through the diode Dr1.
- the diode Dbr1 can prevent such a discharge, the diode Dbr1 is preferably provided. From the viewpoint of preventing discharge during normal operation, the diode Dbr1 may be provided from the boot capacitor Cby1 to the connection point between the diode Dx1 and the switching element Tx1.
- the diode Dbx may not be provided. This is because the diode Dx1 realizes the function of the diode Dbx1 in the series circuit A7, and the diode Dx3 prevents the boot capacitor Cbx from being discharged during normal operation. Thereby, the number of diodes can be reduced, and thus the manufacturing cost can be reduced.
- the diode (diode Dbx or diode Dx1) that prevents discharge from the boot capacitor Cbx (or boot capacitors Cbx1, Cbx2) is on the high potential side of the boot capacitor Cby1. It can be grasped that it is provided in the path from one end to the DC power supply line LH via the boot capacitor Cbx1. This grasp is applied to any of the power converters shown in FIGS.
- the diode Dx2 is provided on the DC power supply line LL side with respect to the switching element Tx2. More specifically, the switching element Tx2, the drive circuit Drx2, and the boot capacitor Cbx2 are provided on the DC power supply line LL side from the point where they are connected in common. Thereby, the diode Dx2 does not intervene on the charging path (series circuits A3, A5) of the boot capacitor Cbx2. Therefore, when the boot capacitor Cbx2 is charged, there is no voltage drop due to the forward voltage of the diode Dx2. In other words, the voltage across the boot capacitor Cbx2 can be increased.
- the diode Dx2 may be provided closer to the input terminal Px than the switching element Tx2, as illustrated in FIG. More specifically, the diode Dx2 may be provided on the input end Px side of the connection point of the switching element Tx2, the boot capacitor Cbx2, and the drive circuit Drx2.
- each boot capacitor is set so that a voltage equal to or higher than a value capable of conducting each switching element (ON voltage) is charged in the boot capacitor over the normal operation period.
- the switching elements Tx1, Ty1, Ty2, and S30 elements that can secure a conduction period that can sufficiently charge the boot capacitors Cbx2, Cbx1, Cby1, Cb1, and Cbx are employed.
- Such a boot capacitor is selected in consideration of the ON voltage of each switching element, the amount of charge consumed by turning on each switching element, the current consumption of each drive circuit, the control method of the converter 1 and the inverter 3, and the like. .
- the power converter illustrated in FIG. 14 is different from the power converter illustrated in FIG. 1 in that there is a clamp circuit 2 and the configuration of the converter 1.
- This power converter does not include the clamp circuit 2.
- the converter 1 has a configuration capable of regenerating to the input terminals Pr, Ps, Pt side (hereinafter also referred to as the power supply side).
- the power supply side the configuration capable of regenerating to the input terminals Pr, Ps, Pt side
- this does not preclude the installation of a clamp circuit for protection in case of abnormal operation.
- the r-phase switching leg includes switching elements Tr11, Tr12, Tr21, Tr22 and diodes Dr11, Dr12, Dr21, Dr22.
- the s-phase switching leg includes switching elements Ts11, Ts12, Ts21, and Ts22 and diodes Ds11, Ds12, Ds21, and Ds22.
- the t-phase switching leg includes switching elements Tt11, Tt12, Tt21, Tt22 and diodes Dt11, Dt12, Dt21, Dt22.
- the r-phase, s-phase, and t-phase switching legs are connected in parallel between the DC power supply lines LH and LL.
- Switching elements Tx11, Tx12, Tx21, and Tx22 are unidirectional control switching elements that conduct / non-conduct only the current flowing from the second electrode to the first electrode. For example, in the case of an insulated gate bipolar transistor, only a current (so-called forward current) flowing from the collector electrode to the emitter electrode is turned on / off. For example, in an insulated gate bipolar transistor, current (so-called reverse current) does not flow from the first electrode (emitter electrode) to the second electrode (collector electrode). Such a switching element is also called a one-way conduction switching element.
- a MOS (Metal-Oxide-Semiconductor) field effect transistor has a parasitic diode which is structurally reverse conducting, so that current flows from the first electrode (source electrode) to the second electrode (drain electrode). Flowing.
- MOS Metal-Oxide-Semiconductor
- the switching element Tx11 and the diode Dx11 are connected in series, the switching element Tx12 and the diode Dx12 are connected in series, the switching element Tx21 and the diode Dx21 are connected in series, and the switching element Tx22 and the diode Dx22 are connected in series. Is done.
- the switching elements Tx11 and Tx21 are arranged with the emitter electrode facing the DC power supply line LH, and the diodes Dx11 and Dx21 are arranged with the cathode facing the DC power supply line LH.
- the switching elements Tx12 and Tx22 are arranged with their emitter electrodes facing the DC power supply line LL, and the diodes Dx12 and Dx22 are arranged with their cathodes facing the DC power supply line LL.
- the series body of the switching element Tx11 and the diode Dx11 and the series body of the switching element Tx12 and the diode Dx12 are connected in parallel to each other between the input terminal Px and the DC power supply line LH.
- the series body of the switching element Tx21 and the diode Dx21 and the series body of the switching element Tx22 and the diode Dx22 are connected in parallel to each other between the input terminal Px and the DC power supply line LL.
- the switching elements Tx11 and Tx12 and the diodes Dx11 and Dx12 constitute a so-called bidirectional switching element.
- the switching elements Tx21 and Tx22 and the diodes Dx21 and Dx22 constitute a bidirectional switching element. Therefore, the converter 1 can flow current from the DC power supply lines LH and LL to the input end Px. That is, the regenerative energy from the inverter 3 side can be regenerated to the power source side.
- Drive circuits Drx11, Drx12, Drx21, Drx22 are connected to the gate electrodes of the switching elements Tx11, Tx12, Tx21, Tx22, respectively. Further, level shift circuits LSx11, LSx12, and LSx21 are connected to the drive circuits Drx11, Drx12, and Drx21, respectively.
- the voltage across the boot capacitor Cbx11 is supplied to the drive circuit Drx11 as an operating power source.
- a diode Dbx11 is provided between the boot capacitors Cbx11 and Cby1. Since the boot capacitor Cbx11 and the diode Dbx11 are the same as the boot capacitor Cbx1 and the diode Dbx1 in the first embodiment, detailed description thereof is omitted.
- the voltage across the boot capacitor Cbx12 is supplied to the drive circuit Drx12 as an operating power source.
- One end of the boot capacitor Cbx12 is connected to the emitter electrode of the switching element Tx12 and the drive circuit Drx12.
- the other end of the boot capacitor Cbx12 is connected to the drive circuit Drx12.
- the other end of the boot capacitor Cbx12 is connected to one end on the high potential side of the boot capacitor Cbx11 via the diode Dbx12.
- the diode Dbx12 prevents the boot capacitor Cbx12 from discharging toward the boot capacitor Cbx11.
- the boot capacitor Cbx12 can be charged using the electric charge stored in the boot capacitor Cbx11 by making the switching element Tx11 conductive. This is because the current flows through the series circuit A8 including the boot capacitor Cbx11, the diode Dbx12, the boot capacitor Cbx12, the diode Dx11, and the switching element Tx11 due to such conduction.
- the boot capacitor Cbx12 is charged and functions as an operation power supply for outputting a switch signal to the switching element Tx12. Therefore, it is not necessary to provide a DC power source for the switching element Tx12, and the manufacturing cost can be reduced. Moreover, since the switching element Tx11 is conductive even in the normal operation of the converter 1, the boot capacitor Cbx12 is charged in the normal operation. Therefore, the capacitance required by the boot capacitor Cbx12 can be reduced.
- the diode Dx11 functions as the diode Dbx12.
- the boot capacitor Cbx12 is not discharged through a path other than the series circuit A8. Therefore, the diode Dbx12 may not be provided.
- the voltage across the boot capacitor Cbx22 is supplied to the drive circuit Drx22 as an operating power source.
- the switching element Tx22 is arranged on the DC power supply line LL side with respect to the diode Dx22. Therefore, the emitter electrode of the switching element Tx22 is directly connected to the DC power supply line LL. Therefore, the DC power supply line LL functions as a common potential for the switching elements Ty2 and Tx22. Therefore, in the illustration of FIG. 15, the boot capacitor Cbx22 is connected in parallel with the DC power supply Ed, and the same potential as that of the DC power supply Ed is supplied as the operating voltage of the switching element Tx22. In this case, the DC power supply Ed may function as an operation power supply for the switching element Tx22 without providing the boot capacitor Cbx22.
- the voltage across the boot capacitor Cbx21 is supplied to the drive circuit Dr21 as an operating power supply.
- One end of the boot capacitor Cbx21 is connected to the emitter electrode of the switching element Tx21 and the drive circuit Drx21.
- the other end of the boot capacitor Cbx21 is connected to the drive circuit Drx21.
- the other end of the boot capacitor Cbx21 is connected to one end on the high potential side of the boot capacitor Cbx22 via the diode Dbx21.
- the diode Dbx21 is arranged with the anode directed toward the boot capacitor Cbx22.
- the diode Dbx21 prevents the boot capacitor Cbx21 from discharging toward the boot capacitor Cbx22.
- the boot capacitor Cbx21 can be charged using the electric charge (or DC power supply Ed) stored in the boot capacitor Cbx22 by making the switching element Tx22 conductive. This is because current flows through the series circuit A9 including the boot capacitor Cbx22 (or the DC power supply Ed), the diode Dbx21, the boot capacitor Cbx21, the diode Dx22, and the switching element Tx22.
- the boot capacitor Cbx21 is charged and functions as an operation power supply for outputting a switch signal to the switching element Tx21. Therefore, it is not necessary to provide a DC power source for the switching element Tx21, and the manufacturing cost can be reduced. Moreover, in the normal operation of the converter 1, when the regenerative energy from the inverter 3 side is regenerated to the power supply side, the switching element Tx22 conducts, so that the boot capacitor Cbx22 is charged in the normal operation.
- the charging current that flows from the DC power supply Ed to the boot capacitor Cbx21 and charges the boot capacitor Cbx21 is smaller than the charging current. Therefore, as a whole, although the current flows in the forward direction through the switching element Tx21 and the diode Dx21, the charging current can flow through the switching element Tx21 and the diode Dx21 in the reverse direction. More specifically, a charging current flows through a series circuit including a DC power supply Ed, a diode Dx21, a boot capacitor Cbx21, a switching element Tx21, and a diode Dx21.
- an operating current I1 flows from the output terminal Py via the switching element Ty2.
- the operating current I1 is subtracted by the charging current I2 at the connection point between the DC power supply Ed and the DC power supply line LL, and a current flows in the forward direction through the diode Dx21 and the switching element Tx21.
- the charging current I2 flows from the DC power supply Ed through the diode Dx21 and the boot capacitor Cbx21.
- the operating current I1 subtracted by the charging current I1 and passed through the switching element Tx21 is added by the charging current I2 at the connection point between the switching element Tx21 and the boot capacitor Cbx21 and flows to the input terminal Px.
- the boot capacitor Cbx21 since the boot capacitor Cbx21 is charged during normal operation, the capacitance required by the boot capacitor Cbx21 can be reduced. Even during power running, the boot capacitor Cbx21 may be charged by turning on the switching element Tx22 at an appropriate timing at which the converter operation does not become abnormal.
- the anode of the diode Dbx21 may be connected to one end of the boot capacitor Cbx11 on the high potential side, similarly to the power conversion device of FIG.
- the anode of the diode Dbx21 may be connected to one end on the high potential side of the boot capacitor Cbx12.
- the boot capacitor Cbx21 can be charged by using the electric charge stored in the boot capacitor Cbx11 by the conduction of the switching element Tx11. Therefore, the boot capacitors Cbx12 and Cbx21 can be charged by the conduction of the switching element Tx11.
- the anode of the diode Dbx21 is preferably connected to the boot capacitor Cbx22 (or the DC power supply Ed). This is because the boot capacitor Cbx21 can be charged using the boot capacitor Cbx22 (or DC power supply Ed) charged with a voltage higher than the voltage across the boot capacitor Cbx11 as a power source.
- a voltage adjustment circuit may be provided to reduce variations in the voltage of each boot capacitor.
- the series body of the switching element Tx11 and the diode Dx11 and the series body of the switching element Tx22 and the diode Dx22 are each realized by one switching element (for example, a reverse blocking insulated gate bipolar transistor). It doesn't matter. As a result, a voltage drop due to the forward voltage of the diodes Dx11 and Dx22 in each charging path (series circuits A8 and A9) can be avoided. Therefore, the voltage across the boot capacitors Cbx12 and Cbx21 can be increased.
- the diode Dbx12 may not be provided. This is because each of the diodes Dx11 performs the function of the diode Dbx12.
- the diode Dx21 is provided closer to the DC power supply line LL than the switching element Tx21. More specifically, the switching element Tx21, the drive circuit Drx21, and the boot capacitor Cbx21 are provided on the DC power supply line LL side from the point where they are connected in common. Thereby, the diode Dx21 does not intervene on the charging path (series circuit A9) of the boot capacitor Cbx21. Therefore, the boot capacitor Cbx2 can be charged while avoiding a voltage drop due to the forward voltage of the diode Dx21.
- the bidirectional switching element can be configured by connecting the collector electrode of the switching element Tx21 and the collector electrode of the switching element Tx22. In this case, the same effect can be obtained. Can do.
- the second to sixth embodiments can be applied to other modes described below.
- FIG. 16 is different from the power converter illustrated in FIG. 15 in that the anode of the diode Dbx12 is connected to the power converter.
- the anode of the diode Dx12 is connected to one end on the high potential side of the boot capacitor Cbx22.
- the boot capacitor Cbx22 and the DC power supply Ed are connected in parallel, it can be understood that the anode of the diode Dx12 is connected to one end on the high potential side of the DC power supply Ed.
- the boot capacitor Cbx21 not only the boot capacitor Cbx21 but also the boot capacitor Cbx12 can be charged by conducting the switching element Tx22. Therefore, the period required for charging can be reduced. This is because such conduction causes a current to flow through the series circuit A9 and the series circuit A9 including the boot capacitor Cbx22 (or DC power supply Ed), the diodes Dbx12 and Dx22, and the switching element Tx22. Moreover, the boot capacitor Cbx12 is charged by using the boot capacitor Cbx22 charged with a voltage higher than that of the boot capacitor Cbx11 as a power source. Therefore, the voltage across the boot capacitor Cbx12 can be increased.
- the power converter illustrated in FIG. 17 is different from the power converter illustrated in FIG. 14 in terms of the configuration of the bidirectional switching element.
- the components of the r-phase, s-phase, and t-phase switching legs are the same, but their connection relationships are different.
- Switching elements Tx11, Tx12 (where x represents r, s, t) are connected in series with each other between the DC power supply line LH and the input terminal Px.
- the emitter electrodes of the switching elements Tx11 and Tx12 are connected to each other.
- the anode of the diode Dx11 is connected to the emitter electrode of the switching element Tx11, and the cathode is connected to the collector electrode of the switching element Tx12.
- the anode of the diode Dx21 is connected to the emitter electrode of the switching element Tx21, and the cathode is connected to the collector electrode of the switching element Tx11.
- the switching elements Tx21 and Tx22 are connected in series between the DC power supply line LL and the input terminal Px.
- the emitter electrodes of the switching elements Tx21 and Tx22 are connected to each other.
- the anode of the diode Dx21 is connected to the emitter electrode of the switching element Tx21, and the cathode is connected to the collector electrode of the switching element Tx22.
- the anode of the diode Dx22 is connected to the emitter electrode of the switching element Tx22, and the cathode is connected to the collector electrode of the switching element Tx21.
- the emitter electrodes of the switching elements Tx11 and Tx12 are connected to each other, and the emitter electrodes of the switching elements Tx21 and Tx22 are connected to each other. Therefore, as illustrated in FIG. 18, the operating power sources of the switching elements Tx11 and Tx12 can be made common, and the operating power sources of the switching elements Tx21 and Tx22 can be made common. This will be described in more detail below.
- Switching elements Tx11 and Tx12 are driven by a drive circuit Drx1.
- the drive circuit Drx1 is commonly connected to the gate electrodes of the switching elements Tx11 and Tx12.
- a level shift circuit LSx1 is connected to the drive circuit Drx1.
- the voltage across the boot capacitor Cbx1 is supplied to the drive circuit Drx1 as an operating power source.
- One end of the boot capacitor Cbx1 is connected to the emitter electrodes of the switching elements Tx11 and Tx12 and the drive circuit Drx1.
- the other end of the boot capacitor Cbx1 is connected to the drive circuit Drx1.
- the other end of the boot capacitor Cbx1 is connected to one end on the high potential side of the boot capacitor Cby1 via the diode Dbx1.
- the diode Dbx1 is provided with its cathode directed to the boot capacitor Cbx1.
- the diode Dbx1 prevents the boot capacitor Cbx1 from discharging toward the boot capacitor Cby1.
- the boot capacitor Cbx1 can be charged using the charge stored in the boot capacitor Cby1 by turning on the switching element Ty1. This is because the current flows through the series circuit A11 including the boot capacitor Cby1, the diode Dbx1, the boot capacitor Cbx1, the diode Dx11, and the switching element Ty1.
- the operating power sources of the switching elements Tx11 and Tx12 can be shared, and the boot capacitor Cbx1 is employed as the operating power source, so that the number of DC power sources can be reduced.
- the diode Dx11 prevents the boot capacitor Cbx1 from discharging in the series circuit A11
- the diode Dbx1 is preferably provided in the power converter. This is because, similarly to the fifth embodiment, it is possible to prevent the boot capacitor Cbx1 from being discharged to the boot capacitor Cby1 side through a path that does not pass through the diode Dx11 in the normal operation.
- the switching elements Tx21 and Tx22 are driven by the drive circuit Drx2.
- the drive circuit Drx2 is commonly connected to the gate electrodes of the switching elements Tx21 and Tx22.
- a level shift circuit LSx2 is connected to the drive circuit Drx2.
- the voltage across the boot capacitor Cbx2 is supplied to the drive circuit Drx2 as an operating power source.
- One end of the boot capacitor Cbx2 is connected to the emitter electrodes of the switching elements Tx21 and Tx22 and the drive circuit Drx2.
- the other end of the boot capacitor Cbx2 is connected to the drive circuit Drx2.
- the other end of the boot capacitor Cbx2 is connected to one end on the high potential side of the boot capacitor Cbx1 via the diode Dbx2.
- the diode Dbx2 is provided with its cathode directed toward the boot capacitor Cbx2.
- the diode Dbx2 prevents the boot capacitor Cbx2 from discharging toward the boot capacitor Cbx1.
- the boot capacitor Cbx2 can be charged using the electric charge stored in the boot capacitor Cbx1 by making the switching elements Tx11 and Ty1 conductive. This is because current flows through the series circuit A12 including the boot capacitor Cbx1, the diode Dbx2, the boot capacitor Cbx2, the diode Dx21, and the switching element Tx11.
- the operating power sources of the switching elements Tx21 and Tx22 can be shared, and the boot capacitor Cbx2 is employed as the operating power source, so that the number of DC power sources can be reduced.
- the switching element Tx12 becomes conductive.
- a current hereinafter also referred to as a charging current
- a relatively large regenerative current from the inverter 3 flows in the forward direction and a relatively small boot charging current flows in the reverse direction in the switching element Tx12.
- a forward current flows through the switching element Tx12.
- Vcby1 The voltage across the boot capacitor Cby1 is expressed as Vcby1
- the forward voltage of the diode Dbx1 is expressed as Vf1
- the voltage between the collector electrode and the emitter electrode of the switching element Tx11 is expressed as Vce1
- the voltage between the collector electrode and the emitter electrode of the switching element Ty1 is expressed as Vce.
- the both-ends voltage Vcbx1_t of the boot capacitor Cbx1 is expressed by the following equation.
- Vcbx1_t Vcby1-Vf1 + Vce1-Vce (7)
- Vf2 the forward voltage of the diode Dx11
- Vcbx1_d of the boot capacitor Cbx1 is expressed by the following equation.
- Vcbx1_d Vcby1-Vf1-Vf2-Vce (8) Further, since the switching element Tx11 does not conduct during power running in normal operation, a current flows through the series circuit A10 and the boot capacitor Cbx1 is charged in the same manner as the charging operation prior to normal operation.
- the diode Dy1 may be conducted instead of the switching element Ty1 at the time of regeneration.
- the expressions (7) and (8) are values obtained by subtracting (Vce + Vf).
- the voltage at both ends of the boot capacitor Cbx1 differs depending on whether it is regenerative or powering. Therefore, in the case where a voltage adjustment circuit is provided for the power conversion device of FIG. 18 as in the second embodiment, which of the equations (7) and (8) is used to design the voltage adjustment circuit? The point of view arises.
- the voltage regulation circuit may be based on either equation (7) or equation (8). This is because at least the variation of each boot capacitor can be reduced.
- the both end voltages Vcbx1_t and Vcbx1_d may be multiplied by a weighting coefficient, and a value obtained by adding them may be grasped as the both end voltages of the boot capacitor Cbx1.
- the weighting coefficient is a positive value, for example, and the sum of these is 1. In view of the operation status of the load 4, if the period during regeneration is relatively large, the weighting coefficient for the voltage Vcbx1_t at both ends may be increased.
- the voltage clamp circuit provides a stable voltage to the drive circuit Dr2. be able to.
- the power converter illustrated in FIG. 19 is different from the power converter illustrated in FIG. 2 in terms of the connection destination of the boot capacitor Cbx1.
- one switching leg of the converter 1 is shown, and two switching legs of the inverter 3 (however, only the upper switching element) are shown.
- one end on the high potential side of the boot capacitor Cbx1 is connected to one end on the high potential side of the boot capacitors Cbu1 and Cbv1 via diodes Dbx11 and Dbx12, respectively.
- the diodes Dbx11 and Dbx12 are arranged with their cathodes facing the boot capacitor Cbx1, respectively.
- the diodes Dbx11 and Dbx12 prevent the boot capacitor Cbx1 from discharging toward the boot capacitors Cbu1 and Cbv1, respectively.
- the boot capacitor Cbx1 can be charged using the electric charge stored in the boot capacitor Cbu1 by the conduction of the switching element Tu1. This is because the current flows through the series circuit A11 including the boot capacitor Cbu1, the diode Dbx11, the boot capacitor Cbx1, and the switching element Tu1 due to the conduction of the switching element Tu1. Furthermore, the boot capacitor Cbx1 can be charged using the electric charge stored in the boot capacitor Cby1 also by the conduction of the switching element Tv1. This is because the current flows through the series circuit A12 including the boot capacitor Cbv1, the diode Dbx12, the boot capacitor Cbx1, and the switching element Tv1 due to the conduction of the switching element Tv1.
- the boot capacitor Cbx1 is charged when at least one of the switching elements Tu1 and Tu2 is made conductive. Therefore, the opportunity for charging the boot capacitor Cbx1 during normal operation increases. In other words, the influence of the conduction / non-conduction state of the switching elements Tu1, Tu2 is averaged, and the voltage across the boot capacitor Cbx1 can be stabilized.
- the boot capacitor Cbx1 is connected to the boot capacitors Cbu1, Cbv1 via a diode. Also good.
- the boot capacitor Cbr1 may be connected to the boot capacitors Cbu1, Cbv1, and Cbw1 via diodes, respectively.
- the boot capacitors Cbr1, Cbs1, and Cbt1 can be charged by any conduction of the switching elements Tu1, Tv1, and Tw1.
- the boot capacitors Cbs1 and Cbt1. Therefore, it is possible to reduce the fluctuation of the voltage across the boot capacitor Cbx1 due to the bias of the conduction / non-conduction state of each switching element Ty1.
- the technology according to the ninth embodiment can be applied to any of the power conversion devices according to the first to eighth embodiments.
- boot capacitors for example, boot capacitors Cbx1, Cbx2, Cb1, and Cbx
- boot capacitors Cbx1, Cbx2, Cb1, and Cbx is not limited to the form of a capacitor as long as electric charge can be stored as an operation power source of the switching element.
- any of the switching elements described above is not limited to an insulated gate bipolar transistor, and may be an element having a different structure, such as a bipolar transistor or a field effect transistor.
- the first electrode corresponds to the source electrode
- the second electrode corresponds to the drain electrode.
- resistor or the like may be inserted into the charging path of any boot capacitor described above to limit the current during charging.
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Abstract
Description
<電力変換装置の一例>
図1に例示するように、本電力変換装置は、その構成要素としての電力変換部である、コンバータ1とクランプ回路2とインバータ3とを備えている。
次に、図2を参照して、スイッチング素子Tx1,Tx2,Ty1,Ty2へとスイッチ信号を出力するための動作電源について説明する。なお、図2の例示では、代表的に、コンバータ1の一つのスイッチングレグとインバータ3の一つのスイッチングレグについてのみ図示している。スナバ・クランプ回路2についての動作電源については後述する。
次に、図6の例示を参照して、スイッチング素子S1の動作電源について説明する。図6の例示では、コンバータ1の図示を省略し、インバータ3については一つのスイッチングレグのみ図示している。またスイッチング素子Ty1,Ty2についての動作電源については図2を参照した説明と同様である。
図8の電力変換装置は図1の電力変換装置と比較してコンバータ1の構成が相違している。なお、図8の例示ではクランプ回路2として図1のクランプ回路2が採用されているが、この構成に限るものではなく、例えば図7のクランプ回路2が採用されてもよい。また、クランプ回路2が設けられていなくても構わない。
次に、図9を参照して、スイッチング素子Tx,Ty1,Ty2の動作電源について説明する。なお、図9の例示では、代表的に、コンバータ1の一つのスイッチングレグとインバータ3の一つのスイッチングレグについてのみ図示している。またスイッチング素子Ty1,Ty2の動作電源については図1を参照した説明と同様であるので説明を省略する。
第1の実施の形態では、各スイッチング素子の動作電源の電圧についてばらつきが生じえる。また、後段の動作電源ほど電圧が低くなってしまう。
Vcbx1=Vcby1-Vf-Vce=Ved-2Vf-2Vce ・・・(2)
Vcbx2=Vcbx1-2Vf-Vce=Ved-4Vf-3Vce ・・・(3)
ここで、Ved,Vcbx1,Vcbx2,Vcby1はそれぞれ直流電源Ed、ブートコンデンサCbx1,Cbx2,Cby1の両端電圧である。VfはダイオードDby1,Dbx1,Dbx2,Dx1の順方向電圧である。Vceはスイッチング素子Tx1,Ty1,Ty2のエミッタ-コレクタ間の電圧である。
Vcbx1=Vcby1-Vf-Vce=Ved-2Vf-2Vce ・・・(5)
Vcbx2=Vcby1-2Vf-2Vce=Ved-3Vf-3Vce・・・(6)
したがって、電圧調整回路VAy2の電圧降下を電圧Vfの3倍と電圧Vceの3倍との和とし、電圧調整回路VAy1の電圧降下を電圧Vfの2倍と電圧Vceの2倍との和とし、電圧調整回路VAx1の降下電圧を電圧Vfと電圧Vceの和とすることが望ましい。これによって、ドライブ回路Drx1,Drx2,Dry1,Dry2の動作電圧を相互に等しくすることができる。
図1,2において、スイッチング素子Tr1,Ts1,Tt1は直接に直流電源線LHと接続されている。換言すれば、ダイオードDr1,Ds1,Dt1がそれぞれスイッチング素子Tr1,Ts1,Tt1よりも入力端Pr,Ps,Pt側に位置している。これによって直流電源線LHがスイッチング素子Tr1,Ts1,Tt1の共通電位として機能する。よって、一のブートコンデンサを、3つのスイッチング素子Tx1へとスイッチ信号を出力するための動作電源として機能させることができる。即ち、3つのスイッチング素子Tx1をそれぞれ駆動する3つのドライブ回路Drx1には、一つのブートコンデンサの両端電圧が動作電源として供給される。これによって、ブートコンデンサの個数を低減することができる。
図1,2,4の例示では、スイッチング素子Tx1とダイオードDx1とが相互に直列接続されているが、これらの機能を一つのスイッチング素子で実現してもよい。例えばメサ型又は分離阻止型の逆阻止絶縁ゲートバイポーラトランジスタを採用してもよい。なお、かかるスイッチング素子は逆阻止構造を持つと把握できる。
図2,4の電力変換装置においてダイオードDbx2は設けられていなくても構わない。ブートコンデンサCbx2の充電経路(直列回路A3,A5)上にダイオードDx1が設けられているので、かかるダイオードDx1はブートコンデンサCbx2がブートコンデンサCbx1側へと放電することを防止できる。換言すれば、ダイオードDx1はコンバータとしての逆阻止能力を発揮すると共に、ブートコンデンサCbx2の充電経路を介した放電を防止できる。したがって、個別にダイオードDx1,Dbx2を設ける場合と比べて、ダイオードの個数を低減でき、ひいては製造コストを低減できる。
図1,2,4の電力変換装置において、ダイオードDx2はスイッチング素子Tx2に対して直流電源線LL側に設けられている。より具体的には、スイッチング素子Tx2とドライブ回路Drx2とブートコンデンサCbx2とが共通して接続される点よりも直流電源線LL側に設けられている。これにより、ブートコンデンサCbx2の充電経路(直列回路A3,A5)上にダイオードDx2が介在しない。よって、ブートコンデンサCbx2の充電に際して、ダイオードDx2の順方向電圧による電圧低下を招かない。換言すればブートコンデンサCbx2の両端電圧を高めることができる。
ここでは、ブートコンデンサやスイッチング素子の性能について考察する。各スイッチング素子を導通できる値(オン電圧)以上の電圧が通常運転の期間に渡って、それぞれブートコンデンサに充電されているように、各ブートコンデンサの静電容量が設定される。またスイッチング素子Tx1,Ty1,Ty2,S30としてはそれぞれブートコンデンサCbx2,Cbx1,Cby1,Cb1,Cbxを十分に充電できる程度の導通期間を確保できるものが採用される。
図14に例示する電力変換装置はクランプ回路2の有無およびコンバータ1の構成という点で図1に示す電力変換装置と相違している。本電力変換装置はクランプ回路2を備えていない。これは後述するように、コンバータ1が入力端Pr,Ps,Pt側(以下、電源側とも呼ぶ)へと回生可能な構成を有しているからである。ただし、動作異常時の保護等のためにクランプ回路を設置することを妨げるものではない。
他方、通常運転に先立つ充電動作においては上述したように直列回路A10に電流が流れてブートコンデンサCbx1が充電される。ダイオードDx11の順方向電圧をVf2と表記すると、ブートコンデンサCbx1の両端電圧Vcbx1_dは次式で表される。
また通常運転において力行時であればスイッチング素子Tx11は導通しないので、通常運転に先立つ充電動作と同様に直列回路A10に電流が流れてブートコンデンサCbx1が充電される。
図19に例示する電力変換装置は、ブートコンデンサCbx1の接続先という観点で図2に例示する電力変換装置と相違する。なお図19においては、コンバータ1の一つのスイッチングレグを示し、インバータ3の2つのスイッチングレグ(ただし、上側のスイッチング素子のみ)を示している。
Dbx1,Dbx2,Dby1,Dx1 ダイオード
Ed 直流電源
LH,LL 直流電源線
Pr,Ps,Pt 入力端
Pu,Pv,Pw 出力端
VAx1,VAx2,VAy1 電圧調整部
Claims (16)
- 第1の電源線(LH)と、
前記第1の電源線よりも低い電位が印加される第2の電源線(LL)と、
出力端(Py)と、
前記出力端と前記第1の電源線との間に設けられた第1スイッチング素子(Ty1,S30)と、相互間で直流電圧が支持される両端を有し、前記両端のうち低電位側の一端が前記第2の電源線側で前記第1スイッチング素子に接続され、前記第1スイッチング素子へとスイッチ信号を出力するための動作電源となる電源供給部(Cby1)とを有する電力変換部と、
前記第1及び前記第2の電源線の間に設けられた第2スイッチング素子(Tx1,Tx2,S1,Tx)と、
前記第1の電源線側で第2スイッチング素子に接続された一端と、前記電源供給部の他端と電気的に接続される他端とを有し、充電されて前記第2スイッチング素子へとスイッチ信号を出力するための動作電源となるブートコンデンサ(Cbx1,Cbx2,Cb1,Cbx)と、
前記電源供給部の他端から前記ブートコンデンサを経由して前記第1の電源線に至るまでの間に設けられ、前記電源供給部から前記ブートコンデンサへと向かう方向のみ電流を流すダイオード(Dbx1,Dbx2,Db1,Dbx)と
を備える、電力変換装置。 - 前記第1及び前記第2の電源線(LH,LL)の間において、前記第2の電源線側で前記第2スイッチング素子(Tx1)に直列に接続される第3スイッチング素子(Tx2)と、
前記第1の電源線側で前記第3スイッチング素子に接続された一端と、他端とを有し、充電されて前記第3スイッチング素子へとスイッチ信号を出力するための動作電源となる第2ブートコンデンサ(Cbx2)と、
前記ブートコンデンサ(Cbx1)の前記他端又は電源供給部(Cby1)の前記他端と、前記第2ブートコンデンサの前記他端との間で、カソードを前記第2ブートコンデンサ側に向けて設けられた第2ダイオード(Dbx2)と
を更に備える、請求項1に記載の電力変換装置。 - 前記第2スイッチング素子は逆阻止構造を有する、請求項1に記載の電力変換装置。
- 前記第2スイッチング素子は逆阻止構造を有する、請求項2に記載の電力変換装置。
- 前記第2の電源線(LL)側で前記第2スイッチング素子(Tx1)と直列に接続され、アノードを前記第2の電源線に向けて設けられる第2ダイオード(Dx1)と、
前記第2スイッチング素子及び前記第2ダイオードの直列体に対して前記第2の電源線側で直列接続される第3スイッチング素子(Tx2)と、
前記直列体に対して前記第2の電源線側で前記第3スイッチング素子と直列接続される第3ダイオード(Dx2)と、
前記第1の電源線側で前記第3スイッチング素子に接続された一端と、前記ブートコンデンサの前記他端と接続される他端とを有し、充電されて前記第3スイッチング素子へとスイッチ信号を出力するための動作電源となる第2ブートコンデンサ(Cbx2)と
を備える、請求項1に記載の電力変換装置。 - 前記第3ダイオード(Dx2)は前記第3スイッチング素子(Tx2)に対して前記第2の電源線(LL)側に位置する、請求項5に記載の電力変換装置。
- 前記ダイオード(Dx1)は前記第2スイッチング素子(Tx)と前記第1の電源線(LH)との間に設けられる、請求項1に記載の電力変換装置。
- 前記第2スイッチング素子(Tx1)と前記ブートコンデンサ(Cbx1)との接続点と前記第1の電源線との間に設けられる第2ダイオード(Dx1)を更に備え、
前記ダイオード(Dbx1)は、前記電源供給部(Cby1)と前記接続点との間に設けられる、請求項1に記載の電力変換装置。 - 前記第2スイッチング素子(Tx11)と直列に接続されて、カソードを前記第1の電源線(LH)に向けて配置される第2のダイオード(Dx11)と、
第3スイッチング素子(Tx12)と、
前記第3スイッチング素子と直列に接続され、カソードを前記第2の電源線(LL)に向けて配置され、前記第3スイッチング素子との直列体が前記第2スイッチング素子と前記第2ダイオードとの直列体と並列に接続される第3ダイオード(Dx12)と、
前記第2の電源線側で前記第3スイッチング素子と接続された一端と、前記ブートコンデンサ(Cbx11)の前記他端と接続される他端とを有し、充電されて前記第3スイッチング素子へとスイッチ信号を出力するための動作電源となる第2ブートコンデンサ(Cbx12)と、
前記ブートコンデンサと前記第2ブートコンデンサの間で、カソードを前記第2ブートコンデンサに向けて配置される第4ダイオード(Dbx12)と
を更に備える、請求項1に記載の電力変換装置。 - 前記第2スイッチング素子(Tx11)と直列に接続されて、カソードを前記第1の電源線に向けて配置される第2ダイオード(Dx11)と、
第3スイッチング素子(Tx12)と、
前記第3スイッチング素子と直列に接続され、カソードを前記第2の電源線に向けて配置され、前記第3スイッチング素子との直列体が前記第2スイッチング素子と前記第2ダイオードとの直列体と並列に接続される第3ダイオード(Dx12)と、
前記第2の電源線側で前記直列体と直列接続される双方向スイッチング素子(Tx21,Tx22,Dx21,Dx22)と、
前記出力端(Py)と前記第2の電源線(LL)との間に設けられた第4スイッチング素子(Ty2)と、
前記第2の電源線側で前記第4スイッチング素子(Ty2)に接続され、前記第4スイッチング素子へとスイッチ信号を出力するための動作電源となる第2電源供給部(Ed)と、
前記第2の電源線側で前記第3スイッチング素子と接続された一端と、前記第2電源供給部の他端と接続される他端とを有し、充電されて前記第3スイッチング素子へとスイッチ信号を出力するための動作電源となる第2ブートコンデンサ(Cbx12)と、
前記第2ブートコンデンサと前記第2の電源供給部の間で、カソードを前記第2ブートコンデンサに向けて配置される第4ダイオード(Dbx12)と
を更に備える、請求項1に記載の電力変換装置。 - 前記第1の電源線(LH)側で前記第2スイッチング素子(Tx11)と接続する第3スイッチング素子(Tx12)と、
カソードを前記第1の電源線に向けて前記第3スイッチング素子と並列に接続される第2ダイオード(Dx11)と、
カソードを前記第2の電源線(LL)に向けて前記第2スイッチング素子と並列に接続される第3ダイオード(Dx12)と
を更に備え、
前記ブートコンデンサは前記第2スイッチング素子及び前記第3スイッチング素子の接続点に共通して接続されて、前記第2スイッチング素子及び前記第3スイッチング素子へとスイッチ信号を出力するための動作電源として機能する、請求項1に記載の電力変換装置。 - 前記第2スイッチング素子(Tr1,Ts1,Tt1)は複数あって、
前記第2スイッチング素子のいずれもが直接に前記第1の電源線(LH)に接続され、前記ブートコンデンサ(Cbx1)は前記複数の第2スイッチング素子のうち2つ以上の第2スイッチング素子へとスイッチ信号を出力するための動作電源として機能する、請求項1乃至6,9及び10のいずれか一つに記載の電力変換装置。 - 前記電力変換部は、前記電源供給部(Cby1)の電圧を降圧して前記第1スイッチング素子(Ty1)の動作電源として機能させる電圧調整部(VAy1)を更に備える、請求項1乃至11のいずれか一つに記載の電力変換装置。
- 前記第1スイッチング素子(Tu1,Tv1,Tw1)と前記電源供給部(Cbu1,Cbv1,Cbw1)とは複数あって、前記複数の電源供給部の一端は前記第2の電源線(LL)側でそれぞれ前記複数の第1スイッチング素子に接続され、
前記ダイオード(Dbx11)は一の前記複数の電源供給部(Cbu1)の他端と前記ブートコンデンサ(Cbx1)の他端との間に設けられ、
他の一の前記複数の電源供給部(Cbv1)の他端と前記ブートコンデンサの他端との間で、カソードを前記ブートコンデンサに向けて設けられたブートダイオード(Dbx12)
をさらに備える、請求項1乃至11のいずれか一つに記載の電力変換装置。 - 前記第1スイッチング素子(Tu1,Tv1,Tw1)と前記電源供給部(Cu1,Cv1,Cw1)とは複数あって、前記複数の電源供給部の一端は前記第2の電源線(LL)側でそれぞれ前記複数の第1スイッチング素子に接続され、
前記ダイオード(Dx1)は前記第2スイッチング素子(Tx1)と前記第1の電源線(LH)との間に設けられる、請求項1乃至11のいずれか一つに記載の電力変換装置。 - 前記電源供給部は第3ブートコンデンサ(Cby1)であって、
前記出力端(Py)と前記第2電源線(LL)との間に設けられた第4スイッチング素子(Ty2)と、
前記第2の電源線側で第4スイッチング素子に接続された一端と、他端とを有し、前記第4スイッチング素子へとスイッチ信号を出力するための動作電源となる直流電源(Ed)と、
前記第3ブートコンデンサの前記他端と前記直流電源の前記他端との間で、アノードを前記直流電源側にカソードを前記第3ブートコンデンサ側にそれぞれ向けて設けられたダイオード(Dby1)と
を備える、請求項1乃至11のいずれか一つに記載の電力変換装置。
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BR112012017708-7A BR112012017708B1 (pt) | 2010-01-18 | 2010-12-15 | conversor de energia |
US13/516,978 US9166494B2 (en) | 2010-01-18 | 2010-12-15 | Power converter |
CN201080061487.4A CN102714456B (zh) | 2010-01-18 | 2010-12-15 | 电力转换装置 |
AU2010342084A AU2010342084B2 (en) | 2010-01-18 | 2010-12-15 | Power converter |
EP10843159.4A EP2528210A4 (en) | 2010-01-18 | 2010-12-15 | Power converter |
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JP5772583B2 (ja) * | 2011-12-28 | 2015-09-02 | ダイキン工業株式会社 | 空気調和機 |
JP5435057B2 (ja) * | 2012-03-02 | 2014-03-05 | ダイキン工業株式会社 | 電力変換装置 |
US9658632B2 (en) * | 2014-08-27 | 2017-05-23 | Cypress Semiconductor Corporation | Systems, methods, and devices for bootstrapped power circuits |
JP6406129B2 (ja) * | 2015-05-27 | 2018-10-17 | 株式会社デンソー | 電力変換装置 |
CN107437890B (zh) * | 2016-05-25 | 2020-09-01 | 松下知识产权经营株式会社 | 电力变换电路及电力传输系统 |
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JP6982770B2 (ja) * | 2018-02-23 | 2021-12-17 | パナソニックIpマネジメント株式会社 | モータ制御装置 |
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CN102714456B (zh) | 2015-05-06 |
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BR112012017708B1 (pt) | 2019-11-12 |
US9166494B2 (en) | 2015-10-20 |
CN102714456A (zh) | 2012-10-03 |
JP2011147307A (ja) | 2011-07-28 |
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BR112012017708A2 (pt) | 2016-04-19 |
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