WO2011059088A1 - 周波数可変アンテナ回路、それを構成するアンテナ部品、及びそれらを用いた無線通信装置 - Google Patents
周波数可変アンテナ回路、それを構成するアンテナ部品、及びそれらを用いた無線通信装置 Download PDFInfo
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- WO2011059088A1 WO2011059088A1 PCT/JP2010/070302 JP2010070302W WO2011059088A1 WO 2011059088 A1 WO2011059088 A1 WO 2011059088A1 JP 2010070302 W JP2010070302 W JP 2010070302W WO 2011059088 A1 WO2011059088 A1 WO 2011059088A1
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- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01Q—ANTENNAS, i.e. RADIO AERIALS
- H01Q9/00—Electrically-short antennas having dimensions not more than twice the operating wavelength and consisting of conductive active radiating elements
- H01Q9/04—Resonant antennas
- H01Q9/30—Resonant antennas with feed to end of elongated active element, e.g. unipole
- H01Q9/42—Resonant antennas with feed to end of elongated active element, e.g. unipole with folded element, the folded parts being spaced apart a small fraction of the operating wavelength
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- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01Q—ANTENNAS, i.e. RADIO AERIALS
- H01Q5/00—Arrangements for simultaneous operation of antennas on two or more different wavebands, e.g. dual-band or multi-band arrangements
- H01Q5/30—Arrangements for providing operation on different wavebands
- H01Q5/378—Combination of fed elements with parasitic elements
- H01Q5/392—Combination of fed elements with parasitic elements the parasitic elements having dual-band or multi-band characteristics
Definitions
- the present invention relates to a frequency variable antenna circuit capable of changing a resonance frequency, an antenna component constituting at least a part thereof, and a wireless communication apparatus including such an antenna component and corresponding to a plurality of frequency bands.
- An antenna element [radiating element, radiating electrode, radiation path (also simply referred to as a line)] constituting an antenna usually has resonance at a fundamental frequency (fundamental mode) and resonance at a higher order frequency (higher-order mode).
- the fundamental mode is 1/4 wavelength and the higher order mode is 3/4 wavelength.
- the DCS band or the like corresponds to resonance in a higher-order mode.
- the DCS band, PCS band, and UMTS band are about 2 to 2.5 times the frequency of the GSM (registered trademark) band, and the multiple frequency bands are not in a 1: 3 relationship. Cannot handle.
- the bandwidth for obtaining VSWR voltage standing wave ratio
- the frequency bandwidth of GSM (registered trademark) 850/900 band is 136 MHz and the center frequency is 892 MHz
- the specific bandwidth is about 15.3% [136 MHz / 892 MHz].
- the frequency bandwidth of the DCS band, the PCS band, and the UMTS Band 1 band is 460 MHz and the center frequency is 1940 MHz
- the specific bandwidth is about 23.7% [460 MHz / 1940 MHz]. In such a frequency band, it is difficult to obtain impedance matching due to resonance by one antenna element, and a sufficient bandwidth cannot be secured.
- Japanese Patent Laid-Open No. 10-107671 proposed an antenna shown in FIG. This antenna is arranged parallel to the feeding cable 7, the ground electrode GND, the radiation plate 4 (antenna element) connected to the feeding cable 7 at the feeding point A and grounded by the short-circuit pin 8, and the radiation plate 4 Frequency adjusting means 30 provided between the open end and the ground electrode GND.
- the frequency adjustment means 30 includes a variable capacitance diode CR1, and the resonance frequency of the antenna can be adjusted in different frequency bands by controlling the bias current to the variable capacitance diode CR1.
- the variable capacitance diode is also called a varicap diode or a varactor diode.
- Japanese Patent Laid-Open No. 2002-232232 discloses a first antenna element 3 for a first frequency band and a second frequency that share a feeding point A and are grounded at one end by a short-circuit path 8.
- a metal plate 2 provided with a second antenna element 4 for the band, and facing the antenna elements 3 and 4 via an insulator 6 between the first and second antenna elements 3 and 4 and the ground electrode GND;
- a multiband antenna is disclosed in which a variable capacitance diode CR1 connected to a plate 2 is arranged. Since the value of the ground capacitance can be changed by controlling the bias current applied to the variable capacitance diode CR1, this multiband antenna can be used in a plurality of frequency bands.
- the antennas disclosed in Japanese Patent Application Laid-Open No. 10-107671 and Japanese Patent Application Laid-Open No. 2002-232232 change the value of the ground capacitance by a variable capacitance diode arranged in series between the antenna element and the ground electrode, and in a plurality of frequency bands. It is possible to use.
- the variable capacitance diode can continuously change its capacitance by applying a reverse bias voltage.
- the power consumption and the battery voltage have been reduced, and the range of change in the voltage that can be applied to the variable capacitance diode has also been reduced.
- variable capacitance diode is simply disposed between the antenna element and the ground electrode, the change range of the capacitance is limited, and it may be difficult to tune within a desired range. Further, since the change in capacitance is not simply inversely proportional to the applied voltage, it is difficult to adjust the resonance frequency.
- the antenna disclosed in JP 2002-232232 has a plurality of antenna elements arranged on one surface, and the metal plate 2 faces the antenna element so as to face the antenna element. There is a problem of enlargement.
- Japanese Patent Laid-Open No. 2005-150937 discloses that an antenna element 4 connected to a feeding point and an antenna element 4 are electromagnetically coupled as shown in FIG.
- the resonance frequency of the fundamental frequency band based on the antenna operation of the antenna element 4 is variable according to the electrostatic capacitance between the ground-side electrode 21 and the open end K of the antenna element 4, and can be combined with the unpaid antenna element 5.
- the high-order frequency band is widened by the resonance state.
- this antenna is multibanded by the antenna element and a parasitic antenna element that is electromagnetically coupled to the antenna element, and the resonance frequency can be varied by changing the capacitance between the open end of the antenna element and the ground electrode. It is said.
- the resonance frequency in the higher frequency band also changes with the change in the resonance frequency in the low frequency band, and the VSWR characteristics are likely to deteriorate. There is a problem. Further, since the antenna element and the parasitic antenna element are arranged in a plane, there is a problem that the antenna becomes large.
- a first object of the present invention is to provide a variable frequency antenna circuit that can adjust the resonance frequency within a desired range and is suitable for use in a wireless communication device such as a cellular phone.
- the second object of the present invention is to cope with a wide range of frequency bands from the low frequency band to the high frequency band, and the resonance frequency of the low frequency band is made variable while the influence on the resonance state in the high frequency band is small. It is an object to provide a small frequency variable antenna circuit, an antenna component used therefor, and a wireless communication apparatus using them.
- a third object of the present invention is to provide a wireless communication device using such a variable frequency antenna circuit (component).
- the frequency variable antenna circuit of the present invention includes a first antenna element having one end serving as a feeding point and the other end serving as an open end, and frequency adjusting means coupled to the first antenna element via coupling means.
- the frequency adjusting means includes a parallel resonant circuit including a variable capacitance circuit and a first inductance element, and a second inductance element connected in series to the parallel resonant circuit.
- the coupling means is any one of a connection line, a capacitance element, an inductance element, and an electrode that is electromagnetically coupled to the first antenna element.
- the frequency variable antenna circuit of the present invention preferably includes a control circuit that changes the capacitance value of the variable capacitance circuit.
- the frequency variable antenna circuit of the present invention includes detection means for detecting a change in the resonance frequency of the first antenna element, and the control circuit sends a control signal for changing a capacitance value based on an output of the detection means to the variable capacitance circuit. It is preferable to provide feedback.
- a directional coupler or the like can be used as means for detecting a change in the resonance frequency to be tuned by a change in the reflected wave of the transmission signal. Further, in order to detect a change in the resonance frequency based on the received signal, a change in the gain of the received signal may be detected.
- the frequency variable antenna circuit of the present invention further includes a second antenna element that is integral with the first antenna element, shares the feeding point, and is shorter than the first antenna element, It is preferable to make a multi-band by double resonance of resonance and resonance of the second antenna element.
- a configuration having three or more antenna elements may be used.
- the first antenna element and the second antenna element preferably share a part of the route from the feeding point.
- a first antenna component of the present invention includes a strip-shaped first antenna element, and frequency adjusting means coupled to the first antenna element via coupling means, the frequency adjusting means comprising a variable capacitance circuit and a first A frequency variable antenna circuit comprising a parallel resonant circuit including one inductance element and a second inductance element connected in series to the parallel resonant circuit is configured, the first antenna element being open at one end serving as a feeding point And a part of the first antenna element is electromagnetically coupled to the coupling means.
- the antenna component of the present invention further includes a band-shaped second antenna element that shares the feeding point and is shorter than the first antenna element, and that combines resonance of the first antenna element and resonance of the second antenna element.
- the frequency variable antenna circuit is preferably multibanded by resonance. It is preferable that a part of the first antenna element is opposed to the second antenna element at a predetermined interval.
- the coupling means preferably has a coupling electrode formed on a support made of a dielectric or soft magnetic material. It is preferable that a connection electrode is formed on the support at a predetermined interval from the coupling electrode and connected to the first antenna element.
- the antenna element and the coupling means are preferably arranged on a mounting board separated from the main circuit board.
- the variable capacitance circuit of the frequency adjusting means is preferably disposed on the mounting board and connected to the coupling means via a connection line.
- the second antenna component of the present invention includes an antenna element provided on a mounting board separated from a main circuit board, a coupling means provided on the mounting board so as to be electromagnetically coupled to the antenna element, and the coupling Frequency adjusting means provided on the mounting substrate so as to connect to the means,
- the antenna element has a band-shaped first antenna element and a second antenna element that are integrally connected so as to share a feeding point, and the second antenna element is shorter than the first antenna element
- the coupling means includes a coupling electrode formed on a dielectric chip attached to the mounting substrate and electromagnetically coupled to a part of the first antenna element.
- the electromagnetic coupling position between the coupling electrode and the first antenna element is not particularly limited, and may be set as appropriate in consideration of the current distribution of the first antenna element.
- the amount of change in the resonance frequency is large, and when installed on the feed point side, the gain is large.
- the dielectric chip preferably has a connection line between the coupling electrode and the frequency adjusting means.
- the coupling electrode is a strip electrode extending substantially parallel to the first antenna element, and a part of the connection line extends substantially parallel to the coupling electrode.
- the connection line is preferably a meander line.
- the first antenna element preferably has a folded portion.
- the first antenna element has a portion extending from the folded portion in the same direction as the second antenna element and a portion extending in the opposite direction, and the dielectric chip is a part of a portion extending in the same direction as the first antenna element. It is preferable to be separated from the portion extending in the opposite direction.
- the wireless communication device of the present invention includes the frequency variable antenna circuit (component).
- the frequency variable antenna circuit (component) of the present invention includes a first antenna element and frequency adjusting means coupled to the first antenna element via coupling means, and the frequency adjusting means includes the variable capacitance circuit and the first Since the parallel resonance circuit including the inductance element and the second inductance element connected in series to the parallel resonance circuit are provided, the resonance frequency can be adjusted within a desired range while being small. In addition, by providing the first and second antenna elements that share the feed point, the resonance frequency can be adjusted so that it can be applied to the low frequency band and the high frequency band and can be received in a wide frequency band. .
- FIG. 1 It is the schematic which shows an example of the frequency variable antenna circuit of this invention. It is the schematic which shows an example of the frequency adjustment means used for the frequency variable antenna circuit of this invention. It is a figure which shows an example of the antenna element used for the frequency variable antenna circuit of this invention. It is a graph which shows roughly the VSWR characteristic of the frequency variable antenna circuit of this invention. It is a graph which shows roughly the change of the VSWR characteristic by a frequency adjustment means. It is a graph which shows roughly the change of the VSWR characteristic by a frequency adjustment means. It is a figure which shows the equivalent circuit of an example of the frequency adjustment means used for the frequency variable antenna circuit of this invention. FIG.
- FIG. 8 is a diagram showing an equivalent circuit of a capacitance unit that constitutes the frequency adjusting means of FIG. It is a figure which shows the equivalent circuit of another example of the frequency adjustment means used for the frequency variable antenna circuit of this invention. It is a figure which shows the equivalent circuit of another example of the frequency adjustment means used for the frequency variable antenna circuit of this invention. It is a figure which shows the equivalent circuit of another example of the frequency adjustment means used for the frequency variable antenna circuit of this invention. It is a figure which shows the equivalent circuit of another example of the frequency adjustment means used for the frequency variable antenna circuit of this invention. It is a block diagram which shows an example of the tuning circuit using the frequency variable antenna circuit of this invention. It is a graph which shows the shift
- FIG. 38 is a cross-sectional view showing the antenna component of FIG. 37.
- FIG. It is a perspective view which shows another example of the conventional antenna component.
- FIG. 1 shows an example of a frequency variable antenna circuit of the present invention.
- the frequency variable antenna circuit 1 includes an antenna element 10, a coupling means 20 that is electromagnetically coupled to the antenna element 10, and a frequency adjusting means 30 that is connected to the coupling means 20 and the ground electrode GND.
- the frequency adjusting unit 30 includes a parallel circuit including a variable capacitance circuit Cv and a first inductance element L1, and a second inductance element L2 connected to the parallel circuit.
- the parallel circuit is on the terminal T1 side, and the second inductance element L2 is connected to the ground electrode GND via the terminal T2, but the second inductance element L2 may be on the terminal T1 side.
- the coupling means 20 can be constituted by any of a connection line, a capacitance element, an inductance element, or an electrode that is electromagnetically coupled to the antenna element 10.
- FIG. 3 shows an example of the antenna element 10 constituting the variable frequency antenna circuit of FIG.
- the antenna element 10 will be described by taking an inverted F antenna as an example.
- the antenna element 10 is not limited thereto, and for example, a monopole antenna, an inverted L antenna, a T antenna, or the like may be used.
- the antenna element 10 has a feeding point A at one end and an open end C at the other end, and includes a section 10a between the feeding point A and the bending point B and a section 10b between the bending point B and the opening end C. .
- the section 10b extends substantially parallel to the ground electrode GND.
- a ground line 15 extends from the bending point B of the antenna element 10 to the ground electrode GND.
- the antenna element 10 has a length (section 10a + total length of the section 10b) equal to about 1/4 of the wavelength ⁇ 1 of the resonance frequency f1r within the fundamental frequency band, and operates in the series resonance mode.
- a length section 10a + total length of the section 10b
- the current distribution when the antenna element 10 having an inverted-F antenna shape is in series resonance is 0 at the open end C, and is the maximum near the connection point (bending point B) with the ground line 15, so the length of the section 10b is Controls the incident / radiation behavior of the antenna element 10. Since the voltage at the connection point with the ground line 15 is substantially 0 and the impedance is in a short state, the impedance of the antenna element 10 can be adjusted by adjusting the position of the connection point with the ground line 15. it can.
- resonance is manifested at a plurality of frequencies.
- the resonance frequency f2r of the parallel circuit composed of the first inductance element L1 and the variable capacitance circuit Cv in the frequency adjusting means 30 is lower than the resonance frequency f1r of the antenna element 10, and the series resonance circuit composed of the variable capacitance circuit Cv and the second inductance element L2
- the resonance frequency f3r is higher than the resonance frequency f1r of the antenna element 10, and the capacitance of the variable capacitance circuit Cv and the inductances of the first and second inductance elements L1 and L2 so that the resonance frequencies f2r and f3r do not occur in the low frequency band. Is set.
- Resonant frequencies f2r and f3r change when the capacitance is changed by the variable capacitance circuit Cv.
- the resonance frequencies f2r and f3r move to the low frequency side when the capacitance increases (f2r ⁇ f2'r, f3r ⁇ f3'r), and conversely move to the high frequency side when the capacitance decreases (f2'r ⁇ f2r, f3 ′).
- r ⁇ f3r Accordingly, the resonance frequency f1r of the antenna element 10 also moves to the low frequency side (f1r ⁇ f1′r) or the high frequency side (f1′r ⁇ f1r).
- the resonance frequency f1r of the antenna element 10 can be changed by only one of the parallel circuit and the series circuit, but the amount of change in the resonance frequency within the capacitance variable range of the variable capacitance circuit Cv is small with the series circuit alone, and is desired. Tuning in the frequency band may be difficult. Further, the amount of change in the resonance frequency is large only with the parallel circuit, and it is difficult to accurately control the resonance frequency f1r of the antenna element 10.
- Figures 5 and 6 show the VSWR characteristics of antennas with different conditions.
- a curved line st0 indicated by a solid line indicates the VSWR characteristic of the configuration A (only the frequency variable antenna circuit 1 shown in FIG. 3 excluding the frequency adjusting unit 30 and the coupling unit 20) including the antenna element 10.
- a curved line st1 indicated by a broken line indicates a VSWR characteristic of the configuration B (configuration in which the frequency adjustment unit 30 is removed from the frequency variable antenna circuit 1) including the antenna element 10 and the coupling unit 20.
- a curve st2 indicated by an alternate long and short dash line indicates a VSWR characteristic of the configuration C including the antenna element 10 and the coupling unit 20, and the coupling unit 20 is grounded via the inductance element L2.
- the curve st3 shown by the one-dot chain line in FIG. 6 shows the VSWR characteristics of the same configuration D as the frequency variable antenna circuit 1 shown in FIG. 3 except that the variable capacitance circuit Cv in the frequency adjusting means 30 is replaced with a capacitance element having a constant capacitance value.
- An example in which the resonance frequency fst0 of configuration A is 900 MHz is described below. Note that although the amount of change in the resonance frequency changes depending on the configuration of the antenna, the tendency of the change in the resonance frequency itself does not change.
- the coupling means 20 having the coupling electrode formed on the dielectric support is disposed at a predetermined distance from the antenna element 10, a coupling capacitance of several pF or less is generated by the coupling electrode, and The resonance frequency moves to the low frequency side by the dielectric disposed in the vicinity of the antenna element 10 (fst0 ⁇ fst1).
- the amount of change in the resonance frequency is about 50 to 300 MHz, depending on the coupling capacitance. If the coupling capacitance is small, the amount of change in the resonance frequency is small, and if the coupling capacitance is large, the amount of change in the resonance frequency is large. Even when a capacitance element of several pF was connected in series between the coupling means 20 and the ground electrode instead of the variable capacitance circuit Cv, the resonance frequency fst1 was not changed.
- variable capacitance circuit Cv is connected in series to the inductance element L2 in the present invention, it is natural to use the capacitance element as the coupling means 20 to obtain the resonance ⁇ .
- a connection line may be used.
- the coupling means 20 coupled to the antenna element 10 is grounded via the frequency adjusting means 30 which is a combination of a parallel circuit and a series circuit.
- the frequency adjusting means 30 which is a combination of a parallel circuit and a series circuit.
- variable capacitance circuit Cv a combination of SPnT (single pole n throw) switch and capacitance element, variable capacitance diode (varicap diode, varactor diode), digital variable capacitance element, MEMS (Micro-ElectromechanicalElectroSystems), etc. can be used.
- SPnT switch a GaAs switch or a CMOS switch may be used alone, or one or a plurality of PIN diodes may be used.
- variable capacitance circuit Cv is connected to the antenna element 10 via the coupling means 20, so that the high frequency of the semiconductor is high frequency. No signal is input and signal distortion can be suppressed.
- FIG. 7 shows an equivalent circuit of frequency adjusting means using a digital variable capacitance circuit.
- This digital variable capacitance circuit may be the same as that disclosed in, for example, Japanese Patent Application Laid-Open No. 2008-166877.
- the variable capacitance circuit Cv includes capacitance elements C1 to Cn connected in parallel between the terminal T1 and the terminal T2, and switch circuits SW1 to SWn connected in series between the terminal T2 and the capacitance elements C1 to Cn-1.
- the capacitance elements C1 to Cn-1 and the switch circuits SW1 to SWn-1 constitute capacitance units CU1 to CUn-1.
- Each of the switch circuits SW1 to SWn-1 can be composed of a MOS-FET.
- FIG. 8 shows an example of each capacitance unit.
- Each capacitance unit CU1 to CUn-1 is composed of a series circuit of a capacitance element and a drain-source between MOS-FETs connected in multiple stages. Since placing the FET on the side closer to the ground electrode GND provides better power resistance, in the example shown, the variable capacitance circuit Cv is connected so that the terminal T1 is on the coupling means 20 side and the terminal T2 is on the ground electrode GND side. However, the connection may be reversed.
- the voltage supply to the gate terminals of the FETs connected in multiple stages in each capacitor unit CU1 to CUn-1 is performed by the common signal lines 61 to 6n-1, and the input ports P1 to Pn of the common signal lines 61 to 6n-1
- a bit of data for ON / OFF control of the FET is supplied from the control circuit 205 to -1.
- the capacitance element Cn and the capacitance units CU1 to CUn-1 are connected in parallel between the terminal T1 and the terminal T2, but the capacitance of the capacitance elements C1 to Cn-1 in each capacitance unit CU1 to CUn-1
- the values are preferably configured as a binary weighted capacitance array corresponding to each data bit.
- the capacitance unit corresponds to the lower bit to the upper bit in the order of CU1 to CUn-1
- the capacitance value of the capacitance element C1 of the capacitance unit CU1 is epF
- the capacitance value of the capacitance element C2 of the capacitance unit CU2 is 2 1 ⁇ e pF
- the capacitance value of the capacitance element C3 of the capacitance unit CU3 is 2 2 ⁇ e pF
- the capacitance value of the capacitance element Cn-2 of the capacitance unit CUn-2 is 2 n-3 ⁇ e pF
- the capacitance value of the capacitance element Cn-1 of the capacitance unit CUn-1 is 2 n-2 ⁇ e pF.
- the bit of data for ON / OFF control of the FET is “00000”
- the bit is “11111”.
- the capacity value can be adjusted in 32 stages (also called states).
- the capacitance value C (composite capacity) of the variable capacitance circuit Cv changes linearly from Cmin (corresponding to the bit string “00000”) to Cmax (corresponding to the bit string “11111”).
- Cmin corresponding to the bit string “00000”
- Cmax corresponding to the bit string “11111”.
- the circuit constants of the frequency variable antenna circuit such as the inductance elements L1 and L2 are set.
- the number of steps of the capacitance and the variable range differ depending on the number of bits, and the change width of the resonance frequency also differs.
- FIG. 9 and FIG. 10 show an example of frequency adjusting means using an SPnT (single pole n throw) switch and a capacitance element as the variable capacitance circuit Cv.
- an SP3T switch is used, and in FIG. 10, an SP2T switch is used.
- the common port P1 side of the switch is the terminal T1 side (coupling electrode 20 side)
- the single port P2, P3, P4 side is the terminal T2 side (ground side)
- the capacitance values differ for each of the single ports P2, P3, P4 Capacitance elements C1, C2, and C3 are connected in series. Since the connection path is changed by switching the switch, a capacitance value corresponding to the connection path is selected, and the resonance frequency is changed.
- variable capacitance circuit Cv of FIG. 9 the series circuit of the inductance element L1 and the capacitance element Cp1 is connected in parallel, and the inductance element L3 is connected in series with the parallel circuit on the terminal T1 side.
- the inductance element L3 and the capacitance element Cse1 are connected in series with the parallel circuit on the terminal T1 side, and the inductance element L1 is connected in parallel to the connection point between the inductance element L3 and the capacitance element Cse1.
- Capacitance elements Cp1 and Cse1 are DC cut capacitors, which stabilize the switch operation.
- the inductance element L3 is provided for the purpose of finely adjusting the inductance.
- variable capacitance circuit Cv shown in FIGS. 9 and 10 Even if the connection direction of the variable capacitance circuit Cv shown in FIGS. 9 and 10 to the switch circuit SW is reversed (the switch circuit SW is on the terminal T2 side and the capacitance element is on the terminal T1 side), the same variable capacitance function is obtained.
- the DC cut capacitors Cp1 and Cse1 are not necessary.
- FIG. 11 shows an example of a variable capacitance circuit Cv using a variable capacitance diode.
- the cathode side of the variable capacitance diode Dv is connected to the terminal T1 side via the DC cut capacitor Cc.
- a reverse bias voltage is applied to the variable capacitance diode Dv
- the width of the internal depletion layer changes, and the capacitance changes continuously. Since the capacitance decreases as the reverse voltage applied to the cathode side of the variable capacitance diode Dv increases, the resonance frequency can be changed in accordance with the change width of the voltage that can be applied to the variable capacitance diode.
- a bias supply circuit for arbitrarily changing the reverse bias voltage is required.
- variable capacitance diode Dv When a large voltage amplitude is input to the variable capacitance diode Dv, a forward bias is applied due to the voltage amplitude, and the forward operation should be performed where the reverse operation should be performed. .
- a countermeasure if another variable capacitance diode is added using the cathode as a common terminal, it is possible to prevent a control voltage having a large amplitude from entering the forward direction.
- the resonance frequency of the antenna element may shift due to the influence of disturbance such as a human body.
- the impedance matching state changes.
- the variable frequency antenna circuit of the present invention the resonance frequency of the antenna element can be easily adjusted.
- FIG. 12 shows an example of a feedback circuit using a variable frequency antenna circuit. Based on the detection result, directional coupler 35 that detects the reflected wave of the transmission signal, detection circuit Di, signal level detector 33 that compares the detection signal from the external reference signal and detection circuit Di, and detects the signal level
- the control circuit 32 changes the capacitance value of the variable capacitance circuit and corrects the deviation of the resonance frequency when the reflected wave becomes large.
- the coupling means and the like are not shown.
- This feedback circuit performs feedback based on the intensity change of the received signal.
- FIG. 13 shows the VSWR characteristics in the free state and the actual use state.
- variable capacitance circuit of the frequency adjusting means 30 is programmed to have a combined capacitance that optimizes the VSWR in the transmission frequency band (for example, the intermediate frequency of 836.5 ⁇ ⁇ MHz) and the reception frequency band (for example, the intermediate frequency of 881.5 MHz) in the free state. ing. If the frequency shift due to disturbance is relatively small, VSWR below a predetermined level can be maintained in the transmission frequency band and the reception frequency band.
- the effect on the VSWR characteristics of the human body appears as a shift in resonance frequency of about 10 to 30 MHz.
- the difference in resonance frequency is not greatly different between the transmission frequency band and the reception frequency band, and is almost the same. Therefore, the control result in either the transmission frequency band or the reception frequency band should be used for control in the other frequency band. Can do.
- the stage of the digital variable capacitance circuit is changed by one step by the control circuit so that the combined capacitance of the digital variable capacitance circuit becomes large (or small).
- the step of changing may be two or more steps.
- the feedback control is continued until the reflected wave becomes smaller than the threshold value, and the feedback control is finished when the reflected wave becomes smaller than the threshold value. If the reflected wave does not become smaller than the threshold value or increases, the feedback control is terminated, and the variable is digitally variable so that the reflected wave becomes the smallest stage (State) based on the detected signal level.
- the capacitor circuit may be controlled.
- the antenna element 10 shown in FIG. 3 is composed of a line extending horizontally with respect to the ground electrode GND. However, it is preferable that the antenna element 10 is miniaturized by providing a folded portion as shown in FIG. There may be a plurality of folded portions.
- the antenna element 10 shown in FIG. 14 includes a section 10a between the feeding point A and the bending point B, a section 10b between the bending point B and the bending point C, and between the bending point C and the bending point D. There is a section 10c and a section 10d between the bending point D and the open end E. The section 10c is a folded portion, and the section 10d extends in the opposite direction to the section 10b.
- the antenna element shown in FIG. 10 Since the length from the feeding point A to the open end E is substantially the same length as the antenna element 10 shown in FIG. 3 and corresponds to the resonance frequency f1r in the low frequency band, the antenna element shown in FIG. 10 operates in series resonance mode. Since the antenna element 10 having the folded portion has a more complex resonance current distribution than that in the case of FIG. 3, it can be shortened. If the length from the feed point A to the bending point C is substantially 1/4 of the wavelength ⁇ 2 corresponding to the resonance frequency in the high frequency band, a multi-resonant antenna operating in the series resonance mode is obtained. Can be easily realized.
- the antenna element 10 may have an antenna element 12 extending from a branch point D in a section 10a between the feeding point A and the bending point B.
- the antenna element 12 includes a section 12a between the feeding point A and the branch point D and a section 12b between the branch point D and the open end E.
- the section 12a of the antenna element 12 is common to a part of the section 10a of the antenna element 10, and the section 12b extends in the same direction as the section 10b of the antenna element 10. If the antenna element 10 has a resonance frequency in the low frequency band and the antenna element 12 has a resonance frequency in the high frequency band, a double resonance antenna is obtained.
- the antenna element 10 is a so-called flexible substrate made of a rigid substrate such as a glass fiber reinforced epoxy resin substrate, a polyimide such as polyimide, polyetherimide, or polyamideimide, a polyamide such as nylon, or a polyester such as polyethylene terephthalate. It can form by performing well-known methods, such as an etching and photolithography, with respect to a printed circuit board. Alternatively, a known method such as a printing method or an etching method may be used to form a low resistance conductor such as Au, Ag, or Cu on a substrate made of a dielectric ceramic such as alumina.
- the antenna element formed on the deformable flexible substrate can be efficiently arranged in a limited space in the housing.
- FIG. 16 shows an example in which antenna elements and coupling means are formed on a substrate.
- the copper foil on the glass fiber reinforced epoxy resin substrate is etched to form the antenna element 10, the electrode pattern of the coupling means 20, the ground electrode GND, the connection lines 21, 22 and the like.
- the ground electrode GND is not formed on the back surface of the substrate. According to this method, not only can each electrode pattern be formed easily and accurately, but also an antenna component that is resistant to the influence of external force and the like can be obtained.
- the frequency variable antenna circuit can be easily manufactured only by mounting the components constituting the frequency adjusting means 30.
- the antenna element may be composed of a thin conductor plate made of Cu or phosphor bronze. Since the conductor thin plate itself is easily processed and has a characteristic that it is not easily deformed by an external force, the antenna element can be formed in a free shape regardless of the support. When a conductor thin plate is integrated with an engineering plastic such as a liquid crystal polymer by injection molding, an antenna component that is not easily deformed by an external force is obtained.
- Fig. 17 shows an example in which an antenna element formed of a thin conductor plate such as phosphor bronze is erected on a glass fiber reinforced epoxy resin substrate having a ground electrode GND made of copper foil and connection lines 21 and 22 formed on the surface.
- the open end of the antenna element 10 is fixed to a support 27 made of a dielectric chip disposed on the substrate.
- an L-shaped electrode pattern is formed as coupling means 20 for electromagnetically coupling to the antenna element 10.
- the coupling means 20 is connected to the ground electrode GND via connection lines 21 and 22 and frequency adjusting means 30 formed on the substrate.
- the radiation gain improves as the antenna element is separated from the ground electrode. Therefore, when the antenna element 10 is made high, not only can the antenna component be configured three-dimensionally, but also the space between the antenna element and the ground electrode can be secured with a small formation area.
- the first antenna element 10 and the second antenna element 12 shorter than the first antenna element 10 may be formed on the large dielectric chip 27 together with the coupling means 20 and the connection line 21.
- the coupling means 20 formed on the additional support 29 is disposed in the vicinity of the antenna element 10.
- the coupling means 20 is disposed in the recessed space of the support 29 having a U-shaped cross section.
- the material of the support 29 may be polycarbonate or the like.
- the antenna element and other components may be provided on different substrates, or the antenna element formed on the ceramic body may be mounted on the printed board. Further, a part of the antenna element 10 may be formed of a thin conductor plate such as phosphor bronze, and the other part may be formed of an electrode pattern on the printed board. Further, in order to adjust the electromagnetic coupling with the coupling means 20, the shape (width and thickness) of the portion of the antenna element 10 facing the coupling means 20 may be different from the other parts. The material of the support, the shape and dimensions of the coupling means 20, the distance from the antenna element 10 and the like are adjusted so as to obtain the optimum coupling between the antenna element 10 and the coupling means 20 while ensuring a sufficient frequency variable range. .
- the coupling means 20 may be formed directly on the substrate together with the antenna element 10 or may be mounted on the substrate after being formed on the support.
- the coupling means 20 formed of a thin conductor (metal) plate having rigidity may be combined with the antenna element 10, but it is difficult to arrange the gap with the antenna element 10 with high accuracy. preferable.
- the coupling means 20 formed on the support 27 is not deformed even when an external force is applied, so that the distance from the antenna element 10 does not change, and it is easy to position the coupling means 20 with respect to the antenna element 10 at a predetermined distance.
- the support 27 of the coupling means 20 arranged in the vicinity of the antenna element 10 exhibits a wavelength shortening effect and shortens the line length of the antenna element 10.
- the coupling means 20 is formed by an electrode pattern formed on the surface of the support 27.
- the material of the electrode pattern is preferably Cu, Ag, Au, or an alloy containing these.
- the support 27 is made of dielectric ceramic such as alumina, Al-Si-Sr ceramic, Mg-Ca-Ti ceramic, Ca-Si-Bi ceramic, Ni-Zn ferrite, Ni-Cu-Zn ferrite, etc. It is preferably made of a soft magnetic ceramic. Glass fiber reinforced epoxy resins can also be used. Since the support 27 is used in a high frequency band, the support 27 is preferably excellent in high frequency characteristics.
- the dielectric material forming the support 27 preferably has a relative dielectric constant of 5 to 30. The temperature characteristics of the material forming the support 27 may be determined together with the characteristics of the reactance element used in the resonance circuit.
- FIG. 21 to 24 show examples of the coupling means 20 formed on the support 27.
- FIG. Each support 27 is formed with a connection electrode pattern 42 to be soldered to the antenna element 10.
- the electrode pattern 42 electrically connected to the antenna element 10 may function as an extension electrode.
- the coupling between the antenna element 10 and the coupling means 20 is determined by the distance between the electrode pattern 42 formed on the support 27 and the coupling means 20.
- the electrode pattern 42 is not necessary, but the positioning of the support 27 with respect to the antenna element 10 is difficult.
- the electrode pattern 42 may be formed on the lower surface of the support 27 as a mounting terminal electrode on the substrate.
- a strip-shaped electrode pattern forming the coupling means 20 is formed on the side surface of the support 27, and the connection line 21 is formed on the same side surface as an electrode pattern integrated with the electrode pattern of the coupling means 20 Thus, an L-shaped electrode pattern is formed.
- a belt-like electrode pattern that forms the coupling means 20 together with the electrode pattern 42 is formed on the upper surface of the support 27, and is connected to the connection line 21 formed on the side surface.
- the connection line 21 may be linear, but may be L-shaped as shown in FIG. 23 or meandered as shown in FIG.
- connection line 21 with a line portion substantially parallel to the electrode pattern of the coupling means 20 because the average gain in the fundamental frequency band is improved.
- the electrode pattern of the coupling means 20 shown in the figure is a band-like electrode having a constant width, but is not limited, and can be appropriately selected according to desired electromagnetic coupling such as a tapered electrode.
- the variable range of the resonance frequency of the antenna element 10 due to the capacitance change of the frequency adjusting means 30 may be extremely narrow. Therefore, it is preferable to arrange the frequency adjusting means 30 in the vicinity of the antenna element 10 and ground it at a short distance (for example, 1/4 wavelength or less of the frequency band to be adjusted).
- FIG. 25 shows an example of a circuit of a radio communication device that includes the variable frequency antenna circuit (antenna part) 1 according to the present invention and supports a plurality of communication systems.
- the variable frequency antenna circuit 1 can obtain a desired VSWR characteristic in a low frequency band and a high frequency band, and makes a resonance frequency variable in a low frequency band.
- GSM registered trademark
- DCS, PCS, UMTS, etc. can be used for the high frequency band.
- the illustrated wireless communication device supports four communication systems of GSM (registered trademark) 850/900 band (824 to 960 MHz), UMTS band (Band 1: 1920 to 2170 MHz, Band 5: 824 to 894 MHz).
- GSM registered trademark
- UMTS band Band 1: 1920 to 2170 MHz, Band 5: 824 to 894 MHz.
- the switch circuit SW is an electrical switch including, for example, an FET switch as a main component, and changes a connection state according to a control voltage applied to a gate.
- the switch circuit SW includes a frequency variable antenna circuit 1, a high-frequency amplifier PA and a low-noise amplifier LNA, which are transmission / reception front ends for a first CDMA communication system (UMTS Band 5), and a second CDMA communication system ( High-frequency amplifier PA and low-noise amplifier LNA that are transmission / reception front ends for UMTS Band 1), high-frequency amplifier PA and low-noise amplifier LNA that are transmission / reception front ends for the first TDMA communication system (GSM900), and TDMA-type Provided between a high-frequency amplifier PA and a low-noise amplifier LNA, which are transmission / reception front ends for the second communication system (GSM850), and switches transmission / reception signals of each communication system.
- GSM900 high-frequency amplifier PA and low-noise amplifier LNA that are transmission / reception front ends for the first TDMA communication system
- GSM850 second communication system
- the low-noise amplifier LNA among the high-frequency amplifier PA and the low-noise amplifier LNA is built in RFIC (Radio-Frequency Integrated Circuit).
- the RFIC is an IC that converts a signal from the baseband unit BBIC into a transmission frequency together with a frequency thin sensorizer (not shown) or the like, and converts a received signal into a frequency that can be processed by the baseband unit BBIC.
- the low-noise amplifier LNA for the first CDMA communication system (UMTS Band 5) and the low-noise amplifier LNA for the second TDMA communication system (GSM850) are shared.
- a duplexer formed by connecting filters such as a low-pass filter and a band-pass filter and filters having different pass bands in parallel is arranged.
- filters such as a low-pass filter and a band-pass filter and filters having different pass bands in parallel
- an unbalanced input-balanced output SAW filter, BAW filter, or BPAW filter is used as the bandpass filter and duplexer, and an inductance element L for impedance adjustment is arranged between the balanced output terminals.
- a capacitance element may be disposed between the balanced output terminals, or a reactance element may be disposed between each balanced output terminal and the ground.
- the wireless communication device generates a local oscillation frequency signal using a control signal from a central processing circuit included in a logic circuit unit (not shown) by a frequency synthesizer, and performs transmission / reception at a frequency determined thereby.
- the variable capacitance circuit in the frequency variable antenna circuit 1 is set to a suitable VSWR in the transmission frequency band and the reception frequency band in the low frequency band of each communication system by the control signal output from the control circuit 32 shown in FIG. Be controlled.
- FIG. 26 shows an example of the frequency variable antenna component of the present invention (corresponding to a low frequency band and a high frequency band), and FIGS. 27 and 28 show its appearance.
- the power supply path to the variable capacitance circuit Cv of the frequency adjusting means 30 is omitted.
- the frequency variable antenna circuit 1 is formed on an antenna substrate 80 that is separated from a main circuit board (not shown) on which the power feeding circuit 200 is formed, and the antenna substrate 80 and the main circuit board are connected by a coaxial cable. Done.
- a connection method for example, a pressing connection (called C-clip) using a grounded leaf spring terminal provided on the main circuit board is used.
- the connection part of the antenna substrate is only the connection electrode terminal.
- the antenna element 10 formed of a conductor thin plate made of Cu includes a first antenna element 10 for low frequency band (consisting of sections 10a, 10b, 10c and 10d) and an auxiliary line 25 branched from the first antenna element 10. And a part of the second antenna element 12 for the high frequency band that is partly opposed to the first antenna element 10 and shorter than the first antenna element 10.
- the auxiliary line 25 branched from the first antenna element 10 contributes to incident radiation of the high frequency signal in the low frequency band together with the first antenna element 10. Therefore, the auxiliary line 25 may be regarded as a part of the first antenna element 10.
- the entire antenna element is composed of an integral strip-shaped conductor having a thickness of 0.2 mm and a width of 1 to 1.5 mm, which is folded back and forth.
- the first antenna element 10 and the second antenna element 12 are used in the low frequency band and the high frequency band. This constitutes an inverted F antenna that resonates at a frequency of.
- the antenna elements are erected on both sides of an antenna substrate (glass fiber reinforced epoxy substrate with copper clad on both sides) 80.
- a part of the first antenna element 10, the second antenna element 12 and the auxiliary line 25 are located on the first main surface of the antenna substrate 80, the first antenna element 10 is bent, and the section 10c is the second main element on the opposite side.
- the section 10d extends toward the feeding point A in parallel and in the opposite direction to the section 10b.
- the first antenna element 10 has a plurality of sections, but the section 10d on the second main surface faces the section 12b of the second antenna element 12 on the first main surface through the antenna substrate 80.
- a dielectric chip 18 having an electrode pattern formed on the surface is disposed under a part of the section 12b of the second antenna element 12. Since the dielectric chip 18 extends to the vicinity of the section 10b and the section 10d, the electromagnetic coupling between the section 10b and the section 12b and between the section 10d and the section 12b is stronger than other portions. There is. Further, since the electrode pattern formed on the surface of the dielectric chip 18 is connected to the second antenna element 12, the second antenna element 12 shortens its line length due to the wavelength shortening effect.
- the antenna substrate 80 constitutes a support body 27 having a coupling means 20 electromagnetically coupled to the auxiliary line 25 formed on the surface, and a frequency adjusting means 30 connected to the coupling means 20.
- Digital variable capacitance circuit element Cv, first and second inductance elements L1 and L2, dielectric chip 18 for adjusting electromagnetic coupling between first antenna element 10 and second antenna element 12, and matching inductance An element Lp and a capacitance element Cp are mounted.
- at least a part of the matching inductance element Lp and capacitance element Cp and frequency adjusting means 30 arranged on the same surface of the antenna substrate 80 may be provided on the back surface.
- the coupling means 20 is composed of an Ag electrode pattern formed on the surface of a support 27 made of a dielectric ceramic.
- An electrode pattern for soldering to the auxiliary line 25 is formed on the support 27.
- the antenna element is provided with a plurality of electrode extensions. The antenna element is fixed to the antenna substrate 80 by the electrode extensions, and further connected to the electrode pattern on the upper surface of the support 27 by the auxiliary line 25. No electromagnetic waves are radiated from the electrode extension toward the antenna substrate 80 side.
- a dielectric ceramic having a relative dielectric constant of 10 was used for the dielectric chip 18 and the support 27.
- the section 10b of the first antenna element 10 on the first main surface has a length of about 25 mm
- the auxiliary line 25 has a length of about 15 mm
- the first antenna element 10 on the second main surface has a length of about 15 mm.
- the section 10d was about 20 mm long
- the section 12b of the second antenna element 12 was about 20 mm long.
- the digital variable capacitance circuit element Cv is the first capacitance element C6 (1.50 pF) and the capacitance elements C1 (0.15 pF), C2 (0.30 pF), C3 (0.60 pF) of the capacitance units CU1, CU2, CU3, CU4, CU5 , C4 (1.20 pF), and C5 (2.40 pF), the variable capacitance range was 1.50-6.15 pF.
- the inductance of the first inductance element L1 is 15 nH
- the inductance of the second inductance element L2 is 18 nH
- the inductance of the matching inductance element Lp is 3.9 nH
- the capacitance value of the matching capacitance element Cp is 1 pF.
- the frequency characteristic of the VSWR was evaluated by changing the resonance frequency f1r in the low frequency band by the frequency adjusting means 30.
- Table 1 shows the change in resonance frequency when the control data is changed. In the table, “-” indicates that the resonance frequency is lower than the measurement frequency.
- FIG. 29 shows VSWR characteristics in which the resonant frequency of the antenna changes according to control data given to the digital variable capacitance circuit element Cv. The control data shown in FIG. 29 is “00000”, “01000”, and “11111”.
- the resonance frequency of the antenna is changed between the low frequency bands while maintaining the characteristics of VSWR of 3 or less. It can be seen that it can be moved. According to the present embodiment, the resonance frequency of the antenna can be changed in a wide range, and a multi-band antenna capable of supporting a wide frequency band is obtained.
- FIG. 30 shows the configuration of the variable frequency antenna circuit of the second embodiment, and FIGS. 31 and 32 show its appearance. A description of the portion of the variable frequency antenna circuit shared with that of the first embodiment will be omitted.
- the configuration of the antenna element is almost the same as that of Example 1 except that the section 10f is added as the first antenna element. Since the antenna element cannot be made sufficiently long in a limited space within the casing of the mobile phone, the resonance frequency can reach the desired frequency by finely adjusting the resonance frequency of the fundamental mode in the section 10f. Since it is preferable to increase the radiation gain when the distance from the ground electrode is increased, the section 10a is set to a height of about 4.5 mm from the main surface of the antenna substrate 80.
- the wide surface of the section 10b of the first antenna element 10 extends in the direction of the open end F in parallel to the main surface of the antenna substrate 80, and the first antenna at the junction (bending point B) between the section 10b and the section 10a.
- Element 10 is folded and section 10a extends vertically.
- the antenna substrate 80 has a substantially rectangular shape of length 12 mm ⁇ width 52 mm ⁇ thickness 0.6 mm, and the section 10b is arranged along the long side.
- the length of the section 10b is about 30 mm.
- the second antenna element 12 extends in the same direction substantially in parallel.
- the length of the section 12b of the second antenna element 12 is about 25 mm.
- the section 10e (auxiliary line 25) of the first antenna element 10 has a length that does not exceed the lengthwise end of the antenna substrate 80, and extends to the open end F in the same height and direction as the section 10b.
- the section 10c extends vertically through the notch provided in the antenna substrate 80 to the opposite surface. The end of the section 10c is divided into two sections 10d and 10f.
- the section 10f extends substantially parallel to the back surface of the antenna substrate 80 and in the same direction as the section 10e, and is about half the length.
- the length of the section 10f functioning for adjusting the fundamental frequency can be set from 0 mm to a considerable degree as necessary.
- the section 10d extends substantially in parallel with the back surface of the antenna substrate 80 and toward the feeding point A in the same direction as the section 10b, and has a length of about 20 mm.
- a dielectric chip (support) 27 is mounted on the antenna substrate 80 so as to contact the section 10b of the first antenna element 10 and the section 12b of the second antenna element 12. With this configuration, the coupling between the section 10b of the first antenna element 10 and the section 12b of the second antenna element 12 is strengthened, and the resonance frequency can be adjusted and widened in the high frequency band.
- the mounting position of the dielectric chip 27 is preferably close to the feeding point A, and the distance between the side surface on the feeding point A side and the feeding point A is 4 mm.
- the dielectric chip 27 has a length of 3 mm, a width of 6 mm, and a height of 4 mm.
- An electrode pattern 42 is formed on almost the entire upper surface of the dielectric chip 27 and is soldered to the section 10b of the first antenna element 10.
- On the side surface of the dielectric chip 27 (opposite to the contact surface with the second antenna element 12), a strip-like electrode pattern having a length of 5 mm ⁇ width of 1 mm is formed.
- the long side of the electrode pattern is located at a position of 3.5 mm from the bottom, and is insulated from the electrode pattern 22 in a DC manner at a predetermined interval.
- the electrode pattern of the coupling means 20 is connected to the frequency adjusting means 30 provided on the antenna substrate 80 via the connection line 21 on the same plane.
- the frequency adjusting means 30 has substantially the equivalent circuit shown in FIG. 10, and is composed of a variable capacitance circuit Cv composed of SP2T FET switch SW and capacitance elements C1 and C2, and inductance elements L1 to L3.
- FIG. 33 shows an example of antenna parts in which the position of the coupling means 20 is different. Since the coupling means 20 is electromagnetically coupled to the section 10e of the first antenna element 10, the frequency adjusting means 30 is separated from the feeding point A. Another dielectric chip 115 is disposed so as to contact the section 10b of the first antenna element 10 and the section 12b of the second antenna element 12. Since the configuration of the antenna element and the frequency adjusting means 30 is the same as that of the second embodiment, description thereof is omitted.
- FIG. 34 shows the resonance frequency dependence of the average gain when the connection path of the switch SW of the variable capacitance circuit Cv constituting the frequency adjusting means 30 in the second and third embodiments is changed.
- the switch SW connection shown in FIG. 10 when the switch SW connection shown in FIG. 10 is switched from port P1-P2 (C1 is connected) to P1-P3 (C2 is connected), the peak position of the average gain is on the low side. Moved to. In FIG. 6, if C2> C1, it changes to the low frequency side.
- the resonance frequency f1r changed in the low frequency band and the VSWR peak position changed in the same way, but the resonance frequency in the high frequency band did not change substantially, and the average gain did not change depending on the connection path. .
- the antenna component of Example 2 had a gain higher than that of the antenna component of Example 3 by 0.5 dB or more.
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Abstract
Description
前記アンテナ要素は、給電点を共有するように一体的に接続した帯状の第一アンテナ要素及び第二アンテナ要素を有し、前記第二アンテナ要素は前記第一アンテナ要素より短く、
前記結合手段は、前記実装基板に取り付けられた誘電体チップ上に形成され、前記第一アンテナ要素の一部と電磁気的に結合する結合電極を有することを特徴とする。
図1は本発明の周波数可変アンテナ回路の一例を示す。この周波数可変アンテナ回路1は、アンテナ要素10と、アンテナ要素10と電磁気的に結合する結合手段20と、結合手段20及びグランド電極GNDに接続された周波数調整手段30とを備えている。周波数調整手段30は、図2に示すように可変容量回路Cvと第一インダクタンス素子L1からなる並列回路と、前記並列回路に接続された第二インダクタンス素子L2とを備えている。並列回路は端子T1側にあり、第二インダクタンス素子L2は端子T2を経てグランド電極GNDに接続されているが、第二インダクタンス素子L2が端子T1側あっても良い。結合手段20は、接続線路、キャパシタンス素子、インダクタンス素子、又はアンテナ要素10に電磁気的に結合する電極のいずれかで構成することができる。
図3に示すアンテナ要素10はグランド電極GNDに対して水平に延びる線路からなるが、図14に示すように折り返し部を設けて小型化するのが好ましい。折り返し部は複数あっても良い。図14に示すアンテナ要素10は、給電点Aと屈曲点Bとの間の区間10aと、屈曲点Bと屈曲点Cとの間の区間10bと、屈曲点Cと屈曲点Dとの間の区間10cと、屈曲点Dと開放端Eとの間の区間10dとを有し、区間10cは折り返し部であり、区間10dは区間10bと逆方向に延びる。給電点Aから開放端Eまでの長さは、図3に示すアンテナ要素10と同ように実質的に低周波数帯域内の共振周波数f1rに対応する長さであるので、図14に示すアンテナ要素10は直列共振モードで動作する。折り返し部を有するアンテナ要素10は、図3の場合より複雑な共振電流分布を有するので、短くできる。また給電点Aから屈曲点Cまでの長さを実質的に高周波数帯域内の共振周波数に対応する波長λ2の約1/4とすれば、直列共振モードで動作する複共振アンテナとなり、マルチバンド化を容易に実現できる。
図25は、本発明の周波数可変アンテナ回路(アンテナ部品)1を具備し、複数の通信システムに対応した無線通信装置の回路の一例を示す。周波数可変アンテナ回路1は、図29に示すように低周波数帯と高周波数帯で所望のVSWR特性が得られるもので、低周波数帯で共振周波数を可変とする。複数の通信システムのうち、例えばGSM(登録商標)850/900等を低周波数帯に使用し、DCS、PCS、UMTS等を高周波数帯に使用することができる。
図26は本発明の周波数可変アンテナ部品の一例(低周波数帯及び高周波数帯に対応する)を示し、図27及び図28はその外観を示す。図中、周波数調整手段30の可変容量回路Cvへの電源経路は省略している。
図30は実施例2の周波数可変アンテナ回路の構成を示し、図31及び図32はその外観を示す。この周波数可変アンテナ回路のうち実施例1のものと共有する部分の説明は省略する。
図33は結合手段20の位置が異なるアンテナ部品の一例を示す。結合手段20は第一アンテナ要素10の区間10eと電磁気的に結合するので、周波数調整手段30は給電点Aから離隔している。第一アンテナ要素10の区間10bと第二アンテナ要素12の区間12bに接するように別の誘電体チップ115が配置されている。アンテナ要素及び周波数調整手段30の構成等は実施例2と同じであるので、それらの説明を省略する。
Claims (21)
- 給電点となる一端と開放端となる他端とを有する第一アンテナ要素と、前記第一アンテナ要素に結合手段を介して結合された周波数調整手段とを備えた周波数可変アンテナ回路であって、前記周波数調整手段が、可変容量回路と第一インダクタンス素子とを含む並列共振回路と、前記並列共振回路に直列に接続された第二インダクタンス素子とを具備することを特徴とする周波数可変アンテナ回路。
- 請求項1に記載の周波数可変アンテナ回路において、前記結合手段が、接続線路、キャパシタンス素子、インダクタンス素子、前記第一アンテナ要素に電磁気的に結合する電極のいずれかであることを特徴とする周波数可変アンテナ回路。
- 請求項1又は2に記載の周波数可変アンテナ回路において、前記可変容量回路の容量値を変化させる制御回路を備えたことを特徴とする周波数可変アンテナ回路。
- 請求項3に記載の周波数可変アンテナ回路において、第一アンテナ要素の共振周波数の変化を検出する検出手段を備え、前記制御回路は前記検出手段の出力に基づいて容量値を変化させる制御信号を前記可変容量回路に出力すること特徴とする周波数可変アンテナ回路。
- 請求項1~4のいずれかに記載の周波数可変アンテナ回路において、前記第一アンテナ要素と一体的であって、前記給電点を共有し、前記第一アンテナ要素より短い第二アンテナ要素をさらに有し、前記第一アンテナ要素の共振と前記第二アンテナ要素の共振との複共振によりマルチバンド化したことを特徴とする周波数可変アンテナ回路。
- 請求項5に記載の周波数可変アンテナ回路において、前記第一アンテナ要素及び前記第二アンテナ要素は前記給電点からの経路の一部を共有していることを特徴とする周波数可変アンテナ回路。
- 帯状の第一アンテナ要素と、前記第一アンテナ要素に結合手段を介して結合された周波数調整手段とを備え、前記周波数調整手段が、可変容量回路と第一インダクタンス素子とを含む並列共振回路と、前記並列共振回路に直列に接続された第二インダクタンス素子とを具備する周波数可変アンテナ回路を構成するアンテナ部品であって、前記第一アンテナ要素は給電点となる一端と開放端となる他端とを有し、前記第一アンテナ要素の一部が前記結合手段と電磁気的に結合していることを特徴とするアンテナ部品。
- 請求項7に記載のアンテナ部品において、前記給電点を共有し、前記第一アンテナ要素より短い帯状の第二アンテナ要素をさらに有し、前記第一アンテナ要素の共振と前記第二アンテナ要素の共振との複共振により前記周波数可変アンテナ回路をマルチバンド化することを特徴とするアンテナ部品。
- 請求項8に記載のアンテナ部品において、前記第一アンテナ要素の一部が前記第二アンテナ要素に所定の間隔で対向していることを特徴とするアンテナ部品。
- 請求項7~9のいずれかに記載のアンテナ部品において、前記結合手段は誘電体又は軟磁性体からなる支持体上に形成された結合電極を有することを特徴とするアンテナ部品。
- 請求項10に記載のアンテナ部品において、前記支持体上に前記結合電極と所定の間隔で接続電極が形成されており、前記接続電極は前記第一アンテナ要素に接続されることを特徴とするアンテナ部品。
- 請求項11に記載のアンテナ部品において、前記アンテナ要素及び前記結合手段が主回路基板と分離した実装基板に配置されていることを特徴とするアンテナ部品。
- 請求項12に記載のアンテナ部品において、前記可変容量回路は前記実装基板に配置され、前記結合手段と接続線路を介して接続されていることを特徴とするアンテナ部品。
- 主回路基板と分離した実装基板に設けられたアンテナ要素と、前記アンテナ要素に電磁気的に結合するように前記実装基板に設けられた結合手段と、前記結合手段に接続するように実装基板に設けられた周波数調整手段とを具備し、
前記アンテナ要素は、給電点を共有するように一体的に接続した帯状の第一アンテナ要素及び第二アンテナ要素を有し、前記第二アンテナ要素は前記第一アンテナ要素より短く、
前記結合手段は、前記実装基板に取り付けられた誘電体チップ上に形成され、前記第一アンテナ要素の一部と電磁気的に結合する結合電極を有することを特徴とするアンテナ部品。 - 請求項14に記載のアンテナ部品において、前記誘電体チップは、前記結合電極と前記周波数調整手段との接続線路を有することを特徴とするアンテナ部品。
- 請求項15に記載のアンテナ部品において、前記結合電極は第一アンテナ要素とほぼ平行に延びる帯状電極であり、前記接続線路の一部は前記結合電極とほぼ平行に延びることを特徴とするアンテナ部品。
- 請求項16に記載のアンテナ部品において、前記接続線路がミアンダ状線路であることを特徴とするアンテナ部品。
- 請求項14~17のいずれかに記載のアンテナ部品において、前記第一アンテナ要素は折り返し部を有することを特徴とするアンテナ部品。
- 請求項18に記載のアンテナ部品において、前記第一アンテナ要素は折り返し部から前記第二アンテナ要素と同方向に延びる部分と逆方向に延びる部分とを有し、前記誘電体チップは前記第一アンテナ要素と同方向に延びる部分の一部と接するが、逆方向に延びる部分から離隔していることを特徴とするアンテナ部品。
- 請求項1~6に記載の周波数可変アンテナ回路を用いたことを特徴とする無線通信装置。
- 請求項7~19に記載のアンテナ部品を用いたことを特徴とする無線通信装置。
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EP10830044.3A EP2458681B1 (en) | 2009-11-13 | 2010-11-15 | Frequency variable antenna circuit, antenna component constituting the same, and wireless communication device using those |
US13/391,954 US9252494B2 (en) | 2009-11-13 | 2010-11-15 | Frequency-variable antenna circuit, antenna device constituting it, and wireless communications apparatus comprising it |
KR1020127015156A KR101705741B1 (ko) | 2009-11-13 | 2010-11-15 | 주파수 가변 안테나 회로, 이를 구성하는 안테나 부품, 및 이들을 사용한 무선 통신 장치 |
JP2011540574A JP5692086B2 (ja) | 2009-11-13 | 2010-11-15 | 周波数可変アンテナ回路、それを構成するアンテナ部品、及びそれらを用いた無線通信装置 |
CN201080051239.1A CN102696149B (zh) | 2009-11-13 | 2010-11-15 | 变频天线电路、构成它的天线部件、以及使用了它们的无线通信装置 |
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Also Published As
Publication number | Publication date |
---|---|
EP2458681B1 (en) | 2019-07-03 |
US20120146865A1 (en) | 2012-06-14 |
EP2458681A4 (en) | 2017-12-27 |
KR20120092663A (ko) | 2012-08-21 |
CN102696149A (zh) | 2012-09-26 |
JP2015084604A (ja) | 2015-04-30 |
US9252494B2 (en) | 2016-02-02 |
JP5939322B2 (ja) | 2016-06-22 |
CN102696149B (zh) | 2014-09-03 |
JPWO2011059088A1 (ja) | 2013-04-04 |
EP2458681A1 (en) | 2012-05-30 |
JP5692086B2 (ja) | 2015-04-01 |
KR101705741B1 (ko) | 2017-02-22 |
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