EP0389847B1 - Circuit - Google Patents

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Publication number
EP0389847B1
EP0389847B1 EP90104513A EP90104513A EP0389847B1 EP 0389847 B1 EP0389847 B1 EP 0389847B1 EP 90104513 A EP90104513 A EP 90104513A EP 90104513 A EP90104513 A EP 90104513A EP 0389847 B1 EP0389847 B1 EP 0389847B1
Authority
EP
European Patent Office
Prior art keywords
circuit
voltage
switching
capacitor
switching transistor
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Expired - Lifetime
Application number
EP90104513A
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German (de)
English (en)
Other versions
EP0389847A3 (fr
EP0389847A2 (fr
Inventor
Alwin Prof. Dr. Ing. Burgholte
Udo Dipl.-Ing. Schuermann
Warner Dipl.-Ing. Hieronimus
Horst Horneborg
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Individual
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Individual
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Publication date
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Publication of EP0389847A2 publication Critical patent/EP0389847A2/fr
Publication of EP0389847A3 publication Critical patent/EP0389847A3/fr
Application granted granted Critical
Publication of EP0389847B1 publication Critical patent/EP0389847B1/fr
Anticipated expiration legal-status Critical
Expired - Lifetime legal-status Critical Current

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Classifications

    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B41/00—Circuit arrangements or apparatus for igniting or operating discharge lamps
    • H05B41/14—Circuit arrangements
    • H05B41/16—Circuit arrangements in which the lamp is fed by dc or by low-frequency ac, e.g. by 50 cycles/sec ac, or with network frequencies
    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B41/00—Circuit arrangements or apparatus for igniting or operating discharge lamps
    • H05B41/14—Circuit arrangements
    • H05B41/26—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc
    • H05B41/28—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc using static converters
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y10—TECHNICAL SUBJECTS COVERED BY FORMER USPC
    • Y10S—TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y10S315/00—Electric lamp and discharge devices: systems
    • Y10S315/05—Starting and operating circuit for fluorescent lamp

Definitions

  • the invention relates to a circuit arrangement for the high-frequency operation of one or more low-pressure discharge lamps connected in parallel to one another according to the preamble of the main claim.
  • Such circuit arrangements are known per se (DE-OS 36 23 749, DE-OS 36 11 611 and DE-OS 37 00 421). Although these circuits can feed a low-pressure discharge lamp at a high frequency and meet the existing regulations regarding the form of the mains current, they still require a considerable amount of components.
  • the desired circuit effects in the known circuits are based on the function of a push-pull output stage in conjunction with at least four diodes and three capacitors.
  • WO 87/04891 relates to a ballast for fluorescent tubes, which comprises a low-pass filter, a bridge rectifier, a smoothing capacitor and circuit devices, the low-frequency mains voltage being filtered and rectified and a high-frequency AC voltage being generated by periodically opening and closing the circuit devices for operating the lamp.
  • the object of the invention is to provide a circuit arrangement for the high-frequency operation of low-pressure discharge lamps, which manages with a minimum of components.
  • the circuit arrangement according to the invention manages with fewer components than the known circuit arrangements, since the high-frequency generator is constructed as a single-ended high-frequency generator which has only one switching transistor, one switching inductance and one oscillating capacitor.
  • the active harmonic filter which has a series inductance, a pump capacitor and two decoupling diodes, an approximately sinusoidal mains current can be achieved, and on the other hand, a lamp current and a lamp voltage result that are suitable for operating the low-pressure discharge lamp.
  • the switching transistor switches the pump capacitor between the series inductance and one of the decoupling diodes against the reference potential.
  • the mains current is modulated sinusoidally with every lamp cycle.
  • an amount of energy proportional to the instantaneous value of the line voltage is drawn from the network and fed to the smoothing capacitor via one of the two decoupling diodes. This ensures a sinusoidally modulated mains current consumption through the harmonic filter.
  • the pump capacitor is connected in parallel with the switching inductance via the two decoupling diodes, so that the amplitude of the negative current half-wave in the lamp is reduced and the crest factor of the lamp current is improved.
  • the pump capacitor is connected from the collector or drain connection of the switching transistor via the one decoupling diode in parallel to the switching inductance and the other decoupling diode, the rise in voltage at the switching transistor due to the resonance behavior, determined by the switching inductance and the pump capacitor. It is also advantageous if the single-ended high-frequency generator is operated in resonance frequency, determined by the switching inductance and the pump capacitor. This switching of the switching transistor creates an advantageous switch-off relief network.
  • the switching transistor is controlled by an electronic control circuit which advantageously has an electronic oscillator and a pulse width modulator.
  • the electronic control circuit forms an electronic interface.
  • the electronic oscillator and the pulse width modulator can be started and stopped electronically and their pulse width or frequency can be set via an electronic control signal. This creates an interface that is desired for various user options.
  • Another improved circuit arrangement enables starting with preheated electrodes and also offers corresponding safety functions and protection against overvoltage and overcurrents, such as those e.g. if a lamp fails.
  • the switching inductance has two additional secondary windings which, depending on the lamp voltage, are switched to the respective heating coil of the lamp via a thyristor and heat the heating coil with their voltages.
  • control electronics are designed such that each time the circuit is started up for the first time, the switching frequency of the single-ended high-frequency converter is first increased, in order then to be reduced continuously to the actual clock frequency in the 1/10 second range, so that an increased heating current is available for each new start-up.
  • both the voltage at the collector of the switching transistor and the electronics intrinsic supply voltage are detected in their respective levels and, if overvoltage occurs, by firing a thyristor used to short-circuit the start-up circuit and the control of the switching transistor. This enables a safe shutdown of the circuit.
  • an electronic supply voltage is derived from the rectified mains voltage via a series resistor, which is switched through with a thyristor when the maximum permissible limit value for the electronic supply voltage is reached, so that the thyristor can hold its own via the electronic supply current.
  • FIG. 1 shows the basic structure of the circuit arrangement for the high-frequency operation of a low-pressure discharge lamp LL1.
  • the circuit arrangement includes a high-frequency filter 1, a mains rectifier 2, a single-ended high-frequency generator with a switching transistor T1 and an electronic control circuit 6 for controlling the single-ended high-frequency generator, as well as a smoothing capacitor 4 and an active harmonic filter 3.
  • the harmonic filter 3 consists of a series inductor L2, a pump capacitor C2, the decoupling diodes D6 and D5 and the switching transistor T1 of the single-ended high-frequency generator.
  • FIG. 2 shows the circuit diagram of a circuit arrangement with the harmonic filter 3 for operating the low-pressure discharge lamp LL1.
  • the high-frequency filter 1 is located at the input of the network, followed by the network rectifier 2 in a 2-pulse, uncontrolled bridge circuit.
  • the single-ended high-frequency generator operated via an electronic control circuit 6 consists of the switching transistor T1, a switching inductance L1 and a resonant capacitor C1.
  • the electrodes of the lamp LL1 are connected on one side E1, H1 to the switching inductance L1, and the smoothing capacitor CO and on the other side E2, H2 to the oscillating capacitor C1.
  • the electrodes of the heating circuits H1 and H2 can, as shown in FIG. 2, be connected via a heating capacitor C3; or a heating winding can be connected separately with E1-H1 and E2-H2 as part winding of the switching inductance L1, as shown in FIG. 4.
  • the high-frequency single-ended converter supplies a portion of the positive current half-wave of the lamp via the oscillating capacitor C1 from the positive pole of the smoothing capacitor C0 when the switching transistor is conductive.
  • the switching inductance L1 charges an energy part proportional to the switch-on time of the switching transistor T1.
  • an oscillating circuit is formed via the lamp, the resonance capacitor C1 and the switching inductance L1, which initially produces the negative current half-wave of the lamp with the same current direction in the switching inductance L1 and then when the current direction is reversed in the switching inductance L1 by discharging the oscillation capacitor C1 the positive current half-wave generated in the lamp.
  • the smoothing capacitor CO is decoupled from the mains voltage via the decoupling diode D6.
  • the circuit arrangement also has an active harmonic filter, which consists of the series inductor L2 located in the positive line, the pump capacitor C2 and the decoupling diodes D5 and D6.
  • the pump capacitor C2 When the switching transistor T1 is switched “on”, the pump capacitor C2 is charged via the series inductor L2 up to the voltage level at the smoothing capacitor C0.
  • the charging current is taken from the network.
  • An energy part is thus stored in the longitudinal inductance L2 and is emitted to the single-ended high-frequency generator, the lamp and the smoothing capacitor CO after charging of the pump capacitor C2 has ended.
  • the amount of energy per cycle is proportional to the voltage time area at the series inductor L2 and is determined by the difference between the instantaneous mains voltage values and the voltage at the pump capacitor C2, which is present in negative polarity due to the preceding "switch-off" cycle. certainly.
  • the line current is modulated sinusoidally with each lamp cycle.
  • the energy output of the longitudinal inductor L2 takes place by demagnetizing the longitudinal inductor L2.
  • the voltage at the series inductor L2 reverses and reaches a voltage value equal to the difference between the voltage at the smoothing capacitor C0 and the respective instantaneous value of the mains voltage.
  • a second phase begins in the action of the pump capacitor C2.
  • the current flowing in the switching inductance L1 commutates from the switching transistor T1 partly to the pump capacitor C2 as a discharge and reversing current and partly to the oscillating capacitor C1 and the low-pressure discharge lamp, which thus receives its negative current half-wave.
  • the pump capacitor C2 thus acts as a switch-off relief network for the switching transistor T1.
  • the voltage at the collector or drain connection of the switching transistor T1 can therefore only change as quickly as the pump capacitor C2 with its resonance frequency, determined by the capacitance of the pump capacitor C2 and the inductance value of the switching inductance L1, is recharged. This limitation of the rise in voltage at the switching transistor T1 considerably reduces its turn-off losses.
  • the negative current half-wave in the oscillating capacitor C1 and the low-pressure discharge lamp LL1 is reduced by the current part which commutates from the switching inductance L1 as the charge-reversal current to the pump capacitor C2. This improves the crest factor of the lamp current and thus the service life of the low-pressure discharge lamp.
  • the electronic control circuit 6 of the switching transistor consists of an electronic oscillator and a pulse width modulator, which can be started and stopped electronically, and its pulse width or frequency via an electronic one Control signal is adjustable. This enables an electronic interface to be implemented, as is required for various user options.
  • the circuit part assigned to the low-pressure discharge lamp LL1 consists of the decoupling diodes D5.1 and D6.1, the switching inductance L1.1, the oscillating capacitor C1.1. and the heating capacitor C3.1.
  • the circuit part assigned to the low-pressure discharge lamp LL2 consists of the decoupling diodes D5.2 and D6.2, the switching inductance L1.2, the oscillating capacitor C1.2 and the heating capacitor C3.2.
  • FIG. 4 shows a modified exemplary embodiment of the circuit from FIG. 2.
  • two heating winding sections L3, L4 are provided, each of which lies between the connections E1 and H1 or E2 and H2 of the low-pressure discharge lamp LL1.
  • the current path leads, when the low-pressure discharge lamp LL1 is inserted, from the diode D6 via the connections H1 and E1 of the low-pressure discharge lamp LL1, the switching inductance L1 and the diode D5 to the switching transistor T1.
  • the path E1-H1 is bridged by the heating winding, while on the other hand the energy present at the switching inductance L1 can no longer be discharged.
  • a further diode D7 is therefore provided as no-load protection, which lies between the switching inductance L1 and the smoothing capacitor C0 and interrupts the inrush current path.
  • FIG. 5 to 7 show current and voltage diagrams of an actually implemented circuit arrangement according to FIG. 2.
  • FIG. 5 is an ozillogram for mains voltage and mains current of the circuit according to FIG. 2.
  • Current curve I shows an approximately sinusoidal curve of the mains current. Without that Harmonic filter in the circuit of Fig. 2 results in a current during 1/10 to 1/15 of the half wave. Such a current spike would lead to grid repercussions, which have to be limited due to legal regulations. Due to the harmonic filter, the maximum of the current is reduced and the current is distributed over the entire half-wave, so that the desired approximation to a sinusoidal current curve results.
  • FIG. 6 shows the harmonic analysis of the mains current shown in FIG. 5.
  • the harmonic component of the mains current is far below the limit values permitted by VDE / IEC.
  • FIG. 7 shows lamp current and lamp voltage of a circuit arrangement according to FIG. 2.
  • the curves of lamp current I and lamp voltage U each show a peak superimposed on a sine curve on the positive half-wave. This peak corresponds to the turn-on time of transistor T1.
  • the low-pressure discharge lamp can be operated with such a current or such a voltage without there being any disadvantageous side effects or a shorter service life.
  • FIG. 8 shows the basic structure of a further circuit arrangement for the high-frequency operation of a low-pressure discharge lamp LL1.
  • Reference numerals a - j in FIG. 8 are also used in FIGS. 9-11 to show the connection points of the various circuit blocks in FIG. 8.
  • the circuit arrangement includes a high-frequency filter 10, a mains rectifier 12, an active harmonic filter 13, a smoothing capacitor 14, a single-ended high-frequency lamp generator 15, control electronics 16, a driver circuit 17, an overvoltage monitor 18, a starting circuit 19 and an electronics supply 20.
  • Fig. 9 shows the circuit diagram of the circuit arrangement of the two additional secondary heating windings L3 and L4, which are connected to the heating coils E2, H2 and E1, H1 with the thyristors Q4 and Q5.
  • the connection depends on the operating state of the lamp.
  • a lamp which has not yet been ignited or is in the starting process shows an increased operating and ignition voltage, which is also available as a secondary voltage and is also available in the form of a winding on the windings L3 and L4 and is used as a trigger voltage.
  • the ignition point for the thyristors Q4 and Q5 is derived via the voltage divider R1 / R2 and R3 / R4.
  • the trigger voltage is no longer reached, so that the heating remains switched off. If the operating voltage of the lamp increases, e.g. B. at low operating temperatures or with a dimmed lamp, the trigger voltage is reached, whereby the heating of the filaments automatically switches on. If the heating coils fail due to an interruption, the diodes D12 and D13 prevent an impermissibly high current load on the voltage divider resistors.
  • the starting behavior can be further improved by increasing the switching frequency of the single-cycle high-frequency lamp generator, because each switching cycle delivers a heating current pulse.
  • the frequency is increased depending on the first time the electronics supply voltage is applied to the control electronics.
  • FIG. 9 also shows the overcurrent detection of the emitter current from T1 via the voltage drop across the resistor RO, which is connected in series with the emitter. If a certain current limit value is reached, the corresponding voltage drop acts on the control electronics 16 in such a way that the driver circuit 17 is switched off and thus the switching transistor T1 is switched off. This circuit arrangement thus acts as an electronic overcurrent protection.
  • the collector voltage of the switching transistor is switched to the trigger diode Q1 via the voltage divider R5 / R6 and the diode D15.
  • the trigger diode Q1 can also be switched via the diode D16 depending on the level of the electronics supply voltage.
  • the capacitor C13 prevents the trigger circuit from responding to voltage spikes that only occur for a short time and, when the trigger diode is switched through, provides the required ignition current for the thyristor Q2. If the thyristor Q2 is ignited by means of a trigger pulse, it drops into a latched state via the resistor R7.
  • FIG. 11 shows the circuit section of the circuit arrangement for the starting circuit 19 and for the electronic self-supply 20.
  • the capacitor C14 is charged via the resistor R10 and the diode D10.
  • a maximum permissible voltage value at C14 is specified via the voltage divider R8 / R9, at which the thyristor Q3 connects this voltage to the electronics supply.

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  • Circuit Arrangements For Discharge Lamps (AREA)
  • Dc-Dc Converters (AREA)
  • Power Conversion In General (AREA)
  • Burglar Alarm Systems (AREA)
  • Slot Machines And Peripheral Devices (AREA)
  • Design And Manufacture Of Integrated Circuits (AREA)

Claims (13)

  1. Configuration de circuit destinée à l'exploitation en haute fréquence d'une ou plusieurs lampes à décharge basse pression montées en parallèle les unes par rapport aux autres, qui comprend un redresseur de réseau (2) avec filtre actif (3) d'harmoniques placé en aval, un condensateur de filtrage (CO) placé en aval, et un générateur à haute fréquence adjoint à chaque lampe (LL1) à décharge basse pression, caractérisée en ce que :
    - le générateur à haute fréquence est un générateur à haute fréquence monophasé qui comprend un transistor de commutation (T1), une inductance de commutation (L1) et un condensateur oscillant (C1),
    - le filtre actif (3) d'harmoniques comprend une inductance série (L2), un condensateur de pompage (C2) et deux diodes de découplage (D5, D6), sachant que :
    - la première diode de découplage (D5) se trouve entre le condensateur oscillant (C1) et le transistor de commutation (T1) et que,
    - la deuxième diode de découplage (D6) se trouve entre le condensateur de filtrage (CO) et la tension du secteur, et la charge du condensateur de pompage (C2) a lieu directement à partir du secteur à la mise en circuit du transistor de commutation (T1).
  2. Configuration de circuit selon la revendication 1, caractérisée en ce que le condensateur de pompage (C2) est monté au-dessus des deux diodes de découplage (D5, D6) parallèlement à l'inductance de commutation (L1).
  3. Configuration de circuit selon la revendication 1 ou 2, caractérisée en ce que le réaccroissement de la tension est prédéfini au niveau du transistor de commutation (T1) au moyen du comportement à la résonance qui est déterminé par l'inductance de commutation (L1) et le condensateur de pompage (C2).
  4. Configuration de circuit selon l'une quelconque des revendications 1 à 3, caractérisée en ce que le générateur à haute fréquence monophasé est utilisé en fréquence de résonance qui est déterminée par l'inductance de commutation (L1) et le condensateur oscillant (C1).
  5. Configuration de circuit selon l'une quelconque des revendications 1 à 4, caractérisée en ce que le transistor de commutation (T1) est commandé par un circuit de commande électronique (6).
  6. Configuration de circuit selon la revendication 5, caractérisée en ce que, grâce au circuit de commande électronique (6), il se forme un point d'intersection électronique.
  7. Configuration de circuit selon la revendication 6, caractérisée en ce que le circuit de commande (6) ccomprend un oscillateur électronique et un modulateur de largeur d'impulsions.
  8. Configuration de circuit selon l'une quelconque des revendications 1 à 7, caractérisée en ce que l'inductance de commutation (L1) possède deux bobinages secondaires supplémentaires (L3) et (L4) qui sont commutés tous les deux par l'intermédiaire d'un thyristor (Q4, Q5), en fonction de la tension de lampe, sur la spirale correspondante du filament de la lampe.
  9. Configuration de circuit selon la revendication 8, caractérisée en ce que, à l'aide d'un dispositif de commande électronique (16), à chaque première mise en service du circuit, la fréquence de commutation du générateur à haute fréquence monophasé est augmentée pour être réduite ensuite dans une plage d'un dixième de seconde continuellement, jusqu'à la fréquence horloge réelle.
  10. Configuration de circuit selon une des revendications 8 ou 9, caractérisée en ce qu'aussi bien la surtension au niveau du collecteur du transistor de commutation (T1) par l'intermédiaire d'un diviseur de tension (R5, R6) et d'une troisième diode (D15) que la surtension d'une alimentation électronique (10) par l'intermédiaire d'une quatrième diode (D16), sont utilisées pour le déclenchement par l'intermédiaire d'une diode de déclenchement (Q1) d'un autre thyristor (Q2) qui de son côté met hors service un circuit de démarrage (19) et le circuit de commande (16) du transistor de commutation.
  11. Configuration de circuit selon une des revendications 8 ou 9, caractérisée en ce que, pour la protection du circuit contre les surintensités, le courant émetteur du transistor de commutation (T1) est détecté en tant que champ électrique au niveau d'une résistance de protection (RO), et un signal correspondant à la chute de tension est amené au circuit de commande (16) qui met le transistor de commutation hors circuit si la chute de tension dépasse une valeur prédéfinie.
  12. Configuration de circuit selon une des revendications 8 ou 9, caractérisée en ce que lors de l'application de la tension de secteur, le circuit accumule automatiquement par l'intermédiaire d'une résistance d'accumulation (R10) et d'une diode d'accumulation (D10), la tension d'alimentation électronique au niveau d'un condensateur (C14) jusqu'à la limite maximale admissible, pour être ensuite commuté à l'aide d'un thyristor supplémentaire (Q3) sur l'alimentation électronique (20).
  13. Configuration de circuit selon l'une quelconque des revendications 8 à 12, caractérisée en ce qu'à chaque cycle de lampe, une tension alternative est prélevée par l'intermédiaire d'un bobinage secondaire supplémentaire (L5) situé sur l'inductance de commutation (L1) ou sur une inductance de protection (L6), et est mise à disposition par l'intermédiaire d'un redresseur (D19) en tant que propre alimentation électronique.
EP90104513A 1989-03-16 1990-03-09 Circuit Expired - Lifetime EP0389847B1 (fr)

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
EP89104702 1989-03-16
EP89104702 1989-03-16

Publications (3)

Publication Number Publication Date
EP0389847A2 EP0389847A2 (fr) 1990-10-03
EP0389847A3 EP0389847A3 (fr) 1992-03-04
EP0389847B1 true EP0389847B1 (fr) 1995-02-15

Family

ID=8201092

Family Applications (1)

Application Number Title Priority Date Filing Date
EP90104513A Expired - Lifetime EP0389847B1 (fr) 1989-03-16 1990-03-09 Circuit

Country Status (10)

Country Link
US (1) US5070276A (fr)
EP (1) EP0389847B1 (fr)
JP (1) JPH03173347A (fr)
KR (1) KR900015582A (fr)
CN (1) CN1024979C (fr)
AT (1) ATE118666T1 (fr)
CA (1) CA2012441A1 (fr)
DE (1) DE59008453D1 (fr)
ES (1) ES2068266T3 (fr)
IN (1) IN171097B (fr)

Families Citing this family (9)

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Publication number Priority date Publication date Assignee Title
DE4217822A1 (de) * 1991-10-18 1993-04-22 Heinrich Korte Elektronisches vorschaltgeraet
TW339496B (en) * 1994-06-22 1998-09-01 Philips Electronics Nv Method and circuit arrangement for operating a high-pressure discharge lamp
FI96734C (fi) 1994-11-22 1996-08-12 Helvar Oy Purkauslampun elektronisen liitäntälaitteen häiriösuodatin
US5682086A (en) * 1995-10-05 1997-10-28 Yin Nan Enterprises Co., Ltd. Dynamic filter for an electronic ballast with a parallel-load resonant inverter
US6137234A (en) * 1999-10-18 2000-10-24 U.S. Philips Corporation Circuit arrangement
US6396220B1 (en) * 2001-05-07 2002-05-28 Koninklijke Philips Electronics N.V. Lamp ignition with compensation for parasitic loading capacitance
EP1905281B1 (fr) * 2005-06-30 2013-09-11 Koninklijke Philips Electronics N.V. Procede d'excitation d'une lampe a decharge de gaz haute pression d'un systeme de projection
DK2523305T3 (en) * 2011-05-12 2018-01-15 Moog Unna Gmbh EMERGENCY ENERGY SUPPLY AND EMERGENCY PROCEDURE
CN111243825B (zh) * 2018-11-29 2023-06-16 阿尔贝特·莫伊雷尔 用于使铁磁材料消磁的装置

Family Cites Families (10)

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Publication number Priority date Publication date Assignee Title
DE3266600D1 (en) * 1981-02-21 1985-11-07 Emi Plc Thorn Lamp driver circuits
JPS59128128A (ja) * 1983-01-13 1984-07-24 Matsushita Electric Works Ltd 積載方法
DE3303374A1 (de) * 1983-02-02 1984-08-02 Rheintechnik Weiland & Kaspar Kg, 6680 Neunkirchen Stromversorgungsschaltung fuer leuchtstoffroehren
DE3312572A1 (de) * 1983-04-08 1984-10-18 Trilux-Lenze Gmbh + Co Kg, 5760 Arnsberg Elektronisches vorschaltgeraet fuer eine leuchtstofflampe
SE444496B (sv) * 1984-08-02 1986-04-14 Innocap Ab Kopplingsanordning for drivning av gasurladdningsror
US4873471A (en) * 1986-03-28 1989-10-10 Thomas Industries Inc. High frequency ballast for gaseous discharge lamps
DE3611611A1 (de) * 1986-04-07 1987-10-08 Patent Treuhand Ges Fuer Elektrische Gluehlampen Mbh Schaltungsanordnung zum hochfrequenten betrieb einer niederdruckentladungslampe
DE3623749A1 (de) * 1986-07-14 1988-01-21 Patent Treuhand Ges Fuer Elektrische Gluehlampen Mbh Schaltungsanordnung zum betrieb von niederdruckentladungslampen
DE3700421A1 (de) * 1987-01-08 1988-07-21 Patent Treuhand Ges Fuer Elektrische Gluehlampen Mbh Schaltungsanordnung zum betrieb einer niederdruckentladungslampe
US4904903A (en) * 1988-04-05 1990-02-27 Innovative Controls, Inc. Ballast for high intensity discharge lamps

Also Published As

Publication number Publication date
DE59008453D1 (de) 1995-03-23
IN171097B (fr) 1992-07-18
US5070276A (en) 1991-12-03
ES2068266T3 (es) 1995-04-16
CA2012441A1 (fr) 1990-09-16
EP0389847A3 (fr) 1992-03-04
EP0389847A2 (fr) 1990-10-03
JPH03173347A (ja) 1991-07-26
ATE118666T1 (de) 1995-03-15
CN1024979C (zh) 1994-06-08
KR900015582A (ko) 1990-10-27
CN1045677A (zh) 1990-09-26

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