EP0050131B1 - Ballast pour une lampe a decharge - Google Patents
Ballast pour une lampe a decharge Download PDFInfo
- Publication number
- EP0050131B1 EP0050131B1 EP81900979A EP81900979A EP0050131B1 EP 0050131 B1 EP0050131 B1 EP 0050131B1 EP 81900979 A EP81900979 A EP 81900979A EP 81900979 A EP81900979 A EP 81900979A EP 0050131 B1 EP0050131 B1 EP 0050131B1
- Authority
- EP
- European Patent Office
- Prior art keywords
- ballast
- inverter
- transistor
- switching device
- bistable switching
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Expired
Links
- 239000003990 capacitor Substances 0.000 claims description 25
- 238000004804 winding Methods 0.000 claims description 8
- 238000012806 monitoring device Methods 0.000 claims 3
- 238000000605 extraction Methods 0.000 abstract 1
- 230000001419 dependent effect Effects 0.000 description 6
- 238000012544 monitoring process Methods 0.000 description 6
- 230000001960 triggered effect Effects 0.000 description 2
- 230000003111 delayed effect Effects 0.000 description 1
- 238000010586 diagram Methods 0.000 description 1
- 230000008030 elimination Effects 0.000 description 1
- 238000003379 elimination reaction Methods 0.000 description 1
- 230000000737 periodic effect Effects 0.000 description 1
- 230000001681 protective effect Effects 0.000 description 1
Images
Classifications
-
- H—ELECTRICITY
- H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
- H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
- H05B41/00—Circuit arrangements or apparatus for igniting or operating discharge lamps
- H05B41/14—Circuit arrangements
- H05B41/26—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc
- H05B41/28—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc using static converters
- H05B41/295—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc using static converters with semiconductor devices and specially adapted for lamps with preheating electrodes, e.g. for fluorescent lamps
- H05B41/298—Arrangements for protecting lamps or circuits against abnormal operating conditions
- H05B41/2981—Arrangements for protecting lamps or circuits against abnormal operating conditions for protecting the circuit against abnormal operating conditions
- H05B41/2985—Arrangements for protecting lamps or circuits against abnormal operating conditions for protecting the circuit against abnormal operating conditions against abnormal lamp operating conditions
Definitions
- the invention relates to a ballast according to the preamble of claim 1, as described for example in DE-A-26 42 272.
- the invention has for its object to protect the ballast against overload.
- the solution to this problem is characterized in claim 1.
- an additional winding of the saturation transformer supplying the control voltages for the transistors of the inverter is preferably short-circuited. According to a development of the invention, this also simultaneously supplies the current-dependent voltage for the RC element in the input of the bistable switching device.
- the RC Link in the input circuit of the bistable switching device must still be charged to such an extent that a new response is triggered.
- the RC element is also connected in parallel with the transistor of the bistable switching device via a decoupling diode via a decoupling diode and is thus discharged when it is triggered.
- the current-dependent shutdown of the ballast is also effective when the lamp is missing if, according to a development of the invention, the connections for the electrodes of the lamp are each bridged by a capacitor dimensioned such that a sufficiently high current flows in the series resonant circuit.
- Another embodiment of the invention relates to a ballast in which a single step-up converter feeds two inverters.
- a selective shutdown of the respective inverter concerned is provided, whereas the intact inverter continues to work and the lamp which it supplies can therefore continue to burn.
- the step-up converter according to fig. 1 contains a storage capacitor C18 which is connected on the one hand via the charging diode D27 and the charging inductor L4 and on the other hand via a measuring resistor R33 to a main rectifier G1 in a two-way circuit, which is fed by an AC voltage network N and has an essentially unsmoothed voltage at its terminals 1, 4 delivers.
- a two-position controller X (see FIG. 2), which controls the main transistor V6 as a switch, is used to regulate the voltage at the storage capacitor C18.
- the signal at the measuring resistor R33 located between the main transistor V6 and the storage capacitor C18 on the one hand and the main rectifier G1 on the other hand is fed to the input 7 of the controller X via a delay element (resistor R27 and capacitor C14).
- the inverter W contains two transistors V7, V8 connected in series between its terminals 11, 8 on the storage capacitor C18. Parallel to the switching path of the transistor V7 is a series resonance circuit with the inductor L7 and the capacitor C23 in series with a switching capacitor C22 and the primary winding L81 of a saturation transformer T8 with secondary windings L82, L83, L84.
- the discharge lamp L is arranged in parallel with the capacitor C23, so that its electrodes are connected in series with the series resonant circuit.
- a circuit known per se, of which only the secondary windings L83, L84 of the saturation transformer T8 are shown, is used for alternating control of the transistors V7, V8: this alternately results in a charging of the reversing capacitor C22 via V8 from C18 and then a discharge via V7.
- the operating frequency of the inverter determined by the saturation transformer is slightly above the resonance frequency of the series resonance circuit: This creates a gap between the reversal of V7 and V8.
- a delayed start-up of the inverter is ensured by means of a capacitor C19, which is only charged when the controller X is working; If there is sufficient voltage at C19, V8 is activated via a trigger diode D34 and C19 is then discharged again via D33 (sufficient energy for a cold start).
- the capacitor C19 is in turn connected in parallel via a capacitor C20 and a diode D32 to the switching path of the main transistor V6 and can therefore only be charged to a value sufficient for the inverter to oscillate when the controller is clocked properly.
- the capacitor C20 is connected in parallel with the protective capacitor C17 via a resistor R40: the energy from C20, like that from C17, therefore serves to charge the partial capacitors C8 and C9, which supply the operating voltages for the electronics.
- the saturation transformer T8 has an additional secondary winding L82 through which a current flows via a bistable switching device K. dependent shutdown is effected.
- the switching device K contains a comparator V12 fed back via a diode D16 and a transistor V10 controlled by it.
- the output - terminal 16 - of the comparator 12 has a negative potential. It only switches over (positive potential at the output) when the voltage at its positive input becomes greater than a reference voltage at its negative input. Then V17 receives a control current via R60 and blocks the transistors V2, V3 and, via these, also V5 and the main transistor V6.
- the transistor V10 blocked in normal operation - positive potential at terminal 15 - is turned on via R13 - zero potential at terminal 15 - and thereby the winding L82 of transformer T8 is short-circuited via diode D41.
- the transistors V7, V8 of the inverter therefore no longer receive a control voltage and block.
- the capacitor C11 is simultaneously discharged to such an extent that no immediate shutdown takes place when the device is started up again.
- the shutdown described is dependent on the voltage across the capacitors C11 and C10, which are discharged via R14 and charged via the diode D41 and resistor R41 with a voltage that is supplied by the secondary winding L82 of the transformer T8 in the inverter and that flows through the current L7 is proportional (particularly high with the lamp not ignited, the series resonance circuit not damped).
- Capacitors C10 and R14 are dimensioned in such a way that a quick succession of fewer start pulses - starting a new lamp - does not lead to switch-off any more than a larger number of pulses with a greater distance (start of an old lamp).
- capacitors C26 and C27 are provided in parallel to the electrodes L1, L2 and are dimensioned such that the current flowing when the lamp is missing is above the response limit value.
- the reactance of the capacitors C26 and CC27 is approximately ten times the resistance of an electrode at the average operating frequency of approximately 40 kHz.
- the heart of the two-point controller shown in FIG. 2 is a comparator V13, the output of which is connected via a resistor R25 to a terminal P, to which a positive operating voltage can be switched via a transistor V3.
- V13 controls a transistor V4, the collector of which is connected to the base of a further transistor V5, via which the control current of the main transistor V6 is then conducted.
- V5 The basis of V5 is also based on the tap of a voltage divider which is connected between the positive terminal P and the terminal 4 which is at zero potential and which supplies the setpoint for the comparator V13; For this purpose, a signal dependent on the rectified mains voltage is fed to the resistor R2 of the voltage divider via the terminal 1 and the resistor R1.
- the hysteresis of the two-point regulator is determined by connecting the collector of transistor V4 to a tap of this voltage divider.
- the setpoint of the controller can be reduced by connecting a transistor V16 to R2 in parallel:
- V16 is controlled by a comparator V15, which normally has a negative output potential, so that V16 blocks. However, V15 controls V16 when the bistable switching device K of the monitoring part U tilts into the switch-off state:. Then the negative input of V15 via D52, terminal 15 and transistor V10 is at zero potential.
- the transistor V3 is used to switch off the controller under certain critical operating conditions, via which the positive operating voltage can be switched to the controller (terminal P).
- This transistor is controlled by a further transistor V2, which is only turned on when the operating voltage has reached a minimum value required for operation.
- the potential of the base of V2 is sufficiently greater than that at the emitter, which is determined by the Zener diode D13: This makes the transistors V2 and V3 conductive and the supply voltage for the controller is at P.
- V3 remains on as long as the monitoring part Ü is in the normal state, has a negative potential at the output of the comparator V12 and at terminal 16, and thus transistor V17 is blocked via diode D62.
- the second inverter is to be connected in parallel with its terminals 11, 13, 14, 8 and 4 to the terminals of the same name in FIG. 1. Only terminals 15 and 16 of the second inverter are to be connected to terminals 15 'and 16' of the common controller X.
- the inputs 16 and 16 ' belong to an AND circuit (R60, D61, D62) on the control path of transistor V17, which is only turned on and thus switches off the controller when both inverters are switched off: as long as one of the inverters is still working, is at terminal 16 or 16 'of its monitoring part minus potential, through which the associated diode D62 or D61 is turned on and V17 is blocked.
- R60, D61, D62 AND circuit
Landscapes
- Circuit Arrangements For Discharge Lamps (AREA)
Abstract
Claims (8)
Priority Applications (1)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
AT81900979T ATE8316T1 (de) | 1980-04-15 | 1981-04-14 | Vorschaltgeraet fuer eine entladungslampe. |
Applications Claiming Priority (4)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
DE3014419A DE3014419C2 (de) | 1980-04-15 | 1980-04-15 | Vorschaltgerät für eine Entladungslampe |
DE3014419 | 1980-04-15 | ||
DE3029672 | 1980-08-05 | ||
DE19803029672 DE3029672A1 (de) | 1980-08-05 | 1980-08-05 | Vorschaltgeraet zum anschluss einer entladungslampe |
Related Child Applications (2)
Application Number | Title | Priority Date | Filing Date |
---|---|---|---|
EP83101515A Division EP0092654A3 (fr) | 1981-04-14 | 1981-04-14 | Appareil ballast |
EP83101515.1 Division-Into | 1983-02-17 |
Publications (2)
Publication Number | Publication Date |
---|---|
EP0050131A1 EP0050131A1 (fr) | 1982-04-28 |
EP0050131B1 true EP0050131B1 (fr) | 1984-07-04 |
Family
ID=25784967
Family Applications (1)
Application Number | Title | Priority Date | Filing Date |
---|---|---|---|
EP81900979A Expired EP0050131B1 (fr) | 1980-04-15 | 1981-04-14 | Ballast pour une lampe a decharge |
Country Status (4)
Country | Link |
---|---|
EP (1) | EP0050131B1 (fr) |
FI (1) | FI69540C (fr) |
IT (1) | IT1137447B (fr) |
WO (1) | WO1981003102A1 (fr) |
Families Citing this family (6)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
EP0092654A3 (fr) * | 1981-04-14 | 1984-04-18 | Siemens Aktiengesellschaft | Appareil ballast |
DE3277718D1 (de) * | 1981-07-31 | 1987-12-23 | Siemens Ag | Dc-ac conventer |
DE3301632A1 (de) * | 1983-01-19 | 1984-07-26 | Siemens AG, 1000 Berlin und 8000 München | Umrichter |
AU2708684A (en) * | 1983-05-05 | 1984-11-08 | Dubank Electronics Pty. Ltd. | Electronic ballast and starter |
DE3503778C2 (de) * | 1985-02-05 | 1986-11-20 | Trilux-Lenze Gmbh + Co Kg, 5760 Arnsberg | Leuchtstofflampen-Vorschaltgerät |
AT390156B (de) * | 1985-05-14 | 1990-03-26 | Zumtobel Ag | Schutzschaltung fuer eine wechselrichterschaltung |
Family Cites Families (3)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
DE2355600A1 (de) * | 1972-11-13 | 1974-05-16 | Gen Electric | Geregelte leistungseinspeisung mit einem halbwellenschalter |
US3913002A (en) * | 1974-01-02 | 1975-10-14 | Gen Electric | Power circuits for obtaining a high power factor electronically |
US3969652A (en) * | 1974-01-04 | 1976-07-13 | General Electric Company | Electronic ballast for gaseous discharge lamps |
-
1981
- 1981-04-10 IT IT21036/81A patent/IT1137447B/it active
- 1981-04-14 WO PCT/DE1981/000058 patent/WO1981003102A1/fr active IP Right Grant
- 1981-04-14 EP EP81900979A patent/EP0050131B1/fr not_active Expired
- 1981-04-15 FI FI811179A patent/FI69540C/fi not_active IP Right Cessation
Also Published As
Publication number | Publication date |
---|---|
FI69540B (fi) | 1985-10-31 |
WO1981003102A1 (fr) | 1981-10-29 |
EP0050131A1 (fr) | 1982-04-28 |
IT8121036A0 (it) | 1981-04-10 |
FI811179L (fi) | 1981-10-16 |
FI69540C (fi) | 1986-02-10 |
IT1137447B (it) | 1986-09-10 |
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