EP1443808B1 - Circuit et méthode d'allumage et de commande du fonctionnement des lampes à décharge de gaz avec filaments de préchauffage - Google Patents

Circuit et méthode d'allumage et de commande du fonctionnement des lampes à décharge de gaz avec filaments de préchauffage Download PDF

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Publication number
EP1443808B1
EP1443808B1 EP03029437A EP03029437A EP1443808B1 EP 1443808 B1 EP1443808 B1 EP 1443808B1 EP 03029437 A EP03029437 A EP 03029437A EP 03029437 A EP03029437 A EP 03029437A EP 1443808 B1 EP1443808 B1 EP 1443808B1
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EP
European Patent Office
Prior art keywords
inverter
frequency
circuit
preheating
discharge lamps
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Expired - Lifetime
Application number
EP03029437A
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German (de)
English (en)
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EP1443808A2 (fr
EP1443808A3 (fr
Inventor
Bernd Rudolph
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Osram GmbH
Original Assignee
Patent Treuhand Gesellschaft fuer Elektrische Gluehlampen mbH
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Publication of EP1443808A3 publication Critical patent/EP1443808A3/fr
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Classifications

    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B41/00—Circuit arrangements or apparatus for igniting or operating discharge lamps
    • H05B41/14—Circuit arrangements
    • H05B41/26—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc
    • H05B41/28—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc using static converters
    • H05B41/282—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc using static converters with semiconductor devices
    • H05B41/285—Arrangements for protecting lamps or circuits against abnormal operating conditions
    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B41/00—Circuit arrangements or apparatus for igniting or operating discharge lamps
    • H05B41/14—Circuit arrangements
    • H05B41/26—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc
    • H05B41/28—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc using static converters
    • H05B41/295—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc using static converters with semiconductor devices and specially adapted for lamps with preheating electrodes, e.g. for fluorescent lamps
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y10—TECHNICAL SUBJECTS COVERED BY FORMER USPC
    • Y10S—TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y10S315/00—Electric lamp and discharge devices: systems
    • Y10S315/05—Starting and operating circuit for fluorescent lamp
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y10—TECHNICAL SUBJECTS COVERED BY FORMER USPC
    • Y10S—TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y10S315/00—Electric lamp and discharge devices: systems
    • Y10S315/07—Starting and control circuits for gas discharge lamp using transistors

Definitions

  • the invention relates to a circuit arrangement according to the preamble of claim 1. It is in particular a circuit arrangement which performs a preheating of electrode filaments of the discharge lamps before the ignition of discharge lamps.
  • Circuit arrangements for starting and operating discharge lamps are used in electronic control gear for discharge lamps.
  • the start of the discharge lamps is understood below to mean a preheating of electrode filaments of the discharge lamps during a preheating phase and the ignition of the discharge lamps during an ignition phase.
  • the start of discharge lamps with a preheat and an ignition phase is also called program start in English.
  • the ignition phase is followed by an operating phase in which the discharge lamp has an arc discharge.
  • An electronic control device for discharge lamps with program start requires according to the prior art, a circuit arrangement comprising a control unit which controls the sequence and the sequence of preheat, ignition and operating phase.
  • Circuit arrangements are known with an inverter, which feeds energy via a matching network in each case one end of the electrode filaments. The other ends are connected via a resonance capacitor.
  • the resonant capacitor and a lamp inductor are part of a resonant circuit having a resonant frequency which, in the undamped case, is at a natural frequency.
  • the matching network is needed to transform the source resistance of the inverter into a source resistance of the operating equipment that is suitable for operating discharge lamps.
  • the said resonant circuit is generally part of the matching network.
  • the inverter generates at an inverter output an inverter voltage having an inverter frequency which is in a preheat phase at a high preheat frequency which is greater than the natural frequency.
  • the value of the resonance capacitor and the preheating frequency are selected so that a heating current through the electrode coils is established, which causes sufficient for the respective lamp type preheating.
  • the inverter frequency is lowered in an ignition phase until it is so close to the natural frequency that an ignition voltage is set at a connected discharge lamp, which causes an ignition of the discharge lamp.
  • controlled variables such. B. lamp power or lamp current fed to a controller.
  • the controller acts via a manipulated variable to the inverter frequency, that sets a desired lamp power or a desired lamp current.
  • control unit which adjusts the required inverter frequency in timely correct sequence in the respective phases.
  • control unit must disable the regulation of lamp power or lamp current during the preheat and ignition phase, since in these phases an inverter frequency is required, which does not depend on lamp power or lamp current.
  • the present invention enables the o. G. To save the control unit.
  • the object is achieved in that a circuit arrangement has been found, which accomplishes a preheat, ignition and operating phase, without requiring a control unit.
  • a circuit arrangement according to the invention has a preheating resistor, which causes a damping of the resonant circuit during a preheating phase via the electrode filaments, whereby the resonant frequency of the resonant circuit is reduced from the natural frequency to a damping resonant frequency.
  • the preheat resistor assumes a value that is designed so that the resonance frequency of the resonant circuit is close to the natural frequency.
  • a controller regulates via a control signal that influences the inverter frequency, the lamp current or the lamp power.
  • lamp current refers to the current flowing through the gas discharge from discharge lamps connected to lamp terminals.
  • a first controller input (B 1) a first electrical variable is fed, which corresponds to the lamp current, wherein in the event that there is no gas discharge, the first electrical variable assumes a start value and in the event that a gas discharge is present, the first electrical Size is above a minimum value.
  • the circuit arrangement is designed so that in the event that the first electrical variable assumes the starting value, the controller adjusts the inverter to a starting frequency which is between the damping resonance frequency and the natural frequency.
  • the starting frequency is output as long as the first electrical quantity is below the minimum value. A regulation therefore does not take place at values of the first electrical variable below the minimum value.
  • the circuitry is either in the preheat or ignition phase. The type of phase is determined by the value of the preheat resistor.
  • the circuit arrangement is in the preheating phase.
  • the resonant frequency of the resonant circuit is depressed to the attenuation resonance frequency by the real part of the resistance of the electrode filaments and the preheat resistor.
  • the starting frequency is above the damping resonance frequency.
  • the resonant frequency of the resonant circuit increases and approaches the starting frequency which the inverter still outputs. At the same time, the attenuation of the Resonant circuit. Both effects lead to a change of the circuit arrangement in the ignition phase.
  • a voltage is applied to connected discharge lamps whose value is so high that the discharge lamps ignite.
  • Control unit is necessary, which controls the sequence of the phases of the circuit arrangement.
  • the figure shows an embodiment of a circuit arrangement according to the invention for the start and operation of discharge lamps.
  • resistors are denoted by the letter R, transistors by the letter T, coils by the letter L, amplifiers by the letter A, diodes by the letter D, node potentials by the letter N and capacitors by the letter C respectively followed by a number ,
  • a mains voltage can be connected at the terminals J1 and J2 .
  • the circuit arrangement is operated at a mains voltage.
  • the present invention is not tied to operation on a mains voltage.
  • a circuit arrangement according to the invention can, for example, also be operated on a battery voltage.
  • the mains voltage is fed to a full bridge rectifier consisting of the diodes D1, D2, D3, D4 via a filter consisting of two capacitors C1, C2 and two coils L1, L2.
  • the full-bridge rectifier provides the rectified mains voltage at its positive output, a node N21, with respect to a reference node N0.
  • circuit arrangements in question are used in operating devices that are operated at a mains voltage, they are subject to relevant regulations regarding mains harmonics, z. Eg IEC 1000-3-2. To comply with these regulations, circuit measures are required to reduce line harmonics.
  • One such measure is the installation of so-called charge pumps.
  • the advantage of charge pumps is the low circuit complexity, which is necessary for their realization.
  • the topology of a charge pump includes that the rectifier is coupled to the main energy storage via an electronic pump switch. This creates a pump node between the rectifier and the electronic pump switch.
  • the pump node is coupled to the inverter output via a pump network.
  • the pump network may include components that can be assigned to the matching network at the same time.
  • the principle of the charge pump is that, during a half-period of the inverter frequency, energy is taken from the mains voltage via the pump node and temporarily stored in the pump network. In the following half-period of the inverter frequency, the cached energy is supplied to the main energy storage via the electronic pump switch.
  • the rectified mains voltage is supplied to two pumping nodes N22 and N23 via the diodes D5 and D6.
  • the embodiment in the figure therefore has two so-called pumping branches.
  • the diodes D5 and D6 are necessary.
  • a pump node can be connected directly to the rectifier output, node N21.
  • the diodes used in the rectifier can switch fast enough to follow the inverter frequency. If this is not the case, even with only one pump branch, a fast diode must be connected between rectifier output and pump node.
  • the pump nodes are coupled to the positive output of the rectifier.
  • the literature also discloses charge pump topologies in which pump nodes are coupled to the negative output of the rectifier.
  • an electronic pump switch which are excited as diodes D7 and D8, respectively, leads to the node N24.
  • the main energy storage which is designed as an electrolytic capacitor C3, connected.
  • node N21 must be connected to node N24.
  • the components D5, D6, D7, D8, C8, C9, and L4 are then eliminated.
  • C3 feeds the inverter, which is designed as a half-bridge.
  • B. flyback converter or full bridge used.
  • a half-bridge is used for lamp powers between 5W and 300W, as it represents the most cost-effective topology.
  • the half-bridge consists of a series connection of two half-bridge transistors T1 and T2 and a series connection of two coupling capacitors C4 and C5. Both series circuits are connected in parallel with C3.
  • a connection node N25 of the half-bridge transistors and a connection node N26 of the coupling capacitors form the inverter output to which a rectangular inverter voltage with an inverter frequency is applied.
  • a lamp inductor L3 is connected between N25 and a lamp voltage node N27.
  • the terminal J3 is connected, to which in the exemplary embodiment, the series connection of two discharge lamps Lp1 and Lp2 is connected.
  • the present invention is also practicable with one or more lamps.
  • the current through the discharge lamps Lp1 and Lp2 flows through a terminal J8 through a winding W1 of a measuring transformer to the node N26.
  • the inverter voltage is thus applied to a series connection of two discharge lamps Lp1, Lp2 and the lamp inductor L3.
  • the current fed in J3 flows to a terminal J4 not only by the gas discharge of the discharge lamps Lp1, Lp2 but also by an outer coil of the first discharge lamp Lp1. From there, continue through a winding W4 of a heating transformer, further through a variable resistor R1, further through a winding W3 of the measuring transformer to the terminal J7. At the terminal J7, an outer coil of the second discharge lamp Lp2 is connected, the other end to the Connection J8 leads. Two inner coils of the discharge lamps Lp1 and Lp2 are connected to the winding W5 of the heating transformer through the terminals J5 and J6, respectively.
  • the inverter voltage causes not only a current through the gas discharge of the discharge lamps Lp1, Lp2 but also a heating current through the outer coils and via the heating transformer also a heating current through the inner coils of the discharge lamps Lp1, Lp2. If only one discharge lamp is to be operated, then the heating transformer can be dispensed with.
  • the heating current is essentially required before the ignition of the discharge lamps Lp1, Lp2 during a preheating as preheating current for the preheating of the helices.
  • the value of the heating current essentially determines the preheating resistor R1.
  • the value of R 1 is so low that a heating current preset by the lamp data is achieved.
  • the value of R1 increases, so that in comparison to the current through the gas discharge of the discharge lamps Lp1, Lp2 negligible heating current flows.
  • R1 is implemented by a so-called PTC or PTC thermistor. This is a resistor which has a low resistance when cold. The heating current heats the PTC thermistor, increasing its resistance.
  • R1 can also be realized by an electronic switch, which is closed in the preheat phase and then opened. In series with this switch, a resistor with a constant resistance value can be switched. This allows a quick transition from the preheating phase to the ignition phase.
  • the resonant frequency of a resonant circuit described in the next section is lower than its natural frequency during the preheating phase due to damping.
  • an inverter frequency which is below the natural frequency is selected during the preheating phase.
  • the lamp voltage node N27 is connected to the pump node N23 via a first resonance capacitor C6. Between N23 and N0 is a second resonant capacitor C7 switched. C6 and C7 form a resonant circuit with the lamp inductor L3. To determine the natural frequency of the resonant circuit, C6 and C7 are considered connected in series. The effective capacitance value of C6 and C7 with respect to the natural frequency is thus the quotient of the product and the sum of the capacitance values of C6 and C7. If the resonance circuit is excited near its natural frequency after the preheating phase, an ignition voltage is produced across the lamps, which leads to the ignition of the discharge lamps. After ignition, L3 acts together with C6 and C7 as a matching network, which transforms an output impedance of the inverter into an impedance necessary to operate the discharge lamps.
  • the combination of L3, C6, and C7 not only acts as a resonant circuit and matching network, but also as a pumping network. If the potential at N23 is lower than the instantaneous mains voltage, the pumping network L3, C6, C7 draws energy from the mains voltage. When the potential at N23 exceeds the voltage at the main energy storage C3, the power absorbed by the mains voltage is supplied to C3.
  • the ratio of the capacitance values of C6 and C7 the effect of network L3, C6, C7 as pumping network can be adjusted. The larger the capacitance value of C7, the lower the effect of the network L3, C6, C7 as the pump network. If the present invention is carried out without a charge pump, then C7 can be omitted.
  • C8 Another pumping action starts from a capacitor C8, which is connected between N23 and the connection node N25 of the half-bridge transistors T1, T2.
  • C8 not only acts as a pump network, but also fulfills the role of a snubber capacitor.
  • Snubber capacitors are commonly known as a measure of switch relieving in inverters.
  • the pumping network for the second pump branch consists of the series connection of a pumping inductor L4 and a pumping capacitor C9. This pump network is connected between the connection node N25 of the half-bridge transistors T1, T2 and the pump node N22.
  • two Pump branches used so that the pumped energy is divided into several components. For a more cost-effective dimensioning of the components is possible. This also gives a degree of freedom in the design of the dependence of the pumped energy on the operating parameters of the discharge lamps. However, the invention can also be realized with only one pump branch.
  • the half-bridge transistors T1, T2 are designed as a MOSFET. Other electronic switches can be used for this purpose.
  • an integrated circuit IC1 is provided in the exemplary embodiment.
  • IC1 in the present example is a circuit of International Rectifier type IR2153. Alternative circuits of this type are also available on the market; z. B. L6571 the company STM.
  • the circuit IR2153 contains a so-called high-sidc driver with which the half-bridge transistor T1 can also be driven, even though it has no connection at the reference potential N0. This requires a diode D10 and a capacitor C10.
  • the operating voltage supply of the IC1 is via the connection 1 of the IC1.
  • a voltage source VCC is provided between terminal 1 of IC1 and N0.
  • the IC can be supplied via a resistor from the rectified mains voltage.
  • the IC1 contains only one oscillator whose oscillation frequency can be set via the terminals 2 and 3. Due to the present invention, no effort is required in IC1 for a control device. It can therefore be used for IC1 a low-cost type.
  • the oscillation frequency of the said oscillator corresponds to the inverter frequency.
  • a frequency-determining resistor R3 is connected between the terminals 2 and 3.
  • the series connection of a frequency-determining capacitor C11 and the emitter-collector path of a bipolar transistor T3 is connected. Parallel to the emitter-collector path of T3, a diode D9 is connected, so that C11 can be charged and discharged.
  • a voltage between the base terminal of T3 and N0 allows the inverter frequency be set and thus forms a control variable for a control loop.
  • the base terminal of T3 is connected to a manipulated variable node N28.
  • T3, IC1 and their wiring can thus be understood as a regulator.
  • the functions of the IC1 and its wiring can also be realized by any voltage or current controlled oscillator, which accomplishes the driving of the half-bridge transistors via driver circuits.
  • the control loop in the embodiment detects the controlled current as the flow through the gas discharge of the discharge lamps Lp1, Lp2.
  • the measuring transformer has a winding W2.
  • the winding sense in the measuring transformer is designed in such a way that the heating current in winding W3 is drawn off from a total current in winding W1, so that a current flows in winding W2 which is proportional to the current through the gas discharge of the discharge lamps Lp1, Lp2.
  • a full-bridge rectifier formed by diodes D11, D12, D13 and D14 rectifies the current through winding W2 and carries it to N0 via a low-impedance measuring resistor R4.
  • the voltage drop across R4 is thus a measure of the current through the gas discharge of the discharge lamps Lp1, Lp2. Via a low pass for averaging, which is formed by a resistor R5 and a capacitor C13, the voltage drop at R4 reaches the input of a non-inverting measuring amplifier.
  • the measuring amplifier is realized in a known manner by an operational amplifier AMP and the resistors R6, R7 and R8. In the exemplary embodiment, a gain of the measuring amplifier of about 10 is set. In the event that the voltage drop at R4 has values that can be used directly as a manipulated variable, the amplifier can be omitted or by an impedance converter, such. As an emitter follower to be replaced.
  • the output of the measuring amplifier is connected to the manipulated variable node N28 via a diode D15.
  • Diode D15 is needed to raise the potential of N28 to a level above that value specified by the measuring amplifier.
  • the anode of D15 represents a first regulator input.
  • the circuit arrangement is designed such that without lamp current the potential of N28 assumes the starting value.
  • the starting value is chosen so that it is below a minimum value which limits the operating range of the transistor T3 and thus of the regulator. Fluctuations in the potential of N28 thus have no effect on the inverter frequency as long as the potential of N28 is below the minimum value. A regulation does not take place; the control loop is not closed.
  • the starting value at the potential of node N28 causes via T3 and IC 1 an inverter frequency which corresponds to the starting frequency.
  • the lowest possible frequency is advantageously selected by means of C11 and R3, since this ensures high heating currents in the electrode coils and thus short preheating phases.
  • the ignition phase is a high load for the half-bridge switches and for the components of the resonant circuit.
  • a protective circuit is provided in the embodiment according to the figure. If the ignition voltage is too high, this will increase the inverter frequency and thus set a greater difference to the natural frequency of the resonant circuit.
  • the protective circuit first acts via an ignition voltage, which is set by means of a threshold value switch.
  • the threshold value is realized in the figure by a varistor MOV. It is connected in series with a capacitor C12, a resistor R2 and a diode D17, which connects the lamp voltage node N27 to the manipulated variable node N28.
  • the anode of D 17 represents a second regulator input.
  • N28 is connected to N0 via the parallel connection of a resistor R9 and a capacitor C14.
  • N27 there is a voltage relative to N0, which is a measure of the reactive energy oscillating in the resonant circuit from L3, C6 and C7 and thus for the ignition voltage is. If this voltage exceeds the threshold voltage of the varistor MOV, a current flows through R9 and C14 is charged. This raises the voltage at the manipulated variable node N28. This causes an increase in the inverter frequency and the reactive energy oscillating in the resonant circuit is reduced because the inverter frequency continues to decrease from the natural frequency of the resonant circuit.
  • diode D16 is connected between N0 and the junction of R2 and D17. This is used in conjunction with C12 to N28, the sum of positive and negative amplitude of the voltage applied, which allows the varistor MOV.
  • the varistor MOV can find any other threshold value use, as it is z. B. can be constructed by zener diodes or suppressor diodes.
  • the threshold value of the varistor MOV is 250Veff in the application example. A higher value allows more reactive energy in the resonant circuit, which leads to a higher ignition voltage at the discharge lamps Lp1, Lp2, but also to a higher load on components. A desired optimum can thus be set via the threshold value of the varistor MOV.
  • the value of the resistor R2 influences the strength of the effect of the intervention according to the invention on the control loop at the manipulated variable node N28. Also advantageous is a non-linear relationship between the voltage at the manipulated variable node N28 and the inverter frequency. This non-linear relationship is realized in the application example by the non-linear characteristic of T3. In addition, it is influenced by the dependence of the frequency of the oscillator in IC1 on the voltage at terminal 3 of the IC1. A large increase in the voltage at N27 leads to a disproportionate increase in the inverter frequency due to the non-linearity, whereby an overload of components such. B. the voltage load of C3 or the current load of T 1 and T2, is prevented.
  • T3 sets an inverter frequency via IC1, which causes a desired lamp current.

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  • Circuit Arrangements For Discharge Lamps (AREA)

Claims (7)

  1. Montage pour amorcer et faire fonctionner des lampes ( Lp1, Lp2 ) à décharge ayant des caractéristiques suivantes :
    • un onduleur, qui émet sur une sortie ( N25, N 26 ) d'onduleur une tension d'onduleur, qui a une fréquence d'onduleur,
    • à la sortie ( N25 ) d'onduleur peuvent être raccordées, par un réseau ( L3, C6, C7 ) d'adaptation qui a un circuit ( L3, C6, C7 ) résonant ayant une fréquence propre, des lampes ( Lp1, Lp2 ) à décharge ayant des filaments d'électrodes par l'intermédiaire de bornes ( J3 à J6 ) de lampes,
    • une résistance ( R1 ) de préchauffage,
    • un régulateur dont la sortie de régulation émet un signal de réglage, la sortie du régulateur étant couplée à l'onduleur de manière à ce que le signal de régulation influe sur la fréquence de l'onduleur,
    • une première entrée de régulateur pour injecter une première grandeur électrique, qui correspond au courant de décharge dans un gaz d'une lampe ( Lp1, Lp2 ) à décharge raccordée, dans lequel, dans le cas où il n'y a pas de décharge dans un gaz, la première grandeur électrique prend une valeur d'amorçage et dans le cas où il y a une décharge dans un gaz, la première grandeur électrique est supérieure à une valeur minimum,
    caractérisé en ce que la résistance ( R1 ) de préchauffage provoque, pendant une phase de préchauffage par les filaments d'électrodes un amortissement du circuit ( L3, C6, C7 ) résonant, de sorte que la fréquence de résonance du circuit ( L3, C6, C7 ) résonant est réduite par la fréquence propre à une fréquence de résonance amortie et qui prend, pendant une phase d'amorçage, des valeurs qui, par rapport à la phase de préchauffage, provoquent un amortissement réduit du circuit ( L3, C6, C7 ) résonant, de sorte que la fréquence de résonance du circuit ( L3, C6, C7 ) résonant tend vers la fréquence propre,
    le régulateur donne une fréquence d'onduleur, qui est comprise entre la fréquence de résonance d'amortissement et la fréquence propre dans le cas où la première grandeur électrique prend la valeur d'amorçage et
    le régulateur donne une fréquence d'onduleur, qui donne un courant de lampe souhaité et une puissance de lampe souhaitée dans le cas où la première grandeur électrique est supérieure à la valeur minimum.
  2. Montage suivant la revendication 1,
    caractérisé en ce que
    le régulateur a une deuxième entrée de régulateur, dans laquelle est injectée par un commutateur ( MOV ) à valeur de seuil une deuxième grandeur électrique qui correspond à une deuxième grandeur de fonctionnement, qui est une mesure de l'énergie réactive qui oscille dans le circuit ( L3, C6, C7 ) résonant,
    dans lequel la valeur de la deuxième grandeur électrique donne, lorsque la valeur de seuil du commutateur ( MOV ) à valeur de seuil est dépassée, une valeur plus grande de la fréquence de l'onduleur.
  3. Montage suivant l'une des revendications précédentes,
    caractérisé en ce que
    l'onduleur comprend une pompe de charge.
  4. Montage suivant l'une des revendications précédentes,
    caractérisé en ce que
    l'onduleur est un onduleur à demi-pont.
  5. Montage suivant l'une des revendications précédentes,
    caractérisé en ce que
    la résistance ( R1 ) de préchauffage est une résistance qui varie en fonction de la température, à coefficient de température positif.
  6. Montage suivant l'une des revendications 1 à 4,
    caractérisé en ce que
    la résistance ( R1 ) de préchauffage est montée en série avec un commutateur électronique.
  7. Procédé pour amorcer et faire fonctionner des lampes à décharge ayant un montage suivant la revendication 1, caractérisé par des stades suivantes :
    • amortissement du circuit ( L3, C6, C7 ) résonant par la résistance ( R1 ) de préchauffage par l'intermédiaire de filaments d'électrodes de lampes à décharge raccordées,
    • retrait de l'amortissement du circuit ( L3, C6, C7 ) résonant.
EP03029437A 2003-01-28 2003-12-19 Circuit et méthode d'allumage et de commande du fonctionnement des lampes à décharge de gaz avec filaments de préchauffage Expired - Lifetime EP1443808B1 (fr)

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
DE10303277A DE10303277A1 (de) 2003-01-28 2003-01-28 Schaltungsanordnung und Verfahren zum Start und Betrieb von Gasentladungslampen mit heizbaren Elektrodenwendeln
DE10303277 2003-01-28

Publications (3)

Publication Number Publication Date
EP1443808A2 EP1443808A2 (fr) 2004-08-04
EP1443808A3 EP1443808A3 (fr) 2006-03-22
EP1443808B1 true EP1443808B1 (fr) 2008-10-08

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Application Number Title Priority Date Filing Date
EP03029437A Expired - Lifetime EP1443808B1 (fr) 2003-01-28 2003-12-19 Circuit et méthode d'allumage et de commande du fonctionnement des lampes à décharge de gaz avec filaments de préchauffage

Country Status (8)

Country Link
US (1) US6936976B2 (fr)
EP (1) EP1443808B1 (fr)
KR (1) KR101009518B1 (fr)
CN (1) CN100551197C (fr)
AT (1) ATE410911T1 (fr)
CA (1) CA2456367A1 (fr)
DE (2) DE10303277A1 (fr)
TW (1) TWI333804B (fr)

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* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
DE102004044180A1 (de) 2004-09-13 2006-03-16 Patent-Treuhand-Gesellschaft für elektrische Glühlampen mbH Elektronisches Vorschaltgerät mit Pumpschaltung für Entladungslampe mit vorheizbaren Elektroden
DE102007016322A1 (de) * 2007-04-04 2008-10-09 Tridonicatco Gmbh & Co. Kg Schaltung zur Wendelheizung
US7982406B2 (en) * 2007-05-07 2011-07-19 Simon Richard Greenwood Active lamp current crest factor control
WO2009008421A1 (fr) * 2007-07-10 2009-01-15 Toyo Seikan Kaisha, Ltd. Électrode de chauffage et procédé pour chauffer un matériau devant être chauffé en utilisant l'électrode de chauffage
DE102008004399A1 (de) * 2008-01-14 2009-07-16 HÜCO electronic GmbH Elektronisches Vorschaltgerät mit Strommesseinrichtung, Verfahren zu seiner Steuerung und Beleuchtungsgerät
DE202008008165U1 (de) * 2008-06-18 2009-11-05 Tridonicatco Gmbh & Co. Kg Betriebsgerät für Gasentladungslampen oder andere Leuchtmittel mit Lampenstrommessung
US11524354B2 (en) 2017-06-09 2022-12-13 Illinois Tool Works Inc. Systems, methods, and apparatus to control weld current in a preheating system
MX2020002936A (es) * 2017-09-29 2020-07-24 Illinois Tool Works Sistemas metodos y aparatos para precalentar alambre de soldadura.

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Publication number Priority date Publication date Assignee Title
SG48019A1 (en) * 1993-04-23 1998-04-17 Koninkl Philips Electronics Nv Power factor correcting circuit
JP3858317B2 (ja) 1996-11-29 2006-12-13 東芝ライテック株式会社 放電灯点灯装置及び照明装置
JP2982804B2 (ja) 1998-01-16 1999-11-29 サンケン電気株式会社 放電灯点灯装置
US6144169A (en) * 1998-12-29 2000-11-07 Philips Electronics North America Corporation Triac dimmable electronic ballast with single stage feedback power factor inverter
JP2001015289A (ja) * 1999-04-28 2001-01-19 Mitsubishi Electric Corp 放電灯点灯装置
US6020691A (en) * 1999-04-30 2000-02-01 Matsushita Electric Works R & D Laboratory, Inc. Driving circuit for high intensity discharge lamp electronic ballast
US6593703B2 (en) * 2001-06-15 2003-07-15 Matsushita Electric Works, Ltd. Apparatus and method for driving a high intensity discharge lamp

Also Published As

Publication number Publication date
CA2456367A1 (fr) 2004-07-28
KR20040069291A (ko) 2004-08-05
DE50310605D1 (de) 2008-11-20
ATE410911T1 (de) 2008-10-15
EP1443808A2 (fr) 2004-08-04
KR101009518B1 (ko) 2011-01-18
US6936976B2 (en) 2005-08-30
DE10303277A1 (de) 2004-07-29
US20040150356A1 (en) 2004-08-05
CN100551197C (zh) 2009-10-14
CN1558706A (zh) 2004-12-29
TWI333804B (en) 2010-11-21
TW200414827A (en) 2004-08-01
EP1443808A3 (fr) 2006-03-22

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