EP1635620B1 - Ballast électronique de pompe a charge pour lampes a décharge avec électrodes de préchauffage - Google Patents

Ballast électronique de pompe a charge pour lampes a décharge avec électrodes de préchauffage Download PDF

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Publication number
EP1635620B1
EP1635620B1 EP05017529A EP05017529A EP1635620B1 EP 1635620 B1 EP1635620 B1 EP 1635620B1 EP 05017529 A EP05017529 A EP 05017529A EP 05017529 A EP05017529 A EP 05017529A EP 1635620 B1 EP1635620 B1 EP 1635620B1
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EP
European Patent Office
Prior art keywords
lamp
preheating
ballast
frequency
converter
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Not-in-force
Application number
EP05017529A
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German (de)
English (en)
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EP1635620A1 (fr
Inventor
Bernd Rudolph
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Osram GmbH
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Patent Treuhand Gesellschaft fuer Elektrische Gluehlampen mbH
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    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B41/00—Circuit arrangements or apparatus for igniting or operating discharge lamps
    • H05B41/14—Circuit arrangements
    • H05B41/26—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc
    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B41/00—Circuit arrangements or apparatus for igniting or operating discharge lamps
    • H05B41/14—Circuit arrangements
    • H05B41/26—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc
    • H05B41/28—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc using static converters
    • H05B41/295—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc using static converters with semiconductor devices and specially adapted for lamps with preheating electrodes, e.g. for fluorescent lamps
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y10—TECHNICAL SUBJECTS COVERED BY FORMER USPC
    • Y10S—TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y10S315/00—Electric lamp and discharge devices: systems
    • Y10S315/05—Starting and operating circuit for fluorescent lamp
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y10—TECHNICAL SUBJECTS COVERED BY FORMER USPC
    • Y10S—TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y10S315/00—Electric lamp and discharge devices: systems
    • Y10S315/07—Starting and control circuits for gas discharge lamp using transistors

Definitions

  • the present invention relates to an electronic ballast designed for the operation of lamps with preheatable electrodes.
  • Such lamps and ballasts have long been known.
  • a so-called PTC element (a resistor with a pronounced positive temperature coefficient) is used to set a preheating time when restarting such a lamp.
  • the PTC element heats up during preheating by a current and terminates the preheating process by increasing its electrical resistance.
  • the control of the converter in particular the one or more switching transistors used therein, on the one hand can be effected by a feedback, wherein one speaks of a so-called self-excited converter.
  • the ballasts are designed for operation on an AC power supply.
  • a rectifier is used to generate a DC link voltage, with which a converter is supplied, the again generates a higher frequency compared to the power supply power to operate the lamp.
  • ballasts An important feature of such ballasts is the type of power extraction from the AC power grid. If the rectifier charges a DC link storage capacitor, it will without further action to jerky charging operations of the intermediate circuit storage capacitor when the instantaneous mains voltage is above the capacitor voltage. This generates mains harmonics and causes a poor power factor.
  • the topology of a pump circuit includes that the mains rectifier is coupled to the DC bus storage capacitor via at least one electronic pump switch. This creates a pump node between the mains rectifier and the electronic pump switch. This is coupled via a pump network to the converter output.
  • the pump network may include components that may be associated with a matching network for coupling the lamp to the converter output.
  • the principle of the pump circuit is to take energy from the rectified mains voltage during the half-period of the converter frequency via the pump node and buffer it in the pump network. In the subsequent half-cycle, the cached energy is supplied via the electronic pump switch to the intermediate circuit storage capacitor.
  • the rectified supply voltage is therefore taken in time with the converter frequency energy.
  • the electronic ballast includes filter circuits which suppress spectral components of the mains current in the range of the converter frequency and above.
  • the pump circuit or circuits may be designed so that the mains current harmonics comply with the mentioned regulations or other requirements.
  • the invention is based on the technical problem of specifying an electronic ballast with a pump circuit which is improved with regard to the preheating of lamp electrodes.
  • the main problem is that the energy dissipation by the PTC element fails as part of the heating process.
  • the energy pumped by the pump circuit must therefore be dissipated elsewhere during preheating. It has been observed that the pumping action of the pump circuit i. a. can pump more energy than is needed for preheating the electrodes. This can lead to an overload of components, in particular of the DC link storage capacitor, by increasing the voltage to impermissible values.
  • the invention thus provides that a much higher converter frequency is used during the preheating compared to the idle resonance frequency.
  • the lowering of the effective pumping action with the frequency is related to the fact that the resonance behavior of the resonant circuit containing the lamp has a frequency dependence that overcompensates the frequency dependence of the capacitive pumping and inductive pumping Has.
  • the effective pump power decreases in capacitive pump circuits approximately proportional to the reciprocal of the frequency square and in inductive pump circuits approximately inversely proportional to the frequency.
  • the frequency used during preheating may be greater than 1.3 times the no-load resonant frequency with frequencies over 1.4 times, 1.5 times, 1.6 times, 1.7 times, 1.8 times greater than or equal to about one-fold, about 1.9 times, or about 2 times, so that the pumping action is significantly reduced over operation.
  • the idle resonance frequency is the usually designated resonant frequency of the lamp circuit without a connected lamp, which results in the well-known manner essentially from the lamp inductor inductance and the capacitance of the resonant capacitor.
  • the invention provides a Vorbytransformator, with a sufficient for preheating current can be generated. Due to the throttling action of the lamp inductor, there is otherwise the risk that the current becomes too small at the preferred relatively high preheat frequencies and thus can not achieve a sufficient preheating effect with regard to the current (not the energy).
  • the increase of the preheating frequency according to the invention therefore initially precludes the generation of sufficiently large preheating currents. However, this problem can be solved by the mentioned preheating transformer.
  • Vortextransformator provides a potential separation to the electrodes, which is also beneficial in many cases.
  • a lamp current or lamp power control is provided in the ballast according to the invention, which changes the converter frequency in the lamp end operation so that a certain target value is maintained. This is ultimately done by approximating or removing the transducer frequency from the resonant frequency of the lamp resonant circuit containing the lamp.
  • a preferred embodiment of the invention provides a voltage regulation circuit which serves to adjust the ignition voltage of the lamp resonant circuit via the frequency of the converter of the ballast.
  • This voltage regulation circuit is advantageous because a relatively accurate frequency adjustment is required for an ignition via a resonance excitation due to the quality of the lamp resonant circuit.
  • the control circuit can now adapt the frequency to the resonance behavior of the lamp resonant circuit or "follow-up" and in particular work by limiting the ignition voltage by changing the frequency.
  • the aforementioned lamp current control circuit can be combined with the voltage regulation circuit insofar as both access the same control input for controlling the operating frequency of the converter. It can preferably be provided that the circuit as a current or power control circuit (ie continuous operation control circuit) works as soon as appreciable lamp currents flow, so the lamp has ignited, and in the other case, the voltage control "has priority".
  • the mentioned combination of continuous operation circuit and voltage regulation circuit may further be adapted to apply the lamp voltage, a potential derived therefrom or another variable correlated therewith to an input of the control amplifier or switching transistor of the continuous operation control circuit.
  • the lamp voltage a potential derived therefrom or another variable correlated therewith
  • it may also suffice to use only a temporal portion of the lamp voltage or the correlating quantity. This has the purpose of deactivating the continuous operation control circuit during preheating and starting until the lamp has been ignited and has reached its burning voltage.
  • the preheating and ignition processes can proceed undisturbed and the continuous operation control circuit is used only in continuous operation.
  • FIG. 1 shows a first exemplary embodiment.
  • Two connections KL1-1 and KL1-2 are marked on the left, to which a mains voltage is to be connected.
  • a filter of two capacitors C1 and C2 and two coupled coils labeled F11 connect the mains voltage terminals to a full-bridge rectifier of the diodes D1-D4.
  • a Pumping circuit has two pump branches, to which diodes D5 - D8 are to be expected, via which the rectified supply voltage is applied to an intermediate circuit storage capacitor C6, which is shown in the figure on the far right.
  • the DC link capacitor C6 feeds the converter constructed here as a half bridge of two switching transistors V1 and V2.
  • the half-bridge transistors V1 and V2 generate by corresponding antiphase clocking at its center tap an alternating potential that oscillates between the two potentials of the rectifier output.
  • This alternating potential is connected via a lamp inductor LD1 and, in the present case, a series connection of two discharge lamps LA1 and LA2 and a measuring transformer TR1 explained in more detail below via two coupling capacitors C15, C16 to the supply branches.
  • FIG. 1 shows that not only a current through the discharge plasma in the lamps LA1 and LA2, but also a preheating current through the upper electrode of the upper lamp LA1, the lower electrode of the lower lamp LA2, the two interconnected electrodes of the lamp LA1 and the lamp LA2 and a respective secondary winding of a heating transformer TR2 can flow.
  • a pump circuit with two pump branches is used here, which prepares a comparatively small circuit complexity.
  • the rectifier is coupled via an electronic pump switch D6 / D8 or D5 / D7 to the main energy store, the DC link storage capacitor C6.
  • the pump nodes lying between the diodes D5 and D7, on the one hand, and D6 and D8, on the other hand, are coupled via a pump network to the output of a converter or inverter, which is explained in more detail below.
  • the cached energy is supplied via the electronic pump switch, here the diodes D8 and D7, the intermediate circuit storage capacitor C6. This energy is taken from the grid in time with the inverter frequency.
  • the filter elements mentioned suppressed largely higher spectral components, so that ultimately a quasi-sinusoidal power consumption takes place.
  • the details of the pumping circuit are not relevant to the present invention.
  • the state of the art and in particular the applications DE 103 03 276.2 and DE 103 03 277.0 the same applicant. It is essential that the pump branches with each period of the inverter pump energy into the circuit, but can not return.
  • the lamp resonant circuit has in addition to the already mentioned lamp inductor LD1 resonant capacitors C5 and C9.
  • the lamp resonant circuit is the first to the voltage overshoot by a resonant near excitation. After ignition, the lamp resonant circuit acts as a matching network to the second, which transforms the output impedance of the inverter into an impedance suitable for operation of the discharge lamps.
  • the lamp resonant circuit also acts as a pump network. If the potential at the already mentioned pump node is lower than the instantaneous mains voltage, then the pump network draws energy from the network. In the opposite case, the absorbed energy is delivered to the DC link capacitor C6. Another pumping action starts from the capacitor C8.
  • the capacitor C8 acts as a so-called. Trapezoidal capacitor for switching discharge of the half-bridge transistors V1 and V2.
  • the pump network for the second pump branch consists of a series connection of a pumping inductor L1 and a pumping capacitor C10.
  • the half-bridge transistors V1 and V2 which are designed as a MOSFET, are driven at their gates by an integrated driver circuit, for example of the type International Rectifier IR2153.
  • This IC also includes a highside driver for driving the "high" half-bridge transistor V1.
  • the diode D9 and the capacitor C4 are provided.
  • the IC includes an oscillator whose frequency can be adjusted via terminals 2 and 3 (RT and CT).
  • the frequency according to RT and CT corresponds to the lowest operating frequency of the half-bridge.
  • a frequency-determining resistor R12 is connected between the terminals 2 and 3.
  • a frequency-determining capacitor C12 is connected between the terminal 3 and serving as a reference potential lower supply branch.
  • a diode D15 is connected to charge and discharge C12.
  • the half-bridge frequency can be adjusted and thus forms a control variable for a control loop.
  • the base terminal of the bipolar transistor T3 is driven by circuit elements drawn further to the right in FIG. The bipolar transistor and the IC and the associated circuitry thus form a regulator.
  • the functions of the IC and the associated circuitry can also be realized by any voltage or current controlled oscillator circuit, which drive via driver circuits, the control of converter transistors.
  • the described inverter is controlled by a sequence controller AS, which is shown in Figure 1 below.
  • the controller detects the lamp current as a controlled variable, specifically, the discharge current. This is detected via a measuring transformer TR1. Another known and applicable Lamp current measurement could take place via one of the two coupling capacitors C15, C16 or a portion of it detected on a measuring resistor.
  • a full-bridge rectifier GL rectifies the current and feeds it via a low-impedance measuring resistor R21 D to the reference potential. Via a low pass of the resistor R21 and the capacitor C21, which is used for averaging, the voltage drop is applied to R21 D in the input of a non-inverting measuring amplifier in the form of an operational amplifier U2-A.
  • the diode D23 decouples the output of the measuring amplifier U2-A from the voltage divider D24, C20, R20, D16, R11, when the potential at the connection point LD1 - D24 is high enough.
  • the circuit arrangement is designed such that, without a discharge current, the potential at the anode of the diode D23 assumes a value defined by the output VCO of the sequence controller AS via a diode D11, ie the sequence controller AS determines the starting frequency.
  • the sequence controller AS therefore provides via the output VCO a frequency value which is above twice the idling resonance frequency.
  • the inverter is thus operated at a predetermined preheating frequency and the primary winding A of the preheating TR2 acted upon accordingly. Consequently, corresponding preheating currents flow in the secondary windings B, C and D.
  • the capacitor C3 serves to set an average potential between the potentials at the DC link storage capacitor C6 as a reference potential for the right terminal of the primary winding A.
  • the sequence controller AS After a pre-heating time predetermined by the sequence controller AS, the sequence controller AS changes into the ignition mode within approximately 1 ms and generates it Resonance increase in the lamp resonant circuit, the necessary ignition voltage.
  • the preheating can be switched off after preheating easy. This prevents any further energy dissipation in the preheating circuits and unnecessary heat input into the lamps LR1 and LR2 by the electrodes.
  • a protective circuit is provided for avoiding ignition voltages that are too high. At the same time, however, this protective circuit also forms a voltage regulation circuit for setting the ignition voltage to a suitable value.
  • the threshold value switch located here in the high-voltage range can also be omitted and a corresponding threshold value circuit can be provided in the low-voltage range, that is to say in the region of the evaluation. This is not shown here, but it is clear to the person skilled in the art.
  • the lamp voltage is given above a certain threshold value between two diodes D16.
  • the anode of the left diode represents a second regulator input.
  • the value of resistor R20 influences the magnitude of the effect of the below-described engagement on the control loop.
  • the tapped via the suppressor diode D24 lamp voltage forms a measure of the fluctuating in the lamp resonant circuit reactive energy and the ignition voltage. If this voltage exceeds the threshold value of the suppressor diode D24, the half-bridge frequency is increased and thus the Reduces reactive energy oscillating in the resonant circuit and on the other hand reduces the lamp voltage.
  • a typical value for the threshold of the suppressor diode D24 is z. B. 250 V.
  • the voltage control circuit then controls above this voltage.
  • the continuous operation control circuit can be disabled when a Zünd needle takes place. This is of interest in order to prevent disturbances during ignition.
  • the lamp current control, ie continuous operation control circuit operates with a time constant in the order of 1 ms.
  • FIG. 2 shows a second exemplary embodiment for which the explanations for the first exemplary embodiment largely apply. There are the same reference numerals for identical or corresponding parts.
  • the lamp inductor LD1 and the preheating transformer TR2 from FIG. 1 are contracted.
  • the lamp inductor LD1 thus corresponds to the primary winding A of the Vorholictransformators. Its function remains otherwise unchanged, however, it is not switched off, so it lacks the switch V3 and the corresponding control output PH of Figure 1.
  • the preheating could namely only be switched off on the secondary side, which because of involved and the corresponding effects on the necessary driver circuits would be costly.
  • the individual preheating circuits each contain a capacitor C7, C11 and C13.
  • capacitors C7, C11 and C13 have the advantage of direct current isolation for a coil breakage detection not shown here despite parallel to the electrodes secondary windings B, C and D. Incidentally, this latter function can also be realized in the embodiment of Figure 1, in which case diodes could be used instead of the capacitors.
  • the first embodiment has the advantage of completely switching off the preheating circuits and is therefore particularly suitable for particularly efficiency-optimized lamps which are sensitive to heat input in terms of their efficiency.
  • the second embodiment of Figure 2 is because in fact only three capacitors (which are incidentally anyway optional) and three Additional windings on the lamp reactor are necessary, particularly simple and inexpensive.
  • FIG. 3 shows, with the hatched area (channel 3), the lamp current which is actually oscillating at the operating frequency in continuous operation.
  • the lamp current has an effective value of about 335 mA at nominal conditions of 230 V supply voltage at 50 Hz.
  • Channel C ie the black solid line, shows the fluctuating between a minimum value of about 47.3 kHz and a maximum value of about 61.5 kHz operating frequency. The fluctuations are due to the lamp current control over the operating frequency. The remaining fluctuations of the lamp current are u. a. conditioned by the time constant of the regulation.
  • the no-load resonance frequency (determined by LD1 and C9) is 42.6 kHz and the ignition frequency (at an open-circuit voltage of 700 V) is about 48 kHz.
  • FIG. 4 shows, with the hatched channel B, the profile of the intermediate circuit voltage U C6 in the vicinity of an ignition process.
  • the preheat frequency here is 98.5 kHz, that is more than twice the idle resonance frequency.

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  • Circuit Arrangements For Discharge Lamps (AREA)
  • Discharge Lamps And Accessories Thereof (AREA)

Claims (8)

  1. Ballast électronique pour au moins une lampe (LA1, LA2) à décharge, ayant des électrodes pouvant être chauffées au préalable, ballast qui a :
    - une borne (KL1-1, KL1-2) d'alimentation en tension alternative,
    - un redresseur (D1 à D4) relié à la borne (KL1-1, KL1-2) d'alimentation,
    - un convertisseur (V1, V2) de production d'une puissance d'alimentation de fréquence plus haute pour la lampe (LA1, LA2) à décharge à partir de la puissance d'alimentation de la borne (KL1-1, KL1-2) d'alimentation redressée par le redresseur (D1 à D4),
    - au moins un circuit (D5/D7, D6/D8) de pompe pour améliorer le facteur de puissance du ballast par prélèvement d'énergie à la borne (KL1-1, KL1-2) d'alimentation en tension alternative,
    caractérisé en ce que le ballast comporte un transformateur (TR2) de chauffage préalable qui est conçu pour, pendant une phase de chauffage préalable, avant un amorçage de la lampe (LA1, LA2), alimenter en une puissance de chauffage préalable les électrodes pouvant être chauffées au préalable qui lui sont raccordées côté secondaire (B, C, D),
    le ballast étant conçu pour, pendant le chauffage préalable, faire fonctionner le convertisseur (V1, V2) à une fréquence plus élevée que la fréquence de résonance en marche à vide du ballast, pour alimenter le côté (A) primaire du transformateur (TR2) de chauffage préalable.
  2. Ballast suivant la revendication 1, dans lequel il est prévu, en série avec le transformateur (TR2) de chauffage préalable, un interrupteur (V3) pour mettre hors circuit le transformateur (TR2) de chauffage préalable.
  3. Ballast suivant la revendication 1, dans lequel l'enroulement (A) primaire du transformateur de chauffage préalable est formé par une bobine (LD1) de lampe du ballast.
  4. Ballast suivant la revendication 2 ou 3, dans lequel il est monté un condensateur (C7, C11, C13) entre le côté secondaire (B, C, D) du transformateur de chauffage préalable et l'une des électrodes pouvant être chauffées au préalable.
  5. Ballast suivant l'une des revendications précédentes, ayant un circuit (TR1, GL, R21-R25, R21D, C21, U2-A, D23, T3, C4, D9, RT, CT, R12, C12, D15) de régulation du fonctionnement dans la durée pour réguler le courant de lampe ou la puissance de lampe lors du fonctionnement de la lampe dans la durée par la fréquence de fonctionnement du convertisseur (V1, V2).
  6. Ballast suivant l'une des revendications précédentes, comprenant un circuit (D24, C20, R20, D16, C4, D9, RT, CT, R12, C12, T3, D15) de régulation de la tension pour régler la tension d'amorçage d'un circuit (LD1, C5, C9) résonant de lampe lors de l'amorçage de la lampe (LA1, LA2) de décharge par la fréquence de fonctionnement du convertisseur (V1, V2).
  7. Ballast suivant l'une des revendications précédentes, dans lequel une commande (AS) de déroulement pour commander le fonctionnement du convertisseur (V1, V2) est conçue de façon à faire se dérouler le passage de la phase de chauffage préalable à la fréquence du convertisseur plus haute que la fréquence de fonctionnement dans la durée à l'amorçage de la lampe (LA1, LA2) à décharge en 10 ms au plus.
  8. Procédé pour faire fonctionner une lampe (LA1, LA2) à décharge ayant des électrodes pouvant être chauffées au préalable à l'aide d'un ballast électronique ayant une borne (KL1-1, KL1-2) d'alimentation en tension alternative, procédé qui a les stades dans lesquels :
    - on redresse une tension alternative s'appliquant à la borne une (KL1-1, KL1-2) d'alimentation en tension alternative,
    - on produit une puissance d'alimentation de fréquence plus haute pour la lampe (LA1, LA2) à décharge à partir de la puissance d'alimentation en tension alternative redressée à l'aide d'un convertisseur (V1, V2),
    - dans lequel on utilise au moins un circuit (D5/D7, D6/D8) de pompe pour améliorer le facteur de puissance du ballast en prélevant de l'énergie de la borne (KL1-1, KL1-2) d'alimentation en tension alternative,
    caractérisé en ce que, pendant une phase de chauffage préalable, avant un amorçage de la lampe (LA1, LA2), on alimente en une puissance de chauffage préalable les électrodes pouvant être chauffées au préalable à l'aide d'enroulements (B, C, D) secondaires d'un transformateur (TR2) de chauffage préalable, le convertisseur (V1, V2) fonctionnant pendant le chauffage préalable à une fréquence plus haute que la fréquence de résonance en marche à vide du ballast, pour alimenter le côté (A) primaire du transformateur (TR2) de chauffage préalable.
EP05017529A 2004-09-13 2005-08-11 Ballast électronique de pompe a charge pour lampes a décharge avec électrodes de préchauffage Not-in-force EP1635620B1 (fr)

Applications Claiming Priority (1)

Application Number Priority Date Filing Date Title
DE102004044180A DE102004044180A1 (de) 2004-09-13 2004-09-13 Elektronisches Vorschaltgerät mit Pumpschaltung für Entladungslampe mit vorheizbaren Elektroden

Publications (2)

Publication Number Publication Date
EP1635620A1 EP1635620A1 (fr) 2006-03-15
EP1635620B1 true EP1635620B1 (fr) 2007-11-28

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EP05017529A Not-in-force EP1635620B1 (fr) 2004-09-13 2005-08-11 Ballast électronique de pompe a charge pour lampes a décharge avec électrodes de préchauffage

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Country Link
US (1) US7193375B2 (fr)
EP (1) EP1635620B1 (fr)
KR (1) KR101171686B1 (fr)
CN (1) CN1750731B (fr)
AT (1) ATE379953T1 (fr)
CA (1) CA2518768A1 (fr)
DE (2) DE102004044180A1 (fr)
TW (1) TW200618676A (fr)

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WO2008015602A1 (fr) * 2006-07-31 2008-02-07 Koninklijke Philips Electronics N.V. Procédé d'alimentation d'un circuit de commande pour une lampe à décharge de gaz pendant le préchauffage de ladite lampe et dispositif pour réaliser ledit procédé
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Cited By (2)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
DE202008008165U1 (de) 2008-06-18 2009-11-05 Tridonicatco Gmbh & Co. Kg Betriebsgerät für Gasentladungslampen oder andere Leuchtmittel mit Lampenstrommessung
DE102009020884A1 (de) 2008-06-18 2010-01-14 Tridonicatco Gmbh & Co. Kg Betriebsgerät für Lampen mit Elektroden, mit Lampenstrommessung

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EP1635620A1 (fr) 2006-03-15
CA2518768A1 (fr) 2006-03-13
CN1750731A (zh) 2006-03-22
KR20060051258A (ko) 2006-05-19
DE102004044180A1 (de) 2006-03-16
TW200618676A (en) 2006-06-01
ATE379953T1 (de) 2007-12-15
KR101171686B1 (ko) 2012-08-06
DE502005002087D1 (de) 2008-01-10
US7193375B2 (en) 2007-03-20
CN1750731B (zh) 2011-01-26
US20060055339A1 (en) 2006-03-16

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