EP0067185B1 - Dispositif electronique pour l'excitation d'un element electromagnetique - Google Patents

Dispositif electronique pour l'excitation d'un element electromagnetique Download PDF

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Publication number
EP0067185B1
EP0067185B1 EP19820900090 EP82900090A EP0067185B1 EP 0067185 B1 EP0067185 B1 EP 0067185B1 EP 19820900090 EP19820900090 EP 19820900090 EP 82900090 A EP82900090 A EP 82900090A EP 0067185 B1 EP0067185 B1 EP 0067185B1
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EP
European Patent Office
Prior art keywords
current
value
soll
nominal
switching transistor
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Expired
Application number
EP19820900090
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German (de)
English (en)
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EP0067185A1 (fr
Inventor
Edwin Petschenka
Winfried Beulen
Erich Rothmeier
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BBC Brown Boveri AG Germany
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Brown Boveri und Cie AG Germany
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Publication of EP0067185A1 publication Critical patent/EP0067185A1/fr
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    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01H—ELECTRIC SWITCHES; RELAYS; SELECTORS; EMERGENCY PROTECTIVE DEVICES
    • H01H47/00—Circuit arrangements not adapted to a particular application of the relay and designed to obtain desired operating characteristics or to provide energising current
    • H01H47/22—Circuit arrangements not adapted to a particular application of the relay and designed to obtain desired operating characteristics or to provide energising current for supplying energising current for relay coil
    • H01H47/32—Energising current supplied by semiconductor device
    • H01H47/325—Energising current supplied by semiconductor device by switching regulator
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01H—ELECTRIC SWITCHES; RELAYS; SELECTORS; EMERGENCY PROTECTIVE DEVICES
    • H01H47/00—Circuit arrangements not adapted to a particular application of the relay and designed to obtain desired operating characteristics or to provide energising current
    • H01H47/02—Circuit arrangements not adapted to a particular application of the relay and designed to obtain desired operating characteristics or to provide energising current for modifying the operation of the relay
    • H01H47/04—Circuit arrangements not adapted to a particular application of the relay and designed to obtain desired operating characteristics or to provide energising current for modifying the operation of the relay for holding armature in attracted position, e.g. when initial energising circuit is interrupted; for maintaining armature in attracted position, e.g. with reduced energising current
    • H01H2047/046—Circuit arrangements not adapted to a particular application of the relay and designed to obtain desired operating characteristics or to provide energising current for modifying the operation of the relay for holding armature in attracted position, e.g. when initial energising circuit is interrupted; for maintaining armature in attracted position, e.g. with reduced energising current with measuring of the magnetic field, e.g. of the magnetic flux, for the control of coil current

Definitions

  • the invention relates to an electronic circuit arrangement for controlling an electromagnetic component, in particular a contactor or relay, the electromagnetic component being in series with a switching transistor and a measuring resistor, an actual current value corresponding to the current through the component can be tapped at the measuring resistor and fed to a comparator , the comparator can be supplied with a current setpoint for the pull-in current and a reduced current setpoint for the holding current and the switching transistor is controlled via the comparator if the actual current value falls below the current setpoint.
  • an electronic circuit arrangement is known from D E-A-2 513 043.
  • Electromagnetic components such as switching relays and contactors, are generally known in numerous design variants.
  • Such switching devices consist of a yoke with one or more coils and an armature which is magnetically attracted by the yoke after application of a control voltage to the coil and thereby actuates switching contacts.
  • a circuit for DC operation for contactors or relays in which the supply voltage is applied to the excitation coil in pulses via an electronic switch.
  • the frequency and / or duration of the pulses are determined by comparing a voltage proportional to the excitation current with a reference voltage.
  • the reference voltage is raised by an adjustable timer for a time longer than the duration of the tightening phase from the value required for holding to or above the value required for tightening.
  • the publication also generally indicates that the time at which the reference voltage changes can be made dependent on the change in inductance of the excitation coil when the air gap is closed.
  • the inductance to be switched is connected in series with a switching transistor and a measuring resistor, the measuring resistor giving an actual current value to a comparison stage.
  • the comparison stage also receives a current setpoint and controls the switching transistor as a function of the control deviation that occurs via a driver stage. It is not intended here to specify different current setpoints for the pull-in current or the holding current.
  • a circuit arrangement for actuating an electromagnetic system to which an electronic switching element lies in series.
  • a sensor is provided, which detects the instantaneous value of the operating state of the electromagnetic system, the signals of which influence the electronic switching element.
  • the excitation power of the electromagnetic system can be changed in accordance with the instantaneous value of the operating state.
  • the field strength, the path, the acceleration, the speed or the current are recorded in the magnet system.
  • a method and a device for operating an electromagnetic consumer are known, in particular an injection valve in internal combustion engines. It is provided to supply a high and then a reduced current to an electromagnetic consumer at the beginning of an actuation signal.
  • the power supply to the consumer should be clocked and / or regulated after reaching a certain current.
  • the switching point of the power supply during clocking should be current and / or time-dependent.
  • the invention has for its object to provide an electronic circuit arrangement for controlling an electromagnetic component of the type mentioned, in which the switching of the current setpoint dependent on the switching state of the component from the value for the pull-in current to the value for the holding current depending on the rate of increase of Current takes place in the component.
  • this object is achieved according to the invention in that the switching transistor is driven in a clocked manner with a constant duty cycle, in that a subtractor is provided for forming the AC component of the actual current value, on the input side the current actual value and the current setpoint are present in that the subtractor has a peak value meter for forming the Peak value of the AC component of the current actual value is connected downstream and that this peak value can be fed to a setpoint generator, which outputs the various current setpoints on the output side for the pull-in current or the holding current depending on the level of the peak values formed (FIG. 2).
  • this object is achieved according to the invention in that the switching transistor is controlled in a clocked manner with a variable duty cycle, that a time recording device is provided for determining the respective duty cycle of the switching transistor, which is required in each case to achieve a specific actual current value, and that the time recording device is a setpoint generator is connected downstream, which outputs the various current setpoints for the starting current or the holding current as a function of the length of the duty cycle of the switching transistor. (Fig. 1.3).
  • the current setpoint is switched from the value for the pull-in current to the value for the holding current depending the rate of rise of the current in the device.
  • the duty cycle of the switching transistor per cycle is fixed and the current setpoint switchover takes place as a function of the peak value of the AC component of the actual current value that occurs during the duty cycle of the switching transistor.
  • the switching transistor is switched on per cycle until the actual current value is equal to the specified current setpoint and the setpoint changeover takes place as a function of the required switch-on period of the switching transistor.
  • the lower voltage limit for the supply voltage is only the minimum voltage of the electronics supply, e.g. approx. 5 V DC voltage and as the upper voltage limit the maximum voltage load capacity of the electronic components, e.g. approx. 1000 V DC voltage.
  • This can drastically reduce the variety of types caused by the various supply voltages (excitation voltages, control voltages) in electromagnetic components, in particular switching devices. For the entire voltage range between 5 V and 1000 V, for example, the same switching device can be used, whereby a safe tightening of the armature is always guaranteed.
  • the actual current value U (I ist ) is tapped at the common connection point between the electromagnetic component 2 and the measuring resistor R 2 as a voltage value and fed to the first input of a comparator 5.
  • the second input of the comparator 5 is supplied with the current setpoint U (I Soll 2 ).
  • the comparator 5 compares the current setpoint and the current actual value and controls the switching transistor 1 directly on the output side whenever the current actual value U (l ist ) falls below the current setpoint U (l soll 2 ).
  • a voltage divider 10 with resistors R 5 , R 6 is provided, which is connected between supply voltage + U v and ground.
  • the resistance ratio R 5 / R 6 corresponds to the ratio R 1 / R 2 .
  • the second input of the subtractor 14 is supplied with the current setpoint U (I soll 1 ).
  • the differential voltage U D corresponds to the voltage U v minus the ohmic voltage drop across the resistors R 1 , R 2 when switch 1 is switched on.
  • the voltage divider 10 is used to adapt the supply voltage U v to the value U (1 des 1 ).
  • the second input of the controllable adder 15 is supplied with the current setpoint U (1 setpoint 1 ).
  • the control input of the adder 15 is connected to the output of the comparator 5.
  • the output signal of the comparator 5 is fed to the input of a time recording device 16.
  • the time detector 16 determines the variable duty cycle t a of the switching transistor 1 and this value to a setpoint value generator 17 to.
  • the setpoint generator 17 outputs the current setpoint U (1 setpoint 1 ) as a function of the duty cycle of the switching transistor 1.
  • this current setpoint U (I shall 1 ) is fed to the subtractor 14 and the controllable adder 15.
  • a smoothing element for example a PT 1 element
  • n is the number of turns in the electromagnetic component 2 (coil, choke), which represents a constant factor.
  • the current 1 1 + 1 4 through the component 2 is controlled by measuring the inductance L such that the magnetic flux 0 remains constant regardless of the supply voltage U v .
  • the inductance L changes depending on whether the armature of the component 2 designed as a switching device is attracted or not.
  • the inductance also changes in saturation of the magnetic material of yoke and armature of the component 2.
  • the differential voltage U D is significant, which corresponds to the voltage U v minus the ohmic voltage drop across the resistors R 1 , R 2 at the moment when the switch 1 is switched on.
  • the influence of the differential voltage U D can be largely eliminated by regulating the peak value U (î) of the alternating current component U (i) to a magnitude that is proportional to the differential voltage U D.
  • the time constant ⁇ varies as a function of L and the duty cycle t a of the switching transistor 1 will be tracked.
  • the target value generator 17 is thereby a high current reference value U (l to 1) when the operating time t a of the switching transistor 1 is small and it is a small current command value U (l to 1) when the operating time t is large, that is, the setpoint value generator 17 changed continuously or in individual stages of the current reference value U (l to 1) in dependence on the determined time recording device 16, a duty cycle t.
  • the current setpoint U (I soll 1 ) is directly given to the comparator 5 via the controllable adder 15 during the off times of the switching transistor 1, ie during the off times of the transistor 1.
  • the transistor 1 is turned on via the comparator 5 when
  • the switching transistor 1 is in turn supplied with the supply voltage + U v via its emitter and is connected via its collector to the electromagnetic component 2 and to the free-wheeling diode 4.
  • the electromagnetic component 2 is in turn connected directly to ground via the measuring resistor R 2 .
  • the actual current value U (I ist ) is tapped at the common connection point between the electromagnetic component 2 and the measuring resistor R 2 as a voltage value and fed to the first input of a comparator 18.
  • the second input of the comparator 18 is supplied with the current setpoint U (l soll ).
  • the comparator 18 compares the values U (l ist ) and U (l soll ) and controls the monostable multivibrator 6 on the output side whenever U (l ist ) ⁇ U (l should ).
  • the monostable multivibrator 6 controls after triggering by the comparator 18 on the output side the switching transistor 1 at a constant duty cycle t to a.
  • a voltage divider 10 with resistors R 5 , R 6 is again provided between + U and ground.
  • the voltage R 2 / (R 1 + R 2 ) .U v is tapped and fed to the first input of a subtractor 19.
  • the second input of the subtractor 19 is supplied with the current setpoint U (I soll ).
  • the subtractor 19 forms the differential voltage and passes this value to the first input of a setpoint generator 20.
  • the second input of the setpoint generator 20 becomes with the peak value U (i) of the alternating current part of the actual current value is applied.
  • the current setpoint U (I soll ) is fed to the comparator 18, the subtractor 19 and the first input of a subtractor 21.
  • the current input value U (I ist ) is applied to the second input of the subtractor 21.
  • the magnetic flux is 0 no longer regulated in the electromagnetic device 2 to a constant value, but it is recognized 2 (switching state of the switching relays) the current state of the electromagnetic device and the current command value U (l soll) switched between two different values according to the state of the component 2.
  • the rate of rise of the current in the electromagnetic component 2 is evaluated, which is a measure of the inductance L of the component 2 and thus allows a statement to be made about the current state of the electromagnetic component 2.
  • the influences of a changing supply voltage U v and a changing ohmic voltage drop across R 1 and R 2 as a result of a changing current setpoint or a change in resistance due to a change in temperature are advantageously eliminated.
  • the influence of a change in resistance of R 1 due to a change in temperature is taken into account when determining the reference value for the setpoint generator 20.
  • the duty cycle is a t the triggered via the comparator 18 the monostable multivibrator 6 constant.
  • the evaluation of the state (switching state) of the electromagnetic component (switching relay) 2 takes place via the peak value U (î) of the AC component U (i) of the detected current actual value U (l ist ). It is assumed that with a constant duty cycle t one of the switching transistor 1, the peak value U (î) of the AC component U (i) is dependent on the inductance L of the component 2 and the differential voltage U D.
  • the differential voltage U D which in turn corresponds to the voltage U v minus the voltage drops across R 1 ' R 2 , is proportional to the height of the peak value U (i).
  • the differential voltage U D specifies the reference for the peak value U (i).
  • the setpoint generator 20 compares the two quantities U D and U (i). If the electromagnetic component (switching relay) 2 is not energized, the inductance L is low, ie the peak value U (î) is large and exceeds the differential voltage U D. Therefore, a high current setpoint U (I soll 1) is specified as a starting current by the setpoint generator 20. If the electromagnetic component (switching relay) 2 is energized, the inductance L is large, ie the peak value U (î) is low. The reference value U D is no longer reached by the peak value U (i) and the setpoint generator 20 specifies a reduced current setpoint U (I soll 2 ) as the holding current.
  • FIG. 3 shows a third embodiment of an electronic circuit arrangement for controlling an electromagnetic component.
  • This embodiment is essentially of the same construction as the circuit arrangement according to FIG. 1, only in the arrangement according to FIG. 3 the setpoint generator 17 is replaced by a setpoint generator 22.
  • the first input of the setpoint generator 22 is determined by the time detecting means 16 duty cycle t of the switching transistor 1 a loaded.
  • a reference time tef is applied to the second input of the setpoint generator 22.
  • the magnetic flux 0 in the electromagnetic component 2 is also not regulated to a constant value, but the instantaneous state of the electromagnetic component 2 is detected and the current setpoint is between two different levels according to the state of the component 2 Values switched.
  • the peak value of U (i) of the alternating current component U (i) is predefined and carried out the evaluation of the state of the electromagnetic device 2 via the duty cycle t of the switching transistor, a first
  • the differential voltage U D at the time the switching transistor 1 is switched on specifies the reference for the peak value U (i) of the AC component. Since the peak value of U (i) at a constant total resistance R 1 + R 2, a constant inductance L and a constant duty cycle ta is proportional to the difference voltage U D are thus v the influences of a changing supply voltage U and a changing voltage drop across R 1, R 2 switched off by changing the current setpoint. In the event of such a change in U v and I should , the differential voltage U D also changes and thus the peak value U (i) is proportional to this. The influence of a change in resistance of R 1 due to an increase in temperature is taken into account when determining the reference value for the setpoint generator 22.
  • the inductance L is small.
  • the duty cycle t a reaches the predetermined reference time t ref and not the reference value generator 22 is thus a higher power level setpoint U (I soll) as a suit current.
  • the duty cycle ten exceeds the predetermined reference time t ref and the setpoint generator 22 consequently emits a reduced current setpoint U (I soll 1 ) as a holding current.
  • the operating time t a of the switching transistor 1 is therefore in each case determined by the time detecting means 16 and the reference value generator 22 outputs, depending on the currently owned duty th an adapted to the switching state of the electromagnetic device 2 current setpoint before.
  • This current target value U (I target 1 ) predetermined by the target value transmitter 22 is fed to the subtractor 14 and the controllable adder 15, respectively.
  • the subtractor 14 subtracts the current setpoint U (I soll1 ) from the evaluated supply voltage R 2 / (R 1 + R 2 ). U v and in this way forms the differential voltage U D when the switching transistor 1 is switched on.
  • This increased current setpoint of U (I soll 2 ) determines the peak value U (i) of the AC component, ie the peak value U (i) is proportional to the differential voltage U D.
  • the invention is used for controlling switching relays and chokes and for monitoring the switching state of switching relays, and for measuring the instantaneous inductance of electromagnetic components under direct current load, such as e.g. Saturation of chokes.

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Relay Circuits (AREA)
  • Control Of Electrical Variables (AREA)
  • Control Of Voltage And Current In General (AREA)

Claims (7)

1. Disposition de circuit électronique pour commander un composant électromagnétique (2), en particulier un disjoncteur ou relais, le composant électronique (2) se trouvant alors en série avec un transistor de commutation (1 ) et une résistance de mesure (R2), une valeur réelle de courant (U(ist) correspondant au courant à travers le composant (2) pouvant être prélevée sur la résistance de la mesure (R2) et appliquée à un comparateur (18) auquel une valeur nominale de courant (U(Isoll) ) pour le courant d'attraction ainsi qu'une valeur nominale de courant réduite (U(Isoll) ) pour le courant de maintien peuvent être amenées et le transistor de commutation (1) étant alors commandé par l'intermédiaire du comparateur (18) au cas où la valeur nominale de courant (U(Isoll) ) dépasse la valeur réelle de courant (U(list), disposition de circuit caractérisée en ce que le transistor de commutation (1 ) est commandé en étant synchronisé avec une durée constante de commutation, en ce qu'on prévoit un soustracteur (21 ) pour former la partie de courant alternatif (U(i) ) de la valeur réelle de courant (U (Iist) ) et auquel on applique du côté de l'entrée la valeur réelle de courant et la valeur nominale de courant (U(Isoll) ), en ce qu'on commute en aval du soustracteur (21 ) un dispositif de mesure de la , valeur crête (13) pour former la valeur crête (U(î) ) de la partie de courant alternatif (U(i) ) de la valeur réelle de courant (U(Iist) ) et en ce que cette valeur crête (U(î) ) peut être amenée à un générateur de valeur nominale (20) qui délivre du côté de la sortie les différentes valeurs nominales de courant (U(Isoll) ) pour le courant d'attraction ou le courant de maintien en fonction de l'amplitude de la valeur crête formée (U (i) ) (figure 2).
2. Disposition de circuit selon la revendication 1, caractérisée en ce qu'on monte en aval du comparateur (18) un élément bascule monostable (6) provoquant une durée constante de commutation du transistor de commutation (1 ).
3. Disposition de circuit selon la revendication 1 et/ou 2, caractérisée en ce que le générateur de valeur nominale (20) compare la valeur crête (U (î) ) à une tension de différence (UD), un soustracteur (19) étant prévu pour former cette tension de différence (UD), la valeur nominale de courant (U(Isoll) ) et une valeur de tension de référence pouvant être appliquées du côté de l'entrée au soustracteur.
4. Disposition de circuit électronique pour commander un composant électromagnétique (2), en particulier un disjoncteur ou relais, le composant électromagnétique (2) se trouvant en série avec un transistor de commutation (1 ) et une résistance de mesure (R2), une valeur réelle de courant (U(Iist) ) correspondant au courant à travers le composant (2) pouvant alors être prélevée sur la résistance de mesure (R2) et appliquée à un comparateur (5) auquel on peut amener une valeur nominale de courant (U(Isoll 2) ) pour le courant d'attraction ainsi qu'une valeur nominale de courant réduite (U(Isoll 2) ) pour le courant de maintien et le transistor de commutation (1 ) étant commandé par l'intermédiaire du comparateur (5) au cas où la valeur nominale de courant (U(Isoll 2)) dépasse la valeur réelle de courant (U(Iist)). disposition de circuit caractérisée en ce que le transistor de commutation (1) est commandé en synchronisme avec une durée de commutation variable, en ce qu'on prévoit un dispositif de détection du temps (16) pour obtenir la durée de commutation respective (tein) du transistor de commutation (1), ce dispositif de détection du temps étant nécessaire pour obtenir respectivement une valeur réelle de courant déterminée, et en ce qu'un générateur de valeur nominale (17, 22) est monté en aval du dispositif de détection du temps (16) et délivre du côté de la sortie les différentes valeurs nominales de courant (U(Isoll 2) ) pour le courant d'attraction ou le courant de maintien en fonction de l'importance de la durée de commutation (tein) du transistor de commutation (1 ) (figures 1,3).
5. Disposition de circuit selon la revendication 4, caractérisée en ce qu'on détermine un temps de référence (tref) pour le générateur de valeur nominale (22).
6. Disposition de circuit selon la revendication 5, caractérisée en ce qu'on prévoit pour la formation de la valeur nominale de courant (U(Isoll 2) ) un additionneur (15) commandable en fonction de la condition de commutation du transistor (1) et auquel on applique du côté de l'entrée la valeur nominale de courant (U(Isoll 1) ) du générateur de valeur nominale (17, 22) ainsi que la tension de différence (UD) survenant entre la dernière valeur nominale de courant (U(Isoll 1) ) et une valeur de tension de référence.
7. Disposition de circuit selon l'une des revendications 3 et/ou 6, caractérisée en ce que pour former la tension de référence, on prévoit un diviseur de tension, dont le rapport de division (R5/R6) est proportionnel au rapport entre les résistances ohmiques du composant électromagnétique (R1 ) et de la résistance de mesure (R2), et qui peut être commandé avec la tension d'alimentation (Uv) appliquée également au transistor de commutation (1).
EP19820900090 1980-12-17 1981-12-16 Dispositif electronique pour l'excitation d'un element electromagnetique Expired EP0067185B1 (fr)

Applications Claiming Priority (1)

Application Number Priority Date Filing Date Title
DE19803047488 DE3047488A1 (de) 1980-12-17 1980-12-17 Elektronische schaltungsanordnung fuer ein elektromagnetisches schaltgeraet

Publications (2)

Publication Number Publication Date
EP0067185A1 EP0067185A1 (fr) 1982-12-22
EP0067185B1 true EP0067185B1 (fr) 1985-09-04

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Country Link
EP (1) EP0067185B1 (fr)
AT (1) AT384119B (fr)
CH (1) CH659345A5 (fr)
DE (2) DE3047488A1 (fr)
GB (1) GB2105132A (fr)
NL (1) NL8120487A (fr)
SE (1) SE439400B (fr)
WO (1) WO1982002115A1 (fr)

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IT1001996B (it) * 1973-11-28 1976-04-30 Organizzazione Servizi Calcest Calcestruzzo incorporante dei corpi pieni oppure cavi a forma sferica c pseudo sferica in vetro
DE2513043A1 (de) * 1975-03-25 1976-10-07 Baum Elektrophysik Gmbh Schaltung zum gleichstrombetrieb fuer schuetze oder relais
DE2601799A1 (de) * 1976-01-20 1977-07-21 Licentia Gmbh Schaltanordnung zur betaetigung eines elektromagnetsystems
GB2015843B (en) * 1978-02-27 1982-05-19 Bendix Corp Circuits for setting three levels of current in inductive loads such as solenoids
DE2828678A1 (de) * 1978-06-30 1980-04-17 Bosch Gmbh Robert Verfahren und einrichtung zum betrieb eines elektromagnetischen verbrauchers, insbesondere eines einspritzventils in brennkraftmaschinen
DE3129610A1 (de) * 1981-07-28 1983-02-17 Bosch und Pierburg System oHG, 4040 Neuss Steuerschaltung fuer stellglieder

Cited By (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
DE3908192A1 (de) * 1989-03-14 1990-09-20 Licentia Gmbh Elektronische schuetzansteuerung

Also Published As

Publication number Publication date
WO1982002115A1 (fr) 1982-06-24
SE8204712L (sv) 1982-08-16
DE3152626D2 (de) 1983-08-11
SE8204712D0 (sv) 1982-08-16
NL8120487A (nl) 1982-11-01
CH659345A5 (de) 1987-01-15
AT384119B (de) 1987-10-12
GB2105132A (en) 1983-03-16
DE3047488A1 (de) 1982-07-22
SE439400B (sv) 1985-06-10
ATA908981A (de) 1987-02-15
DE3152626C1 (de) 1993-04-29
EP0067185A1 (fr) 1982-12-22

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