WO1982002115A1 - Dispositif electronique pour l'excitation d'un element electromagnetique - Google Patents

Dispositif electronique pour l'excitation d'un element electromagnetique Download PDF

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Publication number
WO1982002115A1
WO1982002115A1 PCT/DE1981/000221 DE8100221W WO8202115A1 WO 1982002115 A1 WO1982002115 A1 WO 1982002115A1 DE 8100221 W DE8100221 W DE 8100221W WO 8202115 A1 WO8202115 A1 WO 8202115A1
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WO
WIPO (PCT)
Prior art keywords
value
current
electronic circuit
circuit arrangement
component
Prior art date
Application number
PCT/DE1981/000221
Other languages
German (de)
English (en)
Inventor
Boveri & Cie Brown
Original Assignee
Petschenka Edwin
Beulen Winfried
Rothmeier Erich
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Petschenka Edwin, Beulen Winfried, Rothmeier Erich filed Critical Petschenka Edwin
Priority to NL8120487A priority Critical patent/NL8120487A/nl
Publication of WO1982002115A1 publication Critical patent/WO1982002115A1/fr

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Classifications

    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01H—ELECTRIC SWITCHES; RELAYS; SELECTORS; EMERGENCY PROTECTIVE DEVICES
    • H01H47/00—Circuit arrangements not adapted to a particular application of the relay and designed to obtain desired operating characteristics or to provide energising current
    • H01H47/22—Circuit arrangements not adapted to a particular application of the relay and designed to obtain desired operating characteristics or to provide energising current for supplying energising current for relay coil
    • H01H47/32—Energising current supplied by semiconductor device
    • H01H47/325—Energising current supplied by semiconductor device by switching regulator
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01H—ELECTRIC SWITCHES; RELAYS; SELECTORS; EMERGENCY PROTECTIVE DEVICES
    • H01H47/00—Circuit arrangements not adapted to a particular application of the relay and designed to obtain desired operating characteristics or to provide energising current
    • H01H47/02—Circuit arrangements not adapted to a particular application of the relay and designed to obtain desired operating characteristics or to provide energising current for modifying the operation of the relay
    • H01H47/04—Circuit arrangements not adapted to a particular application of the relay and designed to obtain desired operating characteristics or to provide energising current for modifying the operation of the relay for holding armature in attracted position, e.g. when initial energising circuit is interrupted; for maintaining armature in attracted position, e.g. with reduced energising current
    • H01H2047/046—Circuit arrangements not adapted to a particular application of the relay and designed to obtain desired operating characteristics or to provide energising current for modifying the operation of the relay for holding armature in attracted position, e.g. when initial energising circuit is interrupted; for maintaining armature in attracted position, e.g. with reduced energising current with measuring of the magnetic field, e.g. of the magnetic flux, for the control of coil current

Definitions

  • a comparator (5) reeeives aprede- j termined current order value U (Isoll2) and an actual measured current value UO-st). hen the actua] value goes down below the order value, the comparator (5) actuates, through a mono- stable flip flop element (6), a switching transistor (1) supplied by a supply voltage Uv, arranged in the main current cireuit of the electromagnetic element (2).
  • Electronic circuit arrangement for an electromagnetic component (2) in particular a choke or a coil of an electromagnetic switching device having a magnetic circuit with a coil, yoke and armature.
  • a predetermined current setpoint U (I soI ) and a measured current actual value U (I ist ) are fed to a comparator (5). If the current actual value falls below the current setpoint, the comparator (5) controls one in the main circuit of the electromagnetic component via a monostable trigger element (6) (2) lying through, with supply voltage U v switching transistor (1) through. After a lapse of the constant-time t disables the transistor (1). With a variable switch-on time t e ⁇ n of the switching transistor (1), a differentiated current setpoint is given as a function of the determined switch-on time.
  • a high pull-in current setpoint and after the switchgear has been tightened, a reduced holding current setpoint is specified.
  • the inductance of the coil is used to evaluate the different switching state of the switching device.
  • Electronic circuit arrangement for controlling an electromagnetic component.
  • the invention relates to an electronic circuit arrangement for controlling an electromagnetic component, in particular a choke or a coil of an electromagnetic switching device having a magnetic circuit with a coil, yoke and armature.
  • Electromagnetic components such as switching relays and contactors, are generally known in numerous design variants.
  • Such switching devices consist of a yoke with one or more coils and an armature which is magnetically attracted by the yoke after application of a control voltage to the coil and thereby actuates switching contacts.
  • a disadvantage of the known electromagnetic switching device can be seen in the large variety of types, due to the different excitation voltages with the same switching capacity, the large construction volume and the large necessary control output.
  • the known electromagnetic switching devices can generally be used either only for direct current or only for alternating current.
  • a coil can only be used for a narrow excitation voltage range to ensure that the armature is securely tightened.
  • the invention has for its object to provide an electronic circuit arrangement for controlling an electromagnetic component, which enables universal use of the electromagnetic component, i.e. allows operation for direct and alternating current, which is largely independent of the level of the voltage and also reduces the size and power consumption of the component.
  • this object is achieved in that a comparator has a predetermined current setpoint and a measured current actual value corresponding to the current in the electromagnetic component on the input side, and the comparator on the output side, depending on the control deviation between the current setpoint and current actual value, is in the main circuit of the electromagnetic component, with the supply voltage for controlling the electromagnetic component switch, in particular a switching transistor.
  • this object is achieved according to the invention in that the control deviation between an induction setpoint and an actual induction value of the magnetic circuit of the electromagnetic component is supplied and that the two-point controller controls a switching amplifier connected to the electromagnetic component in such a way that the induction value moves within predefined limit values, the switching amplifier being acted upon on the input side by the supply voltage for actuating the electromagnetic component.
  • the control suppresses the influence of the supply voltage on the coil current, so that a large degree of independence from the supply voltage is achieved.
  • the lower voltage limit for the supply voltage is only the minimum voltage of the electronics supply, e.g. approx. 5V DC voltage and as the upper voltage limit the maximum voltage capacity of the electronic components, e.g. approx. 1000V DC voltage.
  • This can drastically reduce the variety of types caused by the various supply voltages (excitation voltages, control voltages) in electromagnetic components, in particular switching devices. For the entire voltage range between 5V and 1000V, for example, the same switching device can be used, whereby a safe tightening of the armature is always guaranteed.
  • FIGS. 3 and 4 for electronic circuit arrangements
  • FIGS. 5A, B, C, D show the time profiles of the currents and voltages of interest for the arrangement according to FIG. 1, and FIG. 6 shows an electronic circuit arrangement for activating a 7A, B, C the temporal profiles of the currents and voltages of interest for the arrangement according to FIG. 6, FIG. 8 a detailed embodiment for
  • FIG. 9 shows an electronic circuit arrangement for controlling an electromagnetic component with a two-point controller and induction value acquisition
  • FIG. 10A, B, C the temporal profiles of the currents and voltages of interest for the arrangement according to FIG. 9,
  • FIG. 11 a Hall probe used for induction value detection
  • Fig. 12 shows a detailed embodiment for
  • FIG. 13 shows a basic illustration of the arrangement according to FIG. 12,
  • a switching transistor 1 (pnp type) is connected via its emitter to the input terminal E1 of the circuit arrangement.
  • the supply voltage + U v is applied to the input terminal E1 as the control voltage.
  • the supply voltage + U v can be switched via an external switch S.
  • the collector of the switching transistor 1 is connected to an electromagnetic component 2 (eg coil of a switching relay, choke, etc.).
  • the electromagnetic component 2 has an ohmic resistance R 1 and an inductance L.
  • the electromagnetic component 2 is connected via its further terminal to a controllable resistor 3 (for example a field effect transistor).
  • the ohmic resistance of the controllable resistor 3 is denoted by R w .
  • the further connection of the controllable resistor 3 is connected via a measuring resistor R 2 (shunt) to the input terminal E2 and thus to ground.
  • the collector of the Switching transistor 1 is also connected to the cathode of a free-wheeling diode 4, the anode of which is connected to ground.
  • the two connection points of the controllable resistor 3 are bridged by means of a voltage divider consisting of the high-resistance resistors R 3 and R 4 .
  • the resistor R 3 is connected to the electromagnetic component 2 and the resistor R 4 to the measuring resistor R 2 .
  • the resistance ratio R 3 / R 4 corresponds to the ratio R 1 / R 2 .
  • the voltage drop across R 2 + R 4 is therefore proportional to the voltage drop across the entire ohmic resistance R 1 + R 2 + R w for each resistance value R w of the controllable resistor 3.
  • the actual current value U (I ist ) is tapped as a voltage value and fed to the first input of a comparator 5.
  • a current setpoint U (I soll 2 ) is applied to the second input of the comparator 5.
  • the comparator 5 is connected on the output side to a monostable flip-flop 6 and controls the flip-flop 6 whenever the current actual value U (I ist ) is less than or equal to the current setpoint U (I soll 2 ).
  • the duty cycle of a t of the monostable multivibrator 6 is constant.
  • the actual current value U (I ist ) is also the first. Input of a subtractor 7 supplied. The second
  • the current setpoint U (I soll 2 ) is applied to the input of the subtractor 7.
  • the output voltage U (i) of the subtractor 7 becomes a smoothing element 8 (e.g. PT1 link) fed.
  • the smoothing element 8 forms the average of the AC component U (i) and feeds this value to the first input of a subtractor 9.
  • a current setpoint U (Isoll 1) is applied to the second input of the subtractor 9.
  • the subtractor 9 forms the difference value
  • a voltage divider 10 consisting of two resistors R 5 , R 6 is supplied with the supply voltage + U v by its connection formed by resistor R 5 and is connected to ground by its connection formed by resistor R 6 .
  • the resistance ratio R5 / R6 corresponds to the ratio R 1 / R 2 .
  • the voltage value R 2 / (R 1 ) + R 2 ) ⁇ U v can thus be tapped and this voltage value is fed to the first input of a subtractor 11.
  • the second input of the subtractor 11 is in turn connected to the current setpoint U (I soll 2 ).
  • the output value u (i) of the subtractor 7 is fed to a peak value meter 13.
  • the peak value meter 13 forms the peak value of the AC component U (i) and feeds this peak value to the PI controller 12 as the actual value.
  • the PI controller 12 controls the controllable resistor 3 via its control input and in this way changes the ohmic resistance value R w of the resistor 3 as a function of the apex worth it and the differential voltage U D.
  • FIGS. 5A, B, C, D show the time profile of the actual current value U (I is ).
  • the current setpoint U (I soll 2 ) is entered as a constant value.
  • the Eins ⁇ haltdauer the monostable multivibrator 6 and the switching transistor 1 is denoted by t a.
  • the peak value of the AC component is .
  • the mean value of the AC component is designated U (T).
  • 5C shows the time profile of the current I 1 flowing through the switching transistor 1.
  • 5D is the time profile of the current flowing through the freewheeling diode 4 during the blocking times of the switching transistor 1
  • I 1 + I 4 are entered in Figures 1, 2, 3, 4, respectively.
  • the switching transistor 1 is turned on alternately by means of the monostable multivibrator 6 and locked, wherein the duty cycle t on of the switching transistor is always constant.
  • the blocking period of transistor 1 is not constant.
  • the switching transistor 1 is turned on, there is a current flow I 1 from the input terminal via the emitter-collector path of the switching transistor 1, the electromagnetic component 2, the controllable resistor 3 and the measuring resistor R 2 .
  • a current flow I 4 results via the freewheeling diode 4, the electromagnetic component 2, the controllable resistor 3 and the measuring resistor R 2 .
  • a total current I 1 + I 4 flows via the electromagnetic component 2.
  • the actual current value U (I ist ) corresponds to this total current I 1 + I 4 .
  • n is the number of turns in the electromagnetic component 2 (coil, choke), which represents a constant factor.
  • the differential voltage U D is significant, which corresponds to the voltage Uv minus the ohmic voltage drop across the resistors R 1 , R w , R 2 at the moment when the switch 1 is switched on.
  • the time constant t remains constant.
  • the inductance L changes depending on whether the armature of the component 2 designed as a switching device is attracted or not. The inductance also changes when the
  • the electronic circuit arrangement regulates the time constant t via the PI controller 12 and the controllable resistor 3 (keeps t constant) such that the current I 1 through the electromagnetic component 2 for a given switch-on time t one of the switching transistor 1 is determined by the differential voltage Up Maximum value reached.
  • the predetermined setpoint U (I soll 1 ) In order to regulate the flow ⁇ to a mean value, the predetermined setpoint U (I soll 1 ) must be around the mean value of the AC component U (i) can be reduced.
  • the AC component U (i) is formed by the subtractor 7. This draws from the current actual value U (I is) the Strorasollwert U (I should 2).
  • the average value of the AC component U (i) is given by the smoothing element 8 formed and given to the subtractor 9, the current setpoint U (I soll 1 ) is also present on the input side.
  • the current setpoint U (I soll 2 ) on the output side of the subtractor 9 is around the mean value of U (i) is less than the current setpoint U (I target 1 ).
  • the current setpoint value U (I setpoint 1 ) is not corrected by the average value , ie the current setpoint U (I soll 1 ) is fed directly to the comparator 5.
  • the voltage which is present across the resistors R 1 + R 2 + R 3 + R 4 at the moment when the transistor 1 is switched on is subtracted from the supply voltage Uv. Since the voltage across the resistors R 1 + R 2 + R 3 + R 4 at the time the transistor 1 is switched on is proportional to U (I soll 2 ), this value U (I soll 2 ) is obtained with the aid of the subtractor 11 evaluated (adapted) supply voltage R 2 / (R 1 + R 2 ) ⁇ U v subtracted.
  • the voltage divider 10 is used to adapt the supply voltage U v to the value U (I soll 2 ).
  • the voltage drop across the measuring resistor R 2 offers the possibility of making a statement about the current state of the electromagnetic component 2 and of evaluating it electronically (inductance evaluation).
  • the switching state of the relay can be determined in this way, for example, ie whether the armature is attracted or not.
  • the switching transistor 1 is in turn connected to the supply voltage U v via its emitter and is connected via its collector to the electromagnetic component 2 and to the free-wheeling diode 4.
  • the electromagnetic component 2 is connected directly to the measuring resistor R 2 .
  • the actual current value U (I ist ) is tapped at the common connection point between the electromagnetic component 2 and the measuring resistor R 2 as a voltage value and fed to the first input of the comparator 5.
  • the second input of the comparator 5 is in turn supplied with the current setpoint U (I soll 2 ).
  • the comparator 5 compares the current setpoint and the current actual value and directly controls the switching transistor 1 on the output side whenever the current actual value U (I ist ) falls below the current setpoint U (I soll 2).
  • a voltage divider 10 with resistors R 5 , R 6 is again provided, which is connected between supply voltage + U v and ground.
  • the voltage value R 2 / (R 1 + R 2 ) ⁇ U v tapped and fed to the first input of a subtractor 14.
  • the second input of the subtractor 14 is supplied with the current setpoint U (I soll 1).
  • the differential voltage U D corresponds to the voltage U v minus the ohmic voltage drop across the resistors R 1 , R 2 when switch 1 is switched on.
  • the current input value U (I soll 1 ) is applied to the second input of the controllable adder 15.
  • the control input of the adder 15 is connected to the output of the comparator 5.
  • the controllable adder 15 always outputs a current setpoint U (I soll 2 ) - U (I soll 1 ) on the output side when the switching transistor 1 blocks, ie when U (l is ) is greater than U (I soll 2 ) and gives always a current setpoint
  • U (I soll2 ) U (I soll 1 ) + U D on the output side when the switching transistor 1 conducts, ie when U (I ist ) is smaller than U (I soll 2 ).
  • the output signal of the comparator 5 is fed to the input of a time recording device 16.
  • the time detector 16 determines the variable duty cycle t a of the switching transistor 1 and this value to a setpoint value generator 17 to.
  • the setpoint generator 17 outputs the current setpoint U (I soll 1 ) on the output side as a function of the switch-on duration tein of the switching transistor 1. As already mentioned, this current setpoint U (I soll 1 ) is fed to the subtractor 14 and the controllable adder 15.
  • a smoothing element eg PT 1 link
  • a smoothing element can be switched for averaging.
  • the on-time t e in of the switching transistor 1 is kept constant and the time constant t is regulated by changing the total resistance Rges by the peak value to keep the Senstr ⁇ raanteils proportional to Vn, changes in the electronic Wegungsanord ⁇ ung of FIG. 2, the time constant t as a function of L and the duty cycle t a of the switching transistor 1 will be tracked.
  • the target value generator 17 is thereby a high Strorasollwert U (I soll 1) from when the duty cycle t on of the switching transistor 1 is small and it is a small current setpoint Udsoll 1) when the duty ratio f a Sross is, the target value generator 17 that is changed continuously or in individual steps, the current setpoint U (I soll 1) as a function of the on-time determined via the time recording device 18.
  • the transistor 1 is turned on via the comparator 5 when
  • U (I should 2) U (I should 1) + U D. If the current actual value U (I ist ) ⁇ en ⁇ reaches the higher current setpoint U (I soll 1) + U D , transistor 1 is blocked and at the same time the current setpoint becomes U (I should 2 ) switched back to the lower value U (I should 1). This results in a control characteristic with hysteresis.
  • the switching transistor 1 is in turn supplied with the supply voltage + U v via its emitter and is connected via its collector to the electromagnetic component 2 and to the free-wheeling diode 4.
  • the electromagnetic component 2 is in turn connected directly to ground via the measuring resistor R2.
  • the actual current value U (I ist ) is tapped at the common connection point between the electromagnetic component 2 and the measuring resistor R 2 as a voltage value and fed to the first input of a comparator 18.
  • the current input value U (I soll ) is applied to the second input of the comparator 18.
  • the comparator 18 compares the values U (I ist ) and U (I soll ) and controls the monostable multivibrator 6 on the output side whenever U (I ist ) ⁇ U (I soll ).
  • the monostable multivibrator 6 controls after triggering by the comparator 18 on the output side the switching transistor 1 at a constant duty cycle t to a.
  • a voltage divider 10 with resistors R 5 , R 6 is provided between + U v and ground.
  • the voltage R 2 / (R 1 + R 2 ) * U v is tapped and fed to the first input of a subtractor 19.
  • the current input value U (I soll ) is applied to the second input of the subtractor 19.
  • the peak input U (£) of the AC component of the current actual value is applied to the second input of the setpoint generator 20.
  • the current setpoint U (I soll ) is fed to the comparator 18, the subtractor 19 and the first input of a subtractor 21.
  • the current input value U (I ist ) is applied to the second input of the subtractor 21.
  • the magnetic flux ⁇ in the electromagnetic component 2 is no longer regulated to a constant value, but the current state of the electromagnetic component 2 (switching state of the switching relay) is detected and the current setpoint U (I soll ) is switched between two different high values according to the state of the component 2.
  • the rate of rise of the current in the electromagnetic component 2 is evaluated, which is a measure of the inductance L of the component 2 and thus allows a statement to be made about the current state of the electromagnetic component 2.
  • the influences of a changing supply voltage U v and a changing ohmic voltage drop across R 1 and R 2 as a result of a changing current setpoint or a change in resistance due to a change in temperature they are advantageously switched off.
  • the influence of a change in resistance of R 1 due to a change in temperature is taken into account when determining the reference value for the setpoint generator 20.
  • the duty cycle t one of the raonostable flip-flop 6 triggered by the comparator 18 is constant.
  • the state (switching state) of the electromagnetic component (switching relay) 2 is assessed via the peak value of the AC component U (i) of the detected current actual value U (I ist ). It is assumed that with a constant duty cycle t one of the switching transistor 1 the peak value of the AC component U (i) is dependent on the inductance L of the component 2 and the differential voltage U D.
  • the differential voltage U D which in turn corresponds to the voltage U v minus the voltage drops across R 1 , R 2 , is proportional to the height of the peak value H a.
  • the differential voltage Up provides the reference for the peak value for evaluating the state of the component 2 in front.
  • the setpoint generator 20 compares the two quantities Up and U (£). If the electromagnetic component (switching relay) 2 is not energized, the inductance L is low, ie the peak value large and exceeds the differential voltage Up. Therefore, a high current setpoint U (I soll 1) is specified as a starting current by the setpoint generator 20. If the electromagnetic component (switching relay) 2 is energized, the inductance L is large, ie the peak value low.
  • the reference value U D is determined by the peak value U no longer reached and the setpoint generator 20 specifies a reduced current setpoint U (I soll 2) as the holding current.
  • 4 shows a fourth embodiment of an electronic circuit arrangement for controlling an electromagnetic component. This embodiment is essentially of the same construction as the circuit arrangement according to FIG. 2, only in the arrangement according to FIG. 4 the setpoint generator 17 is replaced by a setpoint generator 22.
  • the first input of the setpoint generator 22 is acted upon by the on-time tein of the switching transistor 1 determined by the time recording device 16.
  • a reference time tref is applied to the second input of the setpoint generator 22.
  • the magnetic flux ⁇ in the electromagnetic component 2 is not regulated to a constant value, but the instantaneous state of the electromagnetic component 2 is detected and the current setpoint is in accordance with the state of the component 2 between two different levels Values switched. This is the peak value of the alternating current component U (i) and the evaluation of the state of the electromagnetic component 2 takes place via the on-time tein of the switching transistor 1.
  • the differential voltage U D at the time the switching transistor 1 is switched on provides the reference for the peak value of the AC component. Because the peak value with constant total resistance R 1 + R 2i constant inductance L and constant duty cycle tein is proportional to the differential voltage U D , the influences of a changing supply voltage U v and a changing voltage drop across R 1 , R 2 are switched off by changing the current setpoint. With such a change in U v and Ig0ll, the differential voltage Up also changes and thus the peak value proportional to this . The influence of a change in resistance of R 1 due to an increase in temperature is taken into account when determining the reference value for the setpoint generator 22.
  • the electromagnetic component (switching relay) 2 If the electromagnetic component (switching relay) 2 is not yet tightened, the inductance L is small. Thus, the current ira component 2 rises sharply and the. On time tein of the switching transistor 1 is short. The switch-on time tein does not reach the predetermined reference time tref and the setpoint generator 22 consequently emits an increased current setpoint U (I soll 1 ') as the starting current. When the electromagnetic component (switching relay) 2 is attracted, the current in component 2 rises only slightly due to the large inductance L and the on-time tein of switching transistor 1 is long.
  • the duty cycle exceeds a t tref the predetermined reference time and the reference value generator 22 is thus a reduced nominal current value U (Isoll 1 '') as the holding current.
  • the operating time t a of the switching transistor 1 is therefore in each case determined by the time detecting means 16 and the reference value generator 22 outputs, depending on the currently present operating time t on a switching state of the electromagnetic device 2 matched current setpoint before.
  • U (I shall 1) is the subtractor 14 and the controllable adder 15 fed.
  • the subtractor 14 subtracts the current setpoint U (I soll 1) from the evaluated supply voltage R 2 / (R 1 + R 2 ) ⁇ U v and in this way forms the differential voltage U D at the moment of maintenance of the switching transistor 1.
  • U (I soll 2) U (I soll 1) supplied to D + U.
  • This increased current setpoint of U (I soll 2 ) determines the peak value C of the AC component, ie the peak value is proportional to the differential voltage U D.
  • the high pull-in current required for safely pulling in a switching relay is reduced to a lower holding current after the relay has been energized.
  • This enables the operation of an AC switching relay with direct current, as well as a low-loss operation of the switching relay.
  • the pull-in current is only reduced to the holding current if the switching relay has picked up safely.
  • Another option for detecting the switching state of the electromagnetic component is to use a mechanical auxiliary contact. The switchover from the high starting current to the lower holding current then takes place depending on the auxiliary contact position.
  • FIG. 6 shows a fifth embodiment of an electronic circuit arrangement for controlling an electromagnetic component.
  • the supply voltage U v is applied to a timing element 23 on the input side.
  • the timing element 23 emits a current setpoint U (I soll ), which is compared with an actual current value U (l ist ) and is then fed to a two-point controller 24.
  • the output signal of the two-point controller 24 is fed to a switching amplifier 25, the further input of which is supplied with the supply voltage Uv.
  • the switching amplifier 25 outputs the voltage U for the electromagnetic component 2 on the output side.
  • the actual current value U (I ist ) of the electromagnetic component 2 is determined and fed to the comparison point arranged in front of the two-point controller 24.
  • FIG. 7A, B, C are the time-dependent curves of the supply voltage U v , the current setpoint U (I soll ). and the actual current value U (I is ) for the circuit arrangement according to FIG. 6.
  • the timer 23 specifies an increased current setpoint U (I soll 1) on the output side in the period 0 ⁇ t ⁇ to.
  • the current setpoint U (I soll ) is switched to a lower value U (I soll 2).
  • the difference between the current setpoint and current actual value is fed to the two-point controller 24, which is subject to hysteresis.
  • the two-position controller 24 On / off commands to the switching amplifier 25.
  • the constant supply voltage U v is converted into a pulse duration modulated voltage U and supplied to the electromagnetic component 2.
  • this self-oscillating circuit is used, which uses the natural inductance of the excitation circuit.
  • the coil current in the electromagnetic component is kept between two predefinable limit values.
  • FIG. 8 shows a detailed electronic circuit arrangement for the exemplary embodiment according to FIG. 6. Between the positive and the negative
  • the input voltage is at the supply voltage U v .
  • a capacitor 26 is connected between the two input terminals.
  • a resistor 27, a diode 28 and a positive output terminal are also connected to the positive terminal.
  • Resistor 27 is connected on the one hand via a Zener diode 29 to the negative input terminal, on the other hand to the timing element 23 and the supply input of an amplifier 30.
  • the timer 23, the further supply input of the amplifier 30 and the emitter of a transistor 31 (NPN type) are also connected to the negative input terminal.
  • the collector of the transistor 31 is connected on the one hand to the diode 28 and on the other hand to a negative output terminal via a current measuring device 32.
  • a connecting line leads from the current measuring device 32 to the negative input of the amplifier 30, ie the actual current value U (I ist ) is fed to the negative input of the amplifier 30.
  • the positive input of the amplifier 30 is connected to the timing element 23 and receives the current setpoint U (I soll ).
  • the output of amplifier 30 is connected to the base of transistor 31.
  • the voltage U is present between the output terminals of the electronic circuit arrangement.
  • the function of the amplifier 30 corresponds to that of the two-point controller 24 with a reference junction and the transistor 31 to the switching amplifier 25.
  • the electromagnetic component 2 consisting of a coil 33 with a yoke and armature and switch contacts 34, is connected to the output terminals of the electronic circuit arrangement connected.
  • FIG. 9 shows an electronic circuit arrangement with two-point control and induction value feedback.
  • Addition point 35 is a predetermined induction setpoint B sol 1 and an actual induction value K ⁇ B multiplied by a factor K is compared and the difference is fed to a two-point controller 24.
  • the two-point controller 24 issues on / off commands to the switching amplifier 25.
  • the switching amplifier 25 receives the input side, further, the Versorgu ⁇ gsschreib U v, and outputs the output side, the coil voltage U off to the electromagnetic component. 2, the occurring in the magnetic circuit of the electromagnetic device 2 Induktio ⁇ sistwert B is detected and fed to a reviewer stage 36th
  • the induction actual value K ⁇ B which can be taken from this evaluation stage 36 and is multiplied by the factor K is fed to the addition point 35.
  • the factor K takes into account that only a partial value of the induction value is measured.
  • the tent-dependent curves of the supply voltage U v , the actual coil current value I actual and the coil voltage U are shown in FIG.
  • the supply voltage U v is present at the switching amplifier 25 in the period 0 ⁇ t ⁇ t 4 .
  • the coil current actual value I ist rises to a peak value in the period 0 ⁇ t ⁇ t 1 and has dropped to a value I 7 at time t 1 , which corresponds to a predeterminable induction value, and the two-point controller 24 issues an off command to the switching amplifier 25 , ie the output voltage of the switching amplifier 25, which is equal to the coil voltage, changes from the value U v during the period 0 ⁇ t ⁇ t 1 to the value 0.
  • the coil current reaches the value I 8 .
  • the induction value B is on one has dropped to a minimum value which results in an ON command from the two-point controller 24 to the switching amplifier 25. Consequently, the supply voltage U v is again supplied to the electromagnetic component 2 as a coil voltage.
  • the coil current Iact again reaches the value I 7 , while at the same time the induction actual value B is at a maximum value, which results in an off command from the two-point controller 24.
  • a supply voltage U v1 is applied to a Hall probe 37 with a transistor 38 connected downstream.
  • the emitter of transistor 38 is grounded, while its collector is supplied with a supply voltage U v2 via a resistor 39.
  • a voltage of different magnitude is present at the base of the transistor 38 depending on the magnitude of the magnetic induction Bist of the field, ie the collector-emitter path of the transistor 38 is switched through depending on the actual induction value Bi st or locked.
  • the characteristic U A (B ist ) has a hysteresis ⁇ B and an average induction value B 0 .
  • FIG. 12 shows a detailed electronic circuit arrangement for the exemplary embodiment according to FIG. 9.
  • the supply voltage U v is present between the positive and the negative input terminal.
  • the capacitor 26, the resistor 27, the further resistor 39 and the diode 38 are connected to the positive input terminal.
  • the positive input terminal also forms the positive output terminal of the circuit arrangement.
  • the capacitor 26, the zener diode 29 and the Hall probe 37 with transistor 38 are connected to the negative input terminal.
  • the negative input terminal is connected to the emitter of transistor 38.
  • the Hall probe 37 with transistor 38 is also connected on the input side to the common connection point of Zener diode 29 and resistor 27.
  • This signal input supplies the supply voltage U v1 .
  • the dashed connecting line in Flg. 12 shows that the Hall probe 37 with transistor 38 is arranged in the yoke 41 of the electromagnetic component (switching device) and is there exposed to the actual magnetic value K ⁇ B ist .
  • the output of Hall probe 37 with transistor 38 has the output voltage U A and is connected to the resistor 39 and the base of the transistor 31.
  • the voltage across resistor 39 is designated U v2 .
  • the collector of transistor 31 is connected to the negative output terminal of the circuit arrangement.
  • the coil 33 of the electromagnetic component 2 is connected between the two output terminals.
  • the switch contacts of the electromagnetic component are designated by reference number 34 and the armature provided for their actuation by reference number 43.
  • the Transistor 31 essentially corresponds to the switching amplifier 25 according to FIG. 9, while the two-point regulator 24 with addition point 35 is realized by the arrangement of Hall probe 37 / transistor 38 - resistors 27 and 39.
  • FIG. 13 shows the circuit arrangement according to FIG. 12 in a simplified basic illustration.
  • the supply voltage U v is applied to a switching amplifier 44 via the input clerical arenas.
  • the output of the switching amplifier 44 forms the positive output terminal, while the negative output terminal is connected to the negative input terminal.
  • the coil 33 of the electromagnetic component 2 with yoke 41 is connected between the output cleramen. Furthermore, the switch contacts 34 with armature 43 are shown.
  • the coil voltage U is present between the output terminals.
  • the actual coil current value I ist flows into the coil 33 of the electromagnetic component 2.
  • the current flowing in the yoke 41 and armature 43 is Indutechnischsistwert B is.
  • the partial value of the actual magnetic induction value flowing through the Hall probe 37 arranged in the yoke 41 is K ⁇ B is and is fed to the switching amplifier 44 on the input side.
  • FIGS. 9 to 13 shows the mechanical design of an electronic circuit arrangement according to FIGS. 9 to 13.
  • the coil 33 of the electromagnetic component 2 with yoke 41 and armature 43 are enclosed by the switch housing 45.
  • the electronic circuit arrangement according to FIGS. 9 to 13 also built into the housing is built on a printed circuit board 46.
  • the Hall probe 37 connected to the circuit board 46 is arranged in the yoke 41.
  • Switchgear - AC-operated switchgear reduced the necessary type variety by half.
  • the invention is used for controlling switching relays and chokes and for monitoring the switching state of switching relays, and for measuring the instantaneous inductance of electromagnetic components under direct current load, such as e.g. Saturation of chokes.

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Relay Circuits (AREA)
  • Control Of Electrical Variables (AREA)
  • Control Of Voltage And Current In General (AREA)

Abstract

Dispositif electronique pour l'excitation d'un element electromagnetique, notamment une bobine d'arret ou une bobine d'un appareil de commutation electromagnetique presentant un circuit magnetique avec bobine, culasse et armature. Un comparateur (5) recoit une valeur de consigne de courant predetermine U(Isoll2) et une valeur reelle de courant mesuree U(Iist). Lorsque la valeur reelle descend en dessous de la valeur de consigne, le comparateur (5) active, a travers un element a bascule monostable (6), un transistor de commutation (1) alimente par une tension d'alimentation Uv, situe dans le circuit de courant principal de l'element electromagnetique (2). Apres ecoulement de la duree de conduction tein constante, il bloque le transistor (1). Avec une duree de conduction tein variable du transistor de commutation (1), il en resulte une variation de la valeur de consigne de courant, fonction de la duree de conduction determinee. Afin d'obtenir un mode de fonctionnement sur d'un appareil de commutation electromagnetique comportant une bobine, on etablit une valeur de consigne de courant d'actionnement eleve et, apres l'obtention de l'actionnement de l'appareil de commutation, une valeur de consigne de courant de maintien reduite. Pour l'exploitation des differents etats de commutation de l'appareil de commutation, on tient compte de l'inductivite de la bobine.
PCT/DE1981/000221 1980-12-17 1981-12-16 Dispositif electronique pour l'excitation d'un element electromagnetique WO1982002115A1 (fr)

Priority Applications (1)

Application Number Priority Date Filing Date Title
NL8120487A NL8120487A (nl) 1980-12-17 1981-12-16 Elektronische schakeling voor het besturen van een elektromagnetische onderdeel.

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
DE19803047488 DE3047488A1 (de) 1980-12-17 1980-12-17 Elektronische schaltungsanordnung fuer ein elektromagnetisches schaltgeraet
DE3047488801217 1980-12-17

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WO1982002115A1 true WO1982002115A1 (fr) 1982-06-24

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PCT/DE1981/000221 WO1982002115A1 (fr) 1980-12-17 1981-12-16 Dispositif electronique pour l'excitation d'un element electromagnetique

Country Status (8)

Country Link
EP (1) EP0067185B1 (fr)
AT (1) AT384119B (fr)
CH (1) CH659345A5 (fr)
DE (2) DE3047488A1 (fr)
GB (1) GB2105132A (fr)
NL (1) NL8120487A (fr)
SE (1) SE439400B (fr)
WO (1) WO1982002115A1 (fr)

Cited By (13)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
EP0109540A2 (fr) * 1982-10-27 1984-05-30 Siemens Aktiengesellschaft Agencement de commutation pour l'actionnement d'appareillages de commutation électromagnétiques
FR2559211A1 (fr) * 1984-01-31 1985-08-09 Lucas Ind Plc Circuit d'excitation destine a la commande du courant circulant dans le solenoide d'un dispositif electromagnetique en reponse a un signal de commande
FR2564237A1 (fr) * 1984-05-09 1985-11-15 Diehl Gmbh & Co Procede pour commander un relais monostable et dispositif pour mettre en oeuvre le procede
DE3434343A1 (de) * 1984-09-19 1986-03-27 Licentia Patent-Verwaltungs-Gmbh, 6000 Frankfurt Anordnung zur stromversorgung von relais
GB2168558A (en) * 1984-12-18 1986-06-18 Diesel Kiki Co Current controlling device for electromagnetic windings
GB2213669A (en) * 1987-12-09 1989-08-16 Festo Kg Solenoid actuator circuit
GB2197998B (en) * 1984-11-12 1990-07-18 Inst Elektroswarki Patona Electromagnetic power drive for producing a pulsating axial force in a friction welding machine
DE9409760U1 (de) * 1993-06-25 1994-09-01 Siemens Ag Schaltungsanordnung zur Ansteuerung eines Schützes
DE9409759U1 (de) * 1993-06-25 1994-10-27 Siemens Ag Schaltungsanordnung zur Realisierung eines konstanten Schütz-Haltestroms
WO1997021237A2 (fr) * 1995-12-05 1997-06-12 Siemens Aktiengesellschaft Dispositif de commande pour appareils de commutation
WO1998031035A1 (fr) * 1997-01-09 1998-07-16 Siemens Aktiengesellschaft Contacteurs susceptibles de connectivite et a commande electronique
FR2808619A1 (fr) * 2000-05-08 2001-11-09 Siemens Ag Electronique d'entrainement et procede pour brancher de maniere commandee par moyen electronique un appareil de coupure electromagnetique
EP3806127A1 (fr) * 2019-10-08 2021-04-14 Fico Triad, S.A. Système et procédé de commande d'un contacteur électromécanique d'un circuit électrique

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DE3615908A1 (de) * 1986-05-12 1987-11-19 Siemens Ag Elektromagnetisches schaltgeraet
DE3908192A1 (de) * 1989-03-14 1990-09-20 Licentia Gmbh Elektronische schuetzansteuerung
DE19503536A1 (de) * 1995-02-03 1996-08-08 Bosch Gmbh Robert Schaltungsanordnung für ein Einrückrelais
DE19535211C2 (de) * 1995-09-22 2001-04-26 Univ Dresden Tech Verfahren zur Regelung der Ankerbewegung für ein Schaltgerät
WO1998031034A1 (fr) 1997-01-09 1998-07-16 Siemens Aktiengesellschaft Reduction du temps de mise sous tension des contacteurs a commande electronique
JP2001317394A (ja) * 2000-04-28 2001-11-16 Mitsubishi Electric Corp 筒内噴射エンジンの燃料噴射制御装置
DE102008046374B3 (de) * 2008-09-09 2009-12-31 Siemens Aktiengesellschaft Schaltgerät
DE102008046375B4 (de) 2008-09-09 2016-06-09 Siemens Aktiengesellschaft Verfahren zur Bestimmung des Schließzeitpunktes eines Ankers in einem Magnetsystem eines elektronisch angesteuerten Schaltgerätes
EP2189993B1 (fr) * 2008-11-21 2018-05-30 Mahle International GmbH Actionneur, système de soupape et procédé de fonctionnement associé
DE102010018755A1 (de) 2010-04-29 2011-11-03 Kissling Elektrotechnik Gmbh Relais mit integrierter Sicherheitsbeschaltung
DE102012112692A1 (de) * 2012-12-20 2014-06-26 Eaton Electrical Ip Gmbh & Co. Kg Vorrichtung und Verfahren zum Betrieb eines elektromagnetischen Schaltgeräteantriebs

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DE2425585A1 (de) * 1973-07-19 1975-02-06 Jenoptik Jena Gmbh Anordnung zum schnellen und verlustarmen schalten von induktivitaeten
DE2513043A1 (de) * 1975-03-25 1976-10-07 Baum Elektrophysik Gmbh Schaltung zum gleichstrombetrieb fuer schuetze oder relais
DE2601799A1 (de) * 1976-01-20 1977-07-21 Licentia Gmbh Schaltanordnung zur betaetigung eines elektromagnetsystems
GB2025183A (en) * 1978-06-30 1980-01-16 Bosch Gmbh Robert Operating an electro-magnetic load

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GB2015843B (en) * 1978-02-27 1982-05-19 Bendix Corp Circuits for setting three levels of current in inductive loads such as solenoids
DE3129610A1 (de) * 1981-07-28 1983-02-17 Bosch und Pierburg System oHG, 4040 Neuss Steuerschaltung fuer stellglieder

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DE2425585A1 (de) * 1973-07-19 1975-02-06 Jenoptik Jena Gmbh Anordnung zum schnellen und verlustarmen schalten von induktivitaeten
DE2513043A1 (de) * 1975-03-25 1976-10-07 Baum Elektrophysik Gmbh Schaltung zum gleichstrombetrieb fuer schuetze oder relais
DE2601799A1 (de) * 1976-01-20 1977-07-21 Licentia Gmbh Schaltanordnung zur betaetigung eines elektromagnetsystems
GB2025183A (en) * 1978-06-30 1980-01-16 Bosch Gmbh Robert Operating an electro-magnetic load

Cited By (16)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
EP0109540A3 (fr) * 1982-10-27 1986-07-09 Siemens Aktiengesellschaft Agencement de commutation pour l'actionnement d'appareillages de commutation électromagnétiques
EP0109540A2 (fr) * 1982-10-27 1984-05-30 Siemens Aktiengesellschaft Agencement de commutation pour l'actionnement d'appareillages de commutation électromagnétiques
FR2559211A1 (fr) * 1984-01-31 1985-08-09 Lucas Ind Plc Circuit d'excitation destine a la commande du courant circulant dans le solenoide d'un dispositif electromagnetique en reponse a un signal de commande
FR2564237A1 (fr) * 1984-05-09 1985-11-15 Diehl Gmbh & Co Procede pour commander un relais monostable et dispositif pour mettre en oeuvre le procede
DE3434343A1 (de) * 1984-09-19 1986-03-27 Licentia Patent-Verwaltungs-Gmbh, 6000 Frankfurt Anordnung zur stromversorgung von relais
GB2197998B (en) * 1984-11-12 1990-07-18 Inst Elektroswarki Patona Electromagnetic power drive for producing a pulsating axial force in a friction welding machine
GB2168558A (en) * 1984-12-18 1986-06-18 Diesel Kiki Co Current controlling device for electromagnetic windings
GB2213669B (en) * 1987-12-09 1992-01-29 Festo Kg A control circuit arrangement for solenoid valves
GB2213669A (en) * 1987-12-09 1989-08-16 Festo Kg Solenoid actuator circuit
DE9409760U1 (de) * 1993-06-25 1994-09-01 Siemens Ag Schaltungsanordnung zur Ansteuerung eines Schützes
DE9409759U1 (de) * 1993-06-25 1994-10-27 Siemens Ag Schaltungsanordnung zur Realisierung eines konstanten Schütz-Haltestroms
WO1997021237A2 (fr) * 1995-12-05 1997-06-12 Siemens Aktiengesellschaft Dispositif de commande pour appareils de commutation
WO1997021237A3 (fr) * 1995-12-05 1997-08-21 Siemens Ag Dispositif de commande pour appareils de commutation
WO1998031035A1 (fr) * 1997-01-09 1998-07-16 Siemens Aktiengesellschaft Contacteurs susceptibles de connectivite et a commande electronique
FR2808619A1 (fr) * 2000-05-08 2001-11-09 Siemens Ag Electronique d'entrainement et procede pour brancher de maniere commandee par moyen electronique un appareil de coupure electromagnetique
EP3806127A1 (fr) * 2019-10-08 2021-04-14 Fico Triad, S.A. Système et procédé de commande d'un contacteur électromécanique d'un circuit électrique

Also Published As

Publication number Publication date
SE8204712L (sv) 1982-08-16
DE3152626D2 (de) 1983-08-11
SE8204712D0 (sv) 1982-08-16
NL8120487A (nl) 1982-11-01
EP0067185B1 (fr) 1985-09-04
CH659345A5 (de) 1987-01-15
AT384119B (de) 1987-10-12
GB2105132A (en) 1983-03-16
DE3047488A1 (de) 1982-07-22
SE439400B (sv) 1985-06-10
ATA908981A (de) 1987-02-15
DE3152626C1 (de) 1993-04-29
EP0067185A1 (fr) 1982-12-22

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