WO2022071401A1 - 電力変換装置及びそれを備えたヒートポンプシステム - Google Patents
電力変換装置及びそれを備えたヒートポンプシステム Download PDFInfo
- Publication number
- WO2022071401A1 WO2022071401A1 PCT/JP2021/035881 JP2021035881W WO2022071401A1 WO 2022071401 A1 WO2022071401 A1 WO 2022071401A1 JP 2021035881 W JP2021035881 W JP 2021035881W WO 2022071401 A1 WO2022071401 A1 WO 2022071401A1
- Authority
- WO
- WIPO (PCT)
- Prior art keywords
- current
- unit
- power conversion
- power supply
- reactor
- Prior art date
Links
- 238000006243 chemical reaction Methods 0.000 claims abstract description 191
- 239000003990 capacitor Substances 0.000 claims description 76
- 238000000034 method Methods 0.000 claims description 29
- 230000007274 generation of a signal involved in cell-cell signaling Effects 0.000 claims description 20
- 239000004020 conductor Substances 0.000 claims description 17
- 230000001360 synchronised effect Effects 0.000 claims description 6
- 239000004065 semiconductor Substances 0.000 claims description 5
- 239000000463 material Substances 0.000 claims description 3
- 238000010586 diagram Methods 0.000 description 23
- 238000004378 air conditioning Methods 0.000 description 5
- 238000002474 experimental method Methods 0.000 description 5
- 238000001514 detection method Methods 0.000 description 4
- 230000007935 neutral effect Effects 0.000 description 3
- 230000003071 parasitic effect Effects 0.000 description 3
- 230000010349 pulsation Effects 0.000 description 3
- 230000010354 integration Effects 0.000 description 2
- 238000010587 phase diagram Methods 0.000 description 2
- XLYOFNOQVPJJNP-UHFFFAOYSA-N water Substances O XLYOFNOQVPJJNP-UHFFFAOYSA-N 0.000 description 2
- XUIMIQQOPSSXEZ-UHFFFAOYSA-N Silicon Chemical compound [Si] XUIMIQQOPSSXEZ-UHFFFAOYSA-N 0.000 description 1
- 239000004480 active ingredient Substances 0.000 description 1
- 230000000694 effects Effects 0.000 description 1
- 230000005669 field effect Effects 0.000 description 1
- 238000010438 heat treatment Methods 0.000 description 1
- 229910044991 metal oxide Inorganic materials 0.000 description 1
- 150000004706 metal oxides Chemical class 0.000 description 1
- 229910052710 silicon Inorganic materials 0.000 description 1
- 239000010703 silicon Substances 0.000 description 1
Images
Classifications
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M5/00—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases
- H02M5/40—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc
- H02M5/42—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters
- H02M5/44—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters using discharge tubes or semiconductor devices to convert the intermediate dc into ac
- H02M5/453—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters using discharge tubes or semiconductor devices to convert the intermediate dc into ac using devices of a triode or transistor type requiring continuous application of a control signal
- H02M5/458—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters using discharge tubes or semiconductor devices to convert the intermediate dc into ac using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M5/4585—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters using discharge tubes or semiconductor devices to convert the intermediate dc into ac using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only having a rectifier with controlled elements
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/12—Arrangements for reducing harmonics from ac input or output
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
- H02J3/00—Circuit arrangements for ac mains or ac distribution networks
- H02J3/01—Arrangements for reducing harmonics or ripples
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/0003—Details of control, feedback or regulation circuits
- H02M1/0009—Devices or circuits for detecting current in a converter
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/08—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters
- H02M1/088—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters for the simultaneous control of series or parallel connected semiconductor devices
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/14—Arrangements for reducing ripples from dc input or output
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/38—Means for preventing simultaneous conduction of switches
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/42—Circuits or arrangements for compensating for or adjusting power factor in converters or inverters
- H02M1/4208—Arrangements for improving power factor of AC input
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/44—Circuits or arrangements for compensating for electromagnetic interference in converters or inverters
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/02—Conversion of ac power input into dc power output without possibility of reversal
- H02M7/04—Conversion of ac power input into dc power output without possibility of reversal by static converters
- H02M7/12—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M7/21—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M7/217—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M7/219—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only in a bridge configuration
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
- H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
- H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M7/53—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M7/537—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
- H02M7/5387—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
- H02P23/00—Arrangements or methods for the control of AC motors characterised by a control method other than vector control
- H02P23/04—Arrangements or methods for the control of AC motors characterised by a control method other than vector control specially adapted for damping motor oscillations, e.g. for reducing hunting
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
- H02P27/00—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage
- H02P27/04—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage
- H02P27/06—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage using dc to ac converters or inverters
- H02P27/08—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage using dc to ac converters or inverters with pulse width modulation
- H02P27/085—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage using dc to ac converters or inverters with pulse width modulation wherein the PWM mode is adapted on the running conditions of the motor, e.g. the switching frequency
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
- H02P29/00—Arrangements for regulating or controlling electric motors, appropriate for both AC and DC motors
- H02P29/50—Reduction of harmonics
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
- H02P2201/00—Indexing scheme relating to controlling arrangements characterised by the converter used
- H02P2201/15—Power factor correction [PFC] circuit generating the DC link voltage for motor driving inverter
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
- H02P27/00—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage
- H02P27/04—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage
- H02P27/06—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage using dc to ac converters or inverters
Definitions
- the present disclosure discloses a power conversion device including a power conversion unit that converts power to a three-phase AC output by an AC power supply and a current compensation unit that flows a compensation current to the AC power supply, and a heat pump system including the power conversion unit. Regarding.
- Patent Document 1 discloses a power conversion device including a power conversion unit that performs power conversion for a three-phase AC output by an AC power supply and a current compensation unit that allows a compensation current to flow through the AC power supply. ..
- the current compensation unit includes a current compensation unit inverter having a plurality of switching elements, a current compensation unit capacitor connected between the DC side nodes of the current compensation unit inverter, and the current compensation unit.
- the compensating current reduces the harmonic components contained in the reactor for the current compensation unit connected between the AC side of the AC power supply and the AC power supply and the power supply current supplied from the AC power supply to the power conversion device.
- it has a compensation control unit that obtains an output voltage command value, and a drive signal generation unit that generates a drive signal for driving the switching element by a three-phase modulation method based on the output voltage command value.
- An object of the present disclosure is to more effectively compensate for harmonic components contained in a load current in a power conversion device provided with a current compensation unit.
- the first aspect of the present disclosure is a power conversion unit (10) that performs power conversion for a three-phase AC output by an AC power supply (2), and a compensation current (Ia (uvw)) to the AC power supply (2).
- the current compensating section capacitor (22) connected between the current compensating section inverter (21) and the DC side nodes (21a, 21b) of the current compensating section inverter (21), and the current compensating section inverter (21).
- the current compensating unit inverter (21) is connected to the AC power supply (2) via the current compensating unit reactor (23) by the switching operation of the switching elements (Sr1, Sr2, Ss1, Ss2, St1, St2). ),
- the compensating current (Ia (uvw)) is passed, the carrier frequency adopted for generating the drive signal (Sd) is fsw (kHz), and the maximum input power of the power conversion unit (10) is Pmax (kW).
- the following equation (1) holds when the dead time of the drive signal (Sd) is Td ( ⁇ s).
- the harmonic component contained in the power supply current (Is (uvw)) can be effectively reduced as compared with the case where the equation (1) does not hold. Therefore, it is easy to adapt the power supply current (Is (uvw)) to IEC61000-3-2, which is a harmonic standard established by the IEC (International Electrotechnical Commission).
- the second aspect of the present disclosure is a power conversion unit (10) that performs power conversion for a three-phase AC output by the AC power supply (2), and a compensation current (Ia (uvw)) to the AC power supply (2).
- the current compensating section capacitor (22) connected between the current compensating section inverter (21) and the DC side nodes (21a, 21b) of the current compensating section inverter (21), and the current compensating section inverter (21).
- the current compensating unit inverter (21) is connected to the AC power supply (2) via the current compensating unit reactor (23) by the switching operation of the switching elements (Sr1, Sr2, Ss1, Ss2, St1, St2). ),
- the compensating current (Ia (uvw)) is passed, the carrier frequency adopted for generating the drive signal (Sd) is fsw (kHz), and the maximum input power of the power conversion unit (10) is Pmax (kW).
- the harmonic component contained in the power supply current (Is (uvw)) can be effectively reduced as compared with the case where the equation (2) does not hold. Therefore, it is easy to adapt the power supply current (Is (uvw)) to IEC61000-3-2, which is a harmonic standard established by IEC.
- the dead time can be set longer than when the three-phase modulation method is used.
- a third aspect of the present disclosure is a power conversion unit (10) that performs power conversion for a three-phase AC output by an AC power supply (2), and a compensation current (Ia (uvw)) to the AC power supply (2).
- the current compensating section capacitor (22) connected between the current compensating section inverter (21) and the DC side nodes (21a, 21b) of the current compensating section inverter (21), and the current compensating section inverter (21).
- the current compensating unit inverter (21) is connected to the AC power supply (2) via the current compensating unit reactor (23) by the switching operation of the switching elements (Sr1, Sr2, Ss1, Ss2, St1, St2). ),
- the compensating current (Ia (uvw)) is passed, the carrier frequency adopted for generating the drive signal (Sd) is fsw (kHz), and the maximum input power of the power conversion unit (10) is Pmax (kW).
- the dead time of the drive signal (Sd) is Td ( ⁇ s)
- the inductance of the current compensator reactor (23) when the current flowing through the current compensator reactor (23) is 0 A is Lac (mH).
- the harmonic component included in the power supply current (Is (uvw)) can be effectively reduced as compared with the case where at least one of the equation (3) and the equation (4) does not hold. Therefore, it is easy to adapt the power supply current (Is (uvw)) to IEC61000-3-2, which is a harmonic standard established by IEC.
- a fourth aspect of the present disclosure is a power conversion unit (10) that performs power conversion for a three-phase AC output by an AC power supply (2), and a compensation current (Ia (uvw)) to the AC power supply (2).
- the current compensating section capacitor (22) connected between the current compensating section inverter (21) and the DC side nodes (21a, 21b) of the current compensating section inverter (21), and the current compensating section inverter (21).
- the current compensating unit inverter (21) is connected to the AC power supply (2) via the current compensating unit reactor (23) by the switching operation of the switching elements (Sr1, Sr2, Ss1, Ss2, St1, St2). ),
- the compensating current (Ia (uvw)) is passed, the carrier frequency adopted for generating the drive signal (Sd) is fsw (kHz), and the maximum input power of the power conversion unit (10) is Pmax (kW).
- the dead time of the drive signal (Sd) is Td ( ⁇ s)
- the inductance of the current compensator reactor (23) when the current flowing through the current compensator reactor (23) is 0 A is Lac (mH).
- the harmonic component included in the power supply current (Is (uvw)) can be effectively reduced as compared with the case where at least one of the equation (5) and the equation (6) does not hold. Therefore, it is easy to adapt the power supply current (Is (uvw)) to IEC61000-3-2, which is a harmonic standard established by IEC.
- the dead time can be set longer than when the three-phase modulation method is used.
- a fifth aspect of the present disclosure is, in the third or fourth aspect, the current with respect to the inductance of the current compensator reactor (23) when the current flowing through the current compensator reactor (23) is 0 A. It is characterized in that the ratio of the inductance of the current compensating part reactor (23) when the current flowing through the compensating part reactor (23) is the peak current is set to 1/3 or more.
- the harmonic component contained in the power supply current (Is (uvw)) can be more reliably reduced and the compensation current (Ia (uvw)) can be reduced as compared with the case where the ratio is set to less than 1/3. It can be controlled stably.
- a sixth aspect of the present disclosure is, in any one of the first to fifth aspects, between the AC power supply (2) and the current compensator reactor (23), the current compensator reactor. It is characterized by having a filter reactor (24a) having a smaller inductance than (23) and a filter capacitor (24b), and interposing a filter (24) having a resonance frequency set to 4 kHz or higher. ..
- the influence of the filter (24) on the compensation current (Ia (uvw)) of the resonance can be reduced at a frequency lower than 4 kHz, so that the frequency of the three-phase alternating current is 50 Hz or 60 Hz. Harmonic components up to the 40th order contained in the power supply current (Is (uvw)) can be reliably reduced, and the compensation current (Ia (uvw))) can be controlled stably.
- a seventh aspect of the present disclosure is, in the second or fourth aspect, the drive signal generation unit (27) is a DC voltage between the DC side nodes (21a, 21b) of the current compensation unit inverter (21). It is characterized in that the drive signal (Sd) is generated based on the output voltage command value (Vid, Viq) so that the ratio of the amplitude of the line voltage on the AC side to (Vdc) is 70% or more. ..
- the switching element (Sr1, Sr2, Ss1, Ss2, St1, St2) of the current compensating part inverter (21) is used when switching the phase to be modulated. Since it is possible to suppress a rapid change in the duty ratio of the inverter, it is possible to more reliably reduce the harmonic component contained in the power supply current (Is (uvw)).
- the compensation control unit (26) has a DC voltage (21a, 21b) between the DC side nodes (21a, 21b) of the current compensation unit inverter (21).
- AC of the voltage command value calculation unit (29) that calculates the output voltage command value (Vid, Viq) based on the Vdc) and the DC voltage command value (Vdc *) and the current compensator inverter (21).
- DC voltage command value that calculates the DC voltage command value (Vdc *) based on the output voltage command value (Vid, Viq) so that it is equal to or less than the average value of the line voltage on the side or twice the basic frequency component. It is characterized by having a calculation unit (28).
- the DC voltage command value (Vdc *) is higher than the average value of the line voltage on the AC side of the current compensator inverter (21) or twice the basic frequency component, as compared with the case where the DC voltage command value (Vdc *) is higher than twice. Since the duty ratio of the switching elements (Sr1, Sr2, Ss1, Ss2, St1, St2) of the inverter (21) for the current compensation unit can be suppressed from changing rapidly when the phase to be modulated is switched, the power supply current (Is) can be suppressed. The harmonic component contained in (uvw)) can be reduced more reliably.
- the power conversion unit (10) has a rectifying circuit (11) that rectifies the three-phase alternating current into an alternating current and the alternating current. It is connected between the inverter for the power conversion unit (12) to be converted to AC and the DC side nodes (12a, 12b) of the inverter for the power conversion unit (12), and allows the output voltage of the rectifier circuit (11) to fluctuate. It is characterized by having a power conversion unit capacitor (14) and a power conversion unit reactor (13) connected between one end of the AC power supply (2) and the power conversion unit capacitor (14). do.
- the filter (LC1) is configured by the power conversion unit capacitor (14) and the power conversion unit reactor (13), the capacity of the power conversion unit capacitor (14) is appropriately set.
- the current flowing between the power conversion unit inverter (12) and the AC power supply (2) due to the switching operation of the power conversion unit inverter (12) is the power conversion unit inverter (12). It is possible to suppress fluctuations depending on the frequency of the carrier.
- the capacitor (14) for the power converter allows the fluctuation of the output voltage of the rectifier circuit (11), the fluctuation of the compensation current (Ia (uvw)) can be reduced, so that the power supply current (Is (uvw)) ) Can be more reliably reduced.
- a tenth aspect of the present disclosure is characterized in that, in the ninth aspect, the capacity of the current compensating unit capacitor (22) is larger than the capacity of the power conversion unit capacitor (14).
- the capacity of the capacitor (22) for the current compensation unit is used, and the pulsation of the DC voltage (Vdc) between the DC side nodes (21a, 21b) of the inverter (21) for the current compensation unit is used for the power conversion unit. Since the setting can be made larger than the pulsation of the DC voltage between the DC side nodes (12a, 12b) of the inverter (12), the harmonic component contained in the power supply current (Is (uvw)) can be reduced more reliably. ..
- the current compensating unit inverter (21) has six unipolar transistors constituting three legs and the switching element (Sr1, Sr2). , Ss1, Ss2, St1, St2), the drive signal generation unit (27) generates the drive signal (Sd) so as to cause the current compensation unit inverter (21) to perform synchronous rectification operation. It is a feature.
- the switching element (Sr1, Sr2, Ss1, Ss2, St1, St2) is conducting, as compared with the case where the bipolar transistor is used as the switching element (Sr1, Sr2, Ss1, Ss2, St1, St2). Since the voltage can be lowered, it is possible to suppress an error in the output voltage (Va (uvw)) output by the current compensator inverter (21) with respect to the output voltage command value (Vid, Viq) due to the voltage. .. Therefore, the harmonic component contained in the power supply current (Is (uvw)) can be reduced more reliably.
- the switching element (Sr1, Sr2, Ss1, Ss2, St1, St2) is an element whose main material is a wide bandgap semiconductor, and the switching element (Sr1, Sr2, Ss1, Ss2, St1, St2).
- the on-resistance of Sr1, Sr2, Ss1, Ss2, St1, St2) is 100 m ⁇ or less.
- the switching speed of the switching element (Sr1, Sr2, Ss1, Ss2, St1, St2) can be increased, so that the dead time can be easily shortened. Therefore, it is easy to reduce the harmonic component contained in the power supply current (Is (uvw)).
- the thirteenth aspect of the present disclosure is characterized in that, in any one of the first to twelfth aspects, the carrier frequency is 100 kHz or less.
- the dead time can be secured longer than when the carrier frequency is higher than 100 kHz.
- a fourteenth aspect of the present disclosure is a heat pump system provided with a power conversion device according to any one of the first to thirteenth aspects, wherein the three-phase alternating current has three leads to the power conversion unit (10).
- the heat pump system (1) has a harmonic source (300,400) that produces harmonics in the current of at least one of the three conductors (601,602,603). It is also characterized by having.
- the harmonic component contained in the power supply current (Is (uvw)) can be effectively reduced in the heat pump system (1). Therefore, it is easy to adapt the power supply current (Is (uvw)) to IEC61000-3-2, which is a harmonic standard established by IEC.
- FIG. 1 is a block diagram showing the configuration of an air conditioning system.
- FIG. 2 is a block diagram showing a configuration of a power conversion device according to the first embodiment of the present disclosure.
- FIG. 3 is a circuit diagram of an inverter for a current compensation unit.
- FIG. 4 is a graph showing the relationship between the dead time of the drive signal when the three-phase modulation method is adopted and the ratio of the generated amount during the experiment to the maximum generated amount of the harmonic component defined by IEC61000-3-2. be.
- FIG. 5 shows the amount of power generated during the experiment with respect to the maximum input power of the power conversion unit and the maximum amount of harmonic components generated in IEC61000-3-2 when the three-phase modulation method and the two-phase modulation method are adopted.
- FIG. 6 shows the dead time when the amount of harmonic components generated in the power supply current reaches the maximum amount specified in IEC61000-3-2 when the three-phase modulation method is adopted and when the two-phase modulation method is adopted.
- Is a table showing a plurality of types of second carrier frequencies.
- FIG. 7 is a graph corresponding to the table of FIG. In FIG. 8, when the three-phase modulation method is adopted, the maximum generated amount defined by IEC61000-3-2, the second carrier frequency is 32 kHz, the maximum input power of the power converter is 10 kW, and the dead time is 0.5 ⁇ s.
- FIG. 9A shows a reactor for the current compensation unit when the dead time of the drive signal is 0.5 ⁇ s, the second carrier frequency is 16 kHz, the maximum input power of the power conversion unit is 10 kW, and the current flowing through the reactor for the current compensation unit is 0 A. It is a timing chart which shows the power supply current, the compensation current, and the load current when the inductance of is 1.0 mH.
- FIG. 9B is a diagram corresponding to FIG.
- FIG. 9A when the maximum input power of the power conversion unit is 10 kW and the inductance of the reactor for the current compensation unit is 2.2 mH when the current flowing through the reactor for the current compensation unit is 0 A.
- FIG. 9C is a diagram corresponding to FIG. 9A when the maximum input power of the power conversion unit is 5 kW and the inductance of the reactor for the current compensation unit is 1.0 mH when the current flowing through the reactor for the current compensation unit is 0 A.
- FIG. 9D is a diagram corresponding to FIG. 9A when the maximum input power of the power conversion unit is 5 kW and the inductance of the reactor for the current compensation unit is 2.2 mH when the current flowing through the reactor for the current compensation unit is 0 A.
- FIG. 9C is a diagram corresponding to FIG. 9A when the maximum input power of the power conversion unit is 5 kW and the inductance of the reactor for the current compensation unit is 1.0 mH when the current flowing through the reactor for the current compensation unit is 0 A
- FIG. 10 is a circuit diagram showing an equivalent circuit of the current compensation unit.
- FIG. 11 is a block diagram showing a current control system included in the current compensation unit.
- FIG. 12A shows a gain diagram of the transfer functions Gp, Gc and their total.
- FIG. 12B shows a phase diagram of the transfer functions Gp, Gc and their total.
- FIG. 13A is a graph showing the DC superimposition characteristics of the reactor for the current compensator when the ratio of the peak current inductance to the zero current inductance is less than 1/3.
- FIG. 13B is a diagram corresponding to FIG. 13A when the ratio of the peak current inductance to the zero current inductance is set to 1/3 or more.
- FIG. 13A is a graph showing the DC superimposition characteristics of the reactor for the current compensator when the ratio of the peak current inductance to the zero current inductance is less than 1/3.
- FIG. 13B is a diagram corresponding to FIG. 13A when the ratio of the peak current inductance to the zero
- FIG. 14A shows the power supply current, load current, and compensation current when the maximum input power of the power conversion unit is set to 10 kW and the capacitance value of the capacitor for the power conversion unit is set to absorb fluctuations in the output voltage of the rectifying circuit. It is a timing chart exemplifying.
- FIG. 14B is a diagram corresponding to FIG. 14A when the capacitance value of the capacitor for the power conversion unit is set so as to allow fluctuations in the output voltage of the rectifier circuit.
- FIG. 15A is a timing chart illustrating the power supply current, the compensation current, and the DC voltage when the capacity of the capacitor for the current compensation unit is 195 ⁇ F and the capacity of the capacitor for the power conversion unit is 30 ⁇ F.
- FIG. 15B is a diagram corresponding to FIG.
- FIG. 16 shows a current flowing through a freewheeling diode when a Si-PiN diode is provided as a freewheeling diode in antiparallel to the switching element, a current flowing in the opposite direction of the switching element when the switching element is a MOSFET, and a conduction voltage. It is a graph which shows the relationship of.
- FIG. 17 is a diagram corresponding to FIG. 4 when the two-phase modulation method is adopted. In FIG.
- FIG. 19A is a timing chart showing a DC voltage, a power supply current, a load current, and a compensation current when the second carrier frequency is 48 kHz, the maximum input power of the power converter is 10 kW, and the dead time is 0.5 ⁇ sec. ..
- FIG. 19B is a diagram corresponding to FIG. 19A when the dead time is set to 1.0 ⁇ sec.
- FIG. 20 is a block diagram showing a configuration of a drive signal generation unit according to the second embodiment.
- FIG. 21A is a graph showing the relationship between the duty ratios of the three switching elements of the upper arm of the inverter for the current compensation unit and the phase when the modulation factor is 40%.
- FIG. 21B is a diagram corresponding to FIG. 21A when the modulation factor is 70%.
- FIG. 22 is a diagram corresponding to FIG. 2 of the third embodiment.
- FIG. 1 shows an air conditioning system (1) as a heat pump system.
- This air conditioning system (1) includes a power conversion device (100) according to the first embodiment of the present disclosure, a noise filter (200), an indoor unit (300) as a harmonic generation source, and a harmonic generation source. It is equipped with an outdoor fan (400) and a compressor (500).
- the power conversion device (100) performs power conversion for the three-phase AC output by the AC power supply (2) and input via the noise filter (200).
- the AC power supply (2) is a three-phase four-wire AC power supply.
- the three-phase alternating current is input to the power converter (100) via three first to third conductors (601,602,603).
- the indoor unit (300) is driven by alternating current taken out from the first conductor (601) and the neutral wire (604).
- the indoor unit (300) generates harmonics in the first conductor (601).
- the outdoor fan (400) is driven by the electric power taken out from the second conductor (602) and the neutral wire (604).
- the outdoor fan (400) generates harmonics in the second conductor (602).
- the compressor (500) is equipped with a motor (501) (see FIG. 2).
- the motor (501) is supplied with alternating current after power conversion by the power conversion device (100).
- the power conversion device (100) includes a power conversion unit (10) and a current compensation unit (20).
- the power conversion unit (10) performs power conversion for the three-phase AC output by the AC power supply (2) and input via the first to third conductors (601,602,603).
- the power conversion unit (10) includes a rectifier circuit (11), an inverter for the power conversion unit (12), a reactor for the power conversion unit (13), a capacitor for the power conversion unit (14), and the like. It is equipped with a conversion control unit (15).
- the rectifier circuit (11) rectifies the three-phase AC output by the AC power supply (2) to DC and outputs it to the first and second output nodes (11a, 11b).
- the rectifier circuit (11) is a full-wave rectifier circuit.
- the rectifier circuit (11) has six diodes (not shown) connected in a bridge shape. These diodes have their cathode directed towards the first output node (11a) and their anode directed towards the second output node (11b).
- the inverter (12) for the power converter converts the direct current output by the rectifier circuit (11) into alternating current and outputs it to the motor (501) of the compressor (500).
- the power conversion unit inverter (12) has six switching elements (not shown) and six freewheeling diodes (not shown). The six switching elements are bridge-connected. That is, the power conversion unit inverter (12) includes three switching legs connected between the first and second DC nodes (12a, 12b). A switching leg is one in which two switching elements are connected in series with each other.
- the midpoint between the switching element of the upper arm and the switching element of the lower arm is connected to the coil (u-phase, v-phase, w-phase coil) of each phase of the motor (501). ing.
- One freewheeling diode is connected to each switching element in antiparallel.
- One end of the reactor (13) for the power conversion unit is connected to the first output node (11a) of the rectifier circuit (11), and the other end of the reactor (13) for the power conversion unit is an inverter (12) for the power conversion unit. ) Is connected to the first DC node (12a).
- the power conversion unit capacitor (14) is connected between the first and second DC nodes (12a, 12b) of the power conversion unit inverter (12). Therefore, the reactor (13) for the power conversion unit is connected between the AC power supply (2) and one end of the capacitor (14) for the power conversion unit.
- the capacitance value of the capacitor (14) for the power converter allows fluctuations in the output voltage of the rectifier circuit (11), but is set so that the ripple voltage caused by the switching operation of the inverter (12) for the power converter can be suppressed.
- the ripple voltage is a voltage fluctuation according to the switching frequency in the switching element. Therefore, the DC link voltage, which is the voltage of the capacitor (14) for the power conversion unit, includes a pulsating component corresponding to the frequency of the AC voltage of the AC power supply (2).
- the capacity of the power conversion unit capacitor (14) is 1/10 or less of the average value of the voltage of the power conversion unit capacitor (14) for the voltage fluctuation of the power conversion unit capacitor (14) during the switching cycle. It is set to suppress to. Therefore, the minimum capacity required for the power conversion unit capacitor (14) is determined according to the switching frequency and the motor current flowing between the motor (501) and the power conversion unit capacitor (14).
- the voltage fluctuation of the power conversion unit capacitor (14) during the switching cycle can be controlled by the power conversion unit capacitor (14). It can be suppressed to 1/10 or less of the average value of the voltage of (14).
- equation (I) ignoring the output voltage fluctuation of the rectifying circuit (11) superimposed on the DC link voltage, the average value of the DC link voltage is VAdc, and the peak value of the motor current when the AC power is the maximum power is Imax. , Let the switching period be Ts.
- the switching cycle is a cycle in which the switching element repeatedly turns on and off.
- the switching cycle is the carrier cycle of the first carrier wave used for PWM control.
- the capacitor (14) for the power conversion unit is composed of, for example, a film capacitor.
- the pulsating component corresponding to the frequency of the AC power supply (2) remains in the DC link voltage. Since the AC power supply (2) is a three-phase power supply, the pulsating component corresponding to the frequency of the AC power supply (2) is six times the frequency of the AC power supply (2).
- the power conversion unit filter (LC1) is formed by the inductance component between the AC power supply (2) and the power conversion unit capacitor (14) and the power conversion unit capacitor (14).
- the inductance component includes a reactor (13).
- the capacity of the power conversion unit capacitor (14) is set so that the power conversion unit filter (LC1) attenuates a component of the first carrier frequency included in the current.
- the first carrier frequency is the frequency of the first carrier wave used for generating the control signal of the inverter (12) for the power conversion unit. Therefore, due to the switching operation of the power conversion unit inverter (12), the current flowing between the power conversion unit inverter (12) and the AC power supply (2) fluctuates according to the first carrier frequency. Can be suppressed.
- the conversion control unit (15) controls the on / off of each switching element of the power conversion unit inverter (12) by a control signal (Smd).
- the current compensation unit (20) sends a compensation current (Ia (uvw)) to the AC power supply (2).
- the compensation current (Ia (uvw)) has a negative direction from the AC power supply (2) toward the current compensation unit (20).
- the power supply current (Is (uvw)) supplied by the AC power supply (2) is the load current (Io (uvw)) from the AC power supply (2) to the power conversion unit (10) and the compensation current (Ia (Ia (uvw)). It is the difference from uvw)).
- the current compensation unit (20) includes an inverter (21) for the current compensation unit, a capacitor (22) for the current compensation unit, a reactor (23) for the current compensation unit corresponding to each phase, and current compensation corresponding to each phase. It includes a unit filter (24), a voltage detector (25), a compensation control unit (26), and a drive signal generation unit (27).
- the inverter (21) for the current compensation unit has six switching elements (Sr1, Sr2, Ss1, Ss2, St1, St2).
- the switching elements (Sr1, Sr2, Ss1, Ss2, St1, St2) are unipolar transistors and MOSFETs (metal oxide semiconductor field effect transistors) mainly made of wide bandgap semiconductors.
- the on-resistance of the switching element (Sr1, Sr2, Ss1, Ss2, St1, St2) is 100 m ⁇ or less.
- the six switching elements (Sr1, Sr2, Ss1, Ss2, St1, St2) constitute three switching legs connected between the first and second DC side nodes (21a, 21b).
- the switching leg consists of two switching elements (Sr1, Sr2, Ss1, Ss2, St1, St2) connected in series with each other.
- each switching element contains a parasitic diode (RD).
- the parasitic diode (RD) is a recirculation element that allows current to flow in the opposite direction.
- an IGBT Insulated Gate Bipolar Transistor
- a freewheeling diode is connected in antiparallel to the switching element (Sr1, Sr2, Ss1, Ss2, St1, St2).
- the forward direction is higher than that of the parasitic diode (RD) as in the case of using the IGBT.
- Freewheeling diodes with low voltage may be connected one by one in antiparallel.
- the current compensation unit capacitor (22) is connected between the DC side nodes (21a, 21b) of the current compensation unit inverter (21).
- the voltage of the capacitor (22) for the current compensation unit that is, the voltage between the DC side nodes (21a, 21b) of the inverter (21) for the current compensation unit is the DC voltage (Vdc).
- the capacity of the current compensation unit capacitor (22) is larger than the capacity of the power conversion unit capacitor (14).
- each phase current compensator reactor (u-phase, v-phase, w-phase current compensator reactor) (23) is connected to any one AC side node of the current compensator inverter (21). Has been done.
- the other end of each current compensator reactor (23) is connected to the AC power supply (2) via the corresponding current compensator filter (24). That is, the reactor (23) for the current compensation unit is connected between the AC side of the inverter (21) for the current compensation unit and the AC power supply (2).
- the current compensating section filter (24) for each phase is interposed between the AC power supply (2) and the current compensating section reactor (23).
- Each current compensator filter (24) has a filter reactor (24a) having a smaller inductance than the current compensator reactor (23) and a filter capacitor (24b).
- the resonance frequency of each current compensator filter (24) is set to 4 kHz or higher.
- the voltage detector (25) detects the line voltage of the two-phase power supply voltage among the three-phase power supply voltages output by the AC power supply (2).
- the inverter (21) for the current compensation unit is an AC power supply via the reactor (23) for the current compensation unit by the switching operation of the switching elements (Sr1, Sr2, Ss1, Ss2, St1, St2).
- the compensation current (Ia (uvw)) is passed through (2).
- the compensation control unit (26) contains the DC voltage (Vdc) between the DC side nodes (21a, 21b) of the current compensation unit inverter (21) and the load flowing from the AC power supply (2) to the power conversion unit (10). Based on the current (Io (uvw)), the harmonic component contained in the power supply current (Is (uvw)) supplied to the power converter (100) is reduced by the compensation current (Ia (uvw)). , Obtain the output voltage command value (Vid, Viq).
- the compensation control unit (26) includes a phase detection unit (26a), first and second dq conversion units (26b, 26c), a high-pass filter (26d), and a first subtraction unit (26d). 26e), voltage control unit (26f), first addition unit (26g), second and third subtraction units (26h, 26i), and first and second current control units (26j, 26k). ) And.
- the phase detector (26a) detects the phase ( ⁇ t) of the power supply voltage based on the line voltage detected by the voltage detector (25).
- the voltage detector (25) detects the difference between the power supply voltage of one phase and the voltage of the neutral wire (604) among the three-phase power supply voltages output by the AC power supply (2), that is, the phase voltage. Then, the phase detection unit (26a) may detect the phase ( ⁇ t) of the power supply voltage based on the phase voltage.
- the first dq conversion unit (26b) detects at least two phases of the current (il (rst)) proportional to the load current (Io (uvw)), and detects three phases. / Two-phase conversion is performed to obtain the d-axis component and q-axis component (iq *) of the load current (Io (uvw)).
- the d-axis and the q-axis are coordinate axes of the rotating coordinate system synchronized with the phase ( ⁇ t) detected by the phase detection unit (26a).
- the d-axis component is an active ingredient and the q-axis component is an ineffective component.
- the load current (Io (uvw)) can be calculated by calculating the remaining one phase.
- the d-axis component and the q-axis component (iq *) can be obtained.
- the second dq conversion unit (26c) detects the reactor current (ia (uv)) for two phases of the current (ia (uvw)) proportional to the current flowing through the reactor (23) for the current compensation unit. Three-phase / two-phase conversion is performed to obtain the d-axis component (id) and the q-axis component (iq) of the compensation current (Ia (uvw)). Since the current (ia (uvw)) is three-phase, if the current (ia (uv)) for two of them can be detected, the compensation current (Ia (uvw)) can be calculated by calculating the remaining one phase. The d-axis component (id) and the q-axis component (iq) can be obtained.
- the high-pass filter (26d) outputs the high frequency component (idh) of the d-axis component of the load current (Io (uvw)) obtained by the first dq conversion unit (26b).
- the first subtraction unit (26e) subtracts the DC voltage (Vdc) between the DC side nodes (21a, 21b) of the current compensation unit inverter (21) from the output voltage command value (Vdc *) and subtracts the result. Is output.
- the voltage control unit (26f) performs proportional integral control on the subtraction result output by the first subtraction unit (26e) to obtain a correction value.
- the first addition unit (26g) adds the high frequency component (idh) of the d-axis component output by the high-pass filter (26d) and the correction value obtained by the voltage control unit (26f), and the addition result. Is output as the command value (id *) of the d-axis component.
- the second subtraction unit (26h) is the compensation current (Ia (uvw)) obtained by the second dq conversion unit (26c) from the command value (id *) output by the first addition unit (26g). ) Is subtracted from the d-axis component (id), and the subtraction result is output.
- the third subtraction unit (26i) is a second dq conversion unit (26c) from the q-axis current (iq *) of the load current (Io (uvw)) obtained by the first dq conversion unit (26b).
- the q-axis current (iq) of the compensation current (Ia (uv)) obtained by is subtracted and the subtraction result is output.
- the first current control unit (26j) generates an output voltage command value (Vid) of the d-axis component so that the subtraction result output by the second subtraction unit (26h) becomes small.
- the first current control unit (26j) generates an output voltage command value (Vid) of the d-axis component by, for example, proportional integration control.
- the second current control unit (26k) generates an output voltage command value (Viq) of the q-axis component so that the subtraction result output by the third subtraction unit (26i) becomes small.
- the second current control unit (26k) generates an output voltage command value (Viq) of the q-axis component by, for example, proportional integration control.
- the drive signal generation unit (27) has switching elements (Sr1, Sr2, Ss1, Ss2, St1, St2) of the current compensation unit inverter (21) so that the current compensation unit inverter (21) performs synchronous rectification operation.
- the drive signal (Sd) for driving the inverter is generated by a three-phase modulation method based on the output voltage command value (Vid, Viq).
- the second carrier frequency which is the frequency of the second carrier wave used to generate the drive signal (Sd), is set to 100 kHz or less.
- the dead time of the drive signal (Sd) and the harmonics defined by IEC61000-3-2 which is a harmonic standard established by IEC (International Electrotechnical Commission).
- IEC International Electrotechnical Commission
- FIG. 4 shows each case where the second carrier frequency is 16 kHz, 32 kHz, and 48 kHz.
- the second carrier frequency is the frequency of the second carrier used to generate the drive signal (Sd). Based on the relationship shown in FIG. 4, it is estimated that the higher the second carrier frequency, the shorter the dead time needs to be in order to make the power supply current (Is (uvw)) conform to the standard.
- the maximum input power of the power conversion unit (10) and the maximum generation amount of harmonic components defined by IEC61000-3-2 are measured at the time of the experiment.
- the relationship with the ratio of the amount of harmonic components generated in the power supply current (Is (uvw)) (the ratio of the experimental value to the standard value) is shown in FIG.
- FIG. 5 shows a case where the second carrier frequency is 16 kHz and the dead time is 3.0 ⁇ s, and a case where a three-phase modulation method is adopted and a case where a two-phase modulation method is adopted for generating a drive signal (Sd). Based on the relationship shown in FIG. 5, it is estimated that the larger the maximum input power of the power conversion unit (10), the larger the amount of harmonic components generated.
- FIG. 6 when the maximum input power of the power conversion unit (10) is 10 kW, the amount of harmonic components generated in the power supply current (Is (uvw)) is the maximum defined by IEC61000-3-2. It is a table which shows the dead time ( ⁇ s) when it becomes the generation amount for a plurality of kinds of 2nd carrier frequencies.
- FIG. 7 is a graph corresponding to the table of FIG. 6 and 7 show the dead time when the three-phase modulation method is adopted and the two-phase modulation method is adopted for the generation of the drive signal (Sd).
- FIG. 8 is included in the power supply current (Is (uvw)) when the second carrier frequency is 32 kHz, the maximum input power of the power conversion unit (10) is 10 kW, and the dead time is 0.5 ⁇ s and 1.0 ⁇ s.
- the current value corresponding to each order of the harmonic component is shown.
- the dead time is set to 1.0 ⁇ s, the 35th-order harmonic component exceeds the maximum amount generated in IEC61000-3-2.
- the dead time is set to 0.5 ⁇ s, the harmonic components are below the maximum amount generated in IEC61000-3-2 at all orders.
- the inventors set the dead time of the drive signal (Sd) so that the following equation (II) holds, whereby the power supply current (Is (uvw)). ) Can be effectively reduced, and the power supply current (Is (uvw)) can be easily adapted to IEC61000-3-2.
- the second carrier frequency is fsw (kHz)
- the maximum input power of the power conversion unit (10) is Pmax (kW)
- the dead time of the drive signal (Sd) is Td ( ⁇ s). do.
- the drive signal generation unit (27) generates a drive signal (Sd) so that the above equation (II) holds.
- the drive signal generation unit (27) generates a drive signal (Sd) so that the following equations (III) and (IV) are established in addition to the equation (II).
- the second carrier frequency is fsw (kHz)
- the maximum input power of the power conversion unit (10) is Pmax (kW)
- the dead time of the drive signal (Sd) is Td ( ⁇ s).
- the inductance of the current compensator reactor (23) when the current flowing through the current compensator reactor (23) is 0 A is defined as Lac (mH).
- FIG. 9B the dead time of the drive signal (Sd) is 0.5 ⁇ s, the second carrier frequency is 16 kHz, the maximum input power of the power conversion unit (10) is 10 kW, and the current flowing through the current compensator reactor (23) is 0 A. It is a figure corresponding to FIG. 9A when the inductance of the reactor (23) for the current compensating part is 2.2 mH.
- FIG. 9C the dead time of the drive signal (Sd) is 0.5 ⁇ s, the second carrier frequency is 16 kHz, the maximum input power of the power conversion unit (10) is 5 kW, and the current flowing through the current compensator reactor (23) is 0 A.
- FIG. 9A is a diagram corresponding to FIG.
- FIG. 9A when the inductance of the reactor (23) for the current compensation unit is 1.0 mH.
- the dead time of the drive signal (Sd) is 0.5 ⁇ s
- the second carrier frequency is 16 kHz
- the maximum input power of the power conversion unit (10) is 5 kW
- the current flowing through the current compensator reactor (23) is 0 A. It is a figure corresponding to FIG. 9A when the inductance of the reactor (23) for the current compensating part is 2.2 mH.
- the inverter (21) for the current compensation unit is connected to the power supply system via the reactor (23) for the current compensation unit and the filter (24) for the current compensation unit, the circuit of the current compensation unit (20) is connected.
- the power supply current (Is (uvw)) is is
- the load current (Io ( uvw )) is ii
- the power supply voltage is Vs
- the current value (id, iq) calculated from the reactor current (ia (uvw)) based on the detected reactor current (ia (uvw)) is the load current (Io).
- Feedback control is performed using the first and second current control units (26j, 26k) so as to match the command values (id *, iq *) obtained by extracting the harmonic components from (uvw)). Is going.
- the transfer function of the output voltage (Va (uvw)) output by the current compensator inverter (21) to the reactor current (ia (uvw)) is Gc
- the current control system included in the current compensator (20) is used. , Can be represented as shown in FIG.
- FIG. 12A shows a gain diagram of the transfer functions Gp, Gc and their total
- FIG. 12B shows a phase diagram of the transfer functions Gp, Gc and their total. If the gain characteristics of the first and second current control units (26j, 26k) are constant, the gain characteristics of the entire current compensation unit (20) change according to the inductance of the reactor (23) for the current compensation unit. It will be.
- resonance of the current compensating section filter (24) occurs at a portion surrounded by a broken line.
- the DC superimposition characteristic of the reactor (23) for the current compensation unit is flat. If stability is ensured when the current flowing through the current compensator reactor (23) is the peak current, the control performance deteriorates when the current is small, and the harmonic component included in the power supply current (Is (uvw)). Will increase.
- the current flowing through the current compensator reactor (23) is the peak current with respect to the zero current inductance, which is the inductance of the current compensator reactor (23) when the current flowing through the current compensator reactor (23) is 0 A. By setting the ratio of the peak current inductance, which is the inductance of the current compensating unit reactor (23), to 1/3 or more, the stability of current control can be ensured and the harmonic current can be reduced.
- the ratio of the peak current inductance to the zero current inductance is set to 1/3 or more.
- the peak current (Ipeak) is 12A
- the zero current inductance (Lzero) is 2.2 mH
- the peak current inductance (Lpeak) is 0.6 mH. Therefore, the ratio of the peak current inductance (Lpeak) to the zero current inductance (Lzero) is less than 1/3.
- the peak current (Ipeak) is 12A
- the zero current inductance (Lzero) is 1.3 mH
- the peak current inductance (Lpeak) is 0.6 mH. Therefore, the ratio of the peak current inductance (Lpeak) to the zero current inductance (Lzero) is 1/3 or more.
- the resonance frequency of the current compensator filter (24) is set to 4 kHz or more, the resonance of the current compensator filter (24) is set at a frequency smaller than 4 kHz.
- the effect on the compensation current (Ia (uvw)) can be reduced. Therefore, when the frequency of the three-phase alternating current is 50 Hz or 60 Hz, the harmonic components up to the 40th order included in the power supply current (Is (uvw)) can be reliably reduced, and the compensation current (Ia (uvw)) is stable. Can be controlled.
- the inductance of the reactor (24a) for the filter it is preferable to set the inductance of the reactor (24a) for the filter to be smaller than the inductance of the reactor (23) for the current compensation unit.
- the capacitance value of the power conversion unit capacitor (14) is set small enough to allow fluctuations in the output voltage of the rectifier circuit (11), so that the capacitance value of the power conversion unit capacitor (14) is set. Compared to the case where the fluctuation of the output voltage of the rectifier circuit (11) is set to be large, the fluctuation width of the output current of the rectifier circuit (11) is made smaller and the peak value of the compensation current (Ia (uvw)) is reduced. Can be suppressed.
- FIG. 14A shows a case where the maximum input power of the power conversion unit (10) is 10 kW and the capacitance value of the capacitor (14) for the power conversion unit is set to absorb the fluctuation of the output voltage of the rectifying circuit (11).
- the power supply current (Is (uvw)), load current (Io (uvw)), and compensation current (Ia (uvw)) when the so-called capacitor input type is adopted are exemplified.
- FIG. 14B shows a case where the maximum input power of the power conversion unit (10) is set to 10 kW and the capacitance value of the capacitor (14) for the power conversion unit is set so as to allow fluctuations in the output voltage of the rectifier circuit (11).
- FIG. 14A is a diagram corresponding to FIG. 14A.
- the effective value of the compensation current (Ia (uvw)) is 6.8A, and the peak value of the compensation current (Ia (uvw)) is 15.3A.
- the effective value of the compensation current (Ia (uvw)) is 4.5A, and the peak value of the compensation current (Ia (uvw)) is 11.0A. That is, the effective value and the peak value of the compensation current (Ia (uvw)) can be suppressed to 2/3 of the case of FIG. 14A.
- the capacity of the capacitor (22) for the current compensation unit is equal to or less than the capacity of the capacitor (14) for the power conversion unit, it is between the DC side nodes (21a, 21b) of the inverter (21) for the current compensation unit. Since the pulsation of the direct current voltage (Vdc) can be suppressed, the harmonic component contained in the power supply current (Is (uvw)) can be reduced more reliably.
- FIG. 15A shows the power supply current (Is (uvw)) and the compensation current (Ia (uvw)) when the capacity of the capacitor (22) for the current compensation unit is 195 ⁇ F and the capacity of the capacitor (14) for the power conversion unit is 30 ⁇ F.
- DC voltage (Vdc) are exemplified.
- FIG. 15B is a diagram corresponding to FIG. 15A when the capacity of the capacitor (22) for the current compensation unit is 15 ⁇ F and the capacity of the capacitor (14) for the power conversion unit is 30 ⁇ F.
- the unipolar transistor is used as the switching element (Sr1, Sr2, Ss1, Ss2, St1, St2) of the inverter (21) for the current compensation unit to perform synchronous rectification operation, so that the switching element (Sr1) , Sr2, Ss1, Ss2, St1, St2)
- the conduction voltage generated when the switching element (Sr1, Sr2, Ss1, Ss2, St1, St2) is conducting can be lowered. Therefore, it is possible to suppress an error in the output voltage (Va (uvw)) output by the current compensator inverter (21) due to the conduction voltage, and to suppress the harmonics included in the power supply current (Is (uvw)).
- the components can be reduced more reliably.
- FIG. 16 shows the current flowing through the freewheeling diode when a Si—PiN (Silicon p-intrinsic-n) diode is provided as a freewheeling diode in antiparallel with the switching element (Sr1, Sr2, Ss1, Ss2, St1, St2).
- the switching element Sr1, Sr2, Ss1, Ss2, St1, St2
- the switching element Sr1, Sr2, Ss1, Ss2, St1, St2
- the peak value of the current flowing through the switching elements (Sr1, Sr2, Ss1, Ss2, St1, St2) is set to 12A (indicated by the symbol ip in FIG. 16), and the conduction voltage of a general diode is Vf and MOSFET. Let the conduction voltage be Vsd. Then, while Vf is 1.8V, Vsd is 1.1V as shown in the following equation (VI), assuming that the on-resistance is 100m ⁇ .
- the drive signal (Sd) is generated by the drive signal generation unit (27) so that the above equations (II) to (IV) are satisfied, so that the power supply current (Is (uvw)). Harmonic components contained in can be effectively reduced. Therefore, it is easy to adapt the power supply current (Is (uvw)) to IEC61000-3-2.
- the power supply current (Is (uvw) is compared with the case where the ratio is set to less than 1/3.
- the harmonic component contained in) can be reduced more reliably, and the compensation current (Ia (uvw)) can be controlled stably.
- the switching element (Sr1, Sr2, Ss1, Ss2, St1, St2) is used as an element whose main material is a wide bandgap semiconductor, and the on-resistance of the switching element (Sr1, Sr2, Ss1, Ss2, St1, St2) is set. Since it is set to 100 m ⁇ or less, it is easy to increase the switching speed of the switching element (Sr1, Sr2, Ss1, Ss2, St1, St2) and shorten the dead time. Therefore, it is easy to reduce the harmonic component contained in the power supply current (Is (uvw)).
- the dead time can be secured longer than when the frequency is higher than 100 kHz.
- Embodiment 2 the drive signal (Sd) is set based on the output voltage command value (Vid, Viq) so that the drive signal generation unit (27) causes the current compensation unit inverter (21) to perform synchronous rectification operation. Generated by a two-phase modulation method. Other configurations are the same as those in the first embodiment.
- FIG. 17 shows each case where the second carrier frequency is 16 kHz, 32 kHz, and 48 kHz. Based on the relationship shown in FIG. 17, it is estimated that the higher the second carrier frequency, the shorter the dead time needs to be in order to make the power supply current (Is (uvw)) conform to the standard.
- FIG. 18 shows a power supply current (power supply current) when a two-phase modulation method is adopted, the second carrier frequency is 48 kHz, the maximum input power of the power conversion unit (10) is 10 kW, and the dead times are 0.5 ⁇ sec and 1.0 ⁇ sec.
- Is (uvw)) shows the current value of the harmonic component.
- FIG. 19A shows the DC voltage (Vdc) and power supply current (Is (uvw)) when the second carrier frequency is 48 kHz, the maximum input power of the power converter (10) is 10 kW, and the dead time is 0.5 ⁇ sec.
- the load current (Io (uvw)) and the compensation current (Ia (uvw)) are shown.
- FIG. 19B is a diagram corresponding to FIG. 19A when the second carrier frequency is 48 kHz, the maximum input power of the power conversion unit (10) is 10 kW, and the dead time is 1.0 ⁇ sec.
- the harmonic component included in the power supply current (Is (uvw)) is reduced as compared with FIG. 19B.
- the inventors set the dead time of the drive signal (Sd) so that the following equation (VII) holds. It was derived that the harmonic component contained in the power supply current (Is (uvw)) can be effectively reduced, and the power supply current (Is (uvw)) can be easily adapted to the IEC61000-3-2.
- the second carrier frequency is fsw (kHz)
- the maximum input power of the power conversion unit (10) is Pmax (kW)
- the dead time of the drive signal (Sd) is Td ( ⁇ s).
- the drive signal generation unit (27) generates a drive signal (Sd) so that the above equation (VII) holds.
- the drive signal generation unit (27) generates a drive signal (Sd) so that the following equations (VIII) and (IX) are established in addition to the equation (VII).
- the second carrier frequency is fsw (kHz)
- the maximum input power of the power converter (10) is Pmax (kW)
- the dead time of the drive signal is Td ( ⁇ s)
- current compensation is defined as Lac (mH).
- the drive signal generation unit (27) has an output voltage command value (Vid, Viq) so that the ratio of the amplitude of the line voltage on the AC side to the DC voltage (Vdc) is 70% or more.
- the drive signal generation unit (27) has a modulation factor calculation unit (27a), a limiter (27b), and a PWM modulation unit (27c).
- the modulation factor calculation unit (27a) has a phase ( ⁇ ) and a modulation factor (ks) based on the output voltage command values (Vid, Viq) generated by the first and second current control units (26j, 26k). Is calculated.
- the modulation factor (ks) means the ratio of the amplitude (maximum value) of the line voltage on the AC side to the DC voltage (Vdc).
- Vi is an effective value of the line voltage on the AC side of the inverter (21) for the current compensation unit.
- Vi Vid / cos ⁇ ⁇ ⁇ ⁇ (XI)
- the limiter (27b) determines the modulation factor (ks) calculated by the modulation factor calculation unit (27a) when the modulation factor (ks) calculated by the modulation factor calculation unit (27a) is 0.7 or more. While the output is as it is, if the modulation factor (ks) is less than 0.7, 0.7 is output as the modulation factor (ks).
- the PWM modulation unit (27c) generates a drive signal (Sd) based on the phase ( ⁇ ) and modulation factor (ks) output by the limiter (27b).
- a second carrier wave is used to generate the drive signal (Sd) by the PWM modulation unit (27c).
- the second carrier frequency which is the carrier frequency of the second carrier wave, a frequency of 100 Hz or less is adopted.
- the inverter for the current compensation unit (21) is used when switching the phase to be modulated, as compared with the case where the modulation factor (ks) is less than 70%. It is possible to suppress a rapid change in the duty ratio of the switching elements (Sr1, Sr2, Ss1, Ss2, St1, St2). Therefore, the harmonic component contained in the power supply current (Is (uvw)) can be reduced more reliably.
- FIG. 21A shows the relationship between the duty ratio and the phase of the three switching elements (Sr1, Ss1, St1) of the upper arm of the inverter (21) for the current compensator when the modulation factor (ks) is 40%.
- FIG. 21B is a diagram corresponding to FIG. 21A when the modulation factor (ks) is 70%.
- the switching element (Sr1, The change in duty ratio of Ss1, St1) is small.
- the drive signal (Sd) is generated by the drive signal generation unit (27) so that the above equations (VII) to (IX) are satisfied, so that the power supply current (Is (uvw)). Harmonic components contained in can be effectively reduced. Therefore, it is easy to adapt the power supply current (Is (uvw)) to IEC61000-3-2.
- FIG. 22 shows a power conversion device (100) according to the third embodiment of the present disclosure.
- the drive signal generation unit (27) does not have a limiter (27b), and the PWM modulation unit (27c) is set to the modulation factor (ks) output by the modulation factor calculation unit (27a). Based on this, a drive signal (Sd) is generated.
- the compensation control unit (26) further includes a DC voltage command value calculation unit (28).
- the DC voltage command value calculation unit (28) sets the output voltage command value (Vid) of the d-axis component so that it is less than twice the average value of the line voltage on the AC side of the current compensation unit inverter (21). Calculate the DC voltage command value (Vdc *) based on this.
- the DC voltage command value calculation unit (28) has an average value calculation unit (28a) and a multiplication unit (28b).
- the mean value calculation unit (28a) calculates the mean value of the output voltage command value (Vid) of the d-axis component.
- the multiplication unit (28b) calculates the DC voltage command value (Vdc *) by multiplying the average value calculated by the mean value calculation unit (28a) by a predetermined gain (K VI ).
- the predetermined gain (K VI ) is set to 2 or less.
- the DC voltage command value (Vdc *) may be calculated based on the effective value of the line voltage on the side.
- the relationship between the effective value of the line voltage on the AC side of the current compensation unit inverter (21) and the output voltage command value (Vid) of the d-axis component is as shown in the above equation (XI).
- the DC voltage command value (Vdc *) is calculated so as to be less than twice the average value of the line voltage on the AC side of the current compensation unit inverter (21).
- the ratio of the amplitude of the line voltage on the AC side to the voltage (Vdc) is 70% or more.
- the harmonic generation source is connected to the first and second conductors (601,602) of the first to third conductors (601,602,603), but the first to third conductors (601,602,603) are connected. ) May be connected to only one of the conductors, or may be connected to all three conductors.
- the DC voltage command value calculation unit (28) sets the DC voltage command value (Vdc *) to be twice or less the average value of the line voltage on the AC side of the current compensation unit inverter (21). However, it may be calculated so as to be less than twice the basic frequency component of the line voltage on the AC side of the current compensating unit inverter (21). That is, the mean value calculation unit (28a) may calculate the fundamental frequency component of the output voltage command value (Vid) of the d-axis component.
- the drive signal generation unit (27) generates the drive signal (Sd) so as to satisfy the equations (II) to (IV), but the equation (II) is not satisfied and the equation (III) is satisfied. ) And the drive signal (Sd) may be generated so as to satisfy only the equation (IV). Further, the drive signal (Sd) may be generated so as to satisfy the equation (II) without satisfying both or one of the equation (III) and the equation (IV).
- the drive signal generation unit (27) generates the drive signal (Sd) so as to satisfy the equations (VII) to (IX), but the equation (VII) is not satisfied and the equation (VIII) is satisfied. And the drive signal (Sd) may be generated so as to satisfy only the equation (IX). Further, the drive signal (Sd) may be generated so as to satisfy the equation (VII) without satisfying both or one of the equation (VIII) and the equation (IX).
- the power conversion device (100) is provided in the air conditioning system (1), but it may be provided in another heat pump system for adjusting the temperature, humidity, and the like. Specifically, it may be provided in a heat pump system such as a heating / hot water supply system, a showcase that harmonizes the internal temperature, a refrigerator, a refrigerator, and a water heater.
- a heat pump system such as a heating / hot water supply system, a showcase that harmonizes the internal temperature, a refrigerator, a refrigerator, and a water heater.
- the present disclosure comprises a power conversion device including a power conversion unit that performs power conversion for three-phase AC output by an AC power supply and a current compensation unit that allows a compensation current to flow through the AC power supply. It is useful for heat pump systems equipped with it.
- Air conditioning system (heat pump system) 2 AC power supply 10 Power converter 11 Rectifier circuit 12 Inverter for power converter 12a 1st DC node 12b 2nd DC node 13 Reactor for power converter 14 Capacitor for power converter 20 Current compensation unit 21 Inverter for current compensation unit 21a, 21b DC node 22 Capacitor for current compensation unit 23 Reactor for current compensation unit 24 Filter for current compensator Reactor for 24a filter 24b filter capacitor 26 Compensation control unit 27 Drive signal generator 28 DC voltage command value calculation unit 29 Voltage command value calculation unit 100 Power conversion device 300 Indoor unit (harmonic source) 400 Outdoor fan (harmonic source) 601 First conductor 602 Second conductor 603 Third conductor Ia (uvw) Compensated current Io (uvw) Load current Vid, Viq Output voltage command value Vdc DC voltage Vdc * DC voltage command value Sr1, Sr2, Sr3, Sr4, Sr5, Sr6 switching Element Sd drive signal
Landscapes
- Engineering & Computer Science (AREA)
- Power Engineering (AREA)
- Physics & Mathematics (AREA)
- Electromagnetism (AREA)
- Inverter Devices (AREA)
- Control Of Ac Motors In General (AREA)
- General Induction Heating (AREA)
- Sorption Type Refrigeration Machines (AREA)
- Transforming Light Signals Into Electric Signals (AREA)
Abstract
Description
第1の態様では、式(1)が成り立たない場合に比べ、電源電流(Is(uvw))に含まれる高調波成分を効果的に低減できる。よって、IEC(International Electrotechnical Commission)が制定する高調波規格であるIEC61000-3-2に電源電流(Is(uvw))を適合させ易い。
第2の態様では、式(2)が成り立たない場合に比べ、電源電流(Is(uvw))に含まれる高調波成分を効果的に低減できる。よって、IECが制定する高調波規格であるIEC61000-3-2に電源電流(Is(uvw))を適合させ易い。
Td≦(34.00/fsw-0.145)・・・(4)
第3の態様では、式(3)及び式(4)の少なくとも一方が成り立たない場合に比べ、電源電流(Is(uvw))に含まれる高調波成分を効果的に低減できる。よって、IECが制定する高調波規格であるIEC61000-3-2に電源電流(Is(uvw))を適合させ易い。
Td≦(45.23/fsw-0.135)・・・(6)
第4の態様では、式(5)及び式(6)の少なくとも一方が成り立たない場合に比べ、電源電流(Is(uvw))に含まれる高調波成分を効果的に低減できる。よって、IECが制定する高調波規格であるIEC61000-3-2に電源電流(Is(uvw))を適合させ易い。
図1は、ヒートポンプシステムとしての空気調和システム(1)を示す。この空気調和システム(1)は、本開示の実施形態1に係る電力変換装置(100)と、ノイズフィルタ(200)と、高調波発生源としての室内機(300)と、高調波発生源としての室外ファン(400)と、圧縮機(500)とを備えている。
ここで、スイッチング周期は、スイッチング素子がオンオフを繰り返す周期である。本実施形態1では、PWM制御によりスイッチング素子が制御されるので、スイッチング周期は、PWM制御に用いる第1搬送波のキャリア周期となる。
本実施形態1では、駆動信号生成部(27)が、前記式(II)が成立するように、駆動信号(Sd)を生成する。
Td≦(34.00/fsw-0.145)・・・(IV)
図9Aは、駆動信号(Sd)のデッドタイムを0.5μs、第2キャリア周波数を16kHz、電力変換部(10)の最大入力電力を10kW、電流補償部用リアクトル(23)に流れる電流が0Aであるときの電流補償部用リアクトル(23)のインダクタンスを1.0mHとした場合の電源電流(Is(uvw))、補償電流(Ia(uvw))、及び負荷電流(Io(uvw))を示す。図9Bは、駆動信号(Sd)のデッドタイムを0.5μs、第2キャリア周波数を16kHz、電力変換部(10)の最大入力電力を10kW、電流補償部用リアクトル(23)に流れる電流が0Aであるときの電流補償部用リアクトル(23)のインダクタンスを2.2mHとした場合の図9A相当図である。図9Cは、駆動信号(Sd)のデッドタイムを0.5μs、第2キャリア周波数を16kHz、電力変換部(10)の最大入力電力を5kW、電流補償部用リアクトル(23)に流れる電流が0Aであるときの電流補償部用リアクトル(23)のインダクタンスを1.0mHとした場合の図9A相当図である。図9Dは、駆動信号(Sd)のデッドタイムを0.5μs、第2キャリア周波数を16kHz、電力変換部(10)の最大入力電力を5kW、電流補償部用リアクトル(23)に流れる電流が0Aであるときの電流補償部用リアクトル(23)のインダクタンスを2.2mHとした場合の図9A相当図である。
したがって、本実施形態1によると、前記式(II)~(IV)が成立するように、駆動信号生成部(27)に駆動信号(Sd)を生成させるので、電源電流(Is(uvw))に含まれる高調波成分を効果的に低減できる。よって、IEC61000-3-2に電源電流(Is(uvw))を適合させ易い。
本実施形態2では、駆動信号生成部(27)が、電流補償部用インバータ(21)に同期整流動作をさせるように、駆動信号(Sd)を出力電圧指令値(Vid,Viq)に基づいて二相変調方式により生成する。その他の構成は、実施形態1と同じである。
本実施形態2では、駆動信号生成部(27)が、前記式(VII)が成立するように、駆動信号(Sd)を生成する。
Td≦(45.23/fsw-0.135)・・・(IX)
また、本実施形態2では、駆動信号生成部(27)が、直流電圧(Vdc)に対する交流側の線間電圧の振幅の割合が70%以上となるように、出力電圧指令値(Vid,Viq)に基づいて駆動信号(Sd)を生成する。具体的には、図20に示すように、駆動信号生成部(27)は、変調率算出部(27a)と、リミッタ(27b)と、PWM変調部(27c)とを有している。
変調率(ks)をksとすると、ksは、以下の式(XI)及び(XII)に基づいて算出できる。ここで、Viは、電流補償部用インバータ(21)の交流側の線間電圧の実効値である。
図22は、本開示の実施形態3に係る電力変換装置(100)を示す。
前記実施形態1~3では、高調波発生源を、第1~第3の導線(601,602,603)のうち第1及び第2の導線(601,602)に接続したが、第1~第3の導線(601,602,603)のうち1つの導線だけに接続してもよいし、3つすべての導線に接続してもよい。
2 交流電源
10 電力変換部
11 整流回路
12 電力変換部用インバータ
12a 第1の直流ノード
12b 第2の直流ノード
13 電力変換部用リアクトル
14 電力変換部用コンデンサ
20 電流補償部
21 電流補償部用インバータ
21a,21b 直流ノード
22 電流補償部用コンデンサ
23 電流補償部用リアクトル
24 電流補償部用フィルタ
24a フィルタ用リアクトル
24b フィルタ用コンデンサ
26 補償制御部
27 駆動信号生成部
28 直流電圧指令値算出部
29 電圧指令値算出部
100 電力変換装置
300 室内機(高調波発生源)
400 室外ファン(高調波発生源)
601 第1の導線
602 第2の導線
603 第3の導線
Ia(uvw) 補償電流
Io(uvw) 負荷電流
Vid,Viq 出力電圧指令値
Vdc 直流電圧
Vdc* 直流電圧指令値
Sr1,Sr2,Sr3,Sr4,Sr5,Sr6 スイッチング素子
Sd 駆動信号
Claims (14)
- 交流電源(2)により出力される三相交流に対し、電力変換を行う電力変換部(10)と、
前記交流電源(2)に補償電流(Ia(uvw))を流す電流補償部(20)とを備えた電力変換装置であって、
前記電流補償部(20)は、
複数のスイッチング素子(Sr1,Sr2,Ss1,Ss2,St1,St2)を有する電流補償部用インバータ(21)と、
前記電流補償部用インバータ(21)の直流側ノード(21a,21b)間に接続される電流補償部用コンデンサ(22)と、
前記電流補償部用インバータ(21)の交流側と前記交流電源(2)との間に接続される電流補償部用リアクトル(23)と、
前記交流電源(2)から前記電力変換装置(100)に供給される電源電流(Is(uvw))に含まれる高調波成分を前記補償電流(Ia(uvw))によって低減するように、出力電圧指令値(Vid,Viq)を求める補償制御部(26)と、
前記スイッチング素子(Sr1,Sr2,Ss1,Ss2,St1,St2)を駆動する駆動信号(Sd)を前記出力電圧指令値(Vid,Viq)に基づいて三相変調方式により生成する駆動信号生成部(27)とを有し、
前記電流補償部用インバータ(21)は、前記スイッチング素子(Sr1,Sr2,Ss1,Ss2,St1,St2)のスイッチング動作により、前記電流補償部用リアクトル(23)を介して前記交流電源(2)に前記補償電流(Ia(uvw))を流し、
前記駆動信号(Sd)の生成に採用されるキャリア周波数をfsw(kHz)、前記電力変換部(10)の最大入力電力をPmax(kW)、前記駆動信号(Sd)のデッドタイムをTd(μs)とした場合に、下式(1)が成り立つことを特徴とする電力変換装置。
Td≦(34.00/fsw-0.145)(1.55-0.055*Pmax)・・・(1) - 交流電源(2)により出力される三相交流に対し、電力変換を行う電力変換部(10)と、
前記交流電源(2)に補償電流(Ia(uvw))を流す電流補償部(20)とを備えた電力変換装置であって、
前記電流補償部(20)は、
複数のスイッチング素子(Sr1,Sr2,Ss1,Ss2,St1,St2)を有する電流補償部用インバータ(21)と、
前記電流補償部用インバータ(21)の直流側ノード(21a,21b)間に接続される電流補償部用コンデンサ(22)と、
前記電流補償部用インバータ(21)の交流側と前記交流電源(2)との間に接続される電流補償部用リアクトル(23)と、
前記交流電源(2)から前記電力変換装置(100)に供給される電源電流(Is(uvw))に含まれる高調波成分を前記補償電流(Ia(uvw))によって低減するように、出力電圧指令値(Vid,Viq)を求める補償制御部(26)と、
前記スイッチング素子(Sr1,Sr2,Ss1,Ss2,St1,St2)を駆動する駆動信号(Sd)を前記出力電圧指令値(Vid,Viq)に基づいて二相変調方式により生成する駆動信号生成部(27)とを有し、
前記電流補償部用インバータ(21)は、前記スイッチング素子(Sr1,Sr2,Ss1,Ss2,St1,St2)のスイッチング動作により、前記電流補償部用リアクトル(23)を介して前記交流電源(2)に前記補償電流(Ia(uvw))を流し、
前記駆動信号(Sd)の生成に採用されるキャリア周波数をfsw(kHz)、前記電力変換部(10)の最大入力電力をPmax(kW)、前記駆動信号(Sd)のデッドタイムをTd(μs)とした場合に、下式(2)が成り立つことを特徴とする電力変換装置。
Td≦(45.23/fsw-0.135)(1.48-0.048*Pmax)・・・(2) - 交流電源(2)により出力される三相交流に対し、電力変換を行う電力変換部(10)と、
前記交流電源(2)に補償電流(Ia(uvw))を流す電流補償部(20)とを備えた電力変換装置であって、
前記電流補償部(20)は、
複数のスイッチング素子(Sr1,Sr2,Ss1,Ss2,St1,St2)を有する電流補償部用インバータ(21)と、
前記電流補償部用インバータ(21)の直流側ノード(21a,21b)間に接続される電流補償部用コンデンサ(22)と、
前記電流補償部用インバータ(21)の交流側と前記交流電源(2)との間に接続される電流補償部用リアクトル(23)と、
前記交流電源(2)から前記電力変換装置(100)に供給される電源電流(Is(uvw))に含まれる高調波成分を前記補償電流(Ia(uvw))によって低減するように、出力電圧指令値(Vid,Viq)を求める補償制御部(26)と、
前記スイッチング素子(Sr1,Sr2,Ss1,Ss2,St1,St2)を駆動する駆動信号(Sd)を前記出力電圧指令値(Vid,Viq)に基づいて三相変調方式により生成する駆動信号生成部(27)とを有し、
前記電流補償部用インバータ(21)は、前記スイッチング素子(Sr1,Sr2,Ss1,Ss2,St1,St2)のスイッチング動作により、前記電流補償部用リアクトル(23)を介して前記交流電源(2)に前記補償電流(Ia(uvw))を流し、
前記駆動信号(Sd)の生成に採用されるキャリア周波数をfsw(kHz)、前記電力変換部(10)の最大入力電力をPmax(kW)、前記駆動信号(Sd)のデッドタイムをTd(μs)、前記電流補償部用リアクトル(23)に流れる電流が0Aであるときの前記電流補償部用リアクトル(23)のインダクタンスをLac(mH)とした場合に、下式(3)及び下式(4)が成り立つことを特徴とする電力変換装置。
Lac≦16/Pmax・・・(3)
Td≦(34.00/fsw-0.145)・・・(4) - 交流電源(2)により出力される三相交流に対し、電力変換を行う電力変換部(10)と、
前記交流電源(2)に補償電流(Ia(uvw))を流す電流補償部(20)とを備えた電力変換装置であって、
前記電流補償部(20)は、
複数のスイッチング素子(Sr1,Sr2,Ss1,Ss2,St1,St2)を有する電流補償部用インバータ(21)と、
前記電流補償部用インバータ(21)の直流側ノード(21a,21b)間に接続される電流補償部用コンデンサ(22)と、
前記電流補償部用インバータ(21)の交流側と前記交流電源(2)との間に接続される電流補償部用リアクトル(23)と、
前記交流電源(2)から前記電力変換装置(100)に供給される電源電流(Is(uvw))に含まれる高調波成分を前記補償電流(Ia(uvw))によって低減するように、出力電圧指令値(Vid,Viq)を求める補償制御部(26)と、
前記スイッチング素子(Sr1,Sr2,Ss1,Ss2,St1,St2)を駆動する駆動信号(Sd)を前記出力電圧指令値(Vid,Viq)に基づいて二相変調方式により生成する駆動信号生成部(27)とを有し、
前記電流補償部用インバータ(21)は、前記スイッチング素子(Sr1,Sr2,Ss1,Ss2,St1,St2)のスイッチング動作により、前記電流補償部用リアクトル(23)を介して前記交流電源(2)に前記補償電流(Ia(uvw))を流し、
前記駆動信号(Sd)の生成に採用されるキャリア周波数をfsw(kHz)、前記電力変換部(10)の最大入力電力をPmax(kW)、前記駆動信号(Sd)のデッドタイムをTd(μs)、前記電流補償部用リアクトル(23)に流れる電流が0Aであるときの前記電流補償部用リアクトル(23)のインダクタンスをLac(mH)とした場合に、下式(5)及び下式(6)が成り立つことを特徴とする電力変換装置。
Lac≦16/Pmax・・・(5)
Td≦(45.23/fsw-0.135)・・・(6) - 請求項3又は4に記載の電力変換装置において、
前記電流補償部用リアクトル(23)に流れる電流が0Aであるときの前記電流補償部用リアクトル(23)のインダクタンスに対する前記電流補償部用リアクトル(23)に流れる電流がピーク電流であるときの前記電流補償部用リアクトル(23)のインダクタンスの比率が1/3以上に設定されていることを特徴とする電力変換装置。 - 請求項1~5のいずれか1項に記載の電力変換装置において、
前記交流電源(2)と前記電流補償部用リアクトル(23)との間には、前記電流補償部用リアクトル(23)よりもインダクタンスが小さいフィルタ用リアクトル(24a)と、フィルタ用コンデンサ(24b)とを有し、共振周波数が4kHz以上に設定されたフィルタ(24)が介在していることを特徴とする電力変換装置。 - 請求項2又は4に記載の電力変換装置において、
前記駆動信号生成部(27)は、前記電流補償部用インバータ(21)の直流側ノード(21a,21b)間の直流電圧(Vdc)に対する交流側の線間電圧の振幅の割合が70%以上となるように、前記出力電圧指令値(Vid,Viq)に基づいて前記駆動信号(Sd)を生成することを特徴とする電力変換装置。 - 請求項2又は4に記載の電力変換装置において、
前記補償制御部(26)は、前記電流補償部用インバータ(21)の直流側ノード(21a,21b)間の直流電圧(Vdc)、及び直流電圧指令値(Vdc*)に基づいて、前記出力電圧指令値(Vid,Viq)を算出する電圧指令値算出部(29)と、
前記電流補償部用インバータ(21)の交流側の線間電圧の平均値又は基本周波数成分の2倍以下となるように、前記出力電圧指令値(Vid,Viq)に基づいて前記直流電圧指令値(Vdc*)を算出する直流電圧指令値算出部(28)とを備えることを特徴とする電力変換装置。 - 請求項1~8のいずれか1項に記載の電力変換装置において、
前記電力変換部(10)は、
前記三相交流を直流に整流する整流回路(11)と、
前記直流を交流に変換する電力変換部用インバータ(12)と、
前記電力変換部用インバータ(12)の直流側ノード(12a,12b)間に接続され、前記整流回路(11)の出力電圧の変動を許容する電力変換部用コンデンサ(14)と、
前記交流電源(2)と前記電力変換部用コンデンサ(14)の一端との間に接続された電力変換部用リアクトル(13)とを有することを特徴とする電力変換装置。 - 請求項9に記載の電力変換装置において、
前記電流補償部用コンデンサ(22)の容量は、前記電力変換部用コンデンサ(14)の容量よりも大きいことを特徴とする電力変換装置。 - 請求項1~10のいずれか1項に記載の電力変換装置において、
前記電流補償部用インバータ(21)は、3つのレグを構成する6つのユニポーラトランジスタを前記スイッチング素子(Sr1,Sr2,Ss1,Ss2,St1,St2)として備え、
前記駆動信号生成部(27)は、前記電流補償部用インバータ(21)に同期整流動作をさせるように前記駆動信号(Sd)を生成することを特徴とする電力変換装置。 - 請求項11に記載の電力変換装置において、
前記スイッチング素子(Sr1,Sr2,Ss1,Ss2,St1,St2)は、ワイドバンドギャップ半導体を主材料とした素子であり、
前記スイッチング素子(Sr1,Sr2,Ss1,Ss2,St1,St2)のオン抵抗は、100mΩ以下であることを特徴とする電力変換装置。 - 請求項1~12のいずれか1項に記載の電力変換装置において、
前記キャリア周波数は、100kHz以下であることを特徴とする電力変換装置。 - 請求項1~13のいずれか1項に記載の電力変換装置を備えたヒートポンプシステムであって、
前記三相交流は、前記電力変換部(10)に3本の導線(601,602,603)を介して入力され、
前記ヒートポンプシステム(1)は、前記3本の導線(601,602,603)の少なくとも1本の導線(601,602)の電流に高調波を発生させる高調波発生源(300,400)をさらに備えていることを特徴とするヒートポンプシステム。
Priority Applications (5)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
EP21875701.1A EP4213371A4 (en) | 2020-09-29 | 2021-09-29 | POWER CONVERTER AND HEAT PUMP SYSTEM SUPPLIED THEREWITH |
BR112023005598A BR112023005598A2 (pt) | 2020-09-29 | 2021-09-29 | Conversor de energia e sistema de bomba térmica |
AU2021352737A AU2021352737B2 (en) | 2020-09-29 | 2021-09-29 | Power converter and heat pump system provided therewith |
CN202180066052.7A CN116235406A (zh) | 2020-09-29 | 2021-09-29 | 功率转换装置及包括该功率转换装置的热泵系统 |
US18/126,892 US20230246561A1 (en) | 2020-09-29 | 2023-03-27 | Power converter and heat pump system provided therewith |
Applications Claiming Priority (2)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
JP2020-163992 | 2020-09-29 | ||
JP2020163992A JP7048909B1 (ja) | 2020-09-29 | 2020-09-29 | 電力変換装置及びそれを備えたヒートポンプシステム |
Related Child Applications (1)
Application Number | Title | Priority Date | Filing Date |
---|---|---|---|
US18/126,892 Continuation US20230246561A1 (en) | 2020-09-29 | 2023-03-27 | Power converter and heat pump system provided therewith |
Publications (1)
Publication Number | Publication Date |
---|---|
WO2022071401A1 true WO2022071401A1 (ja) | 2022-04-07 |
Family
ID=80949225
Family Applications (1)
Application Number | Title | Priority Date | Filing Date |
---|---|---|---|
PCT/JP2021/035881 WO2022071401A1 (ja) | 2020-09-29 | 2021-09-29 | 電力変換装置及びそれを備えたヒートポンプシステム |
Country Status (7)
Country | Link |
---|---|
US (1) | US20230246561A1 (ja) |
EP (1) | EP4213371A4 (ja) |
JP (1) | JP7048909B1 (ja) |
CN (1) | CN116235406A (ja) |
AU (1) | AU2021352737B2 (ja) |
BR (1) | BR112023005598A2 (ja) |
WO (1) | WO2022071401A1 (ja) |
Families Citing this family (1)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
JP2024045981A (ja) * | 2022-09-22 | 2024-04-03 | 東芝キヤリア株式会社 | 高調波抑制装置 |
Citations (5)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
JP2012050177A (ja) * | 2010-08-24 | 2012-03-08 | Mitsubishi Electric Corp | 高調波抑制装置 |
JP2015092813A (ja) | 2013-09-30 | 2015-05-14 | ダイキン工業株式会社 | 電力変換装置 |
JP2016116330A (ja) * | 2014-12-15 | 2016-06-23 | ダイキン工業株式会社 | 並列形アクティブフィルタの制御装置 |
JP2016163406A (ja) * | 2015-02-27 | 2016-09-05 | ジョンソンコントロールズ ヒタチ エア コンディショニング テクノロジー(ホンコン)リミテッド | アクティブフィルタ、及びそれを用いたモータ駆動装置、並びに冷凍装置 |
JP2018148757A (ja) * | 2017-03-09 | 2018-09-20 | 三菱重工サーマルシステムズ株式会社 | アクティブフィルタ |
Family Cites Families (2)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
PL219747B1 (pl) * | 2011-08-02 | 2015-07-31 | Akademia Górniczo Hutnicza Im Stanisława Staszica W Krakowie | Sposób sterowania zasilaczem rezonansowym i zasilacz rezonansowy ze sterownikiem |
WO2015001612A1 (ja) * | 2013-07-02 | 2015-01-08 | 三菱電機株式会社 | モータ制御装置 |
-
2020
- 2020-09-29 JP JP2020163992A patent/JP7048909B1/ja active Active
-
2021
- 2021-09-29 WO PCT/JP2021/035881 patent/WO2022071401A1/ja active Application Filing
- 2021-09-29 CN CN202180066052.7A patent/CN116235406A/zh active Pending
- 2021-09-29 EP EP21875701.1A patent/EP4213371A4/en active Pending
- 2021-09-29 AU AU2021352737A patent/AU2021352737B2/en active Active
- 2021-09-29 BR BR112023005598A patent/BR112023005598A2/pt unknown
-
2023
- 2023-03-27 US US18/126,892 patent/US20230246561A1/en active Pending
Patent Citations (5)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
JP2012050177A (ja) * | 2010-08-24 | 2012-03-08 | Mitsubishi Electric Corp | 高調波抑制装置 |
JP2015092813A (ja) | 2013-09-30 | 2015-05-14 | ダイキン工業株式会社 | 電力変換装置 |
JP2016116330A (ja) * | 2014-12-15 | 2016-06-23 | ダイキン工業株式会社 | 並列形アクティブフィルタの制御装置 |
JP2016163406A (ja) * | 2015-02-27 | 2016-09-05 | ジョンソンコントロールズ ヒタチ エア コンディショニング テクノロジー(ホンコン)リミテッド | アクティブフィルタ、及びそれを用いたモータ駆動装置、並びに冷凍装置 |
JP2018148757A (ja) * | 2017-03-09 | 2018-09-20 | 三菱重工サーマルシステムズ株式会社 | アクティブフィルタ |
Non-Patent Citations (1)
Title |
---|
See also references of EP4213371A4 |
Also Published As
Publication number | Publication date |
---|---|
EP4213371A1 (en) | 2023-07-19 |
AU2021352737A9 (en) | 2024-10-10 |
JP7048909B1 (ja) | 2022-04-06 |
CN116235406A (zh) | 2023-06-06 |
JP2022060601A (ja) | 2022-04-15 |
AU2021352737A1 (en) | 2023-06-01 |
EP4213371A4 (en) | 2024-10-02 |
AU2021352737B2 (en) | 2024-03-14 |
US20230246561A1 (en) | 2023-08-03 |
BR112023005598A2 (pt) | 2023-05-09 |
Similar Documents
Publication | Publication Date | Title |
---|---|---|
JP4971750B2 (ja) | 電源回路、及びこれに用いる制御回路 | |
KR101594662B1 (ko) | 전력 변환 장치 | |
US9847735B2 (en) | Power conversion device, motor drive control apparatus including the power conversion device, air blower and compressor including the motor drive control apparatus, and air conditioner including the air blower or the compressor | |
US10804811B2 (en) | Control device for direct power converter for reduction of harmonic distortion | |
JP5873716B2 (ja) | モータ制御装置 | |
WO2012049706A1 (ja) | 3相交流直流変換装置及び3相交流直流変換装置を用いた空気調和機 | |
WO2013046728A1 (ja) | 電力変換装置 | |
JP5717838B2 (ja) | 電力変換装置 | |
JP5451797B2 (ja) | 電力変換装置 | |
US20230246561A1 (en) | Power converter and heat pump system provided therewith | |
US11736025B2 (en) | Electrical power conversion apparatus | |
Singh et al. | Voltage controlled PFC SEPIC converter fed PMBLDCM drive for an air-conditioner | |
RU2817330C1 (ru) | Преобразователь мощности и система теплового насоса, снабженная им | |
KR20200053925A (ko) | 전력 변환 장치, 이를 포함하는 압축기 및 그 제어 방법 | |
KR20180085999A (ko) | 고조파 제어 전원 장치, 이를 포함하는 공기 조화기 및 고조파 제어 방법 | |
JP2019057979A (ja) | モータ制御装置及び空調機 | |
JP4517762B2 (ja) | スイッチング制御方法、整流装置及び駆動システム | |
JP5838554B2 (ja) | 電力変換装置 | |
KR102015440B1 (ko) | 전력 변환 장치 및 이를 포함하는 공기 조화기 | |
JP6513564B2 (ja) | 共振回避可能なインバータ装置 | |
US20240011663A1 (en) | Air conditioner | |
KR102069067B1 (ko) | 리플 저감 정류부를 포함하는 전력 변환 장치 및 이를 포함하는 공기 조화기 | |
WO2023095265A1 (ja) | 電力変換装置、モータ駆動装置および冷凍サイクル適用機器 | |
KR101878146B1 (ko) | 전력 변환 장치 및 이를 포함하는 공기 조화기 | |
WO2020084970A1 (ja) | モータ制御装置及び空調機 |
Legal Events
Date | Code | Title | Description |
---|---|---|---|
121 | Ep: the epo has been informed by wipo that ep was designated in this application |
Ref document number: 21875701 Country of ref document: EP Kind code of ref document: A1 |
|
WWE | Wipo information: entry into national phase |
Ref document number: 202317024507 Country of ref document: IN |
|
REG | Reference to national code |
Ref country code: BR Ref legal event code: B01A Ref document number: 112023005598 Country of ref document: BR |
|
ENP | Entry into the national phase |
Ref document number: 2021875701 Country of ref document: EP Effective date: 20230412 |
|
WWE | Wipo information: entry into national phase |
Ref document number: 2021352737 Country of ref document: AU |
|
NENP | Non-entry into the national phase |
Ref country code: DE |
|
ENP | Entry into the national phase |
Ref document number: 112023005598 Country of ref document: BR Kind code of ref document: A2 Effective date: 20230327 |
|
ENP | Entry into the national phase |
Ref document number: 2021352737 Country of ref document: AU Date of ref document: 20210929 Kind code of ref document: A |