WO2021182037A1 - アンテナモジュールおよびそれを搭載する通信装置 - Google Patents

アンテナモジュールおよびそれを搭載する通信装置 Download PDF

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Publication number
WO2021182037A1
WO2021182037A1 PCT/JP2021/005805 JP2021005805W WO2021182037A1 WO 2021182037 A1 WO2021182037 A1 WO 2021182037A1 JP 2021005805 W JP2021005805 W JP 2021005805W WO 2021182037 A1 WO2021182037 A1 WO 2021182037A1
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Prior art keywords
antenna module
dielectric substrate
radiating element
conductive member
feeding element
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Ceased
Application number
PCT/JP2021/005805
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English (en)
French (fr)
Japanese (ja)
Inventor
航大 荒井
良 小村
薫 須藤
久夫 早藤
弘嗣 森
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Murata Manufacturing Co Ltd
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Murata Manufacturing Co Ltd
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Publication date
Application filed by Murata Manufacturing Co Ltd filed Critical Murata Manufacturing Co Ltd
Priority to JP2022505868A priority Critical patent/JP7294525B2/ja
Priority to CN202180020616.3A priority patent/CN115280598B/zh
Publication of WO2021182037A1 publication Critical patent/WO2021182037A1/ja
Priority to US17/939,956 priority patent/US12283761B2/en
Anticipated expiration legal-status Critical
Ceased legal-status Critical Current

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    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q21/00—Antenna arrays or systems
    • H01Q21/06—Arrays of individually energised antenna units similarly polarised and spaced apart
    • H01Q21/061—Two dimensional planar arrays
    • H01Q21/065—Patch antenna array
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q5/00—Arrangements for simultaneous operation of antennas on two or more different wavebands, e.g. dual-band or multi-band arrangements
    • H01Q5/30—Arrangements for providing operation on different wavebands
    • H01Q5/378—Combination of fed elements with parasitic elements
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q1/00—Details of, or arrangements associated with, antennas
    • H01Q1/12—Supports; Mounting means
    • H01Q1/22—Supports; Mounting means by structural association with other equipment or articles
    • H01Q1/2283—Supports; Mounting means by structural association with other equipment or articles mounted in or on the surface of a semiconductor substrate as a chip-type antenna or integrated with other components into an IC package
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q1/00—Details of, or arrangements associated with, antennas
    • H01Q1/36—Structural form of radiating elements, e.g. cone, spiral, umbrella; Particular materials used therewith
    • H01Q1/38—Structural form of radiating elements, e.g. cone, spiral, umbrella; Particular materials used therewith formed by a conductive layer on an insulating support
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q9/00—Electrically-short antennas having dimensions not more than twice the operating wavelength and consisting of conductive active radiating elements
    • H01Q9/04—Resonant antennas
    • H01Q9/0407—Substantially flat resonant element parallel to ground plane, e.g. patch antenna
    • H01Q9/0414—Substantially flat resonant element parallel to ground plane, e.g. patch antenna in a stacked or folded configuration
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q9/00—Electrically-short antennas having dimensions not more than twice the operating wavelength and consisting of conductive active radiating elements
    • H01Q9/04—Resonant antennas
    • H01Q9/0407—Substantially flat resonant element parallel to ground plane, e.g. patch antenna
    • H01Q9/0442—Substantially flat resonant element parallel to ground plane, e.g. patch antenna with particular tuning means
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B7/00—Radio transmission systems, i.e. using radiation field
    • H04B7/02—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas
    • H04B7/04—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas
    • H04B7/0413—MIMO systems
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B7/00—Radio transmission systems, i.e. using radiation field
    • H04B7/02—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas
    • H04B7/04—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas
    • H04B7/06—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station

Definitions

  • the present disclosure relates to an antenna module and a communication device on which the antenna module is mounted, and more specifically, to a technique for realizing reduction of reflection loss over a wide band and ensuring wide directivity in the antenna module.
  • Patent Document 1 discloses an antenna module in which a feeding element and a high-frequency semiconductor element are integrally mounted on a dielectric substrate.
  • the antenna module disclosed in International Publication No. 2016/066969 (Patent Document 1) is mounted on a mobile terminal such as a mobile phone or a smartphone, for example.
  • the reflection characteristic is widened due to the decrease in the effective permittivity, but on the other hand, the peak gain becomes large and the directivity changes to sharp, so that the beam width that can achieve a predetermined gain becomes narrow. It may end up. That is, when lowering the effective permittivity, there is a trade-off relationship between reducing the reflection loss over a wide band and ensuring a wide directivity.
  • the present disclosure has been made to solve such a problem, and an object thereof is to realize reduction of reflection loss over a wide band and ensuring wide directivity in an antenna module.
  • the antenna module includes a first dielectric substrate on which a first radiating element is formed, a second dielectric substrate on which a ground electrode is formed, and a conductive member.
  • the second dielectric substrate is arranged so as to face the first dielectric substrate.
  • the conductive member is arranged around the first radiating element when viewed in a plan view from the normal direction of the first radiating element.
  • a low dielectric constant layer having a dielectric constant lower than that of the first dielectric substrate is formed between the first dielectric substrate and the second dielectric substrate, and the conductive member is formed on the low dielectric constant layer. ing.
  • the antenna module includes a first dielectric substrate on which the first radiating element is formed, a second dielectric substrate on which the ground electrode is formed, and a conductive member.
  • the second dielectric substrate is arranged so as to face the first dielectric substrate.
  • the conductive member is arranged around the first radiating element when viewed in a plan view from the normal direction of the first radiating element.
  • An air layer is formed between the first dielectric substrate and the second dielectric substrate, and the conductive member is formed in the air layer.
  • the dielectric substrate forming the antenna module is composed of a first dielectric substrate including a radiation element and a second dielectric substrate including a ground electrode, and two dielectrics are used.
  • a low dielectric constant layer (air layer) having a dielectric constant lower than that of the first dielectric substrate is formed between the substrates.
  • FIG. 5 is a block diagram of a communication device to which the antenna module according to the first embodiment is applied. It is a top view and a cross-sectional view of the antenna module which concerns on Embodiment 1.
  • FIG. It is a figure for demonstrating the antenna characteristic of the antenna module which concerns on Embodiment 1, and the antenna module of the comparative example. It is a figure for demonstrating the gain characteristic in an antenna module. It is a figure for demonstrating the directivity of an antenna module. It is sectional drawing of the antenna module which concerns on Embodiment 2.
  • FIG. It is a figure which shows the detail of the vicinity of a conductive member when a resist is applied to a dielectric substrate. It is a figure for demonstrating the antenna characteristic of the antenna module which concerns on Embodiment 3.
  • FIG. It is a figure for demonstrating the antenna characteristic of the antenna module which concerns on Embodiment 4.
  • FIG. It is sectional drawing of the antenna module which concerns on Embodiment 5.
  • FIG. FIG. 5 is a plan view and a cross-sectional view of the antenna module according to the sixth embodiment. It is a figure for demonstrating the reflection loss of the second harmonic in the antenna module of FIG. It is a figure for demonstrating the modification of the arrangement of the conductive member. It is a figure for demonstrating the modification of the low dielectric constant layer.
  • FIG. 1 is an example of a block diagram of a communication device 10 to which the antenna module 100 according to the first embodiment is applied.
  • the communication device 10 is, for example, a mobile phone, a mobile terminal such as a smartphone or a tablet, a personal computer having a communication function, a base station, or the like.
  • An example of the frequency band of the radio wave used for the antenna module 100 according to the present embodiment is a radio wave in the millimeter wave band having a center frequency of, for example, 28 GHz, 39 GHz, 60 GHz, etc., but radio waves in frequency bands other than the above are also available. Applicable.
  • the communication device 10 includes an antenna module 100 and a BBIC 200 constituting a baseband signal processing circuit.
  • the antenna module 100 includes an RFIC 110, which is an example of a power feeding circuit, and an antenna device 120.
  • the communication device 10 up-converts the signal transmitted from the BBIC 200 to the antenna module 100 into a high-frequency signal and radiates it from the antenna device 120, and down-converts the high-frequency signal received by the antenna device 120 to process the signal at the BBIC 200. do.
  • FIG. 1 shows an example in which the antenna device 120 is formed by a plurality of feeding elements 121 arranged in a two-dimensional array, but the feeding elements 121 do not necessarily have to be a plurality, and one feeding element 121 is required.
  • the antenna device 120 may be formed by the feeding element 121. Further, it may be a one-dimensional array in which a plurality of power feeding elements 121 are arranged in a row.
  • the feeding element 121 is a patch antenna having a substantially square flat plate shape.
  • the RFIC 110 includes switches 111A to 111D, 113A to 113D, 117, power amplifiers 112AT to 112DT, low noise amplifiers 112AR to 112DR, attenuators 114A to 114D, phase shifters 115A to 115D, and signal synthesizer / demultiplexer. It includes 116, a mixer 118, and an amplifier circuit 119.
  • the switches 111A to 111D and 113A to 113D are switched to the power amplifiers 112AT to 112DT side, and the switch 117 is connected to the transmitting side amplifier of the amplifier circuit 119.
  • the switches 111A to 111D and 113A to 113D are switched to the low noise amplifiers 112AR to 112DR side, and the switch 117 is connected to the receiving side amplifier of the amplifier circuit 119.
  • the signal transmitted from the BBIC 200 is amplified by the amplifier circuit 119 and up-converted by the mixer 118.
  • the transmitted signal which is an up-converted high-frequency signal, is demultiplexed by the signal synthesizer / demultiplexer 116, passes through four signal paths, and is fed to different power feeding elements 121.
  • the directivity of the antenna device 120 can be adjusted by individually adjusting the degree of phase shift of the phase shifters 115A to 115D arranged in each signal path.
  • the received signal which is a high-frequency signal received by each feeding element 121, passes through four different signal paths and is combined by the signal synthesizer / demultiplexer 116.
  • the combined received signal is down-converted by the mixer 118, amplified by the amplifier circuit 119, and transmitted to the BBIC 200.
  • the RFIC 110 is formed as, for example, a one-chip integrated circuit component including the above circuit configuration.
  • the devices switch, power amplifier, low noise amplifier, attenuator, phase shifter
  • corresponding to each power feeding element 121 in the RFIC 110 may be formed as an integrated circuit component of one chip for each corresponding power feeding element 121. ..
  • FIG. 2 a plan view of the antenna module 100 is shown in the upper row (FIG. 2 (a)), and a cross-sectional view taken along line II-II of the plan view is shown in the lower row (FIG. 2 (b)). There is.
  • the antenna module 100 includes a dielectric substrate 130, 140, a feeding wiring 150, conductive members 170, 180, and a ground electrode GND, in addition to the feeding element 121 and RFIC 110.
  • the positive direction of the Z axis in each figure may be referred to as the upper surface side, and the negative direction may be referred to as the lower surface side.
  • a part of the dielectric substrate 130 is omitted in order to make the internal configuration easy to see.
  • the dielectric substrates 130 and 140 are, for example, a multilayer resin substrate formed by laminating a plurality of low temperature co-fired ceramics (LTCC: Low Temperature Co-fired Ceramics) multilayer substrates and resin layers composed of resins such as epoxy and polyimide. , A multilayer resin substrate formed by laminating a plurality of resin layers composed of a liquid crystal polymer (LCP) having a lower dielectric constant, and formed by laminating a plurality of resin layers composed of a fluorine-based resin. A multilayer resin substrate or a ceramic multilayer substrate other than LTCC.
  • the dielectric substrates 130 and 140 do not necessarily have to have a multi-layer structure, and may be a single-layer substrate. In the antenna module 100 shown in FIG. 2, a case where the dielectric substrate 130 is formed of polyimide and the dielectric substrate 140 is formed of LTCC will be described as an example, but the dielectric substrate 130 and the dielectric substrate 140 will be described as an example. May be made of the same material
  • the dielectric substrate 130 and the dielectric substrate 140 have a rectangular flat plate shape, and the back surface 132 of the dielectric substrate 130 and the front surface 141 of the dielectric substrate 140 are arranged so as to face each other at a predetermined interval. ing. That is, an air layer 185 is formed between the dielectric substrate 130 and the dielectric substrate 140. Conductive members 170 and 180 are formed in the air layer 185, and the dielectric substrate 130 and the dielectric substrate 140 are connected via the conductive members 170 and 180.
  • a substantially square feeding element 121 is arranged on the inner layer of the dielectric substrate 130 or the surface 131 on the upper surface side.
  • a ground electrode GND is arranged on the dielectric substrate 140.
  • Conductive members 170 and 180 are connected to the surface 141 on the upper surface side of the dielectric substrate 140, and RFIC 110 is arranged on the back surface 142 on the lower surface side via solder bumps 160.
  • the power supply wiring 150 penetrates the ground electrode GND from the RFIC 110, and reaches the power supply point SP1 of the power supply element 121 via the conductive member 180.
  • the conductive member 180 functions as a connection electrode for connecting the portion of the power feeding wiring 150 in the dielectric substrate 130 and the portion in the dielectric substrate 140. With such a configuration, the high frequency signal supplied from the RFIC 110 is transmitted to the feeding point SP1 of the feeding element 121 via the feeding wiring 150.
  • the feeding point SP1 is arranged at a position offset in the negative direction of the X axis in FIG. 2 from the center of the feeding element 121 (intersection of diagonal lines).
  • the feeding element 121 radiates a radio wave having the polarization direction in the X-axis direction.
  • the portion of the power feeding wiring 150 inside the dielectric substrate 130 is not an essential configuration, and when the thickness of the dielectric substrate 130 is relatively thin, capacitive coupling between the conductive member 180 and the feeding element 121 is used. Then, the high frequency signal may be supplied to the feeding element 121 in a non-contact manner.
  • the conductive member 170 is any device or member formed including the conductive material.
  • the conductive member 170 may be, for example, a solder bump described later in the second embodiment (FIG. 6) and / or an electrode connecting material such as a columnar conductor column, a conductor pin, or a plated electrode (terminal). good.
  • the conductive member 170 may be an electronic component (resistor, capacitor, etc.) as described later in the ninth embodiment (FIG. 22).
  • the conductive member 170 is a rectangular conductive material having a size smaller than that of the feeding element 121.
  • a plurality of conductive members 170 are arranged around the feeding element 121 apart from the feeding element 121. There is. More specifically, the plurality of conductive members 170 are arranged at intervals from each other along each side of the rectangular power feeding element 121.
  • the conductive member 170 is provided to prevent a part of the electromagnetic field generated between the power feeding element 121 and the ground electrode GND. Therefore, when the wavelength of the radio wave radiated from the feeding element 121 is ⁇ , the conductive member 170 is preferably arranged within a range of ⁇ / 4 from the feeding element 121. As shown in FIG. 2B, the conductive member 170 may be directly connected to the ground electrode GND, or may be indirectly connected by capacitive coupling.
  • the antenna module as described above may be used in a mobile terminal such as a mobile phone or a smartphone.
  • mobile terminals have been required to realize further widening of antenna characteristics such as reflection loss and gain, as well as demands for miniaturization and thinning.
  • an antenna module using a flat plate-shaped patch antenna a method of increasing the distance between the radiation element and the ground electrode or an antenna module is formed in order to realize a wide band of reflection loss.
  • a method of reducing the effective dielectric constant of a dielectric substrate is known.
  • the thickness of the entire antenna module becomes thick as a result, which is a factor that hinders the reduction and miniaturization of the antenna module. obtain.
  • the peak gain becomes large and the directivity can be sharp in addition to the widening of the reflection loss.
  • Increasing the peak gain itself is preferable because the radiable distance of radio waves increases.
  • the space where a predetermined gain can be secured may be narrowed. Then, there is a possibility that the desired gain cannot be realized in the target spatial range.
  • the feeding element 121 and the ground electrode GND are formed on different dielectric substrates 130 and 140, respectively, and an air layer 185 is formed between the dielectric substrate 130 and the dielectric substrate 140. It is formed.
  • the permittivity of air is lower than the permittivity of the dielectric substrates 130 and 140. Therefore, by forming the air layer 185 on the dielectric substrate as in the antenna module 100, the effective dielectric constant between the feeding element 121 and the ground electrode GND can be reduced as compared with the case where the air layer 185 is not provided. can. As a result, the reflection loss can be reduced and the wide band of the reflection loss can be realized.
  • the conductive member 170 is arranged around the feeding element 121 when viewed in a plan view in the air layer 185.
  • the antenna module 100 functions as an antenna by coupling the feeding element 121 and the ground electrode GND with an electromagnetic field, and an electromagnetic field is generated between the feeding element 121 and the ground electrode GND.
  • the lines of electric force generated at this time are mainly between the side of the feeding element 121 orthogonal to the polarization direction (that is, the side parallel to the Y axis in FIG. 2) and the ground electrode GND, the arrow in FIG. It occurs like AR1.
  • the conductive member 170 by arranging the conductive member 170 at a position away from the power feeding element 121, a part of the generated electromagnetic field is captured by the conductive member 170. As a result, although the peak gain at the resonance frequency is slightly reduced, it is possible to suppress the decrease in gain in a wide range. Therefore, it is possible to suppress narrowing of directivity while maintaining a wide band of reflection loss.
  • FIG. 3 is a diagram for explaining the antenna characteristics of the antenna module 100 according to the first embodiment.
  • the antenna characteristics of the antenna module 100 according to the first embodiment will be described in comparison with the antenna characteristics of the two comparative examples.
  • FIG. 3 from the upper part, the configuration of the antenna modules of the first embodiment and the first and second comparative examples, a graph of the reflection loss, a bandwidth in which the reflection loss is smaller than 6 dB, a peak gain, and a peak gain of -3 dB. (Hereinafter referred to as "-3 dB angle”) is shown.
  • FIG. 4 is a diagram showing the gain of the radio wave radiated from the feeding element 121 in three dimensions.
  • the inclination angle around the Z axis from the X axis is indicated by “ ⁇ ”
  • the inclination angle around the X axis from the Z axis is indicated by “ ⁇ ”.
  • the gain peaks in the positive direction of the Z axis.
  • FIG. 5 is a diagram showing the gain when the inclination angle ⁇ around the Z axis is 90 °, with the inclination angle ⁇ around the X axis as a parameter.
  • the maximum value of the gain shown in FIG. 5 is defined as "peak gain”, and the width of the inclination angle ⁇ at which the gain decreases by 3 dB from the peak gain is defined as "-3 dB angle”.
  • the "-3 dB angle" corresponds to the radiation angle of the radio wave.
  • the antenna module 100 # 1 of Comparative Example 1 is an antenna module having a configuration in which an air layer is not provided between the feeding element 121 and the ground electrode GND.
  • the antenna module 100 # 2 of Comparative Example 2 is an antenna module having a configuration in which the conductive member 170 is removed from the configuration of the first embodiment.
  • the frequency bandwidth at which the reflection loss is 6 dB or less is 3.2 GHz, the peak gain is 6.64 dB, and the -3 dB angle is 92.0 °. ..
  • the frequency bandwidth at which the reflection loss is 6 dB or less is 3.4 GHz, and a wider band is realized as compared with Comparative Example 1.
  • the peak gain is 6.87 dB, which is larger than that of Comparative Example 1, and the -3 dB angle is also narrower, 88.4 °.
  • the frequency bandwidth at which the reflection loss is 6 dB or less is 3.4 GHz, which is wider than that of Comparative Example 1 as in Comparative Example 2.
  • the peak gain is 6.72 dB, which is larger than that of Comparative Example 1 but smaller than that of Comparative Example 2.
  • the -3 dB angle is also an intermediate value (89.2 °) between Comparative Example 1 and Comparative Example 2. That is, as compared with Comparative Example 2, it is possible to secure a wide directivity while maintaining the frequency bandwidth.
  • the influence of the conductive member 170 on the gain may change depending on the size, number, position, conductivity, etc. of the arranged conductive member 170. Therefore, the arrangement of the conductive member 170 is appropriately selected according to the desired gain characteristics.
  • the feeding element and the ground electrode are formed on different dielectric substrates, and an air layer is formed between the two dielectric substrates to reduce the reflection loss over a wide band and widen the directivity. It is possible to secure the sex.
  • the “feeding element 121" in the first embodiment corresponds to the "first radiating element” of the present disclosure. Further, the “dielectric substrate 130" and the “dielectric substrate 140" in the first embodiment correspond to the “first dielectric substrate” and the “second dielectric substrate” of the present disclosure, respectively.
  • the “air layer 185" in the first embodiment corresponds to the "low dielectric constant layer” and the “air layer” of the present disclosure.
  • FIG. 6 is a cross-sectional view of the antenna module 100A according to the second embodiment.
  • the conductive members 170 and 180 of the antenna module 100 of the first embodiment have a configuration formed of the electrode connecting material 175, and the other configurations are antennas. It is the same as the module 100.
  • the electrode connecting material 175 is connected to the electrode pad 190 formed on the back surface 132 of the dielectric substrate 130 and the electrode pad 195 formed on the front surface 141 of the dielectric substrate 140.
  • a protective resist may be formed on the back surface 132 of the dielectric substrate 130 and the front surface 141 of the dielectric substrate 140.
  • the resist 196 may be a clearance resist (FIG. 7 (a)) in which a resist 196 is formed by providing a gap between the resist 196 and the electrode pad, or a part of the electrode pad is used. It may be an overresist (FIG. 7B) in which the resist 196 is formed so as to cover it.
  • the antenna characteristics of the antenna module 100A of the second embodiment are basically the same as those of the antenna module 100 of the first embodiment shown in FIG. 3 as long as the conductivity of the conductive member and the electrode connecting material are the same. become. Therefore, even in the antenna module 100A, it is possible to reduce the reflection loss over a wide band and secure a wide directivity.
  • FIG. 8 is a diagram for explaining the antenna characteristics of the antenna module 100B according to the third embodiment.
  • the antenna module 100A shown in the second embodiment will be described as a comparative example.
  • the antenna module 100B of the third embodiment has a via electrode 197 connected to the electrode pad 195 of the dielectric substrate 140 in addition to the configuration of the antenna module 100A of the second embodiment. ing. One end of the via electrode 197 is connected to the electrode pad 195, and the other end is in an open state not connected to another conductive member.
  • the area that obstructs the electromagnetic field between the feeding element 121 and the ground electrode GND becomes large, and as a result, the directivity can be adjusted.
  • the peak gain is 6.72 dB and the -3 dB angle is 89.2 °.
  • the peak gain is 6.65 dB and the -3 dB angle is 90.4 °. That is, in the antenna module 100B, the directivity is expanded.
  • the directivity can be further expanded by forming the via electrode connected to the conductive member arranged in the air layer.
  • the "via electrode 197" in the third embodiment corresponds to the "first via electrode” in the present disclosure.
  • FIG. 9 is a diagram for explaining the antenna characteristics of the antenna module 100C according to the fourth embodiment.
  • the antenna module 100A of the second embodiment is used as a comparative example.
  • the basic configuration of the antenna module 100C is the same as that of the antenna module 100A of the second embodiment, but in the antenna module 100C, the air layer 185 is formed at a position closer to the feeding element 121 than the antenna module 100A.
  • the distance H0 between the feeding element 121 and the ground electrode GND is the same, but in the antenna module 100A, the conductive member is connected to the feeding element 121 in the dielectric substrate 130.
  • the distance H1 to (electrode pad 190) is made larger than the distance H2 from the ground electrode GND to the conductive member (electrode pad 195) on the dielectric substrate 140 (H1> H2).
  • the distance H1A from the feeding element 121 on the dielectric substrate 130 to the conductive member (electrode pad 190) is the distance H2A from the ground electrode GND on the dielectric substrate 140 to the conductive member (electrode pad 195). Is made smaller than (H1A ⁇ H2A).
  • the strength of the electromagnetic field formed between the feeding element 121 and the ground electrode GND tends to become stronger as it is closer to the feeding element 121. Therefore, the closer the air layer 185 is to the feeding element 121, the greater the effect of lowering the effective dielectric constant, and the greater the effect of widening the frequency bandwidth. Further, when the air layer 185 is brought closer to the feeding element 121, the conductive member is brought closer to the feeding element 121 accordingly, so that the electromagnetic field hindered by the conductive member increases. Therefore, the closer the air layer 185 is to the feeding element 121, the greater the effect of expanding the directivity.
  • the frequency bandwidth of the reflection loss is expanded from 3.4 GHz to 4.1 GHz.
  • the -3dB angle has also been expanded from 89.2 ° to 90.4 °. Therefore, by adjusting the thicknesses of the dielectric substrates 130 and 140 to bring the air layer 185 closer to the feeding element 121, it is possible to reduce the reflection loss over a wide band and secure a wide directivity.
  • the peak gain of the antenna module 100C is 6.56 dB, which is lower than the peak gain (6.64 dB) of the antenna module 100 # 1 without an air layer in FIG. Therefore, depending on the required peak gain specifications, the configuration of the antenna module 100C may not be suitable. That is, when the peak gain is emphasized, the distance between the feeding element 121 and the electrode pad 190 in the dielectric substrate 130 is set to the ground electrode GND and the electrode pad 195 of the dielectric substrate 140 as in the antenna module 100A. It is preferably greater than the distance between them.
  • the distance between the power feeding element 121 and the electrode pad 190 in the dielectric substrate 130 is set to the ground electrode GND and the electrode of the dielectric substrate 140 as in the antenna module 100C. It is preferably smaller than the distance from the pad 195.
  • FIG. 10 is a cross-sectional view of the antenna module 100D according to the fifth embodiment.
  • a phase adjusting circuit 155 is formed on the power feeding wiring 150 on the dielectric substrate 140.
  • the dielectric constant ⁇ 2 of the dielectric substrate 140 is larger than the dielectric constant ⁇ 1 of the dielectric substrate 130 ( ⁇ 1 ⁇ 2).
  • the phase adjustment circuit 155 is, for example, a coupler or a distributed constant type that utilizes a line length and / or a capacitance pattern when supplying a high frequency signal to two different feeding points and emitting radio waves in the same polarization direction. It is used to invert the phases of the supplied high frequency signals by forming a filter. Alternatively, it is used when a high frequency signal is supplied to two radiating elements having different resonance frequencies with the same feeding wiring, and a stub is formed on the feeding wiring to remove the signal on the other side.
  • the amount of phase adjustment by the phase adjustment circuit 155 is determined by the wavelength of the high frequency signal passing through the dielectric substrate and the length of the line forming the phase adjustment circuit 155.
  • the wavelength changes depending on the dielectric constant of the dielectric substrate on which the phase adjustment circuit 155 is formed, and the higher the dielectric constant, the shorter the wavelength. Therefore, when it is necessary to adjust the phase significantly, if the dielectric constant of the dielectric substrate is small, it is necessary to increase the size of the phase adjusting circuit 155. Therefore, the phase adjustment circuit 155 can be miniaturized by relatively increasing the dielectric constant of the dielectric substrate on which the phase adjustment circuit 155 is formed.
  • the reduction of the effective dielectric constant is more effective when the dielectric constant in the region close to the feeding element 121 is lowered. Therefore, the phase adjusting circuit 155 is formed on the dielectric substrate 140, which is farther from the feeding element 121, and the dielectric constant of the dielectric substrate 140 is made higher than that of the dielectric substrate 130, so that the reflection loss is widened. It is possible to improve the efficiency of the phase adjusting circuit 155 and to reduce the size of the phase adjusting circuit 155.
  • FIG. 11 is a diagram showing the configuration of the antenna module 100E according to the sixth embodiment.
  • a plan view of the antenna module 100E is shown in the upper row (FIG. 11 (a)), and a cross-sectional view taken along line XI-XI of the plan view is shown in the lower row (FIG. 11 (b)).
  • FIG. 11 (a) a plan view of the antenna module 100E is shown in the upper row
  • FIG. 11 (b) a cross-sectional view taken along line XI-XI of the plan view
  • a plurality of conductive members 170 are arranged in the air layer 185 along each side of the substantially square feeding element 121, similarly to the antenna module 100 of the first embodiment. ing. Then, two adjacent conductive members 170 are connected by a connecting wire 177 formed on the dielectric substrate 140. More specifically, six conductive members 170-1 to 170-6 are arranged along each side of the power feeding element 121, and the conductive member 170-1, the conductive member 170-2, and the conductive member 170-3. The conductive member 170-4 and each pair of the conductive member 170-5 and the conductive member 170-6 are connected by a connecting line 177.
  • the length of the connecting wire 177 is set so that the resonance frequency of the configuration formed by the connecting wire 177 and the two conductive members 170 connected to the connecting wire 177 is twice the resonance frequency of the feeding element 121. NS.
  • the second harmonics radiated from the feeding element 121 are captured by the configuration formed by the connecting wire 177 and the conductive member 170. Therefore, it is possible to reduce the second harmonic component in the radio wave radiated from the antenna module 100E.
  • the resonance frequency of the configuration formed by the connecting wire 177 and the two conductive members 170 connected to the connecting wire 177 is the resonance frequency of the feeding element 121.
  • the Nth harmonic component can be suppressed by adjusting the length of the connecting line 177 so that it is N times the resonance frequency (N is an integer of 3 or more).
  • N is an integer of 3 or more.
  • the size of the third-order or higher harmonic component is smaller than the size of the second-order harmonic component. The influence of harmonic components can be sufficiently reduced.
  • FIG. 12 is a diagram for explaining the reflection loss of the second harmonic in the antenna module 100E of FIG.
  • the solid line LN10 shows the case of the antenna module 100E of the sixth embodiment in which the conductive member 170 is connected
  • the broken line LN11 shows the case of the comparative example in which the conductive member 170 is not connected.
  • the frequency band of the radio wave radiated from the feeding element 121 is 26.5 to 29.5 GHz, and therefore the frequency band of the second harmonic is 53 to 59 GHz.
  • the reflection loss of the antenna module 100E is larger than that in the case of the comparative example. That is, in the antenna module 100E, the second harmonic is less likely to be radiated than in the comparative example. Therefore, the influence of the harmonic component on the radio wave radiated from the feeding element 121 is suppressed.
  • one of the conductive members connected by the connecting wire 177 corresponds to the "first member” of the present disclosure, and the other conductive member corresponds to the "second member” of the present disclosure.
  • the shape and arrangement of the conductive member may be in other embodiments as long as it can prevent the electromagnetic field between the feeding element and the ground electrode.
  • the conductive member 170A in the antenna module 100F of FIG. 13A may be formed in a continuous linear shape along each side of the feeding element 121.
  • linear members along each side are connected to each other and arranged so as to surround the power feeding element 121.
  • the rectangular feeding element 121 In the case of the rectangular feeding element 121, an electric field is generated mainly from the side orthogonal to the polarization direction. Therefore, it is effective to arrange the conductive member at least along the side orthogonal to the polarization direction.
  • a plurality of conductive members 170 may be arranged along the side of the feeding element 121 in the Y-axis direction.
  • the rectangular conductive member 170B may be arranged along the side of the feeding element 121 in the Y-axis direction.
  • a space (air layer 185) is formed between the dielectric substrate 130 and the dielectric substrate 140, but the portion of the air layer 185 is formed.
  • the low dielectric constant layer may be formed by using a material having a dielectric constant lower than that of the dielectric substrate 130.
  • the dielectric substrate 130 and the dielectric substrate 140 are filled with a dielectric 186 having a dielectric constant lower than that of the dielectric substrate 130. There may be. Further, as in the antenna module 100J of FIG. 14B, the side surface of the dielectric substrate 130 is also covered with the dielectric 186A in addition to the space between the dielectric substrate 130 and the dielectric substrate 140. May be good.
  • the low dielectric constant layer does not have to be entirely filled with a dielectric material.
  • the dielectric 186B may be arranged in a portion inside the conductive member 170, and a space may be formed in a portion outside the conductive member 170.
  • the dielectric 186C is arranged in the peripheral portion including the conductive member 170 between the dielectric substrate 130 and the dielectric substrate 140, and the dielectric 186C is arranged more than the dielectric 186C.
  • the mode may be such that a space is formed in the inner portion.
  • a dielectric may be partially formed in the thickness direction (Z-axis direction) between the dielectric substrate 130 and the dielectric substrate 140.
  • the feeding point SP1 arranged in the negative direction of the X-axis from the center of the feeding element 121 and the positive direction of the Y-axis from the center of the feeding element 121 as in the antenna module 100M of FIG. 15A.
  • a low dielectric constant layer is formed between the dielectric substrate 130 and the dielectric substrate 140, and the conductive member 170 is arranged in the low dielectric constant layer. You may do so.
  • the conductive member 170 is arranged along each side of the power feeding element 121.
  • a plurality of feeding points may be formed in each polarization direction.
  • a high frequency signal is supplied.
  • high-frequency signals are supplied from the center of the feeding element 121 to the feeding points SP2A arranged in the positive direction of the Y-axis and the feeding points SP2B arranged in the positive direction of the Y-axis.
  • phase adjustment circuit as described in the fifth embodiment is formed in each feeding wiring. As described in the fifth embodiment, this phase adjusting circuit is formed on the dielectric substrate 140 which is far from the feeding element 121, and the dielectric constant of the dielectric substrate 140 is larger than the dielectric constant of the dielectric substrate 130. It is preferable to do so.
  • FIG. 16 is a plan view of a first example of the array type antenna module according to the eighth embodiment.
  • the antenna module 100P of FIG. 16 two dielectric substrates 130A and 130B are arranged adjacent to each other on the common dielectric substrate 140 in the X-axis direction, and the feeding element 121A is arranged with respect to the dielectric substrates 130A and 130B. , 121B are formed, respectively.
  • a plurality of conductive members 170 are arranged along each side of the feeding element 121A and the feeding element 121B. ing.
  • the “dielectric substrate 130A” and “dielectric substrate 130B” in the first example correspond to the “first substrate” and the “second substrate” in the present disclosure, respectively. Further, the “feeding element 121A” and the “feeding element 121B” in the first example correspond to the "first radiating element” and the “third radiating element” in the present disclosure, respectively.
  • FIG. 17 is a plan view of a second example of the array type antenna module according to the eighth embodiment.
  • the feeding elements 121A and 121B are arranged on the common dielectric substrate 130 in the X-axis direction, and the dielectric substrate 130 is arranged on the dielectric substrate 140.
  • a plurality of conductive members 170 are arranged along each side of the feeding element 121A and the feeding element 121B. ..
  • each feeding element is surrounded by a plurality of conductive members.
  • the feeding elements are arranged on a common dielectric substrate as in the second example and radio waves can be emitted in both the polarization directions of the X-axis direction and the Y-axis direction, each of them. It is desirable to change the side length of the feeding element according to the length of the common dielectric substrate side in order to reduce the difference in the radiation characteristics of both polarized waves. More specifically, as shown in the antenna module 100Q1 of FIG. 18, when the dielectric substrate 130 has a rectangular shape with the long side in the X-axis direction, the feeding elements 121A and 121B are also in the X-axis direction. It is desirable that the dimension LX of the above is larger than LY in the Y-axis direction (LX> LY) so that the distance between the feeding elements is narrowed.
  • the configuration in which the dielectric substrate is shared corresponds to the configuration in which the dielectric is added to the space between the two dielectric substrates 130A and 130B as compared with the antenna module 100P of the first example.
  • the effective permittivity of the two feeding elements in the adjacent direction that is, the X-axis direction
  • the impedance of the feeding element with respect to the polarization in the X-axis direction can be changed.
  • the radiation characteristics of the radio waves whose polarization direction is the X-axis direction and the radiation characteristics of the radio waves whose polarization direction is the Y-axis direction may be different.
  • the impedance related to polarization in the X-axis direction can be adjusted. It is possible to reduce the difference between the radiation characteristics of the radio wave whose polarization direction is the axial direction and the radiation characteristics of the radio waves whose polarization direction is the Y-axis direction.
  • the radiation characteristics of radio waves with the X-axis direction as the polarization direction and the Y-axis direction may be reduced.
  • the feeding elements 121A and 121B are arranged so as to face the sides along the X-axis direction.
  • the conductive member 170 is made smaller than the conductive member 170 arranged so as to face the sides of the feeding elements 121A and 121B along the Y-axis direction. Therefore, the coupling between the radiating element and the conductive member in the Y-axis direction becomes smaller than the coupling between the radiating element and the conductive member in the X-axis direction, and the impedance in the Y-axis direction increases.
  • the impedance in the Y-axis direction is adjusted by changing the coupling with the conductive member, so that the two polarization directions
  • the difference in impedance can be reduced. Therefore, it is possible to reduce the difference in the radiation characteristics of the radio waves in the two polarization directions.
  • the antenna module 100R of FIG. 20 has a configuration in which the conductive member 170 between the feeding element 121A and the feeding element 121B is removed in the configuration of the antenna module 100Q of the third example of FIG.
  • the "feeding element 121A” and the “feeding element 121B” correspond to the "first radiating element” and the “fourth radiating element” in the present disclosure, respectively.
  • the antenna module 100S of FIG. 21 has a configuration in which a plurality of feeding elements are arranged on a common dielectric substrate shown in FIG. 20, and two sets are arranged on a common dielectric substrate 140. That is, the antenna module 100S is a 2 ⁇ 2 array antenna.
  • rectangular dielectric substrates 130 and 130C are arranged adjacent to the common dielectric substrate 140 in the Y-axis direction, and the dielectric substrate 130 has a feeding element.
  • 121A and 121B are arranged adjacent to each other in the X-axis direction.
  • Feeding elements 121C and 121D are arranged adjacent to each other in the X-axis direction on the dielectric substrate 130C.
  • a plurality of conductive members 170 are arranged around each feeding element. The conductive member 170 between the feeding element 121A and the feeding element 121B and the conductive member 170 between the feeding element 121C and the feeding element 121D are excluded.
  • FIG. 22 is a cross-sectional view of the antenna module 100T according to the ninth embodiment.
  • the antenna module 100T includes a feeding element 121 and a non-feeding element 122 as radiation elements.
  • the non-feeding element 122 is formed on the dielectric substrate 130.
  • the feeding element 121 is arranged on the dielectric substrate 140 so as to face the non-feeding element 122.
  • the sizes of the feeding element 121 and the non-feeding element 122 are substantially the same, and the resonance frequencies are also set to be substantially the same.
  • Ground electrodes GND1 and GND2 are arranged on the dielectric substrate 140 so as to face the feeding element 121.
  • the ground electrodes GND1 and GND2 are arranged below the feeding element 121 (in the negative direction of the Z axis), and the ground electrode GND1 is arranged in a layer between the feeding element 121 and the ground electrode GND2. That is, the feeding element 121 is arranged between the non-feeding element 122 and the ground electrode GND1.
  • the layer between the ground electrode GND1 and the ground electrode GND2 is used as a wiring layer.
  • the power feeding wiring 150 is connected to the power feeding element 121 from the RFIC 110 through the ground electrode GND1 and the ground electrode GND2.
  • An air layer 185 is formed between the dielectric substrate 130 and the dielectric substrate 140, and an electronic component 176 is arranged as a conductive member in the air layer 185.
  • the electronic component 176 is arranged around the radiating element (feeding element 121, non-feeding element 122) so as to be separated from the radiating element. Assuming that the wavelength of the emitted radio wave is ⁇ , the electronic components 176 are arranged so that the distance between adjacent electronic components 176 is ⁇ / 4 or less.
  • the frequency band of the reflection loss can be expanded. Further, since the air layer 185 (low dielectric constant layer) is formed between the dielectric substrates 130 and 140, the frequency band of the reflection loss can be further expanded. Then, by arranging the electronic component 176 (conductive member) in the air layer 185, a wide directivity can be ensured.
  • the electronic component 176 generally has higher dimensional accuracy in outer shape than solder. Therefore, by using the electronic component 176 as the conductive member, the dimensional accuracy of the air layer 185 in the height direction (Z-axis direction) can be improved.
  • the feeding element 121 is arranged on the dielectric substrate 140 in FIG. 22, the feeding element 121 may be arranged on the dielectric substrate 130.
  • the "non-feeding element 122" and the “feeding element 121” correspond to the "first radiating element” and the “second radiating element” of the present disclosure, respectively.
  • FIG. 23 is a cross-sectional view of the antenna module 100U according to the tenth embodiment.
  • the arrangement of the radiating elements is different from that of the antenna module 100T of the ninth embodiment.
  • the description of the configuration of the antenna module 100U that overlaps with that of the antenna module 100T will not be repeated.
  • the antenna module 100U includes a feeding element 121 arranged on the dielectric substrate 130 and a non-feeding element 123 arranged on the dielectric substrate 140 as radiation elements.
  • the feeding element 121 and the non-feeding element 123 are arranged so as to face each other, and the non-feeding element 123 is arranged between the feeding element 121 and the ground electrode GND1.
  • the size of the non-feeding element 123 is larger than the size of the feeding element 121. That is, the resonance frequency of the feeding element 121 is higher than the resonance frequency of the non-feeding element 123.
  • the power feeding wiring 150 penetrates the ground electrodes GND1 and GND2 and the non-feeding element 123 from the RFIC 110, and further feeds power via the conductive member 180 arranged in the air layer 185 between the dielectric substrate 130 and the dielectric substrate 140. It is connected to the element 121.
  • a high-frequency signal corresponding to the resonance frequency of the feeding element 121 is supplied from the RFIC 110 to the feeding wiring 150, so that radio waves are radiated from the feeding element 121.
  • the feeding wiring 150 and the non-feeding element 123 are electromagnetically coupled, and radio waves are radiated from the non-feeding element 123. That is, the antenna module 100U functions as a dual band type antenna module.
  • an air layer 185 is formed between the feeding element 121 and the non-feeding element 123. Therefore, it is possible to reduce the reflection loss over a wide band and secure a wide directivity, particularly for the radio wave radiated from the feeding element 121.
  • the non-feeding element 123 may be arranged on the dielectric substrate 130.
  • the air layer 185 is formed between the non-feeding element 123 and the ground electrode GND1
  • the reflection loss over a wide band and the wide directivity are ensured especially for the radio waves radiated from the non-feeding element 123. Can be realized.
  • the "feeding element 121" and the “non-feeding element 123" correspond to the "first radiating element” and the “second radiating element” of the present disclosure, respectively.
  • FIG. 24 is a diagram for explaining the antenna module 100V according to the eleventh embodiment.
  • FIG. 24 (a) in the upper row is a plan view of the antenna module 100V
  • FIG. 24 (b) in the lower row is a cross-sectional view of lines XXII-XXII in FIG. 24 (a).
  • the antenna module 100V includes a via electrode V2 formed on the dielectric substrate 130 and a connecting conductor 165 for connecting the via electrodes V2 in addition to the configuration of the antenna module 100T described in the ninth embodiment. , It has a structure having a via electrode formed on the dielectric substrate 140. In FIG. 24, the description of the elements overlapping with FIG. 22 will not be repeated.
  • the via electrode V1 connects the electronic component 176 and the ground electrode GND1 on the dielectric substrate 140. Further, the via electrode V2 penetrates the dielectric substrate 130, and one end thereof is connected to the electronic component 176. The other end of the via electrode V2 is connected to a connecting conductor 165 arranged on the surface 131 of the dielectric substrate 130.
  • the connecting conductor 165 is arranged so as to surround the non-feeding element 122 (and the feeding element 121) when the antenna module 100V is viewed in a plan view, and connects the via electrodes V2 to each other.
  • the via electrode and the connecting conductor increase the area that obstructs the electromagnetic field generated from the radiating element, it is possible to suppress the peak gain and secure a wide directivity. Further, by connecting the via electrode to the ground electrode, the influence of the outer electromagnetic field can be reduced.
  • the "via electrode V2" in the eleventh embodiment corresponds to the "second via electrode” in the present disclosure.
  • FIG. 25 is a plan view (FIG. 25 (a)) of the antenna module 100W according to the twelfth embodiment, and a cross-sectional view (FIG. 25 (b)) of lines XXIII-XXIII in the plan view.
  • two dielectric substrates 130A and 130B are arranged in the X-axis direction on the common dielectric substrate 140, similarly to the antenna module 100P shown in FIG. 16 of the eighth embodiment. It is configured to be arranged adjacent to.
  • a non-feeding element 122A is arranged on the dielectric substrate 130A
  • a non-feeding element 122B is arranged on the dielectric substrate 130B.
  • the feeding element 121A is arranged so as to face the non-feeding element 122A
  • the feeding element 121B is arranged so as to face the non-feeding element 122B.
  • An air layer 185 is formed between the dielectric substrate 130A and the dielectric substrate 140, and between the dielectric substrate 130B and the dielectric substrate 140.
  • a plurality of electronic components 176 are arranged in the air layer 185 so as to surround the periphery of each radiating element when the antenna module 100W is viewed in a plan view.
  • the electronic component 176 is connected to the ground electrode GND1 arranged on the dielectric substrate 140 by the via electrode V1. Further, the electronic component 176 is connected to the connecting conductor 165 formed on the surface of the dielectric substrates 130A and 130B by the via electrode V2 formed on the dielectric substrates 130A and 130B.
  • FIG. 26 is a plan view for explaining a first example of the antenna module 100X according to the thirteenth embodiment.
  • the antenna module 100 shown in the first embodiment is shown in the left figure (FIG. 26 (a)) for comparison, and the right figure (FIG. 26 (b)) shows the third embodiment.
  • the antenna module 100X is shown.
  • each side of the feeding element 121 is diagonally arranged so as to have an angle of 45 ° with respect to each side of the dielectric substrates 130X and 140X.
  • the feeding element 121 has the same size, but the sizes of the dielectric substrates 130X and 140X are smaller than those of the corresponding dielectric substrates 130 and 140 of the antenna module 100. There is. Along with this, the number of conductive members 170 arranged around the power feeding element 121 is reduced.
  • the distance from the end of the feeding element 121 to the end of the dielectric substrate 130X in the polarization direction is set to the antenna module 100. It can be secured to the same extent. Therefore, it is possible to prevent the frequency bandwidth from being narrowed due to the miniaturization of the dielectric substrate.
  • the radiating element is diagonally arranged with respect to the dielectric substrate in the antenna module, a wide directivity can be ensured by arranging the conductive member around the feeding element, and further, the antenna module. Can be miniaturized.
  • the distance between the conductive members 170 arranged around the feeding element 121 is not uniform, but as in the second example of the antenna module 100Y shown in FIG. 26, the dielectric substrate 130X The distance between the conductive members 170 arranged along each side may be equal.
  • the inclination angle of the feeding element 121 is not necessarily limited to 45 °, and if the distance from the end of the feeding element 121 to the end of the dielectric substrate 130X in the polarization direction can be secured, the angle may be other than 45 °. good.

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