WO2015182211A1 - 電力変換装置及び三相交流電源装置 - Google Patents
電力変換装置及び三相交流電源装置 Download PDFInfo
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- WO2015182211A1 WO2015182211A1 PCT/JP2015/057107 JP2015057107W WO2015182211A1 WO 2015182211 A1 WO2015182211 A1 WO 2015182211A1 JP 2015057107 W JP2015057107 W JP 2015057107W WO 2015182211 A1 WO2015182211 A1 WO 2015182211A1
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
- H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
- H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M7/505—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a thyratron or thyristor type requiring extinguishing means
- H02M7/515—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a thyratron or thyristor type requiring extinguishing means using semiconductor devices only
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
- H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
- H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M7/4807—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode having a high frequency intermediate AC stage
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/14—Arrangements for reducing ripples from dc input or output
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
- H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
- H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
- H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
- H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
- H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
- H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/0048—Circuits or arrangements for reducing losses
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
- H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
- H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M7/53—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M7/537—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
- H02M7/5387—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration
- H02M7/53871—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration with automatic control of output voltage or current
- H02M7/53875—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration with automatic control of output voltage or current with analogue control of three-phase output
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
- H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
- H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M7/53—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M7/537—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
- H02M7/539—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters with automatic control of output wave form or frequency
- H02M7/5395—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters with automatic control of output wave form or frequency by pulse-width modulation
-
- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
Definitions
- the present invention relates to a three-phase AC power supply device that generates three-phase AC power from DC power and a power conversion device used therefor.
- a power converter that boosts the DC voltage input from the DC power supply using a DC / DC converter and converts it to an AC voltage using an inverter, and outputs it to a stand-alone power supply or UPS (Uninterruptible Power Supply) Many are used.
- the DC / DC converter always performs a switching operation, and the inverter also always performs a switching operation.
- the voltage of the DC power supply can be converted into a three-phase AC voltage (see, for example, Patent Document 1 (FIG. 7)).
- FIG. 25 is an example of a circuit diagram of a power converter used when power is supplied from a DC power source to a three-phase AC load.
- the power conversion device 200 generates AC power based on the DC power received from the DC power supply 201 and supplies the power to the three-phase AC load 220.
- the power conversion device 200 includes a capacitor 202, for example, three sets of booster circuits 203, a smoothing circuit 205 that smoothes the voltage of the DC bus 204, a three-phase inverter circuit 207, three sets of AC reactors 208 to 210, and capacitors. 211 to 213.
- the smoothing circuit 205 is formed by connecting capacitors 206 in two series for securing withstand voltage performance and in six parallels for securing capacity.
- the capacitance of the smoothing circuit as a whole is, for example, several mF.
- the booster circuit 203 boosts the voltage, which has been increased in frequency by switching, by the insulating transformer 203t, and then rectifies it.
- the three sets of booster circuits 203 are connected in parallel to the common DC bus 204.
- the outputs of the three sets of booster circuits 203 are smoothed by the large-capacity smoothing circuit 205 and become the voltage of the DC bus 204.
- the three-phase inverter circuit 207 By switching this voltage by the three-phase inverter circuit 207, a three-phase AC voltage including a high-frequency component is generated.
- the high-frequency component is removed by the AC reactors 208 to 210 and the capacitors 211 to 213, and a three-phase AC voltage (power) that can be provided to the three-phase AC load 220 is obtained.
- the line voltage of the three-phase AC load 220 is 400V.
- the voltage of the DC bus 204 needs to have a peak value of AC 400V or more, and is approximately 566V at 400 ⁇ (2 1/2 ), but it is set to 600V with a slight margin.
- the voltage of the DC bus 204 is 600 V
- the switching element in the three-phase inverter circuit 207 is turned off, a voltage greatly exceeding 600 V is applied to the switching element due to resonance caused by the stray inductance and the capacitance of the switching element. Therefore, for example, in order to reliably prevent the dielectric breakdown of the switching element, a withstand voltage performance of 1200 V that is twice the voltage of the DC bus is required.
- the smoothing circuit 205 also requires a withstand voltage performance of 1200 V
- the configuration of FIG. 25 requires a withstand voltage performance of 600 V for each capacitor.
- the present invention provides a three-phase AC power supply device that converts a DC voltage input from a DC power source into a three-phase AC voltage and a power converter used therefor, to reduce power loss associated with the conversion. Objective.
- the present invention is a power conversion device for converting a DC voltage input from a DC power source into a three-phase AC voltage, wherein the DC voltage input from the DC power source is a first phase with respect to a neutral point of the three-phase AC.
- a first phase conversion device that converts the voltage to an AC waveform voltage to be output to the second phase, and a second voltage that converts a DC voltage input from the DC power source to an AC waveform voltage to be output to the second phase relative to the neutral point.
- a phase converter for converting a DC voltage input from the DC power source to a voltage of an AC waveform to be output to the third phase with respect to the neutral point, the first phase converter, A second phase converter, and a control unit for controlling the third phase converter,
- Each of the first phase conversion device, the second phase conversion device, and the third phase conversion device includes a DC / DC converter including an insulating transformer and a smoothing capacitor, and the control unit includes the DC / DC converter.
- a first converter that converts an input DC voltage into a voltage including a pulsating waveform corresponding to an absolute value of a voltage obtained by superimposing a third harmonic on a fundamental wave as an AC waveform to be output by controlling
- the full-bridge inverter is provided after the first conversion unit, and the control unit controls the full-bridge inverter, so that the polarity of the voltage including the pulsating waveform is inverted every cycle.
- a second converter that converts the voltage into an AC waveform voltage.
- the present invention is a three-phase AC power supply apparatus, wherein a DC power supply and a DC voltage input from the DC power supply are converted into a voltage of an AC waveform to be output to the first phase with respect to the neutral point of the three-phase AC.
- Each of the first phase conversion device, the second phase conversion device, and the third phase conversion device includes a DC / DC converter including an insulating transformer and a smoothing capacitor, and the control unit includes the DC / DC converter.
- a first converter that converts an input DC voltage into a voltage including a pulsating waveform corresponding to an absolute value of a voltage obtained by superimposing a third harmonic on a fundamental wave as an AC waveform to be output by controlling
- the full-bridge inverter is provided after the first conversion unit, and the control unit controls the full-bridge inverter, so that the polarity of the voltage including the pulsating waveform is inverted every cycle.
- a second converter that converts the voltage into an AC waveform voltage.
- the power conversion device and the three-phase AC power supply device of the present invention it is possible to reduce power loss accompanying conversion.
- a graph showing the AC voltage V AC output (a) shows the target voltage (ideal value), and (b) is an AC voltage V AC actually the voltage sensor detects.
- (A) is a waveform diagram showing the phase voltages of U, V, W output from the power converter, and (b) is a diagram of UV, VW, applied to a three-phase AC load. It is a wave form diagram which shows the line voltage of WU. It is a figure which shows the gate drive pulse with respect to a full bridge circuit. It is a graph which shows the other example of the production method of the command value of the output waveform in a 1st conversion part, and the horizontal axis represents time and the vertical axis
- shaft represents the voltage.
- (A) is four cycles of the command value (ideal value) of the output waveform of the first converter, and (b) is four cycles of the output waveform that is actually output.
- (A) is a waveform diagram showing the phase voltages of U, V, W output from the power converter, and (b) is a diagram of UV, VW, applied to a three-phase AC load. It is a wave form diagram which shows the line voltage of WU. It is a circuit diagram which shows the three-phase alternating current power supply device which concerns on 2nd Embodiment.
- FIG. 15 It is a figure which shows the internal circuit of the converter for 1 phase in FIG. 15 in detail. It is a figure which shows the gate drive pulse with respect to a full bridge circuit.
- (A) is the command value (ideal value) of the output waveform of the first conversion unit to be obtained by the gate drive pulse of FIG. 17, and (b) is the voltage of the pulsating waveform that actually appears at both ends of the capacitor. It is.
- (A) is the figure which added the waveform of the target voltage of the zero cross vicinity to the figure similar to (b) of FIG. 18 with the dotted line.
- (b) and (c) are gate drive pulses of the switching elements that constitute the full-bridge inverter of the second conversion unit.
- the gist of the embodiment of the present invention includes at least the following.
- a first phase conversion device that converts an AC waveform voltage to be output to one phase, and a DC voltage input from the DC power source to an AC waveform voltage to be output to the second phase with respect to the neutral point
- a second phase converter a third phase converter for converting a DC voltage input from the DC power source into an AC waveform voltage to be output to the third phase with respect to the neutral point
- the first phase converter A control unit for controlling the second phase conversion device and the third phase conversion device,
- Each of the first phase conversion device, the second phase conversion device, and the third phase conversion device includes a DC / DC converter including an insulating transformer and a smoothing capacitor, and the control unit includes the DC / DC converter.
- a first converter that converts an input DC voltage into a voltage including a pulsating waveform corresponding to an absolute value of a voltage obtained by superimposing a third harmonic on a fundamental wave as an AC waveform to be output by controlling
- the full-bridge inverter is provided after the first conversion unit, and the control unit controls the full-bridge inverter, so that the polarity of the voltage including the pulsating waveform is inverted every cycle.
- a second converter that converts the voltage into an AC waveform voltage.
- a converter (first phase, second phase, third phase) is provided for each phase and outputs a phase voltage, so 1 / (( 3 1/2 ) is the voltage V AC (effective value) to be output from the converter.
- the voltage of the DC bus is reduced as compared with the case where the line voltage is supplied by a single three-phase inverter. Further, the voltage of the DC bus is further reduced by the effect of reducing the peak value by superimposing the third harmonic.
- ⁇ ⁇ Switching loss of the switching element decreases due to the voltage reduction of the DC bus. Moreover, even when there is a reactor in the apparatus, the iron loss is reduced. Furthermore, the switching element and the smoothing capacitor connected to the DC bus can be used even if they have low withstand voltage performance. A switching element having a lower withstand voltage performance has a lower on-resistance, so that conduction loss can be reduced.
- the hardware configuration of the first conversion unit is a DC / DC converter, but it does not convert a DC voltage into a simple DC voltage but corresponds to an absolute value of an AC waveform. Convert to voltage including pulsating waveform. Therefore, the waveform that is the basis of the AC waveform is generated by the first converter. And a 2nd conversion part inverts the polarity of the voltage containing a pulsating flow waveform for every period, and converts it into the target voltage of an alternating current waveform.
- the full bridge inverter of the second conversion unit has a drastic reduction in the number of times of switching compared to the conventional inverter operation, and the voltage at the time of switching is low.
- the switching loss of the second conversion unit is greatly reduced. Moreover, even when a reactor is provided in the 2nd conversion part, the iron loss becomes small. Furthermore, the capacitor of the first conversion unit smoothes only high-frequency voltage fluctuations, and does not smooth the low-frequency pulsating waveform. Therefore, a low-capacitance capacitor can be used.
- the first conversion unit may convert the DC voltage into a voltage having a continuous pulsating waveform.
- all (1/2) period waveforms that form the basis of the AC waveform are generated by the first conversion unit, and the second conversion unit performs only polarity reversal at a frequency that is twice the frequency of the output AC waveform. That is, the second conversion unit does not perform inverter operation with high-frequency switching. Therefore, no AC reactor is required on the output side of the second conversion unit, and loss due to the AC reactor can be eliminated.
- the control unit when the voltage output from the first converter is within a predetermined ratio or less with respect to the peak value of the pulsating waveform, the control unit May generate the voltage of the AC waveform within the period by operating the full-bridge inverter at a high frequency.
- the period within a predetermined ratio or less with respect to the peak value of the pulsating current waveform means the vicinity of the zero cross of the target voltage.
- the second converter contributes to the generation of the AC waveform near the zero cross of the target voltage
- the first converter contributes to the generation of the AC waveform otherwise. If an attempt is made to generate the entire region of the pulsating flow waveform only by the first conversion unit, waveform distortion may occur in the vicinity of the zero cross, but such a waveform can be obtained by locally utilizing the inverter operation of the second conversion unit. Distortion can be prevented, and a smoother AC waveform output can be obtained. Since the period during which the second converter is operated as an inverter is short, there is less loss compared to the conventional inverter operation. Loss due to AC reactor is also reduced.
- the predetermined ratio in (3) is preferably 18% to 35%. In this case, it is possible to prevent waveform distortion in the vicinity of the zero cross and to sufficiently ensure the effect of reducing loss. For example, when the “predetermined ratio” is less than 18%, there is a possibility that slight distortion near the zero cross may remain. If it is larger than 35%, the high-frequency inverter operation period in the second conversion unit 2 becomes longer, and the loss reduction effect is reduced accordingly.
- the capacitor smoothes high-frequency voltage fluctuation due to switching in the first converter, but the pulsating waveform is smoothed. It is preferable to have a capacity that does not. In this case, a desired pulsating waveform can be obtained while removing high-frequency voltage fluctuations associated with switching.
- a DC power source and a DC voltage input from the DC power source are converted into an AC waveform voltage to be output to the first phase with respect to the neutral point of the three-phase AC.
- a first phase conversion device, a second phase conversion device that converts a DC voltage input from the DC power source into an AC waveform voltage to be output to the second phase with respect to the neutral point, and an input from the DC power source A third phase conversion device that converts a DC voltage to an AC waveform voltage to be output to the third phase with respect to the neutral point, the first phase conversion device, the second phase conversion device, and the third A control unit for controlling the phase conversion device,
- Each of the first phase conversion device, the second phase conversion device, and the third phase conversion device includes a DC / DC converter including an insulating transformer and a smoothing capacitor, and the control unit includes the DC / DC converter.
- a first converter that converts an input DC voltage into a voltage including a pulsating waveform corresponding to an absolute value of a voltage obtained by superimposing a third harmonic on a fundamental wave as an AC waveform to be output by controlling
- the full-bridge inverter is provided after the first conversion unit, and the control unit controls the full-bridge inverter, so that the polarity of the voltage including the pulsating waveform is inverted every cycle.
- a second converter that converts the voltage into an AC waveform voltage. Also in this case, the same effects as the power conversion device of (1) are exhibited.
- FIG. 1 is a circuit diagram showing a three-phase AC power supply apparatus 500 according to the first embodiment.
- the three-phase AC power supply device 500 includes a power conversion device 100P and a DC power source 5 made of, for example, a storage battery, and is connected to a three-phase AC load 6.
- the power conversion device 100P is configured by three sets of conversion devices (first conversion device, second conversion device, and third conversion device) 100 provided corresponding to each phase of three-phase alternating current.
- the converter 100 converts the DC power input from the DC power supply 5 into AC power and supplies the AC power to the three-phase AC load 6.
- each of the three sets of converters 100 independently supplies AC power with a phase voltage with respect to the neutral point N of the three-phase AC, and in the entire three sets, each phase load 6p (first phase (u), first phase) AC power is supplied to the second phase (v) and the third phase (w) with a line voltage.
- phase voltage When the line voltage of the three-phase AC load 6 is 400 V, the phase voltage is about 231 V (400 V / (3 1/2 )).
- the voltage of the DC bus L B is meant to be reduced (from 566V to 327V). Therefore, switching
- the withstand voltage performance of elements and other electronic devices is not required to be as high as 1200 V, and is approximately 600 V.
- FIG. 2 is a diagram showing the internal circuit of the conversion device 100 for one phase in FIG. 1 in more detail.
- the conversion device 100 converts an input DC voltage VDC into an AC voltage VAC, which is a target voltage having an AC waveform, and outputs the AC voltage.
- the conversion device 100 can also convert from alternating current to direct current, but here, description will be given mainly focusing on conversion from direct current to alternating current (the same applies to the second and third embodiments). .)
- the conversion device 100 is configured with a first conversion unit 1, a second conversion unit 2, and a control unit 3 as main components.
- a DC voltage VDC is input to the first conversion unit 1 via a smoothing capacitor 4.
- the direct current voltage VDC is detected by the voltage sensor 5 s and information on the detected voltage is sent to the control unit 3.
- AC voltage V AC is the second output voltage of the converter unit 2 is detected by a voltage sensor 6s, information of the detected voltage is sent to the control unit 3.
- the first converter 1 includes a DC / DC converter 10 and a smoothing capacitor 14.
- the DC / DC converter 10 includes, in order from the input side, a full bridge circuit 11 including four switching elements Q1, Q2, Q3, and Q4, an insulating transformer 12, and four switching elements Q5, Q6, Q7, and Q8.
- the rectifier circuit 13 is configured, and these are connected as illustrated.
- the second conversion unit 2 includes a full bridge inverter 21 including four switching elements Q9, Q10, Q11, and Q12, and a capacitor 22.
- the output of the second converter 2 becomes an AC voltage V AC of the desired AC waveform.
- the switching elements Q1 to Q12 are controlled by the control unit 3.
- an IGBT Insulated Gate Bipolar Transistor
- an FET Field Effect Transistor
- the voltage of the DC bus L B is reduced, switching converter 100
- the switching loss of elements Q5 to Q12 is reduced.
- the iron loss of the insulation transformer 12 is also reduced.
- DC bus L switching elements Q5 ⁇ Q12 and a capacitor 14 for smoothing is connected to B is also made available as low withstand voltage performance.
- a switching element having a lower withstand voltage performance has a lower on-resistance, so that conduction loss can be reduced.
- FIG. 3 is a diagram illustrating gate drive pulses for the full bridge circuit 11.
- a waveform indicated by two-dot chain line an AC voltage V AC is the target voltage.
- this waveform is not a normal sine wave.
- the frequency of the gate drive pulse is much higher than the frequency (50 or 60 Hz) of the AC voltage VAC (for example, 20 kHz), so individual pulses cannot be drawn, but the pulse width is the peak of the absolute value of the AC waveform. Becomes the widest and becomes narrower as the absolute value approaches zero.
- FIG. 4 is a diagram showing an example of how to generate a gate drive pulse.
- the upper stage is a diagram showing a high-frequency carrier wave and an absolute value of an AC waveform sine wave as a reference wave. Since the time on the horizontal axis is very short, the reference wave appears to be linear, but is rising toward 0 to ⁇ / 2, for example.
- Two sets of carrier waves (a thick line and a thin line) are displayed in an overlapping manner, and are composed of two trapezoidal waveforms that are temporally shifted from each other by a half cycle. That is, it rises diagonally, keeps level 1 for a while, and then suddenly drops to 0 is one cycle of one trapezoidal waveform, such a waveform appears continuously, and the two sets of waveforms are shifted by a half cycle ing.
- a PWM-controlled gate drive pulse shown in the lower stage is obtained.
- the gate drive pulse a pulse for turning on switching elements Q1 and Q4 and a pulse for turning on switching elements Q2 and Q3 are alternately output.
- a positive voltage and a negative voltage are alternately and evenly applied to the primary winding of the insulating transformer 12. Since the pulse width is not easily generated in the vicinity of the zero cross of the reference wave (sine wave), as shown in FIG. 3, the vicinity of the zero cross is in a state equivalent to no gate drive pulse being output.
- the output of the full bridge circuit 11 driven by the gate drive pulse as described above is transformed by the insulation transformer 12 at a predetermined turn ratio, then rectified by the rectifier circuit 13 and smoothed by the capacitor 14. Smoothing works to the extent that it eliminates traces of high-frequency switching, but it cannot smooth low frequencies such as commercial frequencies. That is, the capacity of the capacitor 14 is selected to an appropriate value so as to obtain such a result. If the capacity is much larger than the appropriate value, the waveform is smoothed down to a low frequency such as the commercial frequency, and the waveform shape is distorted. By selecting an appropriate value, a desired pulsating waveform can be obtained while removing high-frequency voltage fluctuations associated with switching.
- the rectifier circuit 13 can perform rectification by a diode built in the element even when the gate drive pulse is not given from the control unit 3 (even when the switching elements Q5 to Q8 are all off). Synchronous rectification can be performed. That is, when diode rectification is performed, a gate drive pulse is applied from the control unit 3 to the switching elements Q5 to Q8 at a timing when current flows through the diode. If it does so, it will become a synchronous rectification system, and since an electric current flows through the semiconductor element, the power loss of the whole rectifier circuit 13 can be reduced.
- FIG. 5 is a graph showing how to create a command value for the output waveform in the first converter 1.
- the horizontal axis represents time and the vertical axis represents voltage.
- the waveform of the command value has a peak value of 327 V shown in (a), and a sine wave having a commercial frequency (50 Hz, 0.02 sec / 1 cycle) is a fundamental wave. Obtained by superimposing waves.
- the amplitude of the third harmonic is, for example, 10% of the amplitude of the fundamental wave.
- an AC waveform including the third harmonic as shown in (b) is obtained.
- FIG. 6A shows four periods of the command value (ideal value) of the output waveform of the first converter 1 set in this way.
- the horizontal axis represents time and the vertical axis represents voltage. That is, this approximates a pulsating waveform obtained by full-wave rectification of the AC waveform of the AC voltage VAC, but since the third harmonic is included, the peak value is reduced from 327V to 283V.
- FIG. 6B shows the voltage of the pulsating waveform that actually appears at both ends of the capacitor 14. As is clear from comparison with (a), a pulsating flow waveform almost equivalent to the command value is obtained.
- FIG. 7 shows gate drive pulses of the switching elements Q9 to Q12 constituting the full bridge inverter of the second conversion unit 2.
- (A) is a gate drive pulse for the switching elements Q9 and Q12
- (b) is a gate drive pulse for the switching elements Q10 and Q11. As shown in the figure, by alternately becoming 1/0, the polarity of the pulsating flow waveform of FIG.
- FIG. 8 is a graph showing one cycle of the AC voltage VAC output in this way, where (a) is the target voltage (ideal value), and (b) is the AC voltage actually detected by the voltage sensor 6s. a V AC. Although there is a slight distortion near the zero cross, an AC waveform almost as the target is obtained.
- the hardware configuration of the first conversion unit 1 is a DC / DC converter.
- the DC voltage is not converted into a mere DC voltage, but the third harmonic. Is converted into a pulsating flow waveform corresponding to the absolute value of the AC waveform including Therefore, the waveform that is the basis of the AC waveform is generated by the first converter 1.
- the 2nd conversion part 2 inverts the polarity of the voltage containing a pulsating flow waveform for every period, and converts it into the target voltage of an alternating current waveform.
- the voltage of the DC bus L B can be reduced, further 3 Since there is also an effect of reducing the peak value by superimposing the second harmonic, the switching loss of the switching elements Q5 to Q12 in the converter 100 is reduced. Moreover, the iron loss of the insulation transformer 12 is also reduced.
- the full bridge inverter of the second conversion unit 2 drastically reduces the number of switching times compared to the conventional inverter operation. That is, for example, it is drastically reduced (1/200) from a high frequency of about 20 kHz to 100 Hz (for example, twice per cycle of 50 Hz).
- the second converter 2 performs switching at the zero cross timing, the voltage at the time of switching is extremely low (ideally 0 V). Therefore, the switching loss of the second conversion unit 2 is greatly reduced.
- the 2nd conversion part 2 does not perform the inverter operation
- the conversion efficiency of the conversion device 100 can be improved. Further, the capacitor 14 of the first converter 1 only needs to smooth the high-frequency voltage fluctuation, and does not smooth the low-frequency pulsating waveform. Therefore, a capacitor having a low capacitance (for example, 10 ⁇ F or 22 ⁇ F) can be used.
- FIG. 9A is a waveform diagram showing the phase voltages of U, V, and W output from the power converter 100P
- FIG. 9B is a waveform diagram of UV, V applied to the three-phase AC load. It is a wave form diagram which shows the line voltage of VW and WU.
- the control unit 3 controls the conversion devices (first conversion device, second conversion device, and third conversion device) 100 for each phase so that the phases of the AC waveforms output by these devices are shifted by (2/3) ⁇ from each other. To do. Even if the third harmonic is included in the phase voltage, the third harmonic is canceled out in the line voltage, and the phases are shifted by (2/3) ⁇ from each other as in the case of the normal sine wave phase voltage.
- the power converter device 100P can apply a three-phase alternating current voltage with respect to the three-phase alternating current load 6, and can supply alternating current power.
- FIG. 10 is a diagram illustrating gate drive pulses for the full bridge circuit 11.
- a waveform indicated by two-dot chain line, an AC voltage V AC is the target voltage.
- this waveform is not a normal sine wave.
- the frequency of the gate drive pulse is much higher than the frequency (50 or 60 Hz) of the AC voltage VAC (for example, 20 kHz), so individual pulses cannot be drawn, but the pulse width is the peak of the absolute value of the AC waveform. Becomes the widest and becomes narrower as the absolute value approaches zero.
- FIG. 11 is a graph showing another example of how to create a command value for an output waveform in the first converter 1.
- the horizontal axis represents time and the vertical axis represents voltage.
- the waveform of the command value has a peak value of 327 V shown in (a), and a sine wave having a commercial frequency (50 Hz, 0.02 sec / 1 cycle) is a fundamental wave. Obtained by superimposing waves.
- the amplitude of the third harmonic is, for example, 20% of the amplitude of the fundamental wave.
- an AC waveform including the third harmonic as shown in (b) is obtained.
- FIG. 12A shows four periods of the command value (ideal value) of the output waveform of the first converter 1 set in this way.
- the horizontal axis represents time and the vertical axis represents voltage. That is, this approximates a pulsating waveform obtained by full-wave rectification of the AC waveform of the AC voltage VAC, but since the third harmonic is included, the peak value is reduced from 327V to 283V.
- FIG. 12B shows the voltage of the pulsating waveform that actually appears at both ends of the capacitor 14. As is clear from comparison with (a), a pulsating flow waveform almost equivalent to the command value is obtained.
- the switching elements Q9 to Q12 constituting the full bridge inverter 21 of the second conversion unit 2 are driven by the gate drive pulse as shown in FIG. 7 as in the first example. As a result, the polarity of the pulsating flow waveform in FIG. 12 is reversed every pulsating flow cycle.
- FIG. 13 is a graph showing one cycle of the AC voltage VAC output in this way, where (a) is the target voltage (ideal value), and (b) is the AC voltage actually detected by the voltage sensor 6s. a V AC. Although there is a slight distortion near the zero cross, an AC waveform almost as the target is obtained.
- the hardware configuration of the first conversion unit 1 is a DC / DC converter.
- the DC voltage is not converted into a mere DC voltage, but the third harmonic. Is converted into a pulsating flow waveform corresponding to the absolute value of the AC waveform including Therefore, the waveform that is the basis of the AC waveform is generated by the first converter 1.
- the 2nd conversion part 2 inverts the polarity of the voltage containing a pulsating flow waveform for every period, and converts it into the target voltage of an alternating current waveform.
- the voltage of the DC bus L B can be reduced, further 3 Since there is also an effect of reducing the peak value by superimposing the second harmonic, the switching loss of the switching elements Q5 to Q12 in the converter 100 is reduced. Moreover, the iron loss of the insulation transformer 12 is also reduced.
- the full bridge inverter of the second conversion unit 2 drastically reduces the number of switching times compared to the conventional inverter operation. That is, for example, it is drastically reduced (1/200) from a high frequency of about 20 kHz to 100 Hz (for example, twice per cycle of 50 Hz).
- the second converter 2 performs switching at the zero cross timing, the voltage at the time of switching is extremely low (ideally 0 V). Therefore, the switching loss of the second conversion unit 2 is greatly reduced.
- the 2nd conversion part 2 does not perform the inverter operation
- the conversion efficiency of the conversion device 100 can be improved. Further, the capacitor 14 of the first converter 1 only needs to smooth the high-frequency voltage fluctuation, and does not smooth the low-frequency pulsating waveform. Therefore, a capacitor having a low capacitance (for example, 10 ⁇ F or 22 ⁇ F) can be used.
- (Three-phase waveform) (A) of FIG. 14 is a waveform diagram showing phase voltages of U, V, W output from the power converter 100P, and (b) is a diagram of UV, V applied to a three-phase AC load. It is a wave form diagram which shows the line voltage of VW and WU.
- the control unit 3 controls the conversion devices (first conversion device, second conversion device, and third conversion device) 100 for each phase so that the phases of the AC waveforms output by these devices are shifted by (2/3) ⁇ from each other. To do. Even if the third harmonic is included in the phase voltage, the third harmonic is canceled out in the line voltage, and the phases are shifted by (2/3) ⁇ from each other as in the case of the normal sine wave phase voltage.
- the power converter device 100P can apply a three-phase alternating current voltage with respect to the three-phase alternating current load 6, and can supply alternating current power.
- the conversion device 100 can also be used for conversion from alternating current to direct current.
- an AC reactor (same as the AC reactor 23 (FIG. 16) in the second embodiment described later) in the electric path from the interconnection point of the switching elements Q9 and Q10 to the capacitor 22.
- the AC reactor and the capacitor 22 constitute a filter circuit (low-pass filter).
- the second converter 2 when power is supplied from the AC side, the second converter 2 is a “rectifier circuit”, and the rectifier circuit 13 of the first converter 1 is an “inverter”. The high-frequency component generated by the “inverter” does not leak to the AC side due to the presence of the filter circuit.
- the full bridge circuit 11 is a “rectifier circuit”.
- the control unit 3 sends power to the insulating transformer 12 by alternately turning on the switching elements Q5 and Q8 and the switching elements Q6 and Q7 at an appropriate switching frequency such that the insulating transformer 12 is not magnetically saturated.
- the output of the insulation transformer 12 is rectified by a full bridge circuit 11 as a “rectifier circuit” to become a DC voltage.
- FIG. 15 is a circuit diagram showing a three-phase AC power supply apparatus 500 according to the second embodiment.
- the three-phase AC power supply device 500 includes a power conversion device 100P and a DC power source 5 made of, for example, a storage battery, and is connected to a three-phase AC load 6.
- FIG. 16 is a diagram showing the internal circuit of the conversion device 100 for one phase in FIG. 15 in more detail.
- FIG. 16 differs from FIG. 2 in that an AC reactor 23 is provided on the output side of the full-bridge inverter 21 in the second converter 2 and the output voltage of the first converter 1 is detected in FIG.
- the voltage sensor 9 is provided, and the other hardware configuration is the same.
- the AC reactor 23 and the capacitor 22 constitute a filter circuit (low-pass filter) that removes a high-frequency component contained in the output of the second conversion unit 2. Information on the voltage detected by the voltage sensor 9 is sent to the control unit 3.
- FIG. 17 is a diagram illustrating gate drive pulses for the full bridge circuit 11.
- V AC the AC voltage
- VAC the AC voltage VAC
- the pulse width is the peak of the absolute value of the AC waveform. Becomes the widest and becomes narrower as the absolute value approaches zero.
- the gate drive pulse is not output in the vicinity of the zero cross of the AC waveform in a wider range than FIG.
- (A) of FIG. 18 is the command value (ideal value) of 4 cycles of the output waveform of the first conversion unit 1 to be obtained by the gate drive pulse of FIG.
- the horizontal axis represents time and the vertical axis represents voltage. That is, as described above, the third harmonic wave having an amplitude ratio of 10% is added to the pulsating current waveform obtained by full-wave rectification of the AC waveform of the AC voltage VAC (however, the lower limit is cut). It is a superposition.
- the peak value is 283 V (200 ⁇ (2 1/2 )).
- FIG. 18B shows the voltage of the pulsating waveform that actually appears at both ends of the capacitor 14.
- a pulsating flow waveform almost equal to the command value is obtained, but within a period when the voltage is a predetermined ratio or less, for example, 100 V or less, with respect to the peak value of the target voltage, The waveform is slightly distorted.
- FIG. 19 is a diagram in which the waveform of the target voltage in the vicinity of the zero cross is added with a dotted line to the same diagram as in (b) in FIG. 19B and 19C show gate drive pulses for the switching elements Q9 to Q12 constituting the full bridge inverter of the second conversion unit 2.
- FIG. (B) is a gate drive pulse for the switching elements Q9 and Q12
- (c) is a gate drive pulse for the switching elements Q10 and Q11.
- PWM control is performed by high-frequency switching.
- the gate drive pulses of (b) and (c) are alternately 1/0.
- the pulsating flow waveform of (a) is inverted every pulsating flow cycle.
- the control unit 3 switches the switching elements Q9 and Q12 when the voltage output from the first conversion unit 1 shown in (a) is 100 V or less, for example. Is switched at a high frequency to perform inverter operation. Thereby, a voltage is output from the 2nd conversion part 2 so that the target voltage near zero crossing may be approached.
- control unit 3 switches the switching elements Q10 and Q11 at a high frequency to perform an inverter operation when the voltage is 100 V or less, for example. Thereby, a voltage is output from the second conversion unit 2 so as to approach the target voltage in the vicinity of the zero cross.
- FIG. 20 is a graph showing the AC voltage VAC output from the second conversion unit 2 via the filter circuit including the AC reactor 23 and the capacitor 22. As shown in the figure, there is no distortion near the zero cross, and an almost ideal AC waveform according to the target voltage is obtained.
- the predetermined ratio for causing the second converter 2 to operate as an inverter is preferably 18% to 35%. In this case, it is possible to prevent waveform distortion in the vicinity of the zero cross and to sufficiently ensure the effect of reducing loss. For example, when the “predetermined ratio” is less than 18%, there is a possibility that slight distortion near the zero cross may remain. If it is larger than 35%, the high-frequency inverter operation period in the second conversion unit 2 becomes longer, and the loss reduction effect is reduced accordingly.
- FIG. 21 is a diagram illustrating gate drive pulses for the full bridge circuit 11.
- V AC AC voltage
- VAC AC voltage
- the pulse width is the peak of the absolute value of the AC waveform. Becomes the widest and becomes narrower as the absolute value approaches zero.
- the difference from FIG. 10 is that the gate drive pulse is not output in a range wider than that of FIG.
- FIG. 22A is another example of the command value (ideal value) of the output waveform of the first converter 1 that is to be obtained by the gate drive pulse of FIG.
- the horizontal axis represents time and the vertical axis represents voltage. That is, as described above, the third harmonic wave having an amplitude ratio of 20% is added to the pulsating current waveform obtained by full-wave rectification of the AC waveform of the AC voltage VAC (however, the lower limit is cut). It is a superposition.
- the peak value is 283 V (200 ⁇ (2 1/2 )).
- FIG. 22B shows the voltage of the pulsating waveform that actually appears at both ends of the capacitor 14.
- a pulsating flow waveform almost equal to the command value is obtained, but within a period when the voltage is a predetermined ratio or less, for example, 100 V or less, with respect to the peak value of the target voltage, The waveform is slightly distorted.
- the same processing as in FIG. 19 is performed.
- the switching elements Q9, Q12 and Q10, Q11 are switched at a high frequency to perform the inverter operation. Thereby, a voltage is output from the second conversion unit 2 so as to approach the target voltage in the vicinity of the zero cross.
- FIG. 23 is a graph showing the AC voltage VAC output from the second conversion unit 2 through the filter circuit including the AC reactor 23 and the capacitor 22. As shown in the figure, there is no distortion near the zero cross, and an almost ideal AC waveform according to the target voltage is obtained.
- the hardware configuration of the first conversion unit 1 is a DC / DC converter.
- 3 It is converted into a pulsating flow waveform (except for the vicinity of the zero cross) corresponding to the absolute value of the AC waveform including the second harmonic. Therefore, the waveform that is the basis of the AC waveform is mainly generated by the first converter 1.
- the 2nd conversion part 2 inverts the polarity of the voltage containing the pulsating flow waveform which the 1st conversion part 1 output for every period, and converts it into the target voltage of an alternating current waveform.
- the second conversion unit 2 performs an inverter operation only in the vicinity of the zero cross, and generates and outputs an AC waveform in the vicinity of the zero cross that the first conversion unit 1 did not generate.
- the voltage of the DC bus L B can be reduced, further 3 Since there is also an effect of reducing the peak value by superimposing the second harmonic, the switching loss of the switching elements Q5 to Q12 in the converter 100 is reduced. Moreover, the iron loss of the insulation transformer 12 is also reduced.
- the second conversion unit 2 In the vicinity of the zero cross of the target voltage, the second conversion unit 2 contributes to the generation of the AC waveform, and otherwise the first conversion unit 1 contributes to the generation of the AC waveform. If the entire region of the pulsating waveform is generated only by the first conversion unit 1, waveform distortion may occur in the vicinity of the zero cross, but this is achieved by utilizing the inverter operation of the second conversion unit 2 locally. It is possible to prevent distortion of the waveform and to obtain a smoother AC waveform output.
- the loss is extremely small as compared with the conventional inverter operation. Further, the loss due to the AC reactor 23 is less than that of the conventional inverter operation. In addition, the relatively low voltage during the period near the zero cross in which the inverter is operated also contributes to reducing the loss due to switching and the loss due to the AC reactor. By reducing the loss as described above, the conversion efficiency of the conversion device 100 can be improved, and a smoother AC waveform output can be obtained.
- standard which determines the period which makes the 2nd conversion part 2 inverter-operate at a high frequency is the same as that of a 1st example.
- FIG. 24 is a circuit diagram of the conversion device 100 for one phase in the three-phase AC power supply device and the power conversion device according to the third embodiment.
- the figure corresponding to FIG. 15 is omitted. That is, the three-phase AC power supply device and the power conversion device according to the third embodiment are obtained by replacing the conversion device 100 in FIG. 15 with the conversion device 100 in FIG.
- FIG. 24 differs from FIG. 16 (second embodiment) in that the primary side (left side in the figure) winding 12p of the isolation transformer 12 is provided with a center tap, and in FIG. A certain point is a push-pull circuit 11A using a center tap.
- the push-pull circuit 11A includes a DC reactor 15 and switching elements Qa and Qb, which are connected as illustrated.
- the switching elements Qa and Qb are PWM-controlled by the control unit 3, and when the push-pull circuit 11A is operating, one is on and the other is off.
- the current by the DC voltage V DC enters the isolation transformer 12 from the DC reactor 15 through the switching element Qa, Qb which is turned on, and exits from the center tap.
- the switching element Qa, Qb which is turned on, and exits from the center tap.
- transformation by the insulating transformer 12 can be performed.
- PWM control By performing PWM control on the gate drive pulses of the switching elements Qa and Qb, the same function as that of the first conversion unit 1 in the second embodiment can be realized.
- the command value (ideal value) of the output waveform of the first converter 1 in the third embodiment is shown in (a) of FIG. 18 as in the second embodiment.
- the gate drive pulses for the switching elements Q9 and Q12 and the gate drive pulses for the switching elements Q10 and Q11 constituting the full bridge inverter 21 of the second conversion unit 2 are respectively shown in FIG. (B) and (c).
- the conversion device 100 of the third embodiment a function similar to that of the second embodiment can be realized, and a smooth AC waveform output can be obtained.
- the push-pull circuit 11A has fewer switching elements than the full bridge circuit 11 (FIG. 16) of the second embodiment, the switching loss is reduced accordingly.
- the conversion device 100 of the first to third embodiments can be widely used in a power supply system (mainly for business use) that supplies AC power from a DC power supply such as a storage battery, a self-supporting power supply, a UPS, and the like. Further, in FIG. 1 or FIG. 15, the DC voltage is input from the common DC power supply 5 to the three sets of conversion devices 100.
- the use of a common DC power supply in this way is also an advantage of the converter 100 using the insulating transformer 12.
- the present invention is not limited to using a common DC power supply, and DC power supplies may be individually provided for a plurality of conversion devices.
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Abstract
Description
一方、三相インバータを用いることにより、直流電源の電圧を三相交流電圧に変換することもできる(例えば、特許文献1(図7)参照。)。
電力変換装置200は、コンデンサ202と、例えば3組の昇圧回路203と、DCバス204の電圧を平滑化する平滑回路205と、三相インバータ回路207と、3組のACリアクトル208~210及びコンデンサ211~213とを備えている。平滑回路205は、耐電圧性能確保のため2直列、容量確保のため6並列に、コンデンサ206を接続して成るものである。この平滑回路全体としての容量は、例えば数mFである。
前記第1相変換装置、前記第2相変換装置及び前記第3相変換装置の各々は、絶縁トランスを含むDC/DCコンバータ及び平滑用のコンデンサを有し、前記制御部が前記DC/DCコンバータを制御することにより、入力される直流電圧を、出力すべき交流波形として基本波に3次高調波を重畳した電圧の絶対値に相当する脈流波形を含む電圧に変換する第1変換部と、前記第1変換部より後段に設けられ、フルブリッジインバータを有し、前記制御部が前記フルブリッジインバータを制御することにより、前記脈流波形を含む電圧を1周期ごとに極性反転して前記交流波形の電圧に変換する第2変換部と、を備えている。
前記第1相変換装置、前記第2相変換装置及び前記第3相変換装置の各々は、絶縁トランスを含むDC/DCコンバータ及び平滑用のコンデンサを有し、前記制御部が前記DC/DCコンバータを制御することにより、入力される直流電圧を、出力すべき交流波形として基本波に3次高調波を重畳した電圧の絶対値に相当する脈流波形を含む電圧に変換する第1変換部と、前記第1変換部より後段に設けられ、フルブリッジインバータを有し、前記制御部が前記フルブリッジインバータを制御することにより、前記脈流波形を含む電圧を1周期ごとに極性反転して前記交流波形の電圧に変換する第2変換部と、を備えている。
本発明の実施形態の要旨としては、少なくとも以下のものが含まれる。
前記第1相変換装置、前記第2相変換装置及び前記第3相変換装置の各々は、絶縁トランスを含むDC/DCコンバータ及び平滑用のコンデンサを有し、前記制御部が前記DC/DCコンバータを制御することにより、入力される直流電圧を、出力すべき交流波形として基本波に3次高調波を重畳した電圧の絶対値に相当する脈流波形を含む電圧に変換する第1変換部と、前記第1変換部より後段に設けられ、フルブリッジインバータを有し、前記制御部が前記フルブリッジインバータを制御することにより、前記脈流波形を含む電圧を1周期ごとに極性反転して前記交流波形の電圧に変換する第2変換部と、を備えている。
この場合、交流波形の基になる(1/2)周期の波形は全て第1変換部によって生成され、第2変換部は出力する交流波形の周波数の2倍の周波数で極性反転のみを行う。すなわち、第2変換部は、高周波のスイッチングを伴うインバータ動作を行わない。そのため、第2変換部の出力側にACリアクトルは不要となり、ACリアクトルによる損失を排除することができる。
この場合、ゼロクロス近傍での波形の歪みを防止し、かつ、損失低減の効果も十分に確保することができる。例えば、「所定の割合」を18%未満にすると、ゼロクロス近傍での僅かな歪みが残る可能性がある。35%より大きくすると、第2変換部2における高周波のインバータ動作期間が長くなるので、その分、損失低減の効果が薄れる。
この場合、スイッチングに伴う高周波の電圧変動は除去しつつ、所望の脈流波形を得ることができる。
前記第1相変換装置、前記第2相変換装置及び前記第3相変換装置の各々は、絶縁トランスを含むDC/DCコンバータ及び平滑用のコンデンサを有し、前記制御部が前記DC/DCコンバータを制御することにより、入力される直流電圧を、出力すべき交流波形として基本波に3次高調波を重畳した電圧の絶対値に相当する脈流波形を含む電圧に変換する第1変換部と、前記第1変換部より後段に設けられ、フルブリッジインバータを有し、前記制御部が前記フルブリッジインバータを制御することにより、前記脈流波形を含む電圧を1周期ごとに極性反転して前記交流波形の電圧に変換する第2変換部と、を備えている。
この場合も、(1)の電力変換装置と同様の作用効果を奏する。
以下、発明の実施形態について、図面を参照して詳細に説明する。
(三相回路図)
図1は、第1実施形態に係る三相交流電源装置500を示す回路図である。三相交流電源装置500は、電力変換装置100Pと、例えば蓄電池からなる直流電源5とを備え、三相交流負荷6に接続される。
図2は、図1における1相分の変換装置100の内部回路を、より詳細に示す図である。
この変換装置100は、入力される直流電圧VDCを、交流波形の目標電圧である交流電圧VACに変換して出力する。なお、変換装置100は、交流から直流への変換も可能であるが、ここでは、主として直流から交流への変換に着目して説明する(第2実施形態及び第3実施形態においても同様である。)。
DC/DCコンバータ10は、入力側から順に、4つのスイッチング素子Q1,Q2,Q3,Q4によって構成されるフルブリッジ回路11と、絶縁トランス12と、4つのスイッチング素子Q5,Q6,Q7,Q8によって構成される整流回路13とを備え、これらは図示のように接続されている。
上記スイッチング素子Q1~Q12は、制御部3によって制御される。スイッチング素子Q1~Q12としては、例えばIGBT(Insulated Gate Bipolar Transistor)やFET(Field Effect Transistor)を用いることができる。
さらに、DCバスLBに接続されるスイッチング素子Q5~Q12及び平滑用のコンデンサ14は、耐電圧性能の低いものでも使用できるようになる。スイッチング素子は耐電圧性能が低い方が、オン抵抗が低いため、導通損を低減することができる。
(波形の第1例)
次に、上記変換装置100の動作について説明する。まず、制御部3は、第1変換部1のフルブリッジ回路11(スイッチング素子Q1~Q4)を、PWM制御する。
図3は、フルブリッジ回路11に対するゲート駆動パルスを示す図である。図中、二点鎖線で示す波形が、目標電圧である交流電圧VACである。但し、後述するが、この波形は通常の正弦波ではない。ゲート駆動パルスの周波数は、交流電圧VACの周波数(50又は60Hz)に比べて格段に高周波(例えば20kHz)であるため、個々のパルスは描けないが、交流波形の絶対値のピークでパルス幅が最も広くなり、絶対値が0に近づくほど狭くなる。
以上のように、上記の変換装置100によれば、第1変換部1のハードウェア構成はDC/DCコンバータであるが、直流電圧を、単なる直流電圧に変換するのではなく、3次高調波を含む交流波形の絶対値に相当する脈流波形に変換する。従って、交流波形の基になる波形は第1変換部1によって生成される。そして、第2変換部2は、脈流波形を含む電圧を1周期ごとに極性反転して交流波形の目標電圧に変換する。
このようにして相電圧を出力すれば、三相交流負荷6に対する線間電圧(400V)を単一の三相インバータで供給する場合と比べて、DCバスLBの電圧が低減され、さらに3次高調波の重畳による波高値の低減効果もあるため、変換装置100内のスイッチング素子Q5~Q12のスイッチング損失が低下する。また、絶縁トランス12の鉄損も低下する。
また、第1変換部1のコンデンサ14は、高周波の電圧変動のみ平滑化すればよく、低周波の脈流波形は平滑化しない。従って、低容量(例えば10μFや22μF)のコンデンサを使用することができる。
図9の(a)は、電力変換装置100Pから出力されるU,V,Wの相電圧を示す波形図であり、また、(b)は、三相交流負荷に印加されるU-V,V-W,W-Uの線間電圧を示す波形図である。
制御部3は、各相の変換装置(第1変換装置,第2変換装置,第3変換装置)100を、これらが出力する交流波形の位相が相互に(2/3)πずれるように制御する。相電圧に3次高調波が含まれていても、線間電圧では3次高調波が打ち消され、通常の正弦波の相電圧の場合と同様に、位相が相互に(2/3)πずれた波高値566V(=400×(21/2)=283×2)の3相の線間電圧が得られる。
これにより、電力変換装置100Pは、三相交流電圧を三相交流負荷6に対して印加し、交流電力を供給することができる。
図10は、フルブリッジ回路11に対するゲート駆動パルスを示す図である。図中、二点鎖線で示す波形が、目標電圧である交流電圧VACである。但し、この波形は通常の正弦波ではない。ゲート駆動パルスの周波数は、交流電圧VACの周波数(50又は60Hz)に比べて格段に高周波(例えば20kHz)であるため、個々のパルスは描けないが、交流波形の絶対値のピークでパルス幅が最も広くなり、絶対値が0に近づくほど狭くなる。
また、図12の(b)は、実際にコンデンサ14の両端に現れる脈流波形の電圧である。(a)との比較により明らかなように、ほぼ、指令値通りの脈流波形が得られる。
以上のように、上記の変換装置100によれば、第1変換部1のハードウェア構成はDC/DCコンバータであるが、直流電圧を、単なる直流電圧に変換するのではなく、3次高調波を含む交流波形の絶対値に相当する脈流波形に変換する。従って、交流波形の基になる波形は第1変換部1によって生成される。そして、第2変換部2は、脈流波形を含む電圧を1周期ごとに極性反転して交流波形の目標電圧に変換する。
このようにして相電圧を出力すれば、三相交流負荷6に対する線間電圧(400V)を単一の三相インバータで供給する場合と比べて、DCバスLBの電圧が低減され、さらに3次高調波の重畳による波高値の低減効果もあるため、変換装置100内のスイッチング素子Q5~Q12のスイッチング損失が低下する。また、絶縁トランス12の鉄損も低下する。
また、第1変換部1のコンデンサ14は、高周波の電圧変動のみ平滑化すればよく、低周波の脈流波形は平滑化しない。従って、低容量(例えば10μFや22μF)のコンデンサを使用することができる。
図14の(a)は、電力変換装置100Pから出力されるU,V,Wの相電圧を示す波形図であり、また、(b)は、三相交流負荷に印加されるU-V,V-W,W-Uの線間電圧を示す波形図である。
制御部3は、各相の変換装置(第1変換装置,第2変換装置,第3変換装置)100を、これらが出力する交流波形の位相が相互に(2/3)πずれるように制御する。相電圧に3次高調波が含まれていても、線間電圧では3次高調波が打ち消され、通常の正弦波の相電圧の場合と同様に、位相が相互に(2/3)πずれた波高値566V(=400×(21/2)=283×2)の3相の線間電圧が得られる。
これにより、電力変換装置100Pは、三相交流電圧を三相交流負荷6に対して印加し、交流電力を供給することができる。
なお、前述のように、変換装置100は、交流から直流への変換にも使用可能である。但し、この場合は、スイッチング素子Q9,Q10の相互接続点からコンデンサ22までの電路にACリアクトル(後述する第2実施形態におけるACリアクトル23(図16)と同じ。)を挿入することが好ましい。
この場合、ACリアクトルはコンデンサ22と共に、フィルタ回路(ローパスフィルタ)を構成する。図2において、交流側から給電する場合には、第2変換部2は「整流回路」となり、第1変換部1の整流回路13が「インバータ」となる。この「インバータ」が発生する高周波成分は、上記のフィルタ回路の存在により交流側には漏出しない。
(三相回路図)
図15は、第2実施形態に係る三相交流電源装置500を示す回路図である。三相交流電源装置500は、電力変換装置100Pと、例えば蓄電池からなる直流電源5とを備え、三相交流負荷6に接続される。
また、図16は、図15における1相分の変換装置100の内部回路を、より詳細に示す図である。
図16が、図2と異なるのは、図16において、第2変換部2におけるフルブリッジインバータ21の出力側に、ACリアクトル23を設けた点、及び、第1変換部1の出力電圧を検知する電圧センサ9を設けた点であり、その他のハードウェア構成は同じである。ACリアクトル23及びコンデンサ22は、第2変換部2の出力に含まれる高周波成分を取り除くフィルタ回路(ローパスフィルタ)を構成する。電圧センサ9が検知した電圧の情報は、制御部3に送られる。
(波形の第1例)
図17は、フルブリッジ回路11に対するゲート駆動パルスを示す図である。図中、二点鎖線で示す波形が、目標電圧の交流電圧VACである。但し、この波形は通常の正弦波ではない。ゲート駆動パルスの周波数は、交流電圧VACの周波数(50又は60Hz)に比べて格段に高周波(例えば20kHz)であるため、個々のパルスは描けないが、交流波形の絶対値のピークでパルス幅が最も広くなり、絶対値が0に近づくほど狭くなる。図3との違いは、交流波形のゼロクロス近傍において図3よりも広い範囲で、ゲート駆動パルスが出力されない点である。
この場合、ゼロクロス近傍での波形の歪みを防止し、かつ、損失低減の効果も十分に確保することができる。例えば、「所定の割合」を18%未満にすると、ゼロクロス近傍での僅かな歪みが残る可能性がある。35%より大きくすると、第2変換部2における高周波のインバータ動作期間が長くなるので、その分、損失低減の効果が薄れる。
三相波形の生成については図9と同様であるので、ここでは説明を省略する。
図21は、フルブリッジ回路11に対するゲート駆動パルスを示す図である。図中、二点鎖線で示す波形が、目標電圧の交流電圧VACである。但し、この波形は通常の正弦波ではない。ゲート駆動パルスの周波数は、交流電圧VACの周波数(50又は60Hz)に比べて格段に高周波(例えば20kHz)であるため、個々のパルスは描けないが、交流波形の絶対値のピークでパルス幅が最も広くなり、絶対値が0に近づくほど狭くなる。図10との違いは、交流波形のゼロクロス近傍において図10よりも広い範囲で、ゲート駆動パルスが出力されない点である。
三相波形の生成については図14と同様であるので、ここでは説明を省略する。
以上のように、第2実施形態の変換装置100によれば、第1変換部1のハードウェア構成はDC/DCコンバータであるが、直流電圧を、単なる直流電圧に変換するのではなく、3次高調波を含む交流波形の絶対値に相当する脈流波形(但し、ゼロクロス近傍を除く。)に変換する。従って、交流波形の基になる波形は主として第1変換部1によって生成される。また、第2変換部2は、第1変換部1が出力した脈流波形を含む電圧を1周期ごとに極性反転して交流波形の目標電圧に変換する。さらに、第2変換部2は、ゼロクロス近傍についてのみ、インバータ動作を行って第1変換部1が生成しなかったゼロクロス近傍の交流波形を生成し、出力する。
以上のような損失の低減により、変換装置100の変換効率を向上させることができ、しかも、より滑らかな交流波形の出力を得ることができる。
図24は、第3実施形態に係る三相交流電源装置及び電力変換装置における、1相分の変換装置100の回路図である。ここでは、図15に対応する図は省略する。すなわち、図15における変換装置100を、図24の変換装置100に入れ替えたものが、第3実施形態に係る三相交流電源装置及び電力変換装置である。
また、第2変換部2のフルブリッジインバータ21を構成するスイッチング素子Q9,Q12に対するゲート駆動パルス、及び、スイッチング素子Q10,Q11に対するゲート駆動パルスは、それぞれ、第2実施形態と同様に、図19の(b)、(c)に示すものとなる。
こうして、第2実施形態と同様に、図20に示すような、ほぼ目標電圧通りの交流波形が得られる。
なお、上記各実施形態では、電力変換装置100Pを三相交流負荷6に接続する場合について説明したが、かかる電力変換装置100Pを、単相負荷や電力系統に接続することも可能である。
また、図1又は図15では、3組の変換装置100に対して共通の直流電源5から直流電圧を入力する構成とした。このように共通の直流電源を使用することができるのは、絶縁トランス12を用いる変換装置100の利点でもある。しかしながら、共通の直流電源を使用することに限定される訳ではなく、複数の変換装置に対して個別に直流電源を設けてもよい。
2 第2変換部
3 制御部
4 コンデンサ
5 直流電源
5s 電圧センサ
6 三相交流負荷
6p 相負荷
6s 電圧センサ
9 電圧センサ
10 DC/DCコンバータ
11 フルブリッジ回路
11A プッシュプル回路
12 絶縁トランス
12p 1次側巻線
13 整流回路
14 コンデンサ
15 DCリアクトル
21 フルブリッジインバータ
22 コンデンサ
23 ACリアクトル
100 変換装置
100P 電力変換装置
200 電力変換装置
201 直流電源
202 コンデンサ
203 昇圧回路
203t 絶縁トランス
204 DCバス
205 平滑回路
206 コンデンサ
207 三相インバータ回路
208~210 ACリアクトル
211~213 コンデンサ
220 三相交流負荷
500 三相交流電源装置
LB DCバス
N 中性点
Q1~Q12,Qa,Qb スイッチング素子
Claims (6)
- 直流電源から入力される直流電圧を、三相交流電圧に変換する電力変換装置であって、
前記直流電源から入力される直流電圧を、三相交流の中性点に対する第1相に出力すべき交流波形の電圧に変換する第1相変換装置と、
前記直流電源から入力される直流電圧を、前記中性点に対する第2相に出力すべき交流波形に変換する第2相変換装置と、
前記直流電源から入力される直流電圧を、前記中性点に対する第3相に出力すべき交流波形の電圧に変換する第3相変換装置と、
前記第1相変換装置、前記第2相変換装置、及び、前記第3相変換装置を制御する制御部と、を備え、
前記第1相変換装置、前記第2相変換装置及び前記第3相変換装置の各々は、
絶縁トランスを含むDC/DCコンバータ及び平滑用のコンデンサを有し、前記制御部が前記DC/DCコンバータを制御することにより、入力される直流電圧を、出力すべき交流波形として基本波に3次高調波を重畳した電圧の絶対値に相当する脈流波形を含む電圧に変換する第1変換部と、
前記第1変換部より後段に設けられ、フルブリッジインバータを有し、前記制御部が前記フルブリッジインバータを制御することにより、前記脈流波形を含む電圧を1周期ごとに極性反転して前記交流波形の電圧に変換する第2変換部と、
を備えている電力変換装置。 - 前記第1変換部は、前記直流電圧を、連続した前記脈流波形の電圧に変換する請求項1に記載の電力変換装置。
- 前記第1変換部の出力する電圧が、前記脈流波形の波高値に対して所定の割合以下となる期間内にあるとき、前記制御部は、前記フルブリッジインバータを、高周波でインバータ動作させることにより、前記期間内の前記交流波形の電圧を生成する請求項1に記載の電力変換装置。
- 前記所定の割合とは、18%~35%である請求項3に記載の電力変換装置。
- 前記コンデンサは、前記第1変換部におけるスイッチングによる高周波の電圧変動を平滑化するが、前記脈流波形は平滑化しない程度の容量を有する請求項1~請求項4のいずれか1項に記載の電力変換装置。
- 直流電源と、
前記直流電源から入力される直流電圧を、三相交流の中性点に対する第1相に出力すべき交流波形の電圧に変換する第1相変換装置と、
前記直流電源から入力される直流電圧を、前記中性点に対する第2相に出力すべき交流波形の電圧に変換する第2相変換装置と、
前記直流電源から入力される直流電圧を、前記中性点に対する第3相に出力すべき交流波形の電圧に変換する第3相変換装置と、
前記第1相変換装置、前記第2相変換装置、及び、前記第3相変換装置を制御する制御部と、を備え、
前記第1相変換装置、前記第2相変換装置及び前記第3相変換装置の各々は、
絶縁トランスを含むDC/DCコンバータ及び平滑用のコンデンサを有し、前記制御部が前記DC/DCコンバータを制御することにより、入力される直流電圧を、出力すべき交流波形として基本波に3次高調波を重畳した電圧の絶対値に相当する脈流波形を含む電圧に変換する第1変換部と、
前記第1変換部より後段に設けられ、フルブリッジインバータを有し、前記制御部が前記フルブリッジインバータを制御することにより、前記脈流波形を含む電圧を1周期ごとに極性反転して前記交流波形の電圧に変換する第2変換部と、
を備えている三相交流電源装置。
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JP2015226427A (ja) | 2015-12-14 |
US20170104422A1 (en) | 2017-04-13 |
US9831676B2 (en) | 2017-11-28 |
CN106464155B (zh) | 2019-03-26 |
EP3151412A4 (en) | 2018-02-07 |
KR20170007328A (ko) | 2017-01-18 |
CN106464155A (zh) | 2017-02-22 |
EP3151412A1 (en) | 2017-04-05 |
KR102352530B1 (ko) | 2022-01-19 |
AU2015265242B2 (en) | 2019-02-14 |
TW201603471A (zh) | 2016-01-16 |
TWI667874B (zh) | 2019-08-01 |
JP6303819B2 (ja) | 2018-04-04 |
EP3151412B1 (en) | 2021-07-28 |
AU2015265242A1 (en) | 2016-11-03 |
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