WO2015029374A1 - 制御回路、スイッチング回路、電力変換装置、充電装置、車両、および、制御方法 - Google Patents
制御回路、スイッチング回路、電力変換装置、充電装置、車両、および、制御方法 Download PDFInfo
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- WO2015029374A1 WO2015029374A1 PCT/JP2014/004223 JP2014004223W WO2015029374A1 WO 2015029374 A1 WO2015029374 A1 WO 2015029374A1 JP 2014004223 W JP2014004223 W JP 2014004223W WO 2015029374 A1 WO2015029374 A1 WO 2015029374A1
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- B—PERFORMING OPERATIONS; TRANSPORTING
- B60—VEHICLES IN GENERAL
- B60L—PROPULSION OF ELECTRICALLY-PROPELLED VEHICLES; SUPPLYING ELECTRIC POWER FOR AUXILIARY EQUIPMENT OF ELECTRICALLY-PROPELLED VEHICLES; ELECTRODYNAMIC BRAKE SYSTEMS FOR VEHICLES IN GENERAL; MAGNETIC SUSPENSION OR LEVITATION FOR VEHICLES; MONITORING OPERATING VARIABLES OF ELECTRICALLY-PROPELLED VEHICLES; ELECTRIC SAFETY DEVICES FOR ELECTRICALLY-PROPELLED VEHICLES
- B60L3/00—Electric devices on electrically-propelled vehicles for safety purposes; Monitoring operating variables, e.g. speed, deceleration or energy consumption
- B60L3/0023—Detecting, eliminating, remedying or compensating for drive train abnormalities, e.g. failures within the drive train
- B60L3/003—Detecting, eliminating, remedying or compensating for drive train abnormalities, e.g. failures within the drive train relating to inverters
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
- H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
- H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M7/53—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M7/537—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
- H02M7/5387—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration
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- B—PERFORMING OPERATIONS; TRANSPORTING
- B60—VEHICLES IN GENERAL
- B60L—PROPULSION OF ELECTRICALLY-PROPELLED VEHICLES; SUPPLYING ELECTRIC POWER FOR AUXILIARY EQUIPMENT OF ELECTRICALLY-PROPELLED VEHICLES; ELECTRODYNAMIC BRAKE SYSTEMS FOR VEHICLES IN GENERAL; MAGNETIC SUSPENSION OR LEVITATION FOR VEHICLES; MONITORING OPERATING VARIABLES OF ELECTRICALLY-PROPELLED VEHICLES; ELECTRIC SAFETY DEVICES FOR ELECTRICALLY-PROPELLED VEHICLES
- B60L15/00—Methods, circuits, or devices for controlling the traction-motor speed of electrically-propelled vehicles
- B60L15/007—Physical arrangements or structures of drive train converters specially adapted for the propulsion motors of electric vehicles
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- B—PERFORMING OPERATIONS; TRANSPORTING
- B60—VEHICLES IN GENERAL
- B60L—PROPULSION OF ELECTRICALLY-PROPELLED VEHICLES; SUPPLYING ELECTRIC POWER FOR AUXILIARY EQUIPMENT OF ELECTRICALLY-PROPELLED VEHICLES; ELECTRODYNAMIC BRAKE SYSTEMS FOR VEHICLES IN GENERAL; MAGNETIC SUSPENSION OR LEVITATION FOR VEHICLES; MONITORING OPERATING VARIABLES OF ELECTRICALLY-PROPELLED VEHICLES; ELECTRIC SAFETY DEVICES FOR ELECTRICALLY-PROPELLED VEHICLES
- B60L50/00—Electric propulsion with power supplied within the vehicle
- B60L50/50—Electric propulsion with power supplied within the vehicle using propulsion power supplied by batteries or fuel cells
- B60L50/60—Electric propulsion with power supplied within the vehicle using propulsion power supplied by batteries or fuel cells using power supplied by batteries
- B60L50/66—Arrangements of batteries
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- B—PERFORMING OPERATIONS; TRANSPORTING
- B60—VEHICLES IN GENERAL
- B60L—PROPULSION OF ELECTRICALLY-PROPELLED VEHICLES; SUPPLYING ELECTRIC POWER FOR AUXILIARY EQUIPMENT OF ELECTRICALLY-PROPELLED VEHICLES; ELECTRODYNAMIC BRAKE SYSTEMS FOR VEHICLES IN GENERAL; MAGNETIC SUSPENSION OR LEVITATION FOR VEHICLES; MONITORING OPERATING VARIABLES OF ELECTRICALLY-PROPELLED VEHICLES; ELECTRIC SAFETY DEVICES FOR ELECTRICALLY-PROPELLED VEHICLES
- B60L53/00—Methods of charging batteries, specially adapted for electric vehicles; Charging stations or on-board charging equipment therefor; Exchange of energy storage elements in electric vehicles
- B60L53/20—Methods of charging batteries, specially adapted for electric vehicles; Charging stations or on-board charging equipment therefor; Exchange of energy storage elements in electric vehicles characterised by converters located in the vehicle
- B60L53/22—Constructional details or arrangements of charging converters specially adapted for charging electric vehicles
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- B—PERFORMING OPERATIONS; TRANSPORTING
- B60—VEHICLES IN GENERAL
- B60L—PROPULSION OF ELECTRICALLY-PROPELLED VEHICLES; SUPPLYING ELECTRIC POWER FOR AUXILIARY EQUIPMENT OF ELECTRICALLY-PROPELLED VEHICLES; ELECTRODYNAMIC BRAKE SYSTEMS FOR VEHICLES IN GENERAL; MAGNETIC SUSPENSION OR LEVITATION FOR VEHICLES; MONITORING OPERATING VARIABLES OF ELECTRICALLY-PROPELLED VEHICLES; ELECTRIC SAFETY DEVICES FOR ELECTRICALLY-PROPELLED VEHICLES
- B60L53/00—Methods of charging batteries, specially adapted for electric vehicles; Charging stations or on-board charging equipment therefor; Exchange of energy storage elements in electric vehicles
- B60L53/30—Constructional details of charging stations
- B60L53/35—Means for automatic or assisted adjustment of the relative position of charging devices and vehicles
- B60L53/36—Means for automatic or assisted adjustment of the relative position of charging devices and vehicles by positioning the vehicle
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/08—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters
- H02M1/088—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters for the simultaneous control of series or parallel connected semiconductor devices
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
- H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
- H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
- H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
- H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/33507—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of the output voltage or current, e.g. flyback converters
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
- H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
- H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
- H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
- H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/337—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only in push-pull configuration
- H02M3/3376—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only in push-pull configuration with automatic control of output voltage or current
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- B—PERFORMING OPERATIONS; TRANSPORTING
- B60—VEHICLES IN GENERAL
- B60L—PROPULSION OF ELECTRICALLY-PROPELLED VEHICLES; SUPPLYING ELECTRIC POWER FOR AUXILIARY EQUIPMENT OF ELECTRICALLY-PROPELLED VEHICLES; ELECTRODYNAMIC BRAKE SYSTEMS FOR VEHICLES IN GENERAL; MAGNETIC SUSPENSION OR LEVITATION FOR VEHICLES; MONITORING OPERATING VARIABLES OF ELECTRICALLY-PROPELLED VEHICLES; ELECTRIC SAFETY DEVICES FOR ELECTRICALLY-PROPELLED VEHICLES
- B60L2210/00—Converter types
- B60L2210/10—DC to DC converters
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- B—PERFORMING OPERATIONS; TRANSPORTING
- B60—VEHICLES IN GENERAL
- B60L—PROPULSION OF ELECTRICALLY-PROPELLED VEHICLES; SUPPLYING ELECTRIC POWER FOR AUXILIARY EQUIPMENT OF ELECTRICALLY-PROPELLED VEHICLES; ELECTRODYNAMIC BRAKE SYSTEMS FOR VEHICLES IN GENERAL; MAGNETIC SUSPENSION OR LEVITATION FOR VEHICLES; MONITORING OPERATING VARIABLES OF ELECTRICALLY-PROPELLED VEHICLES; ELECTRIC SAFETY DEVICES FOR ELECTRICALLY-PROPELLED VEHICLES
- B60L2210/00—Converter types
- B60L2210/30—AC to DC converters
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- B—PERFORMING OPERATIONS; TRANSPORTING
- B60—VEHICLES IN GENERAL
- B60L—PROPULSION OF ELECTRICALLY-PROPELLED VEHICLES; SUPPLYING ELECTRIC POWER FOR AUXILIARY EQUIPMENT OF ELECTRICALLY-PROPELLED VEHICLES; ELECTRODYNAMIC BRAKE SYSTEMS FOR VEHICLES IN GENERAL; MAGNETIC SUSPENSION OR LEVITATION FOR VEHICLES; MONITORING OPERATING VARIABLES OF ELECTRICALLY-PROPELLED VEHICLES; ELECTRIC SAFETY DEVICES FOR ELECTRICALLY-PROPELLED VEHICLES
- B60L2210/00—Converter types
- B60L2210/40—DC to AC converters
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- B—PERFORMING OPERATIONS; TRANSPORTING
- B60—VEHICLES IN GENERAL
- B60L—PROPULSION OF ELECTRICALLY-PROPELLED VEHICLES; SUPPLYING ELECTRIC POWER FOR AUXILIARY EQUIPMENT OF ELECTRICALLY-PROPELLED VEHICLES; ELECTRODYNAMIC BRAKE SYSTEMS FOR VEHICLES IN GENERAL; MAGNETIC SUSPENSION OR LEVITATION FOR VEHICLES; MONITORING OPERATING VARIABLES OF ELECTRICALLY-PROPELLED VEHICLES; ELECTRIC SAFETY DEVICES FOR ELECTRICALLY-PROPELLED VEHICLES
- B60L2240/00—Control parameters of input or output; Target parameters
- B60L2240/10—Vehicle control parameters
- B60L2240/36—Temperature of vehicle components or parts
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- B—PERFORMING OPERATIONS; TRANSPORTING
- B60—VEHICLES IN GENERAL
- B60L—PROPULSION OF ELECTRICALLY-PROPELLED VEHICLES; SUPPLYING ELECTRIC POWER FOR AUXILIARY EQUIPMENT OF ELECTRICALLY-PROPELLED VEHICLES; ELECTRODYNAMIC BRAKE SYSTEMS FOR VEHICLES IN GENERAL; MAGNETIC SUSPENSION OR LEVITATION FOR VEHICLES; MONITORING OPERATING VARIABLES OF ELECTRICALLY-PROPELLED VEHICLES; ELECTRIC SAFETY DEVICES FOR ELECTRICALLY-PROPELLED VEHICLES
- B60L2240/00—Control parameters of input or output; Target parameters
- B60L2240/40—Drive Train control parameters
- B60L2240/52—Drive Train control parameters related to converters
- B60L2240/525—Temperature of converter or components thereof
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/0048—Circuits or arrangements for reducing losses
- H02M1/0054—Transistor switching losses
- H02M1/0058—Transistor switching losses by employing soft switching techniques, i.e. commutation of transistors when applied voltage is zero or when current flow is zero
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
- H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
- H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M7/53—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M7/537—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
- H02M7/5387—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration
- H02M7/53871—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration with automatic control of output voltage or current
- H02M7/53878—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration with automatic control of output voltage or current by time shifting switching signals of one diagonal pair of the bridge with respect to the other diagonal pair
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- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02T—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO TRANSPORTATION
- Y02T10/00—Road transport of goods or passengers
- Y02T10/60—Other road transportation technologies with climate change mitigation effect
- Y02T10/64—Electric machine technologies in electromobility
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- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02T—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO TRANSPORTATION
- Y02T10/00—Road transport of goods or passengers
- Y02T10/60—Other road transportation technologies with climate change mitigation effect
- Y02T10/70—Energy storage systems for electromobility, e.g. batteries
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- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02T—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO TRANSPORTATION
- Y02T10/00—Road transport of goods or passengers
- Y02T10/60—Other road transportation technologies with climate change mitigation effect
- Y02T10/7072—Electromobility specific charging systems or methods for batteries, ultracapacitors, supercapacitors or double-layer capacitors
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- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02T—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO TRANSPORTATION
- Y02T10/00—Road transport of goods or passengers
- Y02T10/60—Other road transportation technologies with climate change mitigation effect
- Y02T10/72—Electric energy management in electromobility
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- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02T—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO TRANSPORTATION
- Y02T10/00—Road transport of goods or passengers
- Y02T10/80—Technologies aiming to reduce greenhouse gasses emissions common to all road transportation technologies
- Y02T10/92—Energy efficient charging or discharging systems for batteries, ultracapacitors, supercapacitors or double-layer capacitors specially adapted for vehicles
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- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02T—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO TRANSPORTATION
- Y02T90/00—Enabling technologies or technologies with a potential or indirect contribution to GHG emissions mitigation
- Y02T90/10—Technologies relating to charging of electric vehicles
- Y02T90/12—Electric charging stations
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- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02T—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO TRANSPORTATION
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- Y02T90/10—Technologies relating to charging of electric vehicles
- Y02T90/14—Plug-in electric vehicles
Definitions
- the present disclosure relates to a control circuit, a switching circuit, a power conversion device, a charging device, a vehicle, and a control method.
- the present disclosure provides a switching circuit, a power conversion device, a charging device, a vehicle, a control circuit, and a control method that can improve the reliability of the switching element.
- a switching circuit includes a first arm including a first switching element and a second switching element, and a second arm connected in parallel to the first arm and including a third switching element and a fourth switching element. And the third switching element is turned off and the fourth switching element is turned on after the first switching element is turned on and the second switching element is turned off. A first control signal group, and the third switching element is turned off and the fourth switching element is turned on before the first switching element is turned on and the second switching element is turned off. And a control circuit for outputting a second control signal group.
- the reliability of the switching element included in the switching circuit can be improved.
- FIG. 1 is a circuit diagram of a configuration example of the DC-DC converter according to the first embodiment.
- FIG. 2 is a timing chart showing an example of the operation of the DC-DC converter.
- FIG. 3 is a timing chart showing an example of the operation of the DC-DC converter.
- FIG. 4 is a timing chart showing the operation of the DC-DC converter according to the comparative example.
- FIG. 5 is a timing chart illustrating the operation of the DC-DC converter according to the embodiment.
- FIG. 6 is a diagram showing the power loss of each switching element in the comparative example and the example.
- FIG. 7 is a timing chart showing Modification Example 1 of the operation of the DC-DC converter.
- FIG. 8 is a timing chart showing Modification Example 2 of the operation of the DC-DC converter.
- FIG. 1 is a circuit diagram of a configuration example of the DC-DC converter according to the first embodiment.
- FIG. 2 is a timing chart showing an example of the operation of the DC-DC converter.
- FIG. 3 is
- FIG. 9 is a timing chart showing a third modification example of the operation of the DC-DC converter.
- FIG. 10 is a block diagram of a configuration example of the charging apparatus according to the second embodiment.
- FIG. 11 is a block diagram of a configuration example of the vehicle according to the third embodiment.
- a full bridge circuit typically includes four switching elements connected in a full bridge.
- the full bridge circuit is controlled by, for example, soft switching.
- phase-shift type soft switching control for example, a resonance coil is connected to the output side of the full bridge circuit, and a capacitor is connected to each switching element.
- the phase shift type soft switching control resonates the resonance coil and the capacitor by turning on and off each switching element. Thereby, zero voltage switching (ZVS) is realized.
- ZVS zero voltage switching
- Soft switching is realized by appropriately setting the inductance of the resonance coil, the capacitance of the capacitor, and the time for turning on / off each switching element.
- the resonance energy varies depending on the magnitude of the output power.
- the inductance of the resonance coil and the capacitance of the capacitor are set so that the resonance energy is maximized when the output voltage is maximized.
- the resonance energy becomes small and soft switching control may become difficult.
- a switching element that is switched from off to on immediately after energy is stored in the resonance coil can be switched by soft switching.
- a switching element that is switched from off to on after the energy of the resonance coil is released may not be switched by soft switching.
- an imbalance of current stress occurs between the switching elements that constitute the legs for which soft switching control is performed and the switching elements that constitute the legs for which soft switching control is not performed.
- the current stress imbalance causes variations in the amount of heat generated between the switching elements.
- a switching circuit includes a first arm including a first switching element and a second switching element, and a second arm connected in parallel to the first arm and including a third switching element and a fourth switching element.
- a full bridge circuit including an arm, and after the first switching element is turned on and the second switching element is turned off, the third switching element is turned off and the fourth switching element is turned on.
- a control circuit that outputs a second control signal group to be output.
- Each switching element is controlled by the first control signal group and the second control signal group, so that the current stress imbalance applied to each switching element is offset and the current stress is leveled. Therefore, for example, heat generation due to current stress imbalance or variation in element characteristics can be reduced, and the reliability of the switching circuit is improved.
- the first control signal group includes the third switching element after the first switching element is turned off and the second switching element is turned on. Is turned on and the fourth switching element is turned off, and the second control signal group is changed before the first switching element is turned off and the second switching element is turned on.
- the third switching element may be turned on and the fourth switching element may be turned off.
- the switching circuit for example, a state in which the first switching element and the third switching element are on, and the second switching element and the fourth switching element are off in the first mode, A state in which the first switching element and the fourth switching element are on, and the second switching element and the third switching element are off in the second mode, the second switching element and the fourth switching element are on, and In the third mode, the first switching element and the third switching element are turned off, the second switching element and the third switching element are turned on, and the first switching element and the fourth switching element are turned off.
- the first The control signal group is a first cycle in which the first mode, the second mode, the third mode, and the fourth mode are changed in this order, and the first switching element, the second switching element, and the third mode A second cycle in which the switching element and the fourth switching element are turned on and off, and the second control signal group transits in the order of the third mode, the second mode, the first mode, and the fourth mode.
- the first switching element, the second switching element, the third switching element, and the fourth switching element may be turned on / off.
- the switching circuit for example, a state in which the first switching element and the third switching element are on, and the second switching element and the fourth switching element are off in the first mode, A state in which the first switching element and the fourth switching element are on, and the second switching element and the third switching element are off in the second mode, the second switching element and the fourth switching element are on, and In the third mode, the first switching element and the third switching element are turned off, the second switching element and the third switching element are turned on, and the first switching element and the fourth switching element are turned off.
- the first The control signal group is a first cycle in which the third mode, the fourth mode, the first mode, and the second mode are changed in this order, and the first switching element, the second switching element, and the third mode A second cycle in which the switching element and the fourth switching element are turned on and off, and the second control signal group transits in the order of the first mode, the fourth mode, the third mode, and the second mode.
- the first switching element, the second switching element, the third switching element, and the fourth switching element may be turned on / off.
- the control circuit repeats the first cycle N times (N is a natural number) and then repeats the second cycle M times (M is a natural number). It may be allowed.
- control circuit may alternately repeat the first cycle and the second cycle.
- a conduction terminal that is not connected to the second switching element among a pair of conduction terminals of the first switching element is a pair of conduction terminals of the third switching element.
- One of the terminals connected to the conduction terminal that is not connected to the fourth switching element, and one of the pair of conduction terminals of the second switching element that is not connected to the first switching element is The pair of conduction terminals of the fourth switching element may be connected to the conduction terminal that is not connected to the third switching element.
- the switching circuit according to an aspect of the present disclosure is, for example, a switching circuit connected to a resonance coil, and the resonance coil includes a connection point between the first switching element and the second switching element, and the third switching. You may connect between an element and the connection point of the said 4th switching element.
- the full bridge circuit includes a first capacitor connected in parallel to the first switching element, and a second capacitor connected in parallel to the second switching element.
- a third capacitor connected in parallel to the third switching element and a fourth capacitor connected in parallel to the fourth switching element may be included.
- the first switching element and the second switching element are turned off in a first dead time mode
- the third switching element and the fourth switching element are turned off.
- the first cycle includes the first dead time mode and the second dead time mode
- the second cycle includes the first dead time mode and the second dead time mode.
- One of the first capacitor and the second capacitor is charged and the other is discharged according to the energy stored in the resonance coil during the first dead time mode.
- the third capacity is determined according to the energy stored in the resonance coil.
- one of the fourth capacitor is charged, and the other one may be discharged.
- the control circuit switches from the first control signal group to the second control signal group, and the second control signal group to the first control signal group.
- the control signal switching unit for selecting one of the switching to the ON state, and the first switching element to be turned on with respect to the time when the fourth switching element is turned on according to the output information signal input from the outside
- a phase control unit for determining the amount of the leading phase or the amount of the lagging phase, selection of the control signal switching unit, and determination of the phase control unit, the first control signal group or the second control signal
- a control signal generation unit that generates a group.
- control signal switching unit may select switching without referring to the output information signal.
- control signal switching unit can execute the switching control between the first control signal group and the second control signal group independently of the phase difference control of the phase control unit.
- a power conversion device includes any one of the switching circuits described above, a first rectifier circuit that rectifies an AC voltage output from the switching circuit, and a smoothed output voltage of the first rectifier circuit. And a smoothing circuit to be converted.
- a power conversion device includes any one of the switching circuits described above, a first rectifier circuit that rectifies an AC voltage output from the switching circuit, and a smoothing of an output voltage of the rectifier circuit And a smoothing circuit that detects the output voltage of the rectifier circuit or the output voltage of the smoothing circuit, and outputs the output information signal to the phase control unit.
- Each switching element is controlled by the first control signal group and the second control signal group, so that the current stress imbalance applied to each switching element is offset and the current stress is leveled. Therefore, for example, heat generation due to current stress imbalance or variation in element characteristics can be reduced, and the reliability of the power conversion device is improved.
- a charging device includes a second rectifier circuit that rectifies an AC voltage from an AC power supply, a power factor improvement circuit that improves a power factor of output power of the second rectifier circuit, and the power factor improvement.
- a power converter that converts the output power of the circuit into DC power to be charged in the battery.
- a vehicle includes a battery and a power conversion device that outputs DC power to be charged to the battery.
- Each switching element is controlled by the first control signal group and the second control signal group, so that the current stress imbalance applied to each switching element is offset and the current stress is leveled. Therefore, for example, heat generation due to current stress imbalance or variation in element characteristics can be reduced, and the reliability of the charging device is improved.
- a control circuit includes a first arm that includes a first switching element and a second switching element, and a first arm that is connected in parallel to the first arm and includes a third switching element and a fourth switching element.
- a switching circuit comprising: a full bridge circuit including two arms; and a control circuit that outputs a control signal for turning on and off the first switching element, the second switching element, the third switching element, and the fourth switching element.
- a first control circuit that changes the third switching element to an off state and the fourth switching element to an on state after the first switching element is turned on and the second switching element is turned off; Control signal group, and the first switching element is on and the second switch is on. Ring element outputs the second control signal group is changed to the third switching element is turned off and the fourth switching element is turned on prior to change in the state of off.
- the first control signal group includes the third switching element after the first switching element is turned off and the second switching element is turned on. Is turned on and the fourth switching element is turned off, and the second control signal group is changed before the first switching element is turned off and the second switching element is turned on.
- the third switching element may be turned on and the fourth switching element may be turned off.
- Each switching element is controlled by the first control signal group and the second control signal group, so that the current stress imbalance applied to each switching element is offset and the current stress is leveled. Therefore, for example, the control circuit of the present disclosure can reduce heat generation due to current stress imbalance or variation in element characteristics, and improve the reliability of the full bridge circuit.
- a control method includes a first arm including a first switching element and a second switching element, and a second arm connected in parallel to the first arm and including a third switching element and a fourth switching element.
- second control for turning on and off the first switching element, the second switching element, the third switching element, and the fourth switching element in a second cycle different from the first cycle.
- the first switching element is on and the second switching element is off.
- the first switching element is turned on and the second switching element is turned off in the second control after the third switching element is turned off and the fourth switching element is turned on.
- the third switching element is turned off and the fourth switching element is turned on.
- the third switching element is turned on and The fourth switching element is changed to an off state
- the second control the third switching element is turned on before the first switching element is turned off and the second switching element is turned on.
- the fourth switching element may be changed to an off state
- the control method of the present disclosure can reduce heat generation due to current stress imbalance or variation in element characteristics, and improve the reliability of the full bridge circuit.
- FIG. 1 is a circuit diagram illustrating a configuration example of the DC-DC converter 5 according to the first embodiment.
- the DC-DC converter 5 in FIG. 1 is one of power converters, which converts an input DC voltage into another DC voltage and outputs it.
- the DC-DC converter 5 includes a full bridge circuit INV, a resonance coil Lre, a high frequency transformer TF, a rectifier circuit RE, a smoothing filter circuit 6, an output voltage detector 11, and a control circuit 8.
- the full bridge circuit INV and the control circuit 8 constitute a switching circuit.
- the full bridge circuit INV includes a first switching element S1, a second switching element S2, a third switching element S3, and a fourth switching element S4 connected in a full bridge form.
- the first arm includes a first switching element S1 on the upper side and a second switching element S2 on the lower side.
- the second arm includes a third switching element S3 on the upper side and a fourth switching element S4 on the lower side. The first arm and the second arm are connected in parallel.
- the first switching element S1 to the fourth switching element S4 are semiconductor switching elements such as MOSFET and IGBT, for example.
- one of the first conduction terminal and the second conduction terminal is a source terminal and the other is a drain terminal.
- one of the first conduction terminal and the second conduction terminal is an emitter terminal and the other is a collector terminal.
- a first reverse conducting diode D1 and a first capacitor C1 are connected in parallel with the first switching element S1.
- the second switching element S2 to the fourth switching element S4 are connected in parallel with the second reverse conducting diode D2 to the fourth reverse conducting diode D4 and the second capacitor C2 to the fourth capacitor C4, respectively.
- the first capacitor C1 to the fourth capacitor C4 are snubber capacitors.
- the resonance coil Lre and the primary winding TF1 of the high-frequency transformer TF are connected in series from the output part of the first arm of the full bridge circuit INV to the output part of the second arm.
- the resonance coil Lre is connected between the output portion of the first arm of the full bridge circuit INV and one end of the primary winding TF1 of the high-frequency transformer TF.
- the output part of the first arm is, for example, a connection point between the first switching element S1 and the second switching element S2.
- the output part of the second arm is, for example, a connection point between the third switching element S3 and the fourth switching element S4.
- the resonance coil Lre may be, for example, a parasitic capacitance or a capacitive element.
- the high frequency transformer TF includes a primary side winding TF1 and a secondary side winding TF2.
- the high frequency transformer TF is a kind of transformer.
- the winding start of the primary side winding TF1 and the secondary side winding TF2 of the high frequency transformer TF is indicated by “ ⁇ ”.
- the full bridge circuit INV converts the DC voltage from the DC voltage source E into an alternating voltage that changes periodically by switching.
- the DC voltage is converted into an AC voltage by a phase shift method.
- the full bridge circuit INV outputs the converted AC voltage to the primary side winding TF1 of the high-frequency transformer TF via the resonance coil Lre.
- the rectifier circuit RE is a kind of AC / DC converter circuit.
- the rectifier circuit RE includes, for example, a first rectifier diode Dr1 and a second rectifier diode Dr2.
- the rectifier circuit RE is connected between the secondary winding TF2 of the high-frequency transformer TF and the smoothing filter circuit 6.
- the winding start of the secondary winding TF2 of the high-frequency transformer TF is connected to the anode of the first rectifier diode Dr1
- the winding end of the secondary winding TF2 is connected to the anode of the second rectifier diode Dr2.
- the cathodes of the first rectifier diode Dr1 and the second rectifier diode Dr2 are commonly connected to one end of the output reactor L0 included in the smoothing filter circuit 6.
- the smoothing filter circuit 6 includes, for example, an output reactor L0 and an output capacitor C0.
- the other end of the output reactor L0 is connected to the positive electrode of the output capacitor C0 and one end of the load resistor R.
- the negative electrode of the output capacitor C0 and the other end of the load resistor R are connected to the center tap of the high frequency transformer TF.
- the rectifier circuit RE performs full-wave rectification of the AC voltage input from the secondary winding TF2 to a DC voltage, and outputs it to the load resistor R via the smoothing filter circuit 6.
- the smoothing filter circuit 6 smoothes the output voltage from the rectifier circuit RE.
- the output voltage detection unit 11 detects the output voltage Vout across the load resistor R connected in parallel with the output capacitor C0 and outputs it to the control circuit 8.
- the control circuit 8 includes a phase control unit 12, a control signal switching unit 13, and a control signal generation unit 10.
- the phase control unit 12 controls the switching phase of the DC-DC converter 5 based on the output voltage Vout detected by the output voltage detection unit 11.
- the phase controller 12 compares the output voltage Vout fed back from the output voltage detector 11 with a preset target voltage Vth. When the output voltage Vout is smaller than the target voltage Vth, the phase controller 12 includes the first arm composed of the first switching element S1 and the second switching element S2, the third switching element S3, and the fourth switching element S4. Control is performed so that the phase difference ⁇ between the second arm and the second arm is small. At this time, the current IR flowing through the resonance coil Lre increases compared to before the control.
- the phase control unit 12 performs control so that the phase difference ⁇ between the first arm and the second arm becomes large. At this time, the current IR flowing through the resonance coil Lre decreases compared to before the control. That is, the phase control unit 12 controls the phase difference ⁇ between the first arm and the second arm so that the output voltage Vout maintains the target voltage Vth. As will be described later, the phase difference ⁇ may be positive or negative. That is, the phase control unit 12 determines the amount of the leading phase or the amount of the lagging phase according to the information on the output voltage Vout input from the output voltage detection unit 11.
- the control signal switching unit 13 selects whether the control signal generation unit 10 outputs the first control signal group or the second control signal group. That is, the control signal switching unit 13 instructs the control signal generation unit 10 to switch from the first control signal group to the second control signal group, or from the second control signal group to the first control signal group. .
- the order of turning on and off the first switching element S1, the second switching element S2, the third switching element S3, and the fourth switching element S4 is different between the first control signal group and the second control signal group. That is, the first control signal group is a signal group that turns on / off each switching element in the first cycle, and the second control signal group turns each switching element on / off in a second cycle different from the first cycle. It is a signal group. Details will be described later.
- the control signal switching unit 13 executes, for example, switching control between the first cycle and the second cycle independently of the phase difference control of the phase control unit 12. That is, the control signal switching unit 13 autonomously selects switching without referring to the output information signal.
- the output information signal is, for example, not only the output voltage Vout but also the output current IL, the current IR flowing through the resonance coil Lre, or the temperature.
- the control signal generation unit 10 generates the first control signal group or the second control signal group according to the determination of the phase control unit 12 and the selection of the control signal switching unit 13.
- the control signal generation unit 10 controls the control signal SS1 and the control signal SS2 for the first switching element S1, the second switching element S2, the third switching element S3, and the fourth switching element S4 in the full bridge circuit INV, respectively.
- the control signal SS3 and the control signal SS4 are output.
- the control signal group includes a control signal SS1, a control signal SS2, a control signal SS3, and a control signal SS4.
- a part of the control signal group that turns on / off each switching element in the first cycle is referred to as a first control signal group
- a part that turns on / off each switching element in the second cycle is the second control signal group.
- the control signal group is a group in which the first control signal group and the second control signal group are arranged in a predetermined order.
- the control signal generation unit 10 is configured by a digital computer such as a microcomputer, for example.
- FIG. 2 is a timing chart showing an example of the operation of the DC-DC converter 5 of FIG.
- control signal SS1 input to the first switching element S1, the control signal SS2 input to the second switching element S2, the control signal SS3 input to the third switching element S3, and the fourth The control signal SS4 input to the switching element S4 is shown.
- the control signals SS1 to SS4 are rectangular waves having a constant period T.
- the control signals SS1 to SS4 consist of two values: a high level for turning on the switching element and a low level for turning off the switching element.
- the control signal SS1 and the control signal SS2 are complementary. That is, when the control signal SS1 is at a high level, the control signal SS2 is at a low level, and when the control signal SS2 is at a high level, the control signal SS1 is at a low level.
- the control signal SS3 and the control signal SS4 are complementary. That is, when the control signal SS3 is at a high level, the control signal SS4 is at a low level, and when the control signal SS3 is at a high level, the control signal SS4 is at a low level.
- a dead time in which the control signal SS1 and the control signal SS2 are at a low level is provided between the time when the control signal SS1 is switched and the time when the control signal SS2 is switched. .
- a dead time in which the control signal SS3 and the control signal SS4 are at a low level is provided between the time when the control signal SS3 is switched and the time when the control signal SS4 is switched.
- the control signal switching unit 13 causes the control signal generation unit 10 to generate control signals SS1 to SS4 that alternately repeat the first cycle and the second cycle.
- Both the first cycle and the second cycle have a period T.
- the first cycle and the second cycle may be different in period due to, for example, the influence of noise.
- each of the plurality of switching elements constituting the full bridge circuit INV is switched from on to off once, for example, and switched from off to on once.
- the control signal group including the control signals SS1 to SS4 includes the following four modes M1 to M4.
- the phase of the second arm when the third switching element S3 is turned off and the fourth switching element S4 is turned on is such that the first switching element S1 is on and the second switching element S2 is off. It is delayed with respect to the phase of the first arm when the state is reached.
- FIG. 2 shows this delayed phase as a first phase difference ( ⁇ ).
- the first switching element S1 is switched from OFF to ON while the third switching element S3 is in the ON state.
- the first phase difference ( ⁇ ) corresponds to the period of the mode M1 in the first cycle.
- the phase of the second arm when the third switching element S3 is off and the fourth switching element S4 is on is such that the first switching element S1 is on and the second switching element S2 is on.
- FIG. 2 shows this lead phase as a second phase difference (+ ⁇ ).
- the first switching element S1 is switched from OFF to ON while the third switching element S3 is in the OFF state.
- the second phase difference (+ ⁇ ) corresponds to the period of the mode M3 in the second cycle.
- the first phase difference ( ⁇ ) and the second phase difference (+ ⁇ ) may have different signs and the same absolute value.
- the control signal generation unit 10 generates the second phase difference (+ ⁇ ) by shifting at least one of the first arm phase and the second arm phase.
- FIG. 2 shows the voltage output from the full bridge circuit INV and input to the primary winding TF1 of the high-frequency transformer TF. As shown in FIG. 2, the waveform of the AC voltage generated by the full bridge circuit INV is substantially the same in the first cycle and the second cycle.
- FIG. 3 is obtained by adding a dead time dt to the timing chart shown in FIG.
- the two switching elements that make up each arm are switched by complementary control signals. Therefore, for example, when the first switching element S1 changes from off to on and the second switching element S2 changes from on to off, both may be instantaneously turned on simultaneously. In this case, a through current passing through the first switching element S1 and the second switching element S2 flows, and wasteful power consumption occurs. The same applies to the third switching element S3 and the fourth switching element S4. Therefore, a dead time dt is provided so that the two switching elements constituting the arm are not simultaneously turned on.
- the start of each mode is after the previous dead time ends, that is, the time when any switching element is turned on.
- the end of each mode is before the start of the immediately following dead time, that is, when one of the switching elements is turned off.
- the first cycle starts from the first mode M1 after the fourth mode M4.
- the first mode M1 starts when the first switching element S1 is turned on.
- the voltage applied to the first switching element S1 is almost 0V immediately before switching, ZVS is realized.
- the first switching element S1 and the third switching element S3 are on, and the second switching element S2 and the fourth switching element S4 are off.
- a current flows from the resonance coil Lre to the resonance coil Lre through the first switching element S1, the third switching element S3, and the primary winding TF1. Flowing. Thereafter, the third switching element S3 is turned off, and the first mode M1 ends.
- the first switching element S1, the DC voltage source E, the fourth capacitor C4, and the primary winding TF1 are removed from the resonance coil Lre by the energy accumulated in the resonance coil Lre.
- a current flows through the path to the resonance coil Lre, and the fourth capacitor C4 is discharged.
- a current flows from the resonance coil Lre to the resonance coil Lre through the first switching element S1, the third capacitor C3, and the primary side winding TF1, The third capacitor C3 is charged.
- the first switching element S1 After the discharge of the fourth capacitor C4 and the charging of the third capacitor C3 are finished, the first switching element S1, the DC voltage source E, the fourth reverse conduction are generated from the resonance coil Lre by the energy accumulated in the resonance coil Lre. A current flows through a path that reaches the resonance coil Lre through the diode D4 and the primary winding TF1. Since the fourth reverse conducting diode D4 is conducting, the voltage applied to the fourth switching element S4 is approximately 0V.
- the second mode M2 starts when the fourth switching element S4 is turned on.
- the voltage applied to the fourth switching element S4 is almost 0V immediately before switching, ZVS is realized.
- the first switching element S1 and the fourth switching element S4 are on, and the second switching element S2 and the third switching element S3 are off.
- the energy stored in the resonance coil Lre passes from the resonance coil Lre to the resonance coil Lre through the first switching element S1, the DC voltage source E, the fourth switching element S4, and the primary winding TF1. A current flows through the route.
- the DC voltage source E causes the first switching element S1, the resonance coil Lre, the primary winding TF1, and the fourth switching element S4 to be moved from the DC voltage source E.
- a current flows through the path to the DC voltage source E and energy is stored in the resonance coil Lre. Thereafter, the first switching element S1 is turned off, and the second mode M2 ends.
- the resonance coil is driven from the resonance coil Lre by the energy accumulated in the resonance coil Lre through the primary winding TF1, the fourth switching element S4, and the second capacitor C2.
- a current flows through the path leading to Lre, and the second capacitor C2 is discharged.
- the energy stored in the resonance coil Lre causes the primary side winding TF1, the fourth switching element S4, and the 2.
- a current flows through the reverse conducting diode D2 to the path reaching the resonance coil Lre. Since the second reverse conducting diode D2 is conducting, the voltage applied to the second switching element S2 is approximately 0V.
- the third mode M3 starts when the second switching element S2 is turned on.
- the voltage applied to the second switching element S2 is almost 0V immediately before switching, ZVS is realized.
- the second switching element S2 and the fourth switching element S4 are on, and the first switching element S1 and the third switching element S3 are off.
- a current flows from the resonance coil Lre to the resonance coil Lre through the primary winding TF1, the fourth switching element S4, and the second switching element S2. Flowing. Thereafter, the fourth switching element S4 is turned off, and the third mode M3 ends.
- the primary coil TF1, the third capacitor C3, the DC voltage source E, and the second switching element S2 are removed from the resonance coil Lre by the energy accumulated in the resonance coil Lre.
- a current flows through the path to the resonance coil Lre, and the third capacitor C3 is discharged.
- a current flows from the resonance coil Lre to the resonance coil Lre through the primary winding TF1, the fourth capacitor C4, and the second switching element S2, The fourth capacitor C4 is charged.
- the primary coil TF1 After the discharge of the third capacitor C3 and the charging of the fourth capacitor C4 are finished, the primary coil TF1, the third reverse conducting diode D3, the direct current from the resonance coil Lre by the energy accumulated in the resonance coil Lre. A current flows through a path that reaches the resonance coil Lre through the voltage source E and the second switching element S2. Since the third reverse conducting diode D3 is conducting, the voltage applied to the third switching element S3 is approximately 0V.
- the fourth mode M4 starts when the third switching element S3 is turned on. When the voltage applied to the third switching element S3 is almost 0V immediately before switching, ZVS is realized. In the fourth mode M4, the second switching element S2 and the third switching element S3 are on, and the first switching element S1 and the fourth switching element S4 are off. At this time, the energy accumulated in the resonance coil Lre passes from the resonance coil Lre to the resonance coil Lre through the primary side winding TF1, the third switching element S3, the DC voltage source E, and the second switching element S2. A current flows through the route.
- the DC voltage source E passes the third switching element S3, the secondary winding TF1, the resonance coil Lre, and the second switching element S2 by the DC voltage source E. As a result, current flows through the path to the DC voltage source E, and energy is accumulated in the resonance coil Lre. Then, the fourth mode M4 ends by turning off the third switching element S3.
- the resonance coil passes through the second switching element S2, the fourth capacitor C4, and the primary winding TF1 from the resonance coil Lre by the energy accumulated in the resonance coil Lre.
- a current flows through the path leading to Lre, and the fourth capacitor C4 is discharged.
- the second switching element S2, the fourth reverse conducting diode D4, and the 1 are supplied from the resonance coil Lre by the energy accumulated in the resonance coil Lre.
- a current flows through a path that reaches the resonance coil Lre through the secondary winding TF1. Since the fourth reverse conducting diode D4 is conducting, the voltage applied to the fourth switching element S4 is approximately 0V.
- the third mode M3 starts when the fourth switching element S4 is turned on.
- the voltage applied to the fourth switching element S4 is almost 0V immediately before switching, ZVS is realized.
- the second switching element S2 and the fourth switching element S4 are on, and the first switching element S1 and the third switching element S3 are off.
- a current flows from the resonance coil Lre to the resonance coil Lre through the second switching element S2, the fourth switching element S4, and the primary winding TF1. Flowing. Thereafter, the second switching element S2 is turned off, and the third mode M3 ends.
- the first capacitor C1, the DC voltage source E, the fourth switching element S4, and the primary side winding TF1 are removed from the resonance coil Lre by the energy accumulated in the resonance coil Lre.
- a current flows through the path to the resonance coil Lre, and the first capacitor C1 is discharged.
- a current flows from the resonance coil Lre to the resonance coil Lre through the second capacitor C2, the fourth switching element S4, and the primary side winding TF1, The second capacitor C2 is charged.
- the energy stored in the resonance coil Lre causes the first reverse conducting diode D1, the DC voltage source E, the fourth switching to be generated from the resonance coil Lre.
- a current flows through the element S4 and the primary winding TF1 to the path to the resonance coil Lre. Since the first reverse conducting diode D1 is conducting, the voltage applied to the first switching element S1 is approximately 0V.
- the second mode M2 starts when the first switching element S1 is turned on. When the voltage applied to the first switching element S1 is almost 0V immediately before switching, ZVS is realized. In the second mode M2, the first switching element S1 and the fourth switching element S4 are on, and the second switching element S2 and the third switching element S3 are off. At this time, the energy stored in the resonance coil Lre passes from the resonance coil Lre to the resonance coil Lre through the first switching element S1, the DC voltage source E, the fourth switching element S4, and the primary winding TF1. A current flows through the route.
- the DC voltage source E causes the first switching element S1, the resonance coil Lre, the primary winding TF1, and the fourth switching element S4 to be moved from the DC voltage source E.
- a current flows through the path to the DC voltage source E and energy is stored in the resonance coil Lre. Thereafter, the fourth switching element S4 is turned off, so that the second mode M2 ends.
- the first mode M1 starts when the third switching element S3 is turned on. In the first mode M1, the first switching element S1 and the third switching element S3 are on, and the second switching element S2 and the fourth switching element S4 are off. At this time, due to the energy accumulated in the resonance coil Lre, a current flows from the resonance coil Lre to the resonance coil Lre through the primary winding TF1, the third switching element S3, and the first switching element S1. Flowing. Thereafter, the first mode M1 is ended by turning off the first switching element S1.
- the primary side winding TF1, the third switching element S3, the DC voltage source E, and the second capacitor C2 are removed from the resonance coil Lre by the energy accumulated in the resonance coil Lre.
- a current flows through the path to the resonance coil Lre, and the second capacitor C2 is discharged.
- a current flows from the resonance coil Lre to the resonance coil Lre through the primary winding TF1, the third switching element S3, and the first capacitor C1, The first capacitor C1 is charged.
- the energy stored in the resonance coil Lre causes the primary winding TF1, the third switching element S3, and the DC voltage to be generated from the resonance coil Lre.
- the fourth mode M4 starts when the second switching element S2 is turned on. When the voltage applied to the second switching element S2 is almost 0V immediately before switching, ZVS is realized. In the fourth mode M4, the second switching element S2 and the third switching element S3 are on, and the first switching element S1 and the fourth switching element S4 are off. At this time, the energy accumulated in the resonance coil Lre passes from the resonance coil Lre to the resonance coil Lre through the primary side winding TF1, the third switching element S3, the DC voltage source E, and the second switching element S2. A current flows through the route.
- the DC voltage source E causes the third switching element S3, the primary winding TF1, the resonance coil Lre, and the second switching element S2 to be moved from the DC voltage source E.
- a current flows through the path to the DC voltage source E and energy is stored in the resonance coil Lre.
- the fourth mode M4 ends by turning off the second switching element S2.
- the resonance coil is supplied from the resonance coil Lre through the first capacitor C1, the third switching element S3, and the primary winding TF1 by the energy accumulated in the resonance coil Lre.
- a current flows through the path leading to Lre, and the first capacitor C1 is discharged.
- the energy accumulated in the resonance coil Lre leads to a path from the resonance coil Lre to the resonance coil Lre through the second capacitor, the DC voltage source E, the third switching element S3, and the primary winding TF1.
- a current flows and the second capacitor C2 is charged.
- the energy stored in the resonance coil Lre causes the first reverse conducting diode D1, the third switching element S3, and 1 from the resonance coil Lre.
- a current flows through a path that reaches the resonance coil Lre through the secondary winding TF1. Since the first reverse conducting diode D1 is conducting, the voltage applied to the first switching element S1 is approximately 0V.
- Switching between the first cycle and the second cycle can be regarded as a change in the order of the first mode M1 to the fourth mode M4 in the control signal. That is, the first cycle includes the first mode M1, the second mode M2, the third mode M3, and the fourth mode M4 in this order.
- the second cycle includes the third mode M3, the second mode M2, the first mode M1, and the fourth mode M4 in this order. That is, the first mode M1 and the third mode M3 are switched between the first cycle and the second cycle.
- the period of the first mode M1 and the period of the third mode M3 may be the same.
- the period of the second mode M2 and the period of the fourth mode M4 may be the same.
- the effect of switching between the first cycle and the second cycle is as follows. In both the first cycle and the second cycle, energy is stored in the resonance coil Lre in the second mode M2 and the fourth mode M4. The first cycle and the second cycle differ in the switching order after energy is stored in the resonance coil Lre.
- the first switching element S1 is first turned on, and then the fourth switching element S4 is turned on. At this time, for example, if the energy stored in Lre of the resonance coil is insufficient, the current stress of the fourth switching element S4 may increase.
- the second switching element S2 is first turned on, and then the third switching element S3 is turned on. At this time, for example, if the energy stored in Lre of the resonance coil is insufficient, the current stress of the third switching element S3 may increase. Therefore, the current stress applied to the third switching element S3 and the fourth switching element S4 can be larger than that of the first switching element S1 and the second switching element S2.
- the fourth switching element S4 is turned on, and then the first switching element S1 is turned on. At this time, for example, if the energy stored in Lre of the resonance coil is insufficient, the current stress of the first switching element S1 may increase.
- the third switching element S3 is first turned on, and then the second switching element S2 is turned on. At this time, for example, if the energy stored in Lre of the resonance coil is insufficient, the current stress of the second switching element S2 may increase. Therefore, the current stress applied to the first switching element S1 and the second switching element S2 can be larger than that of the third switching element S3 and the fourth switching element S4.
- each switching element parasitic capacitance and / or parasitic resistance varies, or each switching element is a different type of device (for example, a full bridge circuit in which IGBTs and MOSFETs are mixed). It can also be applied to current stress imbalances.
- FIG. 4 is a timing chart of the control signals SS1 to SS4 of the comparative example configured only by the first cycle, and an example of the waveform of the current IS1 flowing through the first switching element S1 and the current IS3 flowing through the third switching element S3.
- FIG. 5 is a timing chart of the control signals SS1 to SS4 of the embodiment configured by the first cycle and the second cycle, and the current IS1 flowing through the first switching element S1 and the current flowing through the third switching element S3. It is a figure which shows an example of the waveform of IS3 typically.
- each of the current IS1 and the current IS3 shows the same waveform for each cycle. Further, the waveform of the current IS1 is different from the waveform of the current IS3.
- the control signal group is composed of the first cycle and the second cycle, as shown in FIG. 5, the current IS1 and the current IS3 are both in the first cycle and the second cycle. Different waveforms are shown. Further, the waveform of the current IS1 and the waveform of the current IS3 are different in shape for each cycle, but the shape for each mode is similar. For example, the current IS1 in the first cycle is similar to the waveform of the current I3 in the second cycle, and the current IS3 in the first cycle is similar to the current IS1 in the second cycle. In this way, by alternately switching the first cycle and the second cycle, the current stress imbalance applied to each switching element is canceled out, and the current stress is leveled. Further, by alternately switching between the first cycle and the second cycle, the configuration of the control signal generation unit 10 and / or the control signal switching unit 13 can be simplified.
- FIG. 6 shows the effect of power loss leveling when the control signal group shown in FIG. 5 is input to the DC-DC converter 5.
- FIG. 6A is a graph showing a simulation result of the power loss of each switching element when the full bridge circuit INV is driven by a control signal group composed of only the first cycle as shown in FIG. is there.
- FIG. 6B shows a simulation result of the power loss of each switching element when the full bridge circuit INV is driven by a control signal group composed of the first cycle and the second cycle as shown in FIG. It is a graph which shows.
- the vertical axis represents power consumption
- the horizontal axis represents the power output from the full bridge circuit INV and input to the primary winding TF1 of the high-frequency transformer TF.
- the simulation was performed under the conditions of a drive frequency of 100 kHz and an output voltage of 250 to 2000 W.
- the power loss of the first switching element S1 is PS1
- the power loss of the second switching element S2 is PS2
- the power loss of the third switching element S3 is PS3
- the power loss of the fourth switching element S4 is PS4. It is.
- the power loss PS1 to PS4 of each switching element showed almost the same value in the region from small power to large power. This means that the current stress applied to the switching elements S1 to S3 is leveled by the control method of the present disclosure.
- FIG. 7 is a timing chart showing Modification Example 1 of the operation of the DC-DC converter 5 of FIG.
- the control signal group shown in the upper part of FIG. 7 corresponds to the control signal group shown in FIG. 2 in which the control signal SS1 and the control signal SS2 are replaced and the control signal SS3 and the control signal SS4 are replaced. .
- FIG. 7 shows the voltage output from the full bridge circuit INV and input to the primary side winding TF1 of the high-frequency transformer TF.
- the voltage waveform generated by the full bridge circuit INV shown in FIG. 7 is inverted with respect to the voltage waveform shown in FIG.
- the definitions of the first mode M1, the second mode M2, the third mode M3, and the fourth mode M4 are the same as those described above.
- the first cycle includes the third mode M3, the fourth mode M4, the first mode M1, and the second mode M2 in this order.
- the second cycle includes the first mode M1, the fourth mode M4, the third mode M3, and the second mode M2 in this order. That is, the first mode M1 and the third mode M3 are switched between the first cycle and the second cycle.
- the first phase difference ( ⁇ ) corresponds to the period of the mode M1 in the first cycle
- the second phase difference (+ ⁇ ) corresponds to the period of the mode M3 in the second cycle. To do. Note that a dead time may be further provided in the control signal group shown in FIG.
- This modification 1 also has the same effect as the example shown in FIG. That is, in the first cycle and the second cycle, after energy is stored in the resonance coil Lre, the switching elements are turned on in different orders. Therefore, by combining the first cycle and the second cycle, the current stress imbalance of each switching element is canceled and leveled.
- FIG. 8 is a timing chart showing a second modification of the operation of the DC-DC converter 5 of FIG.
- the control signal group is configured such that after the first cycle is repeated N times (N is a natural number), the second cycle is repeated M times (M is a natural number).
- N is a natural number
- M is a natural number
- the control signal switching unit 13 instructs the control signal generation unit 10 on the number of repetitions, and based on this, the control signal generation unit 10 generates the control signals SS1 to SS4.
- the variable N and the variable M may be the same value or different values.
- the variable N and the variable M may be fixed values or variable values.
- a dead time may be further provided in the control signal group shown in FIG.
- FIG. 8 shows an example in which the second cycle is repeated twice after the first cycle is repeated twice.
- the frequency of replacement may be even lower. That is, N and M may be 3 or more.
- the first cycle and the second cycle may be switched in a shorter period than the period until the temperature of each switching element rises and the temperature of each switching element varies. The period until the variation of the temperature of each switching element can be specified based on, for example, experiments or simulations.
- the operation of the first cycle and the operation of the second cycle are the same as described above.
- the fourth mode M4 in the previous first cycle ends when the second switching element S2 is turned off.
- the behavior of the circuit during the dead time is, for example, the above-described second cycle. This is the same as the dead time after the fourth mode M4 in the cycle.
- the fourth mode M4 in the previous second cycle ends when the third switching element S3 is turned off.
- the behavior of the circuit during the dead time is, for example, the above-described first behavior. This is the same as the dead time after the fourth mode M4 in the cycle.
- This modification 2 also has the same effect as the example shown in FIG. That is, in the first cycle and the second cycle, after energy is stored in the resonance coil Lre, the switching elements are turned on in different orders. Therefore, by combining the first cycle and the second cycle, the current stress imbalance of each switching element is canceled and leveled.
- FIG. 9 is a timing chart showing a third modification example of the operation of the DC-DC converter 5 of FIG.
- the control signal group includes a plurality of first cycles having the same ON / OFF order of the switching elements and different periods, and a plurality of different ON / OFF orders of the switching elements having the same period. At least one of the second cycles.
- the control signal group includes one or more first cycles and one or more second cycles.
- the control signal group has a cycle having a third phase difference different from the first phase difference ( ⁇ ) and the second phase difference (+ ⁇ ).
- the control signal group shown in FIG. 9 includes a first cycle A having a first phase difference ( ⁇ ) and a first period T, a first phase difference ( ⁇ ), and a third phase difference.
- a first cycle B having a period T + T ⁇ ( ⁇ / 2 ⁇ )
- a second cycle A having a second phase difference (+ ⁇ ) and a second period T
- a second cycle B having a fourth period T + T ⁇ ( ⁇ / 2 ⁇ ).
- the third period and the third phase difference, and the fourth period and the fourth phase difference may not be intentionally created.
- the third cycle and the third phase difference may be obtained by deforming the first cycle and the first phase difference due to the influence of noise or the like, for example.
- the fourth period and the fourth phase difference may be obtained by deforming the second period and the second phase difference due to the influence of noise or the like, for example.
- the third period is a modification of the first period
- the fourth period is a modification of the second period.
- the control method of the first embodiment has the following configuration.
- the first switching element is turned on and the second switching element is turned off before the third switching element is turned off and the fourth switching element is turned on.
- the second cycle the first switching element is turned on and the second switching element is turned off after the third switching element is turned off and the fourth switching element is turned on.
- the first switching element is turned off and the second switching element is turned on before the third switching element is turned on and the fourth switching element is turned off.
- the first switching element is turned off and the second switching element is turned on before the third switching element is turned on and the fourth switching element is turned off.
- the first switching element is turned on and the second switching element is turned off means that the time when the first switching element is turned on and the second switching element is turned off.
- the time to be made does not have to match.
- a dead time may be provided between the time when the second switching element is changed to the OFF state and the time when the first switching element is changed to the ON state.
- the signal for changing the first switching element to the on state and the second switching element to the off state is that the first switching element is off and the second switching element is on, and the first switching element is off and It includes a signal that causes the first switching element to turn on and the second switching element to turn off after the second switching element is turned off.
- the signal that changes the first switching element to the on state and the second switching element to the off state substantially corresponds to a signal that changes the first switching element from the off state to the on state.
- the third switching element is turned on and when the fourth switching element is turned off, the third switching element is turned off and the fourth switching element. The same applies to the case where is changed to the ON state.
- the current stress between the first switching element S1 to the fourth switching element S4 can be leveled by mixing the first cycle and the second cycle.
- the amount of heat generated between the first switching element S1 to the fourth switching element S4 can be leveled.
- the specifications of the cooling mechanism such as a heat sink can be unified with those that are not excessive or insufficient, and therefore, the enlargement of the entire cooling mechanism can be suppressed.
- the reliability and life between the first switching element S1 to the fourth switching element S4 are made uniform.
- FIG. 10 is a block diagram of a configuration example of the charging device 7 according to the second embodiment.
- the charging device 7 includes an input filter 2, a rectifier circuit 3, a power factor correction circuit (PFC circuit; Power Factor Correction circuit) 4, and a DC-DC converter 5.
- PFC circuit Power Factor Correction circuit
- DC-DC converter 5 DC-DC converter 5.
- the input filter 2 is a band-pass filter that passes only a predetermined commercial power frequency component from the AC voltage from the commercial power source 1.
- the input filter 2 outputs the passed AC voltage to the rectifier circuit 3.
- the rectifier circuit 3 rectifies the AC voltage input from the input filter 2 into a pulsating voltage and outputs the rectified voltage to the power factor correction circuit 4.
- the rectifier circuit 3 is constituted by a diode bridge circuit in which, for example, four rectifier diodes are connected in a bridge form.
- the power factor correction circuit 4 improves the power factor of the power output from the rectifier circuit 3 and outputs the power factor to the DC-DC converter 5.
- the DC-DC converter 5 is the DC-DC converter 5 according to the first embodiment.
- the DC-DC converter 5 converts the DC voltage input from the power factor correction circuit 4 into a predetermined DC voltage, and outputs it to the battery BT.
- Battery BT is charged by a DC voltage input from DC-DC converter 5.
- the DC-DC converter 5 monitors the output voltage and the output current to the battery BT, and performs constant current charging (CC charging) or constant voltage charging (CV charging).
- the charging device 7 may not include the input filter 2, the rectifier circuit 3, and the power factor correction circuit 4.
- the charging device 7 according to the second embodiment includes the phase shift type DC-DC converter 5 according to the first embodiment, it is possible to perform highly efficient charging with reduced switching loss.
- the current stress between the first switching element S1 to the fourth switching element S4 in the full bridge circuit INV is leveled, heat generation and reliability variations due to current stress imbalance can be reduced.
- FIG. 11 is a block diagram illustrating a configuration example of the vehicle 20 according to the third embodiment.
- the vehicle 20 is, for example, an electric vehicle or a plug-in hybrid vehicle.
- the vehicle 20 includes an outlet 24 for connection to an external commercial power source, the charging device 7 according to the second embodiment, and the battery BT.
- the electric power supplied from the outlet 24 is stored in the battery BT via the charging device 7.
- the vehicle 20 according to the third embodiment includes the charging device 7 according to the second embodiment, highly efficient charging can be performed. In addition, variations in heat generation and reliability due to current stress imbalance between the first switching element S1 to the fourth switching element S4 can be reduced.
- the vehicle 20 according to the third embodiment can reduce running costs and achieve high reliability.
- the vehicle 20 is not limited to a plug-in hybrid vehicle.
- the vehicle 20 may be a hybrid vehicle that does not include the outlet 24 and cannot perform AC charging from the outside.
- an alternator or a motor / generator in the vehicle 20 (not shown) generates electric power and outputs it to the charging device 7.
- the generated power is converted into DC power by an inverter (not shown) and then input to the charging device 7.
- the vehicle 20 may not include the input filter 2, the rectifier circuit 3, and the power factor correction circuit 4 in the charging device 7.
- the present disclosure also includes a modification obtained by a combination of the above-described components and processing processes.
- the second cycle having the order shown in FIG. 7 is repeated M times (M is a natural number). Also good.
- the resonance coil Lre may be a leakage inductance of the high-frequency transformer TF.
- the resonance coil Lre may be connected in series to the secondary winding TF2 of the high-frequency transformer TF.
- the first capacitor C1 to the fourth capacitor C1 to C4 may be parasitic capacitances of the first switching element S1 to the fourth switching element S4, respectively.
- the first reverse conduction diode D1 to the fourth reverse conduction diode D4 may be parasitic diodes of the first switching element S1 to the fourth switching element S4, respectively.
- the rectifier circuit RE may have a configuration in which four diodes are connected in a full bridge.
- the DC-DC converter 5 and / or the control method according to the first embodiment can be applied to an insulation type DC-DC converter of a power conditioner.
- the present disclosure can be used for, for example, an in-vehicle charging device, a power conditioner, and the like.
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Abstract
Description
本発明者らは、DC-DCコンバータにおいて、フルブリッジ回路を構成するスイッチング素子の信頼性を向上すべく、鋭意検討を行い、以下の課題を見出した。
本開示の一態様に係るスイッチング回路は、第1スイッチング素子および第2スイッチング素子を含む第1アームと、前記第1アームに並列に接続され、第3スイッチング素子および第4スイッチング素子を含む第2アームとを含むフルブリッジ回路と、前記第1スイッチング素子がオンかつ前記第2スイッチング素子がオフの状態に変化させた後に前記第3スイッチング素子がオフかつ前記第4スイッチング素子がオンの状態に変化させる第1の制御信号群と、前記第1スイッチング素子がオンかつ前記第2スイッチング素子がオフの状態に変化させる前に前記第3スイッチング素子がオフかつ前記第4スイッチング素子がオンの状態に変化させる第2の制御信号群とを出力する制御回路と、を含む。
[回路構成]
図1は、実施の形態1にかかるDC-DCコンバータ5の構成例を示す回路図である。
図2は、図1のDC-DCコンバータ5の動作の一例を示すタイミングチャートである。
(1)第1モードM1は、第1スイッチング素子S1と第3スイッチング素子S3がオンであって、第2スイッチング素子S2と第4スイッチング素子S4がオフである。
(2)第2モードM2は、第1スイッチング素子S1と第4スイッチング素子S4がオンであって、第2スイッチング素子S2と第3スイッチング素子S3がオフである。
(3)第3モードM3は、第2スイッチング素子S2と第4スイッチング素子S4がオンであって、第1スイッチング素子S1と第3スイッチング素子S3がオフである。
(4)第4モードM4は、第2スイッチング素子S2と第3スイッチング素子S3がオンであって、第1スイッチング素子S1と第4スイッチング素子S4がオフである。
第1のサイクルは、第4モードM4の後の第1モードM1から始まる。
第2のサイクルは、第4モードM4の後の第3モードM3から始まる。
第1のサイクルと第2のサイクルの切り替えは、制御信号における、第1モードM1~第4モードM4の順番入れ替えと捉えることができる。すなわち、第1のサイクルは、第1モードM1、第2モードM2、第3モードM3、および第4モードM4をこの順番で含む。一方、第2のサイクルは、第3モードM3、第2モードM2、第1モードM1、および第4モードM4をこの順番で含む。つまり、第1のサイクルと第2のサイクルとの間で、第1モードM1と第3のモードM3とが入れ替わっている。なお、第1モードM1の期間と第3モードM3の期間とは、同じであってもよい。第2モードM2の期間と第4モードM4の期間とは、同じであってもよい。
図4は、第1のサイクルのみで構成される比較例の制御信号SS1~SS4のタイミングチャート、ならびに、第1スイッチング素子S1を流れる電流IS1および第3スイッチング素子S3を流れる電流IS3の波形の一例を模式的に示す図である。図5は、第1のサイクルと第2のサイクルとで構成される実施例の制御信号SS1~SS4のタイミングチャート、ならびに、第1スイッチング素子S1を流れる電流IS1および第3スイッチング素子S3を流れる電流IS3の波形の一例を模式的に示す図である。
図7は、図1のDC-DCコンバータ5の動作の変形例1を示すタイミングチャートである。
図8は、図1のDC-DCコンバータ5の動作の変形例2を示すタイミングチャートである。
図9は、図1のDC-DCコンバータ5の動作の変形例3を示すタイミングチャートである。
図10は、実施の形態2にかかる充電装置7の構成例を示すブロック図である。充電装置7は、入力フィルタ2、整流回路3、力率改善回路(PFC回路;Power Factor Correction回路)4、DC-DCコンバータ5とを備える。
図11は、実施の形態3にかかる車両20の構成例を示すブロック図である。車両20は、例えば、電気自動車又はプラグインハイブリッド自動車である。車両20は、外部の商用電源に接続するためのコンセント24と、実施の形態2にかかる充電装置7、バッテリBTとを備える。コンセント24から供給される電力は、充電装置7を介してバッテリBTに蓄積される。
2 入力フィルタ
3 整流回路
4 力率改善回路
5 DC-DCコンバータ
BT バッテリ
20 車両
24 コンセント
6 平滑用フィルタ回路
7 充電装置
8 制御回路
10 制御信号生成部
11 出力電圧検出部
12 位相制御部
13 制御信号切替部
E 直流電圧源
INV フルブリッジ回路
S1 第1スイッチング素子
S2 第2スイッチング素子
S3 第3スイッチング素子
S4 第4スイッチング素子
C1 第1キャパシタ
C2 第2キャパシタ
C3 第3キャパシタ
C4 第4キャパシタ
D1 第1逆導通ダイオード
D2 第2逆導通ダイオード
D3 第3逆導通ダイオード
D4 第4逆導通ダイオード
Lre 共振コイル
TF 高周波トランス
Dr1 第1整流ダイオード
Dr2 第2整流ダイオード
RE 整流回路
L0 出力リアクトル
C0 出力キャパシタ
R 負荷抵抗
Claims (20)
- 第1スイッチング素子および第2スイッチング素子を含む第1アームと、前記第1アームに並列に接続され、第3スイッチング素子および第4スイッチング素子を含む第2アームとを含むフルブリッジ回路と、
前記第1スイッチング素子がオンかつ前記第2スイッチング素子がオフの状態に変化させた後に前記第3スイッチング素子がオフかつ前記第4スイッチング素子がオンの状態に変化させる第1の制御信号群と、前記第1スイッチング素子がオンかつ前記第2スイッチング素子がオフの状態に変化させる前に前記第3スイッチング素子がオフかつ前記第4スイッチング素子がオンの状態に変化させる第2の制御信号群とを出力する制御回路と、を含む、
スイッチング回路。 - 前記第1の制御信号群は、前記第1スイッチング素子がオフかつ前記第2スイッチング素子がオンの状態に変化させた後に、前記第3スイッチング素子がオンかつ前記第4スイッチング素子がオフの状態に変化させ、
前記第2の制御信号群は、前記第1スイッチング素子がオフかつ前記第2スイッチング素子がオンの状態に変化させる前に、前記第3スイッチング素子がオンかつ前記第4スイッチング素子がオフの状態に変化させる、
請求項1に記載のスイッチング回路。 - 前記第1スイッチング素子および前記第3スイッチング素子がオン、かつ、前記第2スイッチング素子および前記第4スイッチング素子がオフの状態を第1モード、
前記第1スイッチング素子および前記第4スイッチング素子がオン、かつ、前記第2スイッチング素子および前記第3スイッチング素子がオフの状態を第2モード、
前記第2スイッチング素子および前記第4スイッチング素子がオン、かつ、前記第1スイッチング素子および前記第3スイッチング素子がオフの状態を第3モード、
前記第2スイッチング素子および前記第3スイッチング素子がオン、かつ、前記第1スイッチング素子および前記第4スイッチング素子がオフの状態を第4モードとするとき、
前記第1の制御信号群は、前記第1モード、前記第2モード、前記第3モード、前記第4モードの順で遷移させる第1のサイクルで、前記第1スイッチング素子、前記第2スイッチング素子、前記第3スイッチング素子、および前記第4スイッチング素子をオンオフし、
前記第2の制御信号群は、前記第3モード、前記第2モード、前記第1モード、前記第4モードの順で遷移させる第2のサイクルで、前記第1スイッチング素子、前記第2スイッチング素子、前記第3スイッチング素子、および前記第4スイッチング素子をオンオフする、
請求項1または2に記載のスイッチング回路。 - 前記第1スイッチング素子および前記第3スイッチング素子がオン、かつ、前記第2スイッチング素子および前記第4スイッチング素子がオフの状態を第1モード、
前記第1スイッチング素子および前記第4スイッチング素子がオン、かつ、前記第2スイッチング素子および前記第3スイッチング素子がオフの状態を第2モード、
前記第2スイッチング素子および前記第4スイッチング素子がオン、かつ、前記第1スイッチング素子および前記第3スイッチング素子がオフの状態を第3モード、
前記第2スイッチング素子および前記第3スイッチング素子がオン、かつ、前記第1スイッチング素子および前記第4スイッチング素子がオフの状態を第4モードとするとき、
前記第1の制御信号群は、前記第3モード、前記第4モード、前記第1モード、前記第2モードの順で遷移させる第1のサイクルで、前記第1スイッチング素子、前記第2スイッチング素子、前記第3スイッチング素子、および前記第4スイッチング素子をオンオフし、
前記第2の制御信号群は、前記第1モード、前記第4モード、前記第3モード、前記第2モードの順で遷移させる第2のサイクルで、前記第1スイッチング素子、前記第2スイッチング素子、前記第3スイッチング素子、および前記第4スイッチング素子をオンオフする、
請求項1または2に記載のスイッチング回路。 - 前記制御回路は、前記第1のサイクルをN回(Nは自然数)繰り返させた後に、前記第2のサイクルをM回(Mは自然数)繰り返させる、
請求項3または4に記載のスイッチング回路。 - 前記制御回路は、前記第1のサイクルと前記第2のサイクルとを交互に繰り返させる、
請求項3または4に記載のスイッチング回路。 - 前記第1スイッチング素子の一対の導通端子のうち前記第2スイッチング素子と接続されていない方の導通端子が、前記第3スイッチング素子の一対の導通端子のうち前記第4スイッチング素子と接続されていない方の導通端子と接続され、
前記第2スイッチング素子の一対の導通端子のうち前記第1スイッチング素子と接続されていない方の導通端子が、前記第4スイッチング素子の一対の導通端子のうち前記第3スイッチング素子と接続されていない方の導通端子と接続される、
請求項1から6のいずれか一項に記載のスイッチング回路。 - 共振コイルに接続されるスイッチング回路であって、
前記共振コイルは、前記第1スイッチング素子と第2スイッチング素子との接続点と、前記第3スイッチング素子と前記第4スイッチング素子との接続点との間に接続される、
請求項7に記載のスイッチング回路。 - 前記フルブリッジ回路は、
前記第1スイッチング素子に並列に接続された第1キャパシタと、
前記第2スイッチング素子に並列に接続された第2キャパシタと、
前記第3スイッチング素子に並列に接続された第3キャパシタと、
前記第4スイッチング素子に並列に接続された第4キャパシタとを含む、
請求項8に記載のスイッチング回路。 - 前記第1スイッチング素子および前記第2スイッチング素子がオフの状態を第1デッドタイムモード、
前記第3スイッチング素子および前記第4スイッチング素子がオフの状態を第2デッドタイムモード、とするとき、
前記第1のサイクルは、前記第1デッドタイムモードと第2デッドタイムモードとを含み、
前記第2のサイクルは、前記第1デッドタイムモードと第2デッドタイムモードとを含み、
第1デッドタイムモード中に、前記共振コイルに蓄積されたエネルギーに応じて、前記第1キャパシタおよび前記第2キャパシタのうち一方が充電され、かつ、他方が放電され、
第2デッドタイムモード中に、前記共振コイルに蓄積されたエネルギーに応じて、前記第3キャパシタおよび前記第4キャパシタのうち一方が充電され、かつ、他方が放電される、
請求項9に記載のスイッチング回路。 - 前記制御回路は、
前記第1制御信号群から前記第2制御信号群への切り替え、および、前記第2制御信号群から前記第1制御信号群への切り替えのいずれかを選択する制御信号切替部と、
外部から入力される出力情報信号に応じて、前記第4スイッチング素子をオンに変化させるときに対する、前記第1スイッチング素子をオンに変化させるときの進み位相の量または遅れ位相の量を決定する位相制御部と、
前記制御信号切替部の選択、および、前記位相制御部の決定に応じて、前記第1制御信号群または第2制御信号群を生成する制御信号生成部と、を含む、
請求項1から10のいずれか一項に記載のスイッチング回路。 - 制御信号切替部は、前記出力情報信号を参照せずに切り替えを選択する、
請求項11に記載のスイッチング回路。 - 請求項1から12のいずれか一項に記載のスイッチング回路と、
前記スイッチング回路から出力される交流電圧を整流する第一整流回路と、
前記第一整流回路の出力電圧を平滑化する平滑化回路と、を備える、
電力変換装置。 - 請求項11または12に記載のスイッチング回路と、
前記スイッチング回路から出力される交流電圧を整流する第一整流回路と、
前記整流回路の出力電圧を平滑化する平滑化回路と、
前記整流回路の出力電圧または前記平滑化回路の出力電圧を検出し、前記出力情報信号を前記位相制御部に出力する出力電圧検出部と、を備える、
電力変換装置。 - 交流電源からの交流電圧を整流する第二整流回路と、
前記第二整流回路の出力電力の力率を改善する力率改善回路と、
前記力率改善回路の出力電力を、バッテリに充電すべき直流電力に変換する請求項14に記載の電力変換装置と、を備える、
充電装置。 - バッテリと、
前記バッテリに充電すべき直流電力を出力する請求項14に記載の電力変換装置と、を備える、
車両。 - 第1スイッチング素子および第2スイッチング素子を含む第1アーム、ならびに、前記第1アームに並列に接続され、第3スイッチング素子および第4スイッチング素子を含む第2アームを含むフルブリッジ回路と、前記第1スイッチング素子、前記第2スイッチング素子、前記第3スイッチング素子、および、第4スイッチング素子をオンオフする制御信号を出力する制御回路とを備えるスイッチング回路における前記制御回路であって、
前記第1スイッチング素子がオンかつ前記第2スイッチング素子がオフの状態に変化させた後に前記第3スイッチング素子がオフかつ前記第4スイッチング素子がオンの状態に変化させる第1の制御信号群と、前記第1スイッチング素子がオンかつ前記第2スイッチング素子がオフの状態に変化させる前に前記第3スイッチング素子がオフかつ前記第4スイッチング素子がオンの状態に変化させる第2の制御信号群とを出力する、
制御回路。 - 前記第1の制御信号群は、前記第1スイッチング素子がオフかつ前記第2スイッチング素子がオンの状態に変化させた後に、前記第3スイッチング素子がオンかつ前記第4スイッチング素子がオフの状態に変化させ、
前記第2の制御信号群は、前記第1スイッチング素子がオフかつ前記第2スイッチング素子がオンの状態に変化させる前に、前記第3スイッチング素子がオンかつ前記第4スイッチング素子がオフの状態に変化させる、
請求項17に記載の制御回路。 - 第1スイッチング素子および第2スイッチング素子を含む第1アームと、前記第1アームに並列に接続され、第3スイッチング素子および第4スイッチング素子を含む第2アームとを含むフルブリッジ回路を制御する制御方法であって、
第1スイッチング素子、前記第2スイッチング素子、前記第3スイッチング素子、および、第4スイッチング素子を第1のサイクルでオンオフする第1制御と、
前記第1スイッチング素子、前記第2スイッチング素子、前記第3スイッチング素子、および、第4スイッチング素子を前記第1のサイクルと異なる第2のサイクルでオンオフする第2制御とを選択的に実行し、
前記第1制御において、前記第1スイッチング素子がオンかつ前記第2スイッチング素子がオフの状態に変化させた後に、前記第3スイッチング素子がオフかつ前記第4スイッチング素子がオンの状態に変化させ
前記第2制御において、前記第1スイッチング素子がオンかつ前記第2スイッチング素子がオフの状態に変化させる前に、前記第3スイッチング素子がオフかつ前記第4スイッチング素子がオンの状態に変化させる、
制御方法。 - 前記第1制御において、前記第1スイッチング素子がオフかつ前記第2スイッチング素子がオンの状態に変化させた後に、前記第3スイッチング素子がオンかつ前記第4スイッチング素子がオフの状態に変化させ、
前記第2制御において、前記第1スイッチング素子がオフかつ前記第2スイッチング素子がオンの状態に変化させる前に、前記第3スイッチング素子がオンかつ前記第4スイッチング素子がオフの状態に変化させる、
請求項19に記載の制御方法。
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