WO2012120657A1 - 偏波角度分割ダイバシチ無線送信機、無線受信機、および無線通信システム - Google Patents
偏波角度分割ダイバシチ無線送信機、無線受信機、および無線通信システム Download PDFInfo
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- WO2012120657A1 WO2012120657A1 PCT/JP2011/055462 JP2011055462W WO2012120657A1 WO 2012120657 A1 WO2012120657 A1 WO 2012120657A1 JP 2011055462 W JP2011055462 W JP 2011055462W WO 2012120657 A1 WO2012120657 A1 WO 2012120657A1
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- frequency
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- angle division
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- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04B—TRANSMISSION
- H04B7/00—Radio transmission systems, i.e. using radiation field
- H04B7/02—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas
- H04B7/10—Polarisation diversity; Directional diversity
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- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04B—TRANSMISSION
- H04B7/00—Radio transmission systems, i.e. using radiation field
- H04B7/02—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas
- H04B7/04—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas
- H04B7/06—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station
- H04B7/0613—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station using simultaneous transmission
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- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04B—TRANSMISSION
- H04B7/00—Radio transmission systems, i.e. using radiation field
- H04B7/02—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas
- H04B7/04—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas
- H04B7/08—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the receiving station
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- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04B—TRANSMISSION
- H04B7/00—Radio transmission systems, i.e. using radiation field
- H04B7/02—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas
- H04B7/04—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas
- H04B7/08—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the receiving station
- H04B7/0891—Space-time diversity
- H04B7/0894—Space-time diversity using different delays between antennas
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- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
- H04L27/00—Modulated-carrier systems
- H04L27/18—Phase-modulated carrier systems, i.e. using phase-shift keying
Definitions
- the present invention relates to polarization angle division diversity radio transmitters, radio receivers, and radio communication systems that realize highly reliable radio communication.
- wireless communication technology has made remarkable progress in the field of broadcasting and communication, and has overcome reliability problems such as radio-specific interruptions.
- the application of wireless communication technology to control fields and measurement fields where high reliability is required compared to broadcast fields and communication fields is in progress.
- social infrastructure devices devices that construct social infrastructure
- the social infrastructure equipment is, for example, the elevator system shown in FIG. 14 or the transformation equipment monitoring system shown in FIG.
- Social infrastructure devices are by far larger in size than general consumer devices, and are made of metal members in a robust manner.
- This social infrastructure device itself becomes a scattering source of electromagnetic waves. Therefore, wireless communication in social infrastructure devices is often performed in an environment where multiple waves (multipaths) generated by scattering interfere with each other. For this reason, it is desirable to realize highly reliable wireless communication in an environment where interference due to multiple waves (multipath) is generated.
- an electromagnetic wave generated by a wireless transmitter is reflected by the social infrastructure equipment itself to become a multiple wave (multipath), and may come to the receiver from all directions.
- multipath multiple wave
- space diversity techniques requires many antennas. For example, even if it is limited that multiple waves (multipaths) come in the planar direction, it is necessary to prepare a plurality of arranged antennas.
- the distance between adjacent antennas is a half wavelength of an electromagnetic wave to be received, so there is a possibility that the size can be larger than the size that can be equipped with this social infrastructure device.
- Patent Document 1 Japanese Patent Application Laid-Open No. 10-135919
- FIG. 3 disclose a technique for rotating the polarization plane of radio waves in order to suppress the influence of fading and noise in wireless communication.
- paragraph 0006 of the specification of Patent Document 1 “two pairs of dipole antennas crossed at right angles for transmission by rotating the polarization plane of radio waves at the transmission side, and expanded at right angles to the transmission direction, And at least one transmitting device having two sets of balanced modulation wave outputs for exciting the signal, and the receiving side comprises a receiving device that detects and receives rotation of the polarization plane of the incoming radio wave. ing.
- Patent Document 1 is effective in eliminating the effects of fading and noise that occur in transmission and reception of radio waves.
- the present invention describes nothing about realizing highly reliable wireless communication in an environment where interference due to multiple waves (multipaths) occurs, and reducing the size of a transmitting antenna and a receiving antenna. Absent.
- Patent Document 2 is effective in eliminating the influence of fading in wireless communication to transmit and receive high-quality signals, and reducing the size of the transmitting antenna and the receiving antenna.
- this invention does not describe at all about achieving highly reliable wireless communication in an environment where interference due to multiple waves (multipaths) occurs.
- the present invention is directed to a polarization angle division diversity radio transmitter which realizes highly reliable radio communication with a small transmitting antenna or receiving antenna under an environment where interference due to multiple waves (multipath) is generated, radio reception It is an object of the present invention to provide a wireless communication system and a wireless communication system.
- a polarization angle division diversity radio transmitter modulates an information signal of a first frequency at a second frequency, and outputs a first modulation signal; And an electromagnetic wave transmitting means for transmitting the modulated signal with two independent polarizations and superimposing a third frequency on the polarizations.
- Other means will be described in the form for carrying out the invention.
- polarization angle division diversity radio transmitter for achieving highly reliable radio communication with a small transmitting antenna or receiving antenna in an environment where interference due to multiple waves (multipath) is generated, radio reception And a wireless communication system can be provided.
- FIG. 2 illustrates multipath in a wireless communication system. It is a figure which shows operation
- a polarization angle division diversity radio transmitter which realizes highly reliable radio communication with a small transmitting antenna or receiving antenna in an environment where interference due to multiple waves (multipaths) is generated, radio The polarization of the electromagnetic wave is used to provide a receiver and a wireless communication system.
- FIG. 2 is a diagram showing multipath in a wireless communication system.
- the wireless communication system includes a wireless transmitter 10 and a wireless receiver 30.
- the radio transmitter 10 transmits two independent linear polarizations orthogonal to each other.
- a path from the wireless transmitter 10 to the wireless receiver 30 is blocked by the electromagnetic wave reflector 300-1.
- the electromagnetic wave transmitted from the wireless transmitter 10 is reflected by the electromagnetic wave reflector 300-2 and reaches the wireless receiver 30. Since this electromagnetic wave passes through the path length Lr when it is reflected by the electromagnetic wave reflector 300-2, the electromagnetic wave is represented by Formula 1 below compared with the shortest path length Ld from the wireless transmitter 10 to the wireless receiver 30.
- the phase is shifted by ⁇ .
- Equation 1 ((Lr ⁇ Ld) ⁇ ⁇ ) ⁇ 2 ⁇ (Equation 1)
- ⁇ is the wavelength of the electromagnetic wave.
- the wavelength ⁇ of the electromagnetic wave is calculated by Equation 2 below, where c is the speed of light and f is the frequency of the electromagnetic wave.
- ⁇ c ⁇ f (Equation 2)
- the polarization plane shifts in phase by ⁇ .
- the phase shift ⁇ of the polarization plane is 0 degrees.
- the phase shift ⁇ of the plane of polarization is 180 degrees. That is, in the polarization of the electromagnetic wave, the phase shift ⁇ of the polarization plane of the reflected wave is generated depending on each angle of incidence on the electromagnetic wave reflector 300-2.
- ⁇ n ((Ln ⁇ Ld) ⁇ ⁇ ) ⁇ 2 ⁇ (Equation 3)
- the respective polarization planes of the electromagnetic waves are reflected to the tangent plane of the nth electromagnetic wave reflector, thereby generating phase shifts ⁇ of the polarization planes of the reflected waves.
- the rotation direction of the polarization resulting from the reflection of the radio wave by the electromagnetic wave reflector changes, and at the same time the path also changes.
- the polarization planes of the electromagnetic waves interfering at the reception point are different for each time.
- the polarization of the electromagnetic wave is transmitted independently, so the energy of the electromagnetic wave at this reception point is not zero.
- Two independent orthogonal polarizations can be transmitted, for example, by two orthogonal vertical polarization antennas. These two antennas do not need to be spatially separated, and antennas can be installed in a minimum area.
- the special condition is that the electromagnetic wave energy at the receiving point instantaneously becomes zero at the time of polarization rotation of the transmission electromagnetic wave, and the influence on the information transmission is so small as to be negligible.
- FIGS. 1A and 1B are schematic configuration diagrams showing a wireless communication system according to a first embodiment.
- FIG. 1A shows the configuration of the wireless transmitter 10
- FIG. 1B shows the configuration of the wireless receiver 30.
- the wireless communication system of the present embodiment includes a wireless transmitter 10 and a wireless receiver 30.
- the wireless transmitter 10 shown in FIG. 1A includes an information generation circuit 11, an oscillator 12, a modulator 13 as a first modulation means, a transmission antenna 20 as an electromagnetic wave transmission means, and a motor as a rotation means. And 14).
- the output side of the information generation circuit 11 and the output side of the oscillator 12 are connected to the modulator 13.
- the output side of the modulator 13 is connected to the transmitting antenna 20.
- the information generation circuit 11 has a function of outputting an information signal of the frequency band f1 which is the first frequency to the modulator 13.
- the oscillator 12 has a function of outputting a carrier wave f2, which is the second frequency, to the modulator 13.
- the modulator 13 has a function of modulating the information signal in the frequency band f1 with the carrier wave f2 and outputting the modulated signal as a first modulated signal to the transmission antenna 20.
- the transmitting antenna 20 has a function of transmitting linear polarization.
- the motor 14 has a function of rotating the transmitting antenna 20 at (1 / f3) period, that is, the frequency f3.
- the receiving antennas 31-1 to 31-6 are arranged to be rotated at an angle of 60 degrees, respectively, and have a function of receiving linearly polarized waves having an angle of 60 degrees.
- the receiving antennas 31-1 to 31-6 are connected to path difference phase shifters 32-1 to 32-6, respectively.
- Each of the receiving antennas 31-1 to 31-6 has a function of receiving linearly polarized waves of a predetermined angle.
- the synthesizer 33 has a function of synthesizing and outputting all input signals.
- the phase shifts ⁇ 1 to ⁇ n due to the path difference of the electromagnetic waves indicate the phase shifts at the frequency f2.
- FIGS. 3A to 3C are diagrams showing the operation of the wireless communication system according to the first embodiment.
- Fig.3 (a) is a figure which shows the time change on the y-axis of the electromagnetic waves transmitted from the transmission antenna 20 (FIG. 1).
- the horizontal axis indicates time t, and the vertical axis indicates y-axis coordinates.
- the electromagnetic wave transmitted from the transmitting antenna 20 vibrates in a (1 / f2) cycle by the carrier wave f2. Further, since the transmitting antenna 20 is rotated at the frequency f3 by the motor 14, the polarization plane of the electromagnetic wave transmitted from the transmitting antenna 20 is rotated at (1 / f3) period.
- the frequency f1 which is the first frequency is set lower than the frequency f2 of the carrier wave which is the second frequency and the frequency f3 which is the third frequency.
- the carrier frequency f2 is set higher than the frequency f3.
- FIG. 3B is a diagram showing an operation in which the transmitting antenna 20 is rotated at the frequency f3 on the xy plane.
- the transmitting antenna 20 is rotated clockwise at a frequency f3 on the xy plane. By this rotation, the polarization plane of the electromagnetic wave rotates at the frequency f3.
- FIG. 3C is a perspective view showing the time change of the electromagnetic wave transmitted by the transmission antenna 20 on the xy plane.
- the coordinates of the x-axis, y-axis and t-axis are shown in solid, respectively, and the rotation direction of the antenna shown in FIG. 3B is drawn on the xy plane by dotted arrows.
- the polarization plane of the electromagnetic wave is represented by a waveform of frequency f2. Since the plane of polarization shown by the waveform of this frequency f2 rotates on the xy plane at the frequency f3, the temporal change of the envelope becomes helical in the xy-t space.
- the polarization plane of the electromagnetic wave rotates in accordance with the incident angle to the electromagnetic wave reflector. Therefore, when a plurality of electromagnetic wave reflectors exist in the space in which the wireless transmitter 10 and the wireless receiver 30 are installed, a plurality of electromagnetic waves having different planes of polarization and different polarization planes are received.
- the polarization planes of the plurality of electromagnetic waves temporally change at a frequency f3.
- the receiving antennas 31-2 to 31-6 are installed at different angles in rotational symmetry with the receiving antenna 31-1. Any of the electromagnetic waves arriving to the receiving antennas 31-2 to 31-6 comes from other paths, and therefore, no radio wave interference occurs, and a phenomenon that the electromagnetic wave energy becomes zero does not occur.
- the radio receiver 30 of this embodiment receives electromagnetic waves arriving at a plurality of different polarization angles by the diversity receiving antenna 31 that receives a plurality of different polarizations. Even when the receiving antenna 31-1 causes radio wave interference and the electromagnetic wave energy becomes zero at a certain moment, any of the other receiving antennas 31-2 to 31-6 does not cause radio wave interference There are many.
- the electromagnetic waves arriving with different polarization planes are respectively received by the plurality of receiving antennas 31-1 to 31-6, and the phase shift ⁇ 1 to ⁇ 6 due to the path difference of the received electromagnetic waves is corrected by the path difference phase shifter 32 and this correction
- the combiner 33 By combining the received signals by the combiner 33, it is possible to improve the receiving sensitivity and to improve the reliability of wireless communication.
- the path difference phase shifter 32-i delays the input signal by t0 ⁇ ( ⁇ i ⁇ (2 ⁇ ⁇ f2)).
- t0 is a constant.
- the frequency f3 of rotation of the polarization plane of the electromagnetic wave is set larger than the frequency band f1 for transmitting the information signal.
- the wireless receiver 30 further processes the combined received signal with a resolution of (1 / f3) time to avoid the phenomenon that the electromagnetic wave energy becomes zero due to radio wave interference, and receives the information signal in the frequency band f1 without error It is possible.
- the first embodiment described above has the following effects (A) to (D).
- the electromagnetic waves arriving with different polarization planes are respectively received by the plurality of receiving antennas 31-1 to 31-6, and the path difference phase shifter 32 causes a phase shift based on the path difference of the electromagnetic waves received by each antenna.
- the path difference phase shifter 32 causes a phase shift based on the path difference of the electromagnetic waves received by each antenna.
- the frequency f3 of the rotation of the polarization plane of the electromagnetic wave is made larger than the frequency band f1 for transmitting the information signal.
- the radio receiver 30 further processes the synthesized received signal with a resolution of (1 / f3) time to avoid the phenomenon that the electromagnetic wave energy becomes zero due to radio wave interference, and the information signal in the frequency band f1 is error-free. It is possible to receive.
- FIGS. 4A and 4B are schematic configuration diagrams showing a wireless communication system according to a second embodiment, and the elements common to the elements in FIG. 1 showing the first embodiment are common.
- the code is attached.
- FIG. 4A shows the configuration of the wireless transmitter 10
- FIG. 4B shows the configuration of the wireless receiver 30a.
- the wireless communication system of this embodiment includes a wireless transmitter 10 and a wireless receiver 30a.
- the wireless transmitter 10 shown in FIG. 4 (a) has the same configuration as the wireless transmitter 10 of FIG. 1 (a) showing the first embodiment. Therefore, the description is omitted.
- the time division switch 37 includes an input switch 37a and an output switch 37b, and can switch the combination of the connections.
- the receiving antennas 31-1 to 31-6 in the present embodiment are, respectively, delay units 34-1 to 34-6 and path difference phase shifters 32-1 to 32-6 via the time division switch 37. After being connected to the delay devices 35-1 to 35-6, they are all connected to the synthesizer 33.
- the wireless receiver 30a uses the time division switch 37 to switch the connection between the receiving antennas 31-1 to 31-6 and the delay units 34-1 to 34-6 at high speed in a (1 / f3) cycle.
- the frequency f1 which is the first frequency is set lower than the frequency f2 of the carrier wave which is the second frequency and the frequency f3 which is the third frequency. .
- the frequency f2 of the carrier wave is set higher than the frequency f3.
- the wireless receiver 30a connects the receiving antenna 31-1 and the delay unit 34-1 by the time division switch 37, and the receiving antenna 31-2
- the delay device 34-2 is connected, and the receiving antenna 31-6 and the delay device 34-6 are connected similarly in the same manner.
- the wireless receiver 30a connects the receiving antenna 31-1 and the delay unit 34-2 by the time division switch 37, and the receiving antenna 31-2
- the delay device 34-3 is connected, and the receiving antenna 31-6 and the delay device 34-1 are connected similarly in the same manner.
- the wireless receiver 30a connects the receiving antenna 31-1 and the delay device 34-3 by the time division switch 37, and the receiving antenna 31-2
- the delay device 34-4 is connected, and the receiving antenna 31-6 and the delay device 34-2 are connected similarly in the same manner.
- the wireless receiver 30a connects the reception antenna 31-1 and the delay device 34-4 by the time division switch 37, and the reception antenna 31-2
- the delay device 34-5 is connected, and the receiving antenna 31-6 and the delay device 34-3 are connected similarly in the same manner.
- the wireless receiver 30a connects the receiving antenna 31-1 and the delay device 34-5 by the time division switch 37, and the receiving antenna 31-2
- the delay device 34-6 is connected, and the receiving antenna 31-6 and the delay device 34-4 are connected similarly in the same manner.
- the wireless receiver 30a connects the receiving antenna 31-1 and the delay device 34-6 by the time division switch 37, and the receiving antenna 31-2
- the delay unit 34-1 is connected, and the receiving antenna 31-6 and the delay unit 34-5 are similarly connected in the same manner.
- This switching is synchronized with the mechanical rotation of the transmitting antenna 20.
- the relative angle between the receiving antennas 31-1 to 31-6 connected to the delay units 34-1 to 34-6 and the transmitting antenna 20 always falls within a predetermined range.
- the wireless receiver 30a further delays the input signal by delay amounts T to 6T by the delay units 34-1 to 34-6, respectively. Since the polarization plane of the input electromagnetic wave is rotated at (1 / f3) period, interference due to radio wave scattering occurs at (1 / f3) period. In order to suppress the interference due to the radio wave scattering, the delay amount T is a value ((1 / f3) ⁇ 6) capable of evenly sampling the (1 / f3) period.
- the path difference phase shifters 32-1 to 32-6 correct the phase shifts ⁇ 1 to ⁇ 6 of these delay signals due to the path difference of the electromagnetic waves.
- the path difference of the electromagnetic wave is generated by reflection of the polarized wave, and the polarization of the electromagnetic wave is rotated at (1 / f3) period, so that the phase shift due to the path difference of the electromagnetic wave is also (1 / f3) period.
- radio interference can be suppressed by other delay signals without performing optimum phase shift correction at every moment. Therefore, the correction values of the phase shifts ⁇ 1 to ⁇ 6 due to the path difference of the electromagnetic waves may be set as predetermined fixed values with the least interference.
- the delay units 35-1 to 35-6 respectively delay the rotational phase-compensated input signal by (t1 ⁇ T) to (t1-6T).
- the predetermined time t1 is a constant and may be a value of 6T or more. Thereby, the delay amounts of all the delay signals can be made equal to the predetermined time t1.
- the combiner 33 adds all the input signals. Thereby, even if radio wave interference occurs in any of the receiving antennas 31-1 to 31-6, it is possible to avoid the phenomenon that the electromagnetic wave energy becomes zero due to the interference.
- the frequency band f1 of the information signal is a frequency lower than the frequency f3
- the combined received signal may have a predetermined signal strength in any of the (1 / f3) periods. Therefore, it is possible to avoid a communication error due to radio wave interference.
- the radio transmitter 10 and the radio receiver 30a according to the present embodiment are changed by radio interference even when the installation environment changes and the path of the electromagnetic wave reaching the radio receiver 30a from the radio transmitter 10 changes dynamically. It is possible to avoid communication errors. As a result, the reception sensitivity can be improved, and the reliability of wireless communication can be improved.
- the second embodiment described above has the following effects (E) and (F).
- (E) The radio transmitter 10 and the radio receiver 30a according to the present embodiment have radio interference even when the installation environment changes and the path of the electromagnetic wave reaching the radio receiver 30a from the radio transmitter 10 changes dynamically. It is possible to avoid communication errors due to As a result, the reception sensitivity can be improved, and the reliability of wireless communication can be improved.
- the analog non-linear element is, for example, a basic element constituting a wireless communication device such as an analog mixer, an analog modulator, and an analog frequency synthesizer.
- the operating point (operating area) of the semiconductor element needs to be strictly fixed.
- the semiconductor element which is the main stream of the analog non-linear element the operating point (operating area) of the semiconductor element fluctuates due to the change in environmental temperature or the secular change. Therefore, it is necessary to re-adjust the operating point of the semiconductor element, which has been an obstacle to increasing the life of the wireless communication device.
- sampling theorem in order to realize the same function as an analog circuit in a decidal circuit, it is necessary to digitize an analog signal with a sampling period of at least twice the frequency to handle and operate the digital circuit in this sampling period It is.
- the frequency related to this sampling period is called the Nyquist frequency.
- a wireless communication device uses an electromagnetic wave propagating in space as a transmission medium for communication.
- the frequency of the electromagnetic wave that can propagate in space is in the range of 300 MHz to 3 GHz.
- the frequency of electromagnetic waves is 300 MHz or less, the efficiency of radiating radio waves into the air is significantly reduced.
- the frequency of the electromagnetic wave is 3 GHz or more, the attenuation of the electromagnetic wave energy becomes large due to the scattering phenomenon due to shielding, reflection, diffraction, etc. when the radio wave propagates in the air, communication can not be performed over long distances, only short distance communication is possible. It becomes. Therefore, the frequency handled by the wireless communication device is limited to the range of 300 MHz to 3 GHz.
- the operating frequency of general-purpose digital elements is increased from several hundred MHz to several GHz, so it is possible to introduce digital circuits to wireless communication devices and achieve no adjustment and long life.
- an analog signal is converted to a digital signal and processed will be described.
- FIG. 5 (a) and 5 (b) are schematic configuration diagrams showing a wireless communication system according to a third embodiment, and the elements common to the elements in FIG. 1 showing the first embodiment are common.
- the code is attached.
- the wireless communication system of the present embodiment includes a wireless transmitter 10 b and a wireless receiver 30 b.
- the wireless transmitter 10b shown in FIG. 5A includes the same information generation circuit 11 as the wireless transmitter 10 of the first embodiment, the oscillator 12, and the modulator 13, and wireless transmission of the first embodiment. And a base band circuit 17, an oscillator 16, a phase shift circuit 15 which is a phase shift means, and a modulator 18 which is a second modulation means. And a modulator 18-2 which is a third modulation means.
- the output side of the information generation circuit 11 is connected to the baseband circuit 17.
- the output side of the baseband circuit 17 and the output side of the oscillator 12 are connected to the modulator 13.
- the output side of the modulator 13 is connected to the modulator 18-1 and the modulator 18-2.
- the output side of the oscillator 16 is further connected to the modulator 18-1.
- the output side of the oscillator 16 is further connected to the modulator 18-2 via the phase shift circuit 15.
- the output side of the modulator 18-1 is connected to a transmitting antenna 20b-1, which is a first transmitting antenna.
- the output side of the modulator 18-2 is connected to a transmitting antenna 20b-2, which is a second transmitting antenna.
- the baseband circuit 17 has a function of converting the signal output from the information generation circuit 11 into a digital signal.
- the oscillator 16 has a function of outputting an oscillation signal of frequency f3.
- the modulators 18-1 and 18-2 further have a function of modulating the signal output from the modulator 13 at the frequency f3.
- the phase shift circuit 15 has a function of shifting the phase of the oscillation signal of frequency f3 by 90 degrees. However, the angle may not be exactly 90 degrees, and may be between 85 degrees and 95 degrees.
- the transmitting antenna 20b-1 and the transmitting antenna 20b-2 have a function of transmitting linear polarized waves, and are arranged to be at an angle of 90 degrees to each other. However, the angle may not be exactly 90 degrees, and may be between 85 degrees and 95 degrees.
- the wireless receiver 30b shown in FIG. 5 (b) is a first receiving antenna 31b-1 which is a first receiving antenna, a receiving antenna 31b-2 which is a second receiving antenna, and a first rotational frequency detecting means.
- the rotational frequency detection circuit 60-1, the rotational frequency detection circuit 60-2 as the second rotational frequency detection means, the delay synthesis circuit 40 as the delay synthesis means, the digital demodulation circuit 47, and the baseband circuit 48 Have.
- each of the rotational frequency detection circuits 60-1 and 60-2 includes a rectification circuit 61, a low pass filter 62, and an analog / digital converter (hereinafter referred to as "A / D converter") 63.
- the output sides of the receiving antennas 31b-1 and 31b-2 are connected to the rotational frequency detecting circuits 60-1 and 60-2, respectively.
- the outputs of the rotational frequency detection circuits 60-1 and 60-2 are connected to the delay synthesis circuit 40.
- the output side of the delay synthesis circuit 40 is connected to the digital demodulation circuit 47.
- the output side of the digital demodulation circuit 47 is connected to the baseband circuit 48.
- the output terminal of the baseband circuit 48 is the output terminal of the wireless receiver 30b.
- the receiving antennas 31b-1 and 31b-2 are disposed vertically to each other, and have a function of receiving linearly polarized waves. However, the angle may not be exactly 90 degrees, and may be between 85 degrees and 95 degrees.
- the rotational frequency detection circuits 60-1 and 60-2 have a function of rectifying the input signal to detect a signal having a frequency of f3 or less, and performing analog / digital conversion.
- the input terminals to the rotational frequency detection circuits 60-1 and 60-2 are connected to the rectification circuit 61.
- the output side of the rectifier circuit 61 is connected to the low pass filter 62.
- the output side of the low pass filter 62 is connected to the A / D converter 63.
- the output side of the A / D converter 63 is connected to the output terminals of the rotational frequency detection circuits 60-1 and 60-2.
- the delay synthesis circuit 40 delays the input signal by a predetermined amount, performs polarization phase rotation to correct the phase shift ⁇ of the polarization plane due to the reflection of the electromagnetic wave, and corrects the phase shift ⁇ of the electromagnetic wave due to the path difference. After performing the phase correction, it has a function of compensating and combining the delay of the predetermined amount.
- the digital demodulation circuit 47 has a function of demodulating the input digital signal into a baseband signal.
- the baseband circuit 48 has a function of processing the input baseband signal.
- the frequency f1 which is the first frequency is set lower than the frequency f2 of the carrier wave which is the second frequency and the frequency f3 which is the third frequency.
- the carrier frequency f2 is set higher than the frequency f3.
- FIG. 6A the horizontal axis indicates time t, and the vertical axis indicates voltage Vc.
- the voltage Vc vibrates finely at the carrier wave f2, and the envelope of the waveform vibrates largely at the frequency f3.
- the horizontal axis indicates time t
- the vertical axis indicates voltage Vd.
- the voltage Vd vibrates finely on the carrier wave f2, and the envelope of the waveform vibrates largely at the frequency f3 and vibrates 90 ° out of phase with the voltage Vc.
- FIG. 6C is a three-dimensional view showing the time change on the xy plane of the electromagnetic waves transmitted and synthesized from the transmission antennas 20b-1 and 20b-2. Similar to the time change of the electromagnetic wave shown in FIG. 3C, the polarization plane of the electromagnetic wave indicated by the waveform of this frequency f2 rotates at the frequency f3 on the xy plane, so the time change of the envelope is x It becomes helical in space.
- the radio transmitter 10b modulates the signal modulated by the carrier wave f2 with a signal of the frequency f3 larger than the frequency f2 to generate a first output signal, and transmits it using the transmission antenna 20b-1. Further, the radio transmitter 10b modulates the signal modulated by the carrier wave f2 with a signal obtained by rotating the phase of the frequency f3 by 90 degrees to generate a second output signal, and generates 90 degrees with respect to the transmitting antenna 20b-1. It transmits by the transmitting antenna 20b-2 installed at an angle.
- the transmitting antenna 20b-1 and the transmitting antenna 20b-2 transmit electromagnetic waves having two orthogonal polarization components which are orthogonal to each other, and therefore, they do not interfere with each other due to their installation positions. Therefore, it is possible to paste the two transmitting antennas 20b-1 and 20b-2 in a cross shape and integrate them, thereby miniaturizing the entire transmitting antenna.
- the wireless receiver 30b receives the vertically polarized wave component of the electromagnetic wave by the receiving antenna 31b-1 installed in the vertical direction, and receives the horizontally polarized wave component of the electromagnetic wave by the receiving antenna 31b-2 installed in the horizontal direction Do. Since the receiving antenna 31b-1 and the receiving antenna 31b-2 receive electromagnetic waves having two orthogonal polarization components orthogonal to each other, they do not interfere with each other due to their installation positions. Therefore, the two receiving antennas 31 b-1 and 31 b-2 can be attached in a cross shape and integrated to miniaturize the entire receiving antenna.
- the electromagnetic waves arriving at any polarization angle can be received by the two integrated receiving antennas 31b-1 and 31b-2. Therefore, downsizing and cost reduction of the device can be achieved by reducing the number of receiving antennas.
- the third embodiment described above has the following effects (G) to (J).
- the transmitting antenna 20b-1 and the transmitting antenna 20b-2 transmit electromagnetic waves to two independent polarization components orthogonal to each other, and therefore, they do not interfere with each other by the installation position. Therefore, it is possible to integrate two transmitting antennas 20b-1 and 20b-2 and to miniaturize the whole transmitting antenna.
- the receiving antenna 31 b-1 and the receiving antenna 31 b-2 receive electromagnetic waves of two independent polarization components orthogonal to each other, and therefore do not interfere with each other by the installation position. Therefore, it is possible to unify two receiving antennas 31b-1 and 31b-2 and to miniaturize the whole receiving antenna.
- the two integrated receiving antennas 31b-1 and 31b-2 can receive an electromagnetic wave arriving at any polarization angle. Therefore, downsizing and cost reduction of the device can be achieved by reducing the number of receiving antennas.
- FIGS. 7A and 7B are schematic configuration diagrams showing a wireless communication system according to a fourth embodiment. Elements common to the elements in FIG. 5 showing the third embodiment are assigned the same reference numerals.
- a wireless transmitter 10c shown in FIG. 7A is similar to the wireless transmitter 10b of FIG. 5A showing the third embodiment, an information generation circuit 11, an oscillator 12, a modulator 13, and a baseband.
- a circuit 17 and modulators 18-1 and 18-2 are provided.
- the transmission antennas 20c-1 and 20c-2 are provided.
- the transmitting antenna 20c-1 and the transmitting antenna 20c-2 each have a function of transmitting a circularly polarized electromagnetic wave, and are arranged to transmit circularly polarized waves in opposite directions to each other.
- the transmission antenna 20c-1 which is the first transmission antenna, has a function of transmitting right-handed circularly polarized waves.
- the transmitting antenna 20c-2 which is the second transmitting antenna, has a function of transmitting left-handed circularly polarized waves.
- the transmitting antenna 20c-1 and the transmitting antenna 20c-2 transmit circularly polarized electromagnetic waves whose rotational directions are opposite to each other.
- the transmitting antenna 20c-1 and the transmitting antenna 20c-2 transmit an electromagnetic wave having two independent polarization components only by attaching them so that the rotational directions are opposite to each other. That is, compared with the transmission antennas 20b-1 and 20b-2 of the third embodiment, there is little possibility that the polarization components are mixed with each other even if they are not arranged vertically exactly, and it is easy to manufacture and after manufacture The effect is that adjustment is unnecessary.
- the wireless receiver 30c shown in FIG. 7 (b) includes rotational frequency detection circuits 60-1 and 60-2 similar to the wireless receiver 30b of FIG. 5 (b) showing the third embodiment, and a delay combining circuit 40. And a digital demodulation circuit 47 and a baseband circuit 48. Furthermore, receiving antennas 31c-1 and 31c-2 different from the wireless transmitter 10b of FIG. 5A showing the third embodiment are provided.
- the receiving antenna 31c-1 which is the first receiving antenna and the receiving antenna 31c-2 which is the second receiving antenna each have a function of receiving an electromagnetic wave of circular polarization, and are circularly polarized in opposite directions to each other. It is arranged to receive the waves.
- the receiving antenna 31c-1 has a function of receiving right-handed circularly polarized waves.
- the receiving antenna 31c-2 has a function of receiving left-handed circularly polarized waves.
- the receiving antennas 31c-1 and 31c-2 similarly transmit electromagnetic waves having two independent polarization components only by pasting them so that the rotational directions are opposite to each other. That is, there is little possibility that the two polarized wave components are mixed with each other even if they are not installed vertically exactly, and it is easy to manufacture as compared with the receiving antenna 31b-1 and the receiving antenna 31b-2 of the third embodiment. And, there is an effect that adjustment after production is unnecessary.
- the frequency f1 which is the first frequency is lower than the frequency f2 of the carrier wave which is the second frequency and the frequency f3 which is the third frequency.
- the carrier frequency f2 is higher than the frequency f3.
- the radio transmitter 10c of the fourth embodiment differs from the electromagnetic wave consisting of vertical polarization and horizontal polarization of the radio transmitter 10b of the third embodiment, and is an electromagnetic wave consisting of left-handed circular polarization and right-handed circular polarization. Is the same as the operation of the wireless transmitter 10b of the third embodiment except for transmitting.
- the radio receiver 30c of the fourth embodiment differs from the electromagnetic wave consisting of vertical polarization and horizontal polarization of the radio receiver 30b of the third embodiment, and is an electromagnetic wave consisting of left-handed circular polarization and right-handed circular polarization. Is the same as the operation of the wireless receiver 30b of the third embodiment except for receiving the signal.
- the fourth embodiment described above has the following effects (K) and (L).
- K The transmitting antenna 20c-1 and the transmitting antenna 20c-2 transmit an electromagnetic wave having two independent polarization components only by attaching them so that the rotational directions are opposite to each other. Therefore, it is easy to manufacture and there is an effect that adjustment after manufacture is unnecessary.
- the receiving antennas 31c-1 and 31c-2 similarly transmit electromagnetic waves having two independent polarization components only by bonding so that the rotational directions are opposite to each other. Therefore, it is easy to manufacture and there is an effect that adjustment after manufacture is unnecessary.
- FIGS. 8A and 8B are schematic configuration diagrams showing a wireless communication system according to a fifth embodiment. Elements common to the elements in FIG. 7 showing the fourth embodiment are assigned the same reference numerals.
- a wireless transmitter 10d shown in FIG. 8A includes an information generation circuit 11 similar to the wireless transmitter 10c of the fourth embodiment, a baseband circuit 17, and a transmission antenna 20c-1 which is a first transmission antenna. And a transmission antenna 20c-2 which is a second transmission antenna. Furthermore, the oscillator 12-1 and 12-2 different from the radio transmitter 10c of the fourth embodiment, the modulator 13-1 as the first modulation means, and the modulator 13- as the fourth modulation means And an adder 19-1 as a first combining means, and an adder 19-2 as a second combining means.
- the output side of the information generation circuit 11 is connected to the baseband circuit 17.
- the output side of the baseband circuit 17 and the output side of the oscillator 12-1 are connected to the modulator 13-1.
- the output side of the baseband circuit 17 and the output side of the oscillator 12-2 are connected to the modulator 13-2.
- the output side of the modulator 13-1 and the output side of the modulator 13-2 are connected to an adder 19-1.
- the output side of the adder 19-1 is connected to the transmitting antenna 20c-1.
- the output side of the modulator 13-2 is connected to the inversion phase shift circuit 15b, and the output side of the inversion phase shift circuit 15b and the output side of the modulator 13-1 are connected to the adder 19-2. It is done.
- the output side of the adder 19-2 is connected to the transmitting antenna 20c-2.
- the wireless receiver 30c shown in FIG. 8 (b) has the same configuration as the wireless receiver 30c of the fourth embodiment.
- the frequency f1 which is the first frequency is lower than any of the frequency f2a of the carrier wave which is the second frequency, the frequency f2b of the carrier wave which is the fourth frequency, and the frequency f3 which is the third frequency.
- the carrier frequency f2a and the frequency f2b are higher than the frequency f3.
- the oscillator 12-1 has a function of outputting a carrier wave f2a, which is the second frequency, to the modulator 13-1.
- the oscillator 12-2 has a function of outputting, to the modulator 13-2, a carrier wave f2b which is a fourth frequency slightly different in frequency from the carrier wave f2a.
- the difference between the frequency f2a and the frequency f2b is between 80% and 125% of the frequency f2a.
- the modulator 13-1 has a function of modulating the information signal in the frequency band f1 with the carrier wave f2a, which is the second frequency, and outputting it as a first modulated signal.
- the modulator 13-2 has a function of modulating the information signal in the frequency band f1 with the carrier wave f2b which is the fourth frequency and outputting it as a fourth modulated signal.
- the inversion phase shift circuit 15 b has a function of inverting and outputting the first modulation signal.
- the adder 19-1 has a function of adding the inverted first modulation signal and the inverted fourth modulation signal and outputting the result to the transmission antenna 20c-1.
- the adder 19-2 has a function of adding the first modulation signal and the fourth modulation signal and outputting the result to the transmission antenna 20c-2.
- FIGS. 9A and 9B illustrate the operation of the wireless communication system according to the fifth embodiment.
- the horizontal axis in FIG. 9A indicates time t, and the vertical axis indicates the respective signal voltages.
- the waveform of the carrier wave f2a is indicated by an alternate long and short dash line
- the waveform of the carrier wave f2b is indicated by a dotted line
- a synthetic wave f3 obtained by combining these by the adder 19-2 is indicated by a thick line. Due to the slight difference in frequency between the carrier wave f2a and the carrier wave f2b, the combined wave f3 vibrates finely with the carrier wave (f2a + f2b) / 2, and the envelope of the combined wave f3 vibrates largely at the frequency f3.
- the frequency of the carrier wave included in the combined wave is f2a.
- the horizontal axis of FIG. 9 (b) indicates time t, and the vertical axis indicates the respective signal voltages.
- the waveform of the carrier wave f2a is indicated by the alternate long and short dashed line
- the waveform of the inverted carrier wave (-f2b) is indicated by the dashed line
- the synthetic wave f3b obtained by combining these by the adder 19-2 is indicated by the bold line. Due to the slight difference in frequency between the carrier wave f2a and the carrier wave (-f2b), the combined wave f3b finely vibrates on the carrier wave f2, and the envelope of the combined wave f3b greatly vibrates at the frequency f3.
- the envelope of the synthetic wave f3b is 90 degrees out of phase with the envelope of the synthetic wave f3.
- the output signals of two oscillators slightly shifted in frequency are modulated as carrier waves respectively, and the frequency f3 is generated by adding the two modulated signals.
- the envelope of the time waveform of the signal after addition changes at a frequency
- an inverted phase shift circuit 15 b that reverses the signal and rotates the phase by 180 degrees is mounted. Therefore, adjustment of the phase rotation amount of the phase shift circuit 15 is unnecessary, and therefore, there is an effect of contributing to non-adjustment of the wireless transmitter 10d.
- the fifth embodiment described above has the following effect (M).
- M instead of the phase shift circuit 15 that rotates the phase by 90 degrees, since the inverted phase shift circuit 15 b that reverses the signal and rotates the phase by 180 degrees is mounted, adjustment of the phase rotation amount of the phase shift circuit 15 Thus, there is an effect of contributing to no adjustment of the wireless transmitter 10d.
- FIG. 10 is a diagram showing the concept of the delay combining circuit according to the sixth embodiment.
- the output sides of the receiving antennas 31c-1 and 31c-2 are connected to the delay synthesis circuit 40 via rotation frequency detection circuits 60-1 and 60-2.
- the output side of the delay synthesis circuit 40 is connected to the digital demodulation circuit 47.
- the output side of the digital demodulation circuit 47 is connected to the baseband circuit 48.
- the output side of the baseband circuit 48 is the output of the wireless receiver 30e.
- the delay synthesis circuit 40 When the frequency f3 component of the electromagnetic waves received by the receiving antennas 31c-1 and 31c-2 is input, the delay synthesis circuit 40 generates n number of signals of delay amounts T to nT, and the electromagnetic waves of these delay signals are generated.
- the signal power is increased by correcting the phase shift .theta.i of the polarization plane, correcting the phase shift .phi.i due to the path difference of the electromagnetic wave, and synthesizing the signal with the delay amount restored.
- the reflected phase shift detector 42-i (i is a natural number from 1 to n) has a function of delaying the input signal by (i ⁇ T) and correcting the phase shift ⁇ i of the polarization plane due to the reflection of the electromagnetic wave. ing.
- the delay unit 43-i has a function of delaying the input signal by (i ⁇ T).
- the adder 44-i adds the output signal of the reflection phase-shifting delay unit 42-i and the output signal of the delay unit 43-i, and the multiplex waves received by the receiving antennas 31c-1 and 31c-2 are It has a function of outputting polarization signals delayed by delay times T to 6T, respectively.
- the adder 44-i has a function of adding the output signal of the reflection phase shift delaying device 42-i and the output signal of the delay device 43-i.
- the delay amount T is a value ((1 / f3) ⁇ n) which can uniformly sample the (1 / f3) period without bias. Thereby, even if radio wave interference occurs at any timing of the delay time T to 6T, it is possible to avoid the phenomenon that the electromagnetic wave energy becomes zero due to the interference. Furthermore, the present invention is not limited to this, and the delay amount T may be set to an arbitrary value such as an integral multiple, a half, or a 3/2 multiple of ((1 / f3) ⁇ n) period.
- the path difference phase shift delay unit 45-i corrects the phase shift ⁇ i due to the path difference of the electromagnetic wave, and makes the delays of the input signals in the reflection phase shift shift delay unit 42-i and the delay block 43-i uniform.
- the combiner 46 increases signal power by combining these signals.
- the output side of the rotational frequency detection circuit 60-1 is connected to the reflective phase shift shift delayers 42-1 to 42-n, and the output side of the rotational frequency detection circuit 60-2 is a delay device 43-1 to 43-n. It is connected to the.
- the output side of the reflection phase shift delay circuit 42-1 and the output side of the delay device 43-1 are connected to the adder 44-1.
- the output side of the adder 44-1 is connected to the path difference phase shift delay unit 45-1.
- the output side of the reflection phase shift delaying device 42-i and the output side of the delay device 43-i are connected to the adder 44-i.
- the output side of the adder 44-i is connected to the path difference phase shift delayer 45-i.
- the phase difference due to the path difference of the electromagnetic wave of the ith delay signal is corrected by the path difference phase shift delay device 45-i and is input to the combiner 46.
- the combiner 46 increases the signal power of the output signal by combining everything from the first delay signal to the nth delay signal.
- the output side of the combiner 46 is the output side of the delay combining circuit 40 and is connected to the digital demodulation circuit 47.
- the output side of the digital demodulation circuit 47 is connected to the baseband circuit 48.
- the delay synthesis circuit 40 can minimize the error rate after demodulation of the digital demodulation circuit 47 by increasing the signal power by correction.
- FIG. 11 is a schematic block diagram showing a delay combining circuit according to the sixth embodiment. Similar to the delay combining circuit 40 of FIG. 10, the output sides of the receiving antennas 31c-1 and 31c-2 are connected to the delay combining circuit 40a via rotation frequency detection circuits 60-1 and 60-2. The output side of the delay synthesis circuit 40 is connected to the digital demodulation circuit 47. The output side of the digital demodulation circuit 47 is connected to the baseband circuit 48. Further, a control signal from the digital demodulation circuit 47 is connected to the delay synthesis circuit 40a. By this control signal, it is possible to control the correction of the phase shift ⁇ 1 to ⁇ n of the polarization plane due to the reflection of the electromagnetic wave and the correction of the phase shift ⁇ 1 to ⁇ n due to the path difference of the electromagnetic wave.
- the delay unit 43-i has a function of delaying the input signal by (i ⁇ T).
- the adder 44-i adds the output signal of the reflection phase shift shifter 49-i and the output signal of the delay unit 43-i, and multiplexes the multiple waves received by the receiving antennas 31c-1 and 31c-2, respectively. It has a function of outputting a polarization signal delayed by delay time T to 6T.
- the path difference phase shifters 49a-i have a function of correcting the phase shifts ⁇ 1 to ⁇ n due to the path difference of the electromagnetic waves.
- the delay unit 50-i has a function of delaying the signal by a delay time (t2-i ⁇ T). Thus, all the signals output from the delay units 50-1 to 50-n become signals delayed by a predetermined time t2.
- the combiner 46 increases signal power by combining these signals.
- the output side of the combiner 46 is the output side of the delay combining circuit 40, and is connected to the digital demodulation circuit 47a.
- the output side of the digital demodulation circuit 47 a is connected to the baseband circuit 48.
- the digital demodulation circuit 47a further has a function to control correction of phase shift ⁇ 1 to ⁇ n of polarization plane due to reflection of electromagnetic wave of the delay synthesis circuit 40a and correction of phase shift ⁇ 1 to ⁇ n due to path difference of electromagnetic wave. .
- the phase shifts ⁇ 1 to ⁇ n due to the path difference of the electromagnetic waves indicate the phase shifts at the frequency f3.
- the electromagnetic waves arriving at the receiving antennas 31c-1 and 31c-2 are converted into two digital signals of (1 / f3) period respectively by the rotational frequency detection circuits 60-1 and 60-2.
- One digital signal is input to the delay units 43a-1 to 43a-n, and the other digital signal is input to the delay units 43-1 to 43-n and delayed by a predetermined delay amount.
- the output signals of the delay devices 43a-1 to 43a-n are corrected by the reflected phase shifters 49-1 to 49-n, respectively, so that the phase shift ⁇ i of the polarization plane due to the reflection of the electromagnetic wave is corrected.
- the reflection phase shifters 49-1 to 49-n correct the phase shift ⁇ i of the polarization plane, for example, by delaying the input signal by a predetermined time (( ⁇ i ⁇ 2 ⁇ ) ⁇ f3).
- the correction signals output from the reflection phase shifters 49-1 to 49-n and the output signals from the delay units 43-1 to 43-n are added by adders 44-1 to 44-n, respectively.
- the output signals of the adders 44-1 to 44-n correspond to the delay times T to nT, respectively, and are reception signals in which the phase shifts ⁇ 1 to ⁇ n of the polarization plane due to the reflection of the electromagnetic waves are corrected.
- the output signals of the adders 44-1 to 44-n are corrected for phase shift due to path difference of electromagnetic waves by path difference phase shifters 49a-1 to 49a-n, respectively, and delay elements 50-1 to 50-n
- the delay amounts of the respective signals all become the predetermined time t2.
- the output signals of the delay units 50-1 to 50-n are combined by the combiner 46, and the signal power of the output signal is increased.
- the electromagnetic waves arriving at the receiving antennas 31c-1 and 31c-2 have the polarization plane rotating at (1 / f3) period, so when interference due to radio wave scattering occurs, the (1 / f3) period occurs. .
- (1 / f3) periods are uniformly extracted without bias and signal processing is performed by the delay devices 43-1 to 43-n and the delay devices 43a-1 to 43a-n. Therefore, the unit T of the delay amount of the delay devices 43-1 to 43-n and the delay devices 43a-1 to 43a-n may be a value obtained by dividing the (1 / f3) period by n or (1 / f3) A value obtained by dividing 1/2 of the cycle by n.
- the delay amount T may be set to an arbitrary value such as an integral multiple, a half, or a 3/2 multiple of ((1 / f3) ⁇ n) period.
- FIG. 12 is a diagram showing an operation of the wireless communication system according to the sixth embodiment. On the horizontal axis, the operation of the wireless transmitter 10, the transmission path, and the operation of the wireless receiver 30f are described, and on the vertical axis, the passage of time t is shown.
- the wireless transmitter 10 transmits a training signal at timing T1, which is a training period. This training signal is transmitted to the transmission line.
- the digital demodulation circuit 47a of the wireless receiver 30f receives this training signal at timing R1 and corrects the phase shift ⁇ 1 to ⁇ n of the polarization plane due to the reflection of the electromagnetic wave so that the intensity of the combined reception signal is maximized, The correction of the phase shift ⁇ 1 to ⁇ n due to the path difference of the electromagnetic wave is optimized.
- the wireless transmitter 10 transmits an information signal at timing T2. This information signal is transmitted to the transmission line.
- the wireless receiver 30f receives this information signal at timing R2 and corrects the phase shift ⁇ 1 to ⁇ n of the polarization plane due to the reflection of the optimized electromagnetic wave and the phase shift ⁇ 1 to ⁇ n due to the path difference of the electromagnetic wave. Go and decrypt.
- the optimization is, for example, changing the correction amount of the phase shift ⁇ 1 to ⁇ n of the polarization plane due to the reflection of the electromagnetic wave in each delay time T to nT and adjusting the correction amount of the phase shift ⁇ 1 to ⁇ n due to the path difference. .
- phase shift ⁇ 1 of the polarization plane is changed in a predetermined range to obtain an optimum value, and then the value of phase shift ⁇ 1 due to path difference is changed in a predetermined range to obtain an optimum value. It is possible to carry out by repeatedly applying the value after the phase shift ⁇ 2 of the wavefront and the value after the phase shift ⁇ 2 due to the path difference.
- the sixth embodiment described above has the following effect (N).
- N In the training period, the correction amount of the phase shift ⁇ 1 to ⁇ n of the polarization plane due to reflection and the correction amount of the phase shift ⁇ 1 to ⁇ n due to the path difference are optimized, so the installation environment changes. Even when the path of the electromagnetic wave reaching the wireless receiver 30 f from 10 changes dynamically, it is possible to further avoid a communication error due to radio wave interference.
- FIG. 13 is a schematic block diagram showing a delay combining circuit according to the seventh embodiment. Elements common to the elements in FIG. 11 showing the sixth embodiment are assigned the same reference numerals.
- the wireless receiver 30g in this embodiment has a digital demodulation circuit 47 different from the digital demodulation circuit 47a of the wireless receiver 30f shown in the sixth embodiment, and a base of the wireless receiver 30f shown in the sixth embodiment. Except having the baseband circuit 48a different from the band circuit 48, the configuration is the same as the wireless receiver 30f shown in the sixth embodiment.
- the baseband circuit 48a has a function of controlling the correction amount of the phase shift ⁇ 1 to ⁇ n of the polarization plane due to the reflection of the electromagnetic wave of the delay synthesis circuit 40a and the correction amount of the phase shift ⁇ 1 to ⁇ n due to the path difference of the electromagnetic wave. There is.
- the operation of the wireless receiver 30g according to the seventh embodiment will be described based on FIG.
- the wireless transmitter 10 transmits a training signal at timing T1, which is a training period. This training signal is transmitted to the transmission line.
- the baseband circuit 48a of the wireless receiver 30g receives this training signal at timing R1 and phase shift ⁇ 1 to ⁇ n of the polarization plane due to the reflection of the electromagnetic wave so as to minimize the error rate after demodulation of the combined received signal. And the amount of correction of the phase shift ⁇ 1 to ⁇ n due to the path difference of the electromagnetic wave.
- the seventh embodiment described above has the following effect (O).
- FIG. 14 is a schematic configuration view showing an elevator system according to an eighth embodiment.
- the elevator system 100 includes a building 101 which is a vertically long rectangular solid and an elevator cage 111. In the interior of the building 101, a space in which the lift cage 111 moves up and down is provided. The lift cage 111 raises and lowers the internal space of the building 101 by a rope and a drive mechanism (not shown).
- a base station radio 102-1 and an antenna 103-1 are installed on a ceiling of an internal space of the building 101, and a floor of the internal space of the building 101 is a base station radio 102-2 and an antenna 103- 2 and are installed.
- the base station radios 102-1 and 102-2 are polarization angle division diversity radios having the same configuration as the radio receiver 30c shown in FIG. 8 (b).
- the antennas 103-1 and 103-2 are orthogonal polarization integrated antennas similar to the receiving antenna 31c shown in FIG. 8 (b).
- An antenna 113-1 is provided on the upper surface of the lift cage 111, an antenna 113-2 is provided on the lower surface, and the high-frequency cable 114 is connected to the terminal station wireless device 112.
- the terminal station wireless device 112 is a polarization angle division diversity wireless device similar to the wireless transmitter 10d shown in FIG. 8 (a).
- the antennas 113-1 and 113-2 are orthogonal polarization integrated antennas similar to the transmitting antenna 20c shown in FIG. 8 (a).
- the radio wave transmitted from the terminal station wireless device 112 is transmitted via the antenna 113-1 and the antenna 113-2.
- the transmitted radio waves are subject to multiple reflections by the inner wall of the building 101 and the outer wall of the elevator cage 111 because the internal space of the building 101 is used as a wireless transmission medium. That is, the interior space of the building 101 forms a multiple wave interference environment. Radio waves that have received multiple reflections reach antennas 103-1 and 103-2, respectively.
- high-quality wireless transmission can be realized even in a multiwave interference environment by polarization angle division diversity. Since the elevator car 111 can be controlled / monitored from the building 101 by the wireless connection means, the space in which the elevator car 111 ascends and descends is not wasted by the wired connection means such as a cable. Therefore, it is possible to make the building 101 a small volume or to increase the dimension of the lift cage 111 with the same volume of the building 101 to improve the transport capacity. At the same time, the weight of the lift cage 111 can be reduced.
- the weight of the wired connection means such as a cable connected to the lift cage 111 is an unignorable weight in a high-rise building.
- the eighth embodiment described above has the following effect (P).
- P Since the elevator car 111 can be controlled / monitored from the building 101 by the wireless connection means, the space in which the elevator car 111 ascends and descends is not wasted by the wired connection means such as a cable. Therefore, it is possible to increase the transport capacity by increasing the size of the elevator cage 111 with the volume of the small building 101 or with the volume of the same building 101.
- FIG. 15 is a schematic block diagram showing a power transformation equipment monitoring system according to a ninth embodiment.
- the transformation equipment monitoring system 200 of the present embodiment includes a plurality of transformers 201-1 to 201-12 and a plurality of radio base stations 211-1 to 211-4 set in the vicinity thereof.
- the number of transformers 201-1 to 201-12 is larger than the number of radio base stations 211-1 to 211-4.
- Each of the transformers 201-1 to 201-12 includes a terminal station radio 203 performing polarization angle division diversity and an orthogonal polarization integrated antenna 202.
- the dimensions of the transformers 201-1 to 201-12 are on the order of several meters.
- the radio base stations 211-1 to 211-4 respectively include a base station radio 213 performing polarization angle division diversity and an orthogonal polarization integrated antenna 212.
- the dimensions of the transformers 201-1 to 201-12 are overwhelmingly large compared to the wavelength of the electromagnetic wave having a frequency of several hundred MHz to several GHz used by the wireless device.
- the electromagnetic waves are subject to multiple reflections by the plurality of transformers 201-1 to 201-12.
- a multiple wave interference environment is formed.
- the terminal station wireless device 203 of this embodiment and the base station wireless device 213 can realize high-quality wireless transmission even in a multiwave interference environment by the polarization angle division diversity function, and a plurality of wireless base stations 211- Remote control and remote monitoring of the substations 201-1 to 201-12 can be performed by 1 to 211-4. Therefore, while being able to solve the problem of high voltage induction power which becomes a problem when using a cable etc., the cost of cable installation can be eliminated, and the safety improvement of the control / monitoring system of substations 201-1 to 201-12 Cost reduction is possible.
- the ninth embodiment described above has the following effect (Q).
- Q With the polarization angle division diversity radio of this embodiment, high quality radio transmission can be realized even in a multiwave interference environment. Control and monitoring of the transformers 201-1 to 201-12 can be remotely performed by the plurality of radio base stations 211-1 to 211-4. Therefore, while being able to solve the problem of the high voltage induction electric power which becomes a problem when using the said wired connection means, such as a cable, the laying cost of a cable can be deleted and the safety of the control / monitoring system of substation 201-1-201-12 It is possible to improve performance and reduce costs.
- the wireless receiver 30a of the second embodiment includes six receiving antennas 31-1 to 31-6.
- the present invention is not limited to this, and any n (n is a natural number) receiving antennas may be used.
- the delay amount T be a value ((1 / f3) ⁇ n) capable of sampling (1 / f3), which is the rotation period of the polarization plane of the electromagnetic wave, without bias.
- the value is (((1 / f3) / 2) ⁇ n) which can be sampled without bias ((1 / f3) ⁇ 2) which is a half of the rotation period of the polarization plane of the electromagnetic wave.
- a wireless transmitter 10d includes a transmitting antenna 20c-1 which is a first transmitting antenna for transmitting circularly polarized waves, and a transmitting antenna 20c-2 which is a second transmitting antenna.
- the present invention is not limited thereto, and the first transmitting antenna transmits linearly polarized waves, and the second transmitting antenna transmits a predetermined angle (85 degrees to 95 degrees) to the linearly polarized waves transmitted by the first transmitting antenna. Alternatively, it may transmit a linearly polarized wave.
- the polarization angle division diversity radio transmitter and radio receiver of the present invention may be applied to radio communication between a central control device in a security system and a door sensor, a window sensor or the like. This makes it possible to provide a security system that requires high communication quality.
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Abstract
Description
すなわち、本発明の偏波角度分割ダイバシチ無線送信機は、第1の周波数の情報信号を第2の周波数で変調し、第1の変調信号を出力する第1の変調手段と、前記第1の変調信号を独立した2つの偏波で送信すると共に、この偏波に第3の周波数を重畳する電磁波発信手段と、を備えることを特徴とする。
その他の手段については、発明を実施するための形態のなかで説明する。
本発明の実施形態では、多重波(マルチパス)による干渉が発生している環境下で、小さな送信アンテナや受信アンテナによって高信頼性の無線通信を実現する偏波角度分割ダイバシチ無線送信機、無線受信機、および無線通信システムを提供するため、電磁波の偏波を用いる。
この無線通信システムは、無線送信機10と、無線受信機30とを有している。無線送信機10から直交する2つの独立した直線偏波が送信される。電磁波反射体300-1によって、無線送信機10から無線受信機30への行路が遮られている。しかし、無線送信機10から送信された電磁波は、電磁波反射体300-2によって反射され、無線受信機30に到達する。この電磁波は、電磁波反射体300-2によって反射されると、行路長Lrを経ているので、無線送信機10から無線受信機30への最短の行路長Ldに比べて、以下の数式1に示すφだけ位相がずれる。
φ=((Lr-Ld)÷λ)×2π ・・・ (数式1)
ここで、λは、電磁波の波長である。電磁波の波長λは、光速をcとし、電磁波の周波数をfとすると、以下の数式2で算出される。
λ=c÷f ・・・ (数式2)
φn=((Ln-Ld)÷λ)×2π ・・・ (数式3)
更に、電磁波のそれぞれの偏波面がn番目の電磁波反射体の接平面に対して反射することにより、それぞれ反射波の偏波面の位相変移θが発生する。
図1(a),(b)は、第1の実施形態に係る無線通信システムを示す概略の構成図である。図1(a)は、無線送信機10の構成を示し、図1(b)は、無線受信機30の構成を示している。
本実施形態の無線通信システムは、無線送信機10と無線受信機30とを有している。
情報生成回路11の出力側と、発振器12の出力側は、変調器13に接続されている。変調器13の出力側は、送信アンテナ20に接続されている。
情報生成回路11は、第1の周波数である周波数帯域f1の情報信号を、変調器13に出力する機能を有している。
発振器12は、第2の周波数である搬送波f2を、変調器13に出力する機能を有している。
変調器13は、周波数帯域f1の情報信号を搬送波f2で変調し、第1の変調信号として送信アンテナ20に出力する機能を有している。
行路差位相変移器32(=32-1~32-6)の出力は、すべて合成器33に接続されている。
図3(a)~(c)は、第1の実施形態に係る無線通信システムの動作を示す図である。
図3(a)は、送信アンテナ20(図1)から送信された電磁波の、y軸上の時間変化を示す図である。横軸は時間tを示し、縦軸はy軸座標を示している。送信アンテナ20から送信された電磁波は、搬送波f2によって、(1/f2)周期で振動する。更に、モータ14によって、送信アンテナ20は周波数f3で回転しているので、この送信アンテナ20から送信された電磁波の偏波面は、(1/f3)周期で回転する。
以上説明した第1の実施形態では、次の(A)~(D)のような効果がある。
(A) 無線送信機10が送信する電磁波の偏波面は回転しているので、受信アンテナ31-1で干渉が発生しても、次の瞬間には受信アンテナ31-1に到来する電磁波の行路は変化し、よって電波干渉を起こさなくなる。よって、電磁波エネルギーがゼロになる現象を回避可能である。
図4(a),(b)は、第2の実施形態に係る無線通信システムを示す概略の構成図であり、第1の実施形態を示す図1中の要素と共通の要素には共通の符号が付されている。図4(a)は、無線送信機10の構成を示し、図4(b)は、無線受信機30aの構成を示している。
本実施形態の無線通信システムは、無線送信機10と無線受信機30aとを有している。図4(a)に示す無線送信機10は、第1の実施形態を示す図1(a)の無線送信機10と同様な構成を有している。このため、説明を省略する。
無線受信機30aは、時分割スイッチ37によって、受信アンテナ31-1~31-6と遅延器34-1~34-6との接続を(1/f3)周期で高速に切替えている。
以上説明した第2の実施形態では、次の(E),(F)のような効果がある。
(E) 本実施形態の無線送信機10と無線受信機30aは、設置環境が変化し、無線送信機10から無線受信機30aに到達する電磁波の行路が動的に変化する場合でも、電波干渉による通信誤りを回避することが可能である。これにより、受信感度を向上可能であると共に、無線通信の信頼性を向上可能である。
通信機器の高寿命化の妨げとなっているのは、アナログ非線形素子である。アナログ非線形素子は、例えば、アナログミキサ、アナログ変調器、アナログ周波数シンセサイザなど、無線通信機器を構成する基本素子である。これらアナログ非線形素子は、アナログ信号を取り扱うため、半導体素子の動作点(動作領域)が厳格に固定される必要がある。アナログ非線形素子の主流である半導体素子では、環境温度の変化や経年変化によって、半導体素子の動作点(動作領域)が変動する。よって、半導体素子の動作点の再調整が必要であり、これが無線通信機器の高寿命化の妨げとなっていた。
以下、第3の実施形態から第7の実施形態において、アナログ信号からデジタル信号に変換して処理する例を示す。
図5(a),(b)は、第3の実施形態に係る無線通信システムを示す概略の構成図であり、第1の実施形態を示す図1中の要素と共通の要素には共通の符号が付されている。
本実施形態の無線通信システムは、無線送信機10bと無線受信機30bとを有している。
ベースバンド回路17は、 情報生成回路11から出力された信号を、デジタル信号に変換する機能を有している。
発振器16は、周波数f3の発振信号を出力する機能を有している。
変調器18-1,18-2は、変調器13から出力された信号を、更に周波数f3で変調する機能を有している。
移相回路15は、周波数f3の発振信号の位相を90度移動させる機能を有している。しかし、この角度は厳密に90度でなくともよく、85度から95度の間であれば良い。このとき、角度ずれに起因する発振信号のノイズ成分の最大値は、COS(85度)=COS(95度)=8.7%となる。85度未満の場合や、95度を超えた場合には、角度ずれに起因する発振信号のノイズ成分の最大値は、8.7%以上となる。
送信アンテナ20b-1と、送信アンテナ20b-2とは、直線偏波を送信する機能を有し、相互に90度の角度となるように配置されている。しかし、この角度は厳密に90度でなくともよく、85度から95度の間であれば良い。このとき、角度ずれに起因する直線偏波のノイズ成分の最大値は、COS(85度)=COS(95度)=8.7%となる。85度未満の場合や、95度を超えた場合には、角度ずれに起因する発振信号のノイズ成分の最大値は、8.7%以上となる。
受信アンテナ31b-1,31b-2は、相互に垂直に設置されており、それぞれ直線偏波を受信する機能を有している。しかし、この角度は厳密に90度でなくとも良く、85度から95度の間であれば良い。このとき、角度ずれに起因する受信信号のノイズ成分は、COS(85度)=COS(95度)=8.7%以下となる。85度未満の場合や、95度を超えた場合には、角度ずれに起因する発振信号のノイズ成分の最大値は、8.7%以上となる。
移相回路15の位相の移動量と、送信アンテナ20b-1,20b-2の設置角度と、受信アンテナ31b-1,31b-2の設置角度とが、すべて85度または95度であった場合を考える。このとき、角度ずれに起因するノイズ成分の総和は、8.7%×3=26.1%である。よって、移相回路15の位相の移動量と、送信アンテナ20b-1,20b-2の設置角度と、受信アンテナ31b-1,31b-2の設置角度のずれ、全てが復号して起因する発振信号のノイズ成分は、26.1%以下となる。
回転周波数検出回路60-1,60-2は、入力された信号を整流してf3以下の周波数の信号を検出し、アナログ/デジタル変換する機能を有している。
回転周波数検出回路60-1,60-2への入力端子は、整流回路61に接続されている。整流回路61の出力側は、ローパスフィルタ62に接続されている。ローパスフィルタ62の出力側は、A/Dコンバータ63に接続されている。A/Dコンバータ63の出力側は、この回転周波数検出回路60-1,60-2の出力端子に接続されている。
デジタル復調回路47は、入力されたデジタル信号をベースバンド信号に復調する機能を有している。
ベースバンド回路48は、入力されたベースバンド信号を処理する機能を有している。
図6(a)~(c)は、第3の実施形態に係る無線通信システムの動作を示す図である。
図6(a)は、横軸に時間tを示し、縦軸に電圧Vcを示している。電圧Vcは、搬送波f2で細かく振動すると共に、波形の包絡線は、周波数f3で大きく振動している。
以上説明した第3の実施形態では、次の(G)~(J)のような効果がある。
(G) 送信アンテナ20b-1と送信アンテナ20b-2とは、直交する2つの独立の偏波成分を電磁波を送信するので、相互の設置位置によって干渉することはない。よって2つの送信アンテナ20b-1,20b-2を一体化して、送信アンテナ全体を小型化することが可能である。
図7(a),(b)は、第4の実施形態に係る無線通信システムを示す概略の構成図である。第3の実施形態を示す図5中の要素と共通の要素には共通の符号が付されている。
第4の実施形態の無線送信機10cは、第3の実施形態の無線送信機10bの垂直偏波と水平偏波からなる電磁波とは異なり、左旋円偏波と右旋円偏波からなる電磁波を送信するほかは、第3の実施形態の無線送信機10bの動作と同様である。
以上説明した第4の実施形態では、次の(K),(L)のような効果がある。
(K) 送信アンテナ20c-1と送信アンテナ20c-2は、回転方向が反対になるように貼りあわせるだけで、2つの独立した偏波成分を有する電磁波を送信する。よって、製造しやすく、かつ製造後の調整が不要という効果を奏する。
図8(a),(b)は、第5の実施形態に係る無線通信システムを示す概略の構成図である。第4の実施形態を示す図7中の要素と共通の要素には共通の符号が付されている。
本実施形態において、第1の周波数である周波数f1は、第2の周波数である搬送波の周波数f2a、第4の周波数である搬送波の周波数f2b、第3の周波数である周波数f3のいずれよりも低い。搬送波の周波数f2aと周波数f2bとは、周波数f3よりも高い。
発振器12-1は、第2の周波数である搬送波f2aを、変調器13-1に出力する機能を有している。
発振器12-2は、搬送波f2aと僅かに周波数が異なる第4の周波数である搬送波f2bを、変調器13-2に出力する機能を有している。本実施形態において、周波数f2aと周波数f2bとの差は、周波数f2aの80パーセントから125パーセントの間である。周波数f2aと周波数f2bとの差が、周波数f2aの80パーセント未満や125パーセント以上であると、後述する合成波f3,f3bの包絡線の周波数が周波数f2a,f2bに近接してしまい、合成波f3,f3bの包絡線の抽出が困難となる。
変調器13-1は、周波数帯域f1の情報信号を、第2の周波数である搬送波f2aで変調し、第1の変調信号として出力する機能を有している。
変調器13-2は、周波数帯域f1の情報信号を、第4の周波数である搬送波f2bで変調し、第4の変調信号として出力する機能を有している。
反転移相回路15bは、第1の変調信号を反転して出力する機能を有している。
加算器19-1は、反転した第1の変調信号と第4の変調信号を加算して、送信アンテナ20c-1に出力する機能を有している。
加算器19-2は、第1の変調信号と第4の変調信号を加算して、送信アンテナ20c-2に出力する機能を有している。
図9(a)の横軸は時間tを示し、縦軸はそれぞれの信号電圧を示している。搬送波f2aの波形が一点鎖線で、搬送波f2bの波形が鎖線で、これらを加算器19-2で合成した合成波f3が太線で示されている。搬送波f2aと搬送波f2bの僅かな周波数の違いによって、合成波f3は搬送波(f2a+f2b)÷2で細かく振動すると共に、合成波f3の包絡線は周波数f3で大きく振動している。ここで、f2aとf2bとは僅かに周波数が違うだけなので、以下、合成波に含まれている搬送波の周波数をf2aとする。
以上説明した第5の実施形態では、次の(M)のような効果がある。
(M) 位相を90度回転させる移相回路15の代わりに、信号を反転させて位相を180度回転させる反転移相回路15bを搭載しているので、移相回路15の位相回転量の調整が不要で、よって、無線送信機10dの無調整化に寄与するという効果を奏する。
図10は、第6の実施形態に係る遅延合成回路の概念を示す図である。
遅延合成回路40には、受信アンテナ31c-1,31c-2の出力側が回転周波数検出回路60-1,60-2を介して接続されている。遅延合成回路40の出力側は、デジタル復調回路47に接続されている。デジタル復調回路47の出力側は、ベースバンド回路48に接続されている。ベースバンド回路48の出力側は、この無線受信機30eの出力である。
加算器44-iは、反射移相変移遅延器42-iの出力信号と、遅延器43-iの出力信号とを加算する機能を有している。
図11は、第6の実施形態に係る遅延合成回路を示す概略の構成図である。
遅延合成回路40aには、図10の遅延合成回路40と同様に、受信アンテナ31c-1,31c-2の出力側が回転周波数検出回路60-1,60-2を介して接続されている。遅延合成回路40の出力側は、デジタル復調回路47に接続されている。デジタル復調回路47の出力側は、ベースバンド回路48に接続されている。遅延合成回路40aには更に、デジタル復調回路47からの制御信号が接続されている。この制御信号により、電磁波の反射による偏波面の位相変移θ1~θnの補正と、電磁波の行路差による位相ずれφ1~φnの補正とを制御可能である。
受信アンテナ31c-1,31c-2に到来する電磁波は、回転周波数検出回路60-1,60-2によって、それぞれ(1/f3)周期の2つのデジタル信号に変換される。
更に、これに限定されず、遅延量Tを、((1/f3)÷n)周期の整数倍、1/2倍、3/2倍など、任意の値に設定しても良い。
以上説明した第6の実施形態では、次の(N)のような効果がある。
(N) トレーニング期間において、反射による偏波面の位相変移θ1~θnの補正量と、行路差による位相ずれφ1~φnの補正量とを最適化しているので、設置環境が変化し、無線送信機10から無線受信機30fに到達する電磁波の行路が動的に変化する場合でも、電波干渉による通信誤りを更に回避することが可能である。
図13は、第7の実施形態に係る遅延合成回路を示す概略の構成図である。第6の実施形態を示す図11中の要素と共通の要素には共通の符号が付されている。
本実施例における無線受信機30gは、第6の実施形態に示す無線受信機30fが有するデジタル復調回路47aとは異なるデジタル復調回路47と、第6の実施形態に示す無線受信機30fが有するベースバンド回路48とは異なるベースバンド回路48aとを有している他は、第6の実施形態に示す無線受信機30fと同様の構成を有している。
図12を元に、第7の実施形態に係る無線受信機30gの動作を説明する。
無線送信機10は、トレーニング期間であるタイミングT1において、トレーニング信号を送信する。伝送路には、このトレーニング信号が送信される。無線受信機30gのベースバンド回路48aは、タイミングR1において、このトレーニング信号を受信し、合成した受信信号の復調後の誤り率が最小となるよう、電磁波の反射による偏波面の位相変移θ1~θnの補正量と、電磁波の行路差による位相ずれφ1~φnの補正量とを最適化する。
以上説明した第7の実施形態では、次の(O)のような効果がある。
(O) トレーニング期間において電磁波の反射による偏波面の位相変移θ1~θnの補正量と、電磁波の行路差による位相ずれφ1~φnの補正量とを最適化しているので、設置環境が変化し、無線送信機10から無線受信機30fに到達する電磁波の行路が動的に変化する場合でも、電波干渉による復調後の誤り率を最小にすることが可能である。
図14は、第8の実施形態に係る昇降機システムを示す概略の構成図である。
この昇降機システム100は、縦長の直方体である建物101と、昇降カゴ111とを有している。建物101の内部には、昇降カゴ111が昇降する空間が設けられている。昇降カゴ111は図示しないロープと駆動機構によって、建物101の内部空間を昇降する。
端末局無線機112から送信された電波は、アンテナ113-1とアンテナ113-2を介して送信される。送信された電波は、建物101の内部空間を無線伝送媒体とするので、建物101の内壁および昇降カゴ111の外壁により多重反射を受ける。すなわち、建物101の内部空間は、多重波干渉環境を形成する。多重反射を受けた電波は、それぞれアンテナ103-1,103-2に到達する。
あわせて、昇降カゴ111の軽量化も可能となる。昇降カゴ111に接続されるケーブル等の有線接続手段の重さは、高層ビルにおいて、無視し得ない重さとなる為である。
以上説明した第8の実施形態では、次の(P)のような効果がある。
(P) 建物101から無線接続手段によって昇降カゴ111の制御/監視が可能となるので、ケーブル等の有線接続手段によって昇降カゴ111が昇降する空間を無駄にすることがなくなる。よって、小さい建物101の体積とするか、または、同一の建物101の体積で昇降カゴ111の寸法を増大させて輸送能力を向上させることが可能である。
図15は、第9の実施形態に係る変電設備監視システムを示す概略の構成図である。
本実施形態の変電設備監視システム200は、複数の変電機201-1~201-12と、これらの近傍に設定されている複数の無線基地局211-1~211-4とを備えている。本実施形態では、変電機201-1~201-12の数は無線基地局211-1~211-4の数より多い。
本実施形態の変電設備監視システム200において、電磁波は、複数の変電機201-1~201-12により多重反射を受ける。変電設備監視システム200には、多重波干渉環境が形成される。
以上説明した第9の実施形態では、次の(Q)のような効果がある。
(Q) 本実施形態の偏波角度分割ダイバシチ無線機により、多重波干渉環境下でも高品質の無線伝送が実現可能となる。変電機201-1~201-12の制御・監視を複数の無線基地局211-1~211-4により遠隔で実施可能である。よって、ケーブル等の該有線接続手段を用いる場合に問題となる高圧誘導電力の問題を解決できると共に、ケーブルの敷設コストを削除でき、変電機201-1~201-12の制御/監視システムの安全性向上、および、コスト削減が可能となる。
本発明は、上記実施形態に限定されることなく、本発明の趣旨を逸脱しない範囲で、変更実施が可能である。この利用形態や変形例としては、例えば、次の(a)~(b)のようなものがある。
11 情報生成回路
12,12-1,12-2 発振器
13,13-1 変調器(第1の変調手段)
13-2 変調器(第4の変調手段)
14 モータ(回転手段)
15 移相回路(移相手段)
15b 反転移相回路
16 発振器
17 ベースバンド回路
18-1 変調器(第2の変調手段)
18-2 変調器(第3の変調手段)
19-1 加算器(第1の合成手段)
19-2 加算器(第2の合成手段)
20 送信アンテナ(電磁波発信手段)
20b-1,20c-1 送信アンテナ(第1の送信アンテナ)
20b-2,20c-2 送信アンテナ(第2の送信アンテナ)
30,30a,30b,30c,30d,30e 無線受信機
31 ダイバシチ受信アンテナ
31b-1,31c-1 受信アンテナ(第1の受信アンテナ)
31b-2,31c-2 受信アンテナ(第2の受信アンテナ)
32-1~32-6 行路差位相変移器(複数の信号補正手段)
33 合成器(合成手段)
34-1~34-6 遅延器
35-1~35-6 遅延器
37 時分割スイッチ
37a 入力側スイッチ
37b 出力側スイッチ
40,40a 遅延合成回路(遅延合成手段)
42(=42-1~42-n) 反射移相変移遅延器
43(=43-1~43-n),43a(=43a-1~43a-n) 遅延器
44-1~44-n 加算器
45(=45-1~45-n) 行路差位相変移遅延器
46 合成器
47,47a デジタル復調回路
48,48a ベースバンド回路
49(=49-1~49-n) 反射移相変移器
49a(=49a-1~49a-n) 行路差位相変移器
50(=50-1~50-n) 遅延器
60-1 回転周波数検出回路(第1の回転周波数検出手段)
60-2 回転周波数検出回路(第2の回転周波数検出手段)
61 整流回路
62 ローパスフィルタ
63 A/Dコンバータ
Claims (20)
- 第1の周波数の情報信号を第2の周波数で変調し、第1の変調信号を出力する第1の変調手段と、
前記第1の変調信号を独立した2つの偏波で送信すると共に、この偏波に第3の周波数を重畳する電磁波発信手段と、
を備えることを特徴とする偏波角度分割ダイバシチ無線送信機。 - 請求の範囲第1項に記載の電磁波発信手段は、
前記第1の変調信号を直線偏波で送信する送信アンテナと、
前記送信アンテナを前記第3の周波数で機械的に回転させ、前記直線偏波の角度を前記第3の周波数で回転させる回転手段と、
を有すること特徴とする偏波角度分割ダイバシチ無線送信機。 - 請求の範囲第1項に記載の電磁波発信手段は、
前記第1の変調信号を、前記第3の周波数で変調して第1の出力信号を得る第2の変調手段と、
前記第1の出力信号を、第1の偏波で送信する第1の送信アンテナと、
前記第3の周波数の位相を、所定角度だけシフトする移相手段と、
前記第1の変調信号を、前記シフトした第3の周波数で変調して第2の出力信号を得る第3の変調手段と、
前記第2の出力信号を第2の偏波で送信する第2の送信アンテナと、
を有することを特徴とする偏波角度分割ダイバシチ無線送信機。 - 前記第1の送信アンテナは、直線偏波を送信するアンテナであり、
前記第2の送信アンテナは、前記第1の送信アンテナと85度から95度の間の角度をなして設置され、直線偏波を送信するアンテナである
ことを特徴とする請求の範囲第3項に記載の偏波角度分割ダイバシチ無線送信機。 - 前記第1の送信アンテナは、円偏波を送信するアンテナであり、
前記第2の送信アンテナは、前記第1の送信アンテナと反対方向に回転する円偏波を送信するアンテナである
ことを特徴とする請求の範囲第3項に記載の偏波角度分割ダイバシチ無線送信機。 - 前記第1の周波数は前記第2の周波数および前記第3の周波数よりも低く設定され、前記第2の周波数は前記第3の周波数よりも高く設定されていることを特徴とする請求の範囲第1項ないし請求の範囲第5項のいずれか1項に記載の偏波角度分割ダイバシチ無線送信機。
- 第1の周波数の情報信号を第2の周波数で変調し、第1の変調信号を出力する第1の変調手段と、
前記情報信号を、前記第2の周波数と僅かに異なる第4の周波数で変調し、第4の変調信号を出力する第4の変調手段と、
前記第1の変調信号と前記第4の変調信号とを合成して、前記第2の周波数と前記第4の周波数の差によって生じた第3の周波数で更に変調した第1の出力信号を出力する第1の合成手段と、
前記第1の変調信号と前記第4の変調信号の反転信号とを合成して、前記第2の周波数と前記第4の周波数の反転信号との差によって生じた前記第3の周波数で更に変調した第2の出力信号を出力する第2の合成手段と、
前記第1の出力信号を、第1の偏波で送信する第1の送信アンテナと、
前記第2の出力信号を、第2の偏波で送信する第2の送信アンテナと、
を有することを特徴とする偏波角度分割ダイバシチ無線送信機。 - 前記第1の送信アンテナは、直線偏波を送信するアンテナであり、
前記第2の送信アンテナは、前記第1の送信アンテナと85度から95度の間を成して設置され、直線偏波を送信するアンテナである
ことを特徴とする請求の範囲第7項に記載の偏波角度分割ダイバシチ無線送信機。 - 前記第1の送信アンテナは、円偏波を送信するアンテナであり、
前記第2の送信アンテナは、前記第1の送信アンテナとは反対方向に回転する円偏波を送信する
ことを特徴とする請求の範囲第7項に記載の偏波角度分割ダイバシチ無線送信機。 - 前記第1の周波数は前記第2の周波数、前記第4の周波数、前記第3の周波数のいずれよりも低く、前記第2の周波数と前記第4の周波数は、前記第3の周波数よりも高いことを特徴とする請求の範囲第7項ないし請求の範囲第9項のいずれか1項に記載の偏波角度分割ダイバシチ無線送信機。
- 請求の範囲第1項に記載の偏波角度分割ダイバシチ無線送信機が発信する電磁波を受信する偏波角度分割ダイバシチ無線受信機であって、
この偏波角度分割ダイバシチ無線送信機が発信する電磁波を、複数の偏波面でそれぞれ受信して複数の入力信号を得る複数のアンテナと、
前記入力信号ごとに行路差による位相を補正し、それぞれ受信信号を生成する複数の信号補正手段と、
複数の前記受信信号を合成する合成手段と、
を備えることを特徴とする偏波角度分割ダイバシチ無線受信機。 - 請求の範囲第3項に記載の偏波角度分割ダイバシチ無線送信機が発信する電磁波を受信する偏波角度分割ダイバシチ無線受信機であって、
この偏波角度分割ダイバシチ無線送信機が発信する前記第1の偏波を受信して第1の入力信号を得る第1の受信アンテナと、
この偏波角度分割ダイバシチ無線送信機が発信する前記第2の偏波を受信して第2の入力信号を得る第2の受信アンテナと、
前記第1の入力信号を、前記第3の周波数より2倍以上高い周波数を遮断して第1の受信信号を生成する第1の回転周波数検出手段と、
前記第2の入力信号を、前記第3の周波数より2倍以上高い周波数を遮断して第2の受信信号を生成する第2の回転周波数検出手段と、
前記第1の受信信号と前記第2の受信信号を遅延して合成する遅延合成手段と
を備えたことを特徴とする偏波角度分割ダイバシチ無線受信機。 - 前記第1の受信アンテナは、直線偏波を受信するアンテナであり、
前記第2の受信アンテナは、前記第1の受信アンテナと85度から95度の間を成して設置され、直線偏波を受信するアンテナである
ことを特徴とする請求の範囲第12項に記載の偏波角度分割ダイバシチ無線送信機。 - 請求の範囲第7項に記載の偏波角度分割ダイバシチ無線送信機が発信する電磁波を受信する偏波角度分割ダイバシチ無線受信機であって、
この偏波角度分割ダイバシチ無線送信機が発信する前記第1の偏波を受信して第1の入力信号を得る第1の受信アンテナと、
この偏波角度分割ダイバシチ無線送信機が発信する前記第2の偏波を受信して第2の入力信号を得る第2の受信アンテナと、
前記第1の入力信号を、前記第3の周波数より2倍以上高い周波数を遮断して第1の受信信号を生成する第1の回転周波数検出手段と、
前記第2の入力信号を、前記第3の周波数より2倍以上高い周波数を遮断して第2の受信信号を生成する第2の回転周波数検出手段と、
前記第1の受信信号と前記第2の受信信号を遅延して合成する遅延合成手段と
を備えたことを特徴とする偏波角度分割ダイバシチ無線受信機。 - 前記第1の受信アンテナは、円偏波を受信するアンテナであり、
前記第2の受信アンテナは、前記第1の受信アンテナと反対方向に回転する円偏波を受信するアンテナである
ことを特徴とする請求の範囲第14項に記載の偏波角度分割ダイバシチ無線送信機。 - 請求の範囲第12項または請求の範囲第14項に記載の前記遅延合成手段は、
所定の遅延時間ごとに、前記第1の受信信号と前記第2の受信信号の偏波位相回転を行って加算し、
前記加算した受信信号ごとに、行路差にもとづく行路差位相補正を行い、
前記補正した受信信号を合成する
ことを特徴とする偏波角度分割ダイバシチ無線受信機。 - 前記合成した受信信号の強度が最大となるよう、前記偏波位相回転および前記行路差位相補正を決定することを特徴とする請求の範囲第16項に記載の偏波角度分割ダイバシチ無線受信機。
- 前記合成した受信信号の復調後の誤り率が最小となるよう、前記偏波位相回転および前記行路差位相補正を決定することを特徴とする請求の範囲第16項に記載の偏波角度分割ダイバシチ無線受信機。
- 請求の範囲第3項または請求の範囲第7項に記載の偏波角度分割ダイバシチ無線送信機と、
請求の範囲第16項に記載の偏波角度分割ダイバシチ無線受信機と、
を具備する偏波角度分割ダイバシチ無線通信システムであって、
この偏波角度分割ダイバシチ無線送信機は、情報を送受信する前に、あらかじめ定められた既知の情報を送信する所定のトレーニング動作を行い、
この偏波角度分割ダイバシチ無線受信機は、前記所定のトレーニング動作において、前記合成した受信信号の強度が最大となるよう、前記偏波位相回転および前記行路差位相補正を決定する
ことを特徴とする偏波角度分割ダイバシチ無線通信システム。 - 請求の範囲第3項または請求の範囲第7項に記載の偏波角度分割ダイバシチ無線送信機と、
請求の範囲第16項に記載の偏波角度分割ダイバシチ無線受信機と、
を具備する偏波角度分割ダイバシチ無線通信システムであって、
この偏波角度分割ダイバシチ無線送信機は、情報を送受信する前に、あらかじめ定められた既知の情報を送信する所定のトレーニング動作を行い、
この偏波角度分割ダイバシチ無線受信機は、前記所定のトレーニング動作において、前記合成した受信信号の復調後の誤り率が最小となるよう、前記偏波位相回転および前記行路差位相補正を決定する
ことを特徴とする偏波角度分割ダイバシチ無線通信システム。
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JP5890917B2 (ja) * | 2013-01-30 | 2016-03-22 | 株式会社日立製作所 | 回転体、固定体間の電波を用いた通信装置 |
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JP2015043550A (ja) * | 2013-08-26 | 2015-03-05 | 日本電信電話株式会社 | 無線通信システム及びアンテナ装置 |
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JP2017046117A (ja) * | 2015-08-25 | 2017-03-02 | 株式会社日立製作所 | 無線通信システム |
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Also Published As
Publication number | Publication date |
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US9407349B2 (en) | 2016-08-02 |
US20130336417A1 (en) | 2013-12-19 |
US20160226571A1 (en) | 2016-08-04 |
JPWO2012120657A1 (ja) | 2014-07-07 |
JP5632530B2 (ja) | 2014-11-26 |
US9722687B2 (en) | 2017-08-01 |
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