WO2012098873A1 - 電力変換装置 - Google Patents
電力変換装置 Download PDFInfo
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- WO2012098873A1 WO2012098873A1 PCT/JP2012/000273 JP2012000273W WO2012098873A1 WO 2012098873 A1 WO2012098873 A1 WO 2012098873A1 JP 2012000273 W JP2012000273 W JP 2012000273W WO 2012098873 A1 WO2012098873 A1 WO 2012098873A1
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- motor
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
- H02P6/00—Arrangements for controlling synchronous motors or other dynamo-electric motors using electronic commutation dependent on the rotor position; Electronic commutators therefor
- H02P6/10—Arrangements for controlling torque ripple, e.g. providing reduced torque ripple
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/08—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/12—Arrangements for reducing harmonics from ac input or output
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
- H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
- H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
- H02P21/00—Arrangements or methods for the control of electric machines by vector control, e.g. by control of field orientation
- H02P21/05—Arrangements or methods for the control of electric machines by vector control, e.g. by control of field orientation specially adapted for damping motor oscillations, e.g. for reducing hunting
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
- H02P27/00—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage
- H02P27/04—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
- H02P1/00—Arrangements for starting electric motors or dynamo-electric converters
- H02P1/16—Arrangements for starting electric motors or dynamo-electric converters for starting dynamo-electric motors or dynamo-electric converters
Definitions
- the present invention relates to a power conversion device that switches input power and converts it into predetermined power.
- a capacitor having a relatively small capacity is provided in the DC link unit to generate ripples in the DC link voltage, and in synchronization with the DC link voltage.
- the current of the motor connected as a load is reduced to near zero to generate a large current pulsation. Therefore, in the above example, the effective value of the motor current may increase and the motor efficiency may decrease.
- the present invention has been made paying attention to the above-mentioned problems, and aims to improve the efficiency of a motor connected as a load while improving the power factor in a power conversion device.
- the first invention is: A converter circuit (2) for full-wave rectification of the power supply voltage (v in ) of the AC power supply (6); A DC link section (3) having a capacitor (3a) connected in parallel to the output of the converter circuit (2) and outputting a pulsating DC voltage (v dc ); An inverter circuit (4) for switching the output of the DC link part (3) to convert to AC and supplying the connected motor (7); A controller (5) for controlling the switching so that the current (iu, iv, iw) of the motor (7) pulsates in synchronization with the pulsation of the power supply voltage (v in ), The controller (5) controls the switching to reduce the pulsation amplitude of the current (iu, iv, iw) according to the load of the motor (7) or the operating state of the motor (7). It is characterized by.
- the capacity of the capacitor (3a) is set so that the DC link voltage (v dc ) pulsates more, so the current conduction width of the converter circuit (2) becomes wider and the power factor is improved. Is possible. Moreover, since the switching in the inverter circuit (4) is controlled so that the current (iu, iv, iw) of the motor (7) pulsates in synchronization with the pulsation of the power supply voltage (v in ), the AC power supply The harmonics of the input current (i in ) input from (6) to the power converter (1) are reduced.
- the pulsation amplitude of the current (iu, iv, iw) is reduced according to the load by the motor (7) connected to the inverter circuit (4) or the operating state of the motor (7).
- the effective value of the current (iu, iv, iw) flowing through 7) is reduced.
- the second invention In the power converter of the first invention, wherein the control unit (5), the current of the motor (7) (iu, iv, iw), and wherein the power, speed (omega m), and according to at least one of torque, of reducing the pulsation amplitude To do.
- the magnitude of the load of the inverter circuit (4) by the motor (7) can be reduced. It can be detected. Therefore, in this configuration, the pulsation amplitude of the current (iu, iv, iw) is controlled by any one of these detection values or a combination of these detection values.
- the phase angle ( ⁇ in ) of the input AC, the current (iu, iv, iw), the speed ( ⁇ m ), and the torque of the motor (7) may be conventionally provided with a detection mechanism in the power converter. Many can be easily detected.
- the control unit (5) reduces the pulsation amplitude while controlling the switching so that the DC voltage (v dc ) is greater than zero.
- control unit (5) controls the switching so that the DC link voltage (v dc ) is greater than zero. Therefore, when the so-called shunt method is adopted as the current detection means of the motor (7), the switching state of the inverter circuit (4) can be reliably detected.
- the fourth invention is In the power converter of the first invention, The control unit (5) reduces the pulsation amplitude when the motor (7) is started.
- the controller (5) is characterized by gradually increasing the pulsation amplitude after the motor (7) is started.
- the control unit (5) controls the command value (i d * , i q * ) of the current (iu, iv, iw) and the actual current by at least one of proportional control, integral control, and differential control.
- a current controller (56) for controlling the deviation from the values (i d , i q ) to be small is provided, and the control gain of the control is changed when the pulsation amplitude is reduced.
- the pulsation amplitude of the current (iu, iv, iw) of the motor (7) is controlled by at least one of proportional control, integral control, and differential control.
- the effective value of the current flowing through the motor (7) is reduced, so that the efficiency of the motor (7) is improved. Is possible. That is, according to the present invention, both power factor improvement and efficiency improvement of the motor (7) can be achieved.
- the load applied to the inverter circuit (4) can be easily detected, so that the pulsation amplitude can be easily controlled.
- the switching state of the inverter circuit (4) can be reliably detected, so that the current value of the motor (7) Can be reliably controlled.
- the torque of the motor (7) at the time of starting can be controlled to be constant, so that the motor (7) can be stably controlled.
- the harmonics of the input current (i in ) input from the AC power source (6) to the power converter (1) are reduced, the power after the motor (7) is started is reduced.
- the rate can be improved.
- the pulsation amplitude of the motor current (iu, iv, iw) is generally controlled by the current controller (56) provided in the inverter circuit (4). Can be realized.
- FIG. 1 is a block diagram illustrating a configuration of a power conversion apparatus according to Embodiment 1 of the present invention.
- FIG. 3 is a diagram illustrating waveforms of the DC link voltage and the drive current command value when k is smaller than 1 in the formula (1) described later.
- FIG. 4 is a timing chart showing the relationship between the ripple amount and the load.
- FIG. 5 is a timing chart showing the relationship between the ripple amount and the control gain in the dq-axis current control unit when the motor is started.
- FIG. 1 is a block diagram showing a configuration of a power conversion device (1) according to Embodiment 1 of the present invention.
- the power converter (1) includes a converter circuit (2), a DC link unit (3), an inverter circuit (4), and a control unit (5), and a single-phase AC power source (6).
- the AC power supplied from is converted into power of a predetermined frequency and supplied to the motor (7).
- the motor (7) of this embodiment is a three-phase alternating current motor, and is for driving the compressor provided in the refrigerant circuit of the air conditioner.
- the converter circuit (2) is connected to the AC power supply (6), and full-wave rectifies the AC output from the AC power supply (6) into DC.
- the converter circuit (2) is a diode bridge circuit in which a plurality (four in the present embodiment) of diodes (D1 to D4) are connected in a bridge shape. These diodes (D1 to D4) perform full-wave rectification of the AC voltage of the AC power source (6) and convert it to a DC voltage.
- the DC link part (3) includes a capacitor (3a).
- the capacitor (3a) is connected in parallel to the output of the converter circuit (2), and the DC voltage (DC link voltage (v dc ) generated across the capacitor (3a) is connected to the input node of the inverter circuit (4) Has been.
- the capacitor (3a) is constituted by, for example, a film capacitor. This capacitor (3a) has a capacitance capable of smoothing only the ripple voltage (voltage fluctuation) generated corresponding to the switching frequency when the switching element (described later) of the inverter circuit (4) performs switching operation. ing.
- the capacitor (3a) is a small-capacitance capacitor that does not have a capacitance that smoothes the voltage rectified by the converter circuit (2) (voltage fluctuation caused by the power supply voltage). Therefore, the DC link voltage (v dc ) output from the DC link unit (3) has a large pulsation such that its maximum value is twice or more of its minimum value.
- the inverter circuit (4) has an input node connected in parallel to the capacitor (3a) of the DC link section (3), and switches the output of the DC link section (3) to convert it to three-phase AC, and is connected to the motor (7) to supply.
- the inverter circuit (4) of the present embodiment is configured by a plurality of switching elements being bridge-connected. Since this inverter circuit (4) outputs three-phase alternating current to the motor (7), it has six switching elements (Su, Sv, Sw, Sx, Sy, Sz).
- the inverter circuit (4) includes three switching legs formed by connecting two switching elements in series with each other, and in each switching leg, an upper arm switching element (Su, Sv, Sw) and a lower arm switching element.
- the midpoints of (Sx, Sy, Sz) are respectively connected to coils (not shown) of each phase of the motor (7).
- free-wheeling diodes Du, Dv, Dw, Dx, Dy, Dz
- the inverter circuit (4) switches the DC link voltage (v dc ) input from the DC link unit (3) by turning on and off these switching elements (Su, Sv, Sw, Sx, Sy, Sz). Then, it is converted into a three-phase AC voltage and supplied to the motor (7).
- the control unit (5) controls the on / off operation.
- the control unit (5) is configured so that the current flowing through the motor (7) (motor current (iu, iv, iw)) pulsates in synchronization with the pulsation of the power supply voltage (v in ). Controls switching (on / off operation).
- the control unit (5) includes a speed control calculation unit (50), a current command generation unit (51), a multiplier (52), a dq current command value generation unit (54), a coordinate conversion unit (55), A dq axis current control unit (56) and a PWM calculation unit (57) are provided.
- the speed control calculation unit (50) includes a subtracter (50a) and a PI calculation unit (50b).
- the subtracter (50a) obtains the difference between the rotation angle frequency ( ⁇ m ) of the mechanical angle of the motor (7) and the command value ( ⁇ m * ) of the mechanical angle.
- the PI calculation unit (50b) performs a proportional / integral calculation (PI calculation) on the calculation result of the subtractor (50a), and outputs the first current command value (i m * ) to the multiplier (52).
- the current command generator (51) receives a sine value (sin ( ⁇ in )) of the phase angle ( ⁇ in ) of the power supply voltage (v in ), and is expressed by the following equation (1) based on the input value.
- the modulation coefficient (ripple) to be obtained is obtained and output to the multiplier (52).
- Equation (1) k is a real number satisfying 0 ⁇ k ⁇ 1, and the current command generation unit (51) determines k according to the magnitude of the load by the motor (7), as will be described in detail later.
- the value (hereinafter also referred to as ripple amount) is changed.
- the current command generator (51) sets k to a constant value when the load is greater than or equal to a predetermined value, and reduces the value of k when the load is smaller than the predetermined value.
- the current command generator (51) checks the DC link voltage (v dc ) and continuously changes the set value of k, as will be described in detail later.
- the current command generator (51) controls the pulsation amplitude of the motor current (iu, iv, iw) according to the load.
- the magnitude of the load is based on the speed ( ⁇ m ), torque, motor current (iu, iv, iw) of the motor (7), at least one detected value of power, or a combination of these detected values. I can know.
- the multiplier (52) multiplies the first current command value (i m * ) output from the speed control calculation unit (50) and the modulation coefficient (ripple) output from the current command generation unit (51), (Drive current command value (i dq * )) is output to the dq current command value generation unit (54).
- the value of the drive current command value (i dq * ) can be expressed by the following equation (2).
- the dq current command value generation unit (54) calculates a d-axis current command value (i) based on the following equation (3) from the drive current command value (i dq * ) and a current phase command value ( ⁇ * ) described later. i d * ) and q-axis current command value (i q * ) are obtained and output to the dq-axis current control section (56).
- dq current command value generating portion (54) includes a negative sine value of the drive current command value predetermined value with respect to (i dq *) ( ⁇ * ) (-sin ⁇ *) and the cosine value (cos .beta *) To generate a d-axis current command value (i d * ) and a q-axis current command value (i q * ), respectively.
- ⁇ * is a command value of the phase ⁇ of the current flowing through the motor (7).
- the coordinate conversion unit (55) calculates the d-axis current (i) from the rotation angle (electrical angle ( ⁇ e )) of the rotor (not shown) of the motor (7) and the motor current (iu, iv, iw). d ) and q-axis current (i q ) are obtained. Specifically, the coordinate conversion unit (55) obtains a d-axis current (i d ) and a q-axis current (i q ) based on the following equation (4).
- the dq axis current controller (56) is an example of the current controller of the present invention.
- the dq axis current control unit (56) includes a PWM calculation unit (57) so that the deviation between the command value (i d * , i q * ) of the motor current (iu, iv, iw) and the actual current value becomes small.
- the inverter circuit (4) is controlled via
- the dq-axis current control unit (56) is provided with three controllers: a proportional controller, an integral controller, and a derivative controller. That is, the dq axis current control unit (56) performs PID control.
- the dq-axis current control unit (56) is configured such that the electrical angular speed ( ⁇ e ), the d-axis current (i d ), the q-axis current (i q ), and the d-axis current command, which are the speeds of the motor (7).
- the value (i d * ) and the q-axis current command value (i q * ) are input, and the d-axis voltage command value (v d * ) and the q-axis voltage command value (v q are based on the following equation (5). * ) Is output to the PWM calculation unit (57).
- Ld and Lq are d-axis and q-axis motor inductances, respectively, and ⁇ a is a motor counter electromotive voltage constant.
- R a is a motor winding resistance.
- s is a differential operator.
- K Pd , K Id , and K Dd are a proportional control gain, an integral control gain, and a differential control gain, respectively.
- the first and second terms on the right side are terms based on a general motor model, and the third term is a term based on PID control.
- the PWM calculation unit (57) receives the d-axis voltage command value (v d * ), the q-axis voltage command value (v q * ), the DC link voltage (v dc ), and the electrical angle ( ⁇ e ). Based on these values, a command value signal (Tu, Tv, Tw) for controlling the on / off operation of each switching element (Su, Sv, Sw, Sx, Sy, Sz) is generated. Specifically, the PWM calculation unit (57) first obtains phase voltage command values (v u * , v v * , v w * ) for each phase based on the following equation (6).
- the PWM calculation unit (57) calculates each phase voltage command value (v u * , v v * , v * ) and the DC link voltage (v dc ) using the following equation (7).
- the on-time ⁇ j of the switching element (Su, Sv, Sw) on the upper arm side of the phase is obtained.
- Tc is a carrier period.
- the PWM calculation unit (57) sets the on-time ⁇ j as the carrier cycle (Tc) when the calculation result according to the equation (7) exceeds the carrier cycle (Tc), and the calculation result is less than 0. Sets the on-time ⁇ j to zero.
- the PWM calculation unit (57) commands to turn on / off the switching elements (Su, Sv, Sw, Sx, Sy, Sz) of each phase according to the obtained on-time ⁇ j for each carrier cycle (Tc).
- the value signal (Tu, Tv, Tw) is output to the inverter circuit (4).
- the present embodiment is characterized by the control of the inverter circuit (4) at a light load such as when the motor (7) is operated at a low speed. Therefore, the operation of the power conversion device (1) at the time of light load will be described below.
- the drive current command value (i dq * ) decreases to near zero, and the motor current pulsates greatly.
- the effective value of the motor current may increase at a light load, and the motor efficiency may decrease.
- the capacitance of the capacitor (3a) of the DC link part (3) is used to switch the switching elements (Su, Sv, Sw, Sx, Sy, Sz) when the load is maximum. It is considered to be set so that the accompanying ripple can be smoothed.
- the DC link voltage (v dc ) does not decrease to zero near the zero cross of the voltage of the AC power source (6), and the capacitor (3a ) Is charged.
- the current of the motor (7) connected as a load is reduced to near zero, and a large current pulsation is generated. In this state, no torque was generated in the motor (7) near the zero cross.
- the capacitor (3a) is charged in the vicinity of the zero cross, it is considered that torque can be generated in the motor (7) using the charging voltage of the capacitor (3a). Specifically, the capacitor (3a) is discharged by reducing the pulsation (ripple) of the motor current (iu, iv, iw). As a result, the effective value of the motor current (iu, iv, iw) required to generate the torque can be reduced as compared with the conventional case.
- the current command generation unit (51) of the control unit (5) reduces the value of k in the equation (1) at the time of light load to be smaller than that at the time of high load, thereby modulating the modulation coefficient.
- the magnitude of the load is determined by at least one detected value of the speed ( ⁇ m ), torque, motor current (iu, iv, iw) of the motor (7), or a combination of these detected values. Can know based on.
- FIG. 4 is a timing chart showing the relationship between the ripple amount (k) and the load. As shown in FIG. 4, when the load starts to decrease from the predetermined value, the control unit (5) gradually decreases the value of k.
- the on-time of the upper arm side switching element (Su, Sv, Sw) of a predetermined phase becomes longer, the charge charged in the capacitor (3a) is discharged, and the motor current (iu, iv, iw) The pulsation amplitude is reduced.
- the pulsation amplitude is reduced and the effective value of the motor current (iu, iv, iw) is reduced, the copper loss of the motor (7) is improved and the motor efficiency is improved.
- the current command generator (51) continuously changes the set value of k while checking the voltage of the DC link voltage (v dc ) in the mode of reducing the value of k.
- the power source power factor may decrease or the harmonic component of the input current may increase, so it is necessary to set the value of k according to the operating conditions.
- the DC link voltage (v dc ) is greatly pulsated in the DC link unit (3), and the current conduction width in the converter circuit (2) is widened, thereby reducing the power factor. It becomes possible to improve. Further, when the load is light, the effective value of the current flowing through the motor (7) can be reduced, and the efficiency of the motor (7) can be improved.
- Embodiment 2 of the Invention a control example when the motor (7) is started will be described. Also in this embodiment, the circuit configuration itself of the power conversion device (1) is the same as that of the device of the first embodiment.
- the inverter circuit (4) is controlled so that the torque, that is, the motor current (iu, iv, iw) is constant when the motor (7) is started.
- FIG. 5 is a timing chart showing the relationship between the ripple amount (k) and the control gain in the dq-axis current controller (56) when the motor (7) is started.
- the dq-axis current control unit (56) includes, for example, at least one controller of proportional control, integral control, and differential control, and a command value (i d * , motor current (iu, iv, iw)).
- the controller is configured to perform control so that the deviation between i q * ) and the actual current value becomes small.
- the control gain of the dq-axis current control unit (56) is, for example, the control gain of the control when any one of the above-described controls is performed in the dq-axis current control unit (56). Further, in the dq-axis current control unit (56), when a plurality of types of control are performed in combination, it is a control gain in at least one of the controls.
- control gain is set to be relatively large by the dq-axis current control unit (56) during the start-up process (start-up process period).
- the activation process is a process for causing the motor (7) to reach the activation target rotational speed from the stopped state.
- the motor current (iu, iv, iw) can be prevented from pulsating during the start-up process period.
- the dq-axis current control unit (56) gradually decreases the control gain.
- the control unit (5) gradually increases the value k in accordance with the magnitude of the load after the start-up process is completed. As a result, the pulsation amplitude of the motor current (iu, iv, iw) gradually increases.
- the value of k (ripple amount) is controlled to 1.
- the motor current (iu, iv, iw) is controlled so as not to pulsate until the motor (7) is started and reaches a predetermined rotation speed. Therefore, in this embodiment, the torque of the motor (7) can be controlled to be constant at the time of startup, and the motor (7) can be stably controlled. In addition, it is possible to suppress a decrease in efficiency at startup. Further, since the pulsation amplitude of the motor current (iu, iv, iw) is gradually increased after the start-up process is completed, the power factor can be improved after the start-up process.
- the method of obtaining the modulation coefficient (ripple) (formula (1)) is an example.
- various calculation methods may be employed such as using the square value of the sine value instead of the absolute value of the sine value of the phase angle ( ⁇ in ).
- the modulation coefficient (ripple) may be set so that the pulsation amplitude of the motor current (iu, iv, iw) varies depending on the load or the operating state of the motor (7).
- the configuration of the dq axis current control unit (56) is an example.
- the dq-axis current control unit (56) is configured by any one of a proportional controller, an integral controller, and a derivative controller, or a combination of any of a proportional controller, an integral controller, and a derivative controller.
- the deviation between the command value (i d * , i q * ) of the motor current (iu, iv, iw) and the actual current value may be controlled.
- the present invention is useful as a power conversion device that switches input power to predetermined power by switching.
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Abstract
Description
交流電源(6)の電源電圧(vin)を全波整流するコンバータ回路(2)と、
前記コンバータ回路(2)の出力に並列接続されたコンデンサ(3a)を有し、脈動する直流電圧(vdc)を出力する直流リンク部(3)と、
前記直流リンク部(3)の出力をスイッチングして交流に変換し、接続されたモータ(7)に供給するインバータ回路(4)と、
前記モータ(7)の電流(iu,iv,iw)が、前記電源電圧(vin)の脈動に同期して脈動するように、前記スイッチングを制御する制御部(5)とを備え、
前記制御部(5)は、前記モータ(7)の負荷、又は前記モータ(7)の運転状態に応じ、前記スイッチングを制御して前記電流(iu,iv,iw)の脈動振幅を低減させることを特徴とする。
第1の発明の電力変換装置において、
前記制御部(5)は、前記モータ(7)の電流(iu,iv,iw)、電力、速度(ωm)、及びトルクの少なくとも1つに応じ、前記脈動振幅を低減させることを特徴とする。
第1又は第2の発明の電力変換装置において、
前記制御部(5)は、前記直流電圧(vdc)がゼロよりも大きくなるように前記スイッチングを制御しつつ、前記脈動振幅を低減することを特徴とする。
第1の発明の電力変換装置において、
前記制御部(5)は、前記モータ(7)の起動の際に、前記脈動振幅を低減させることを特徴とする。
第4の発明の電力変換装置において、
前記制御部(5)は、前記モータ(7)が起動した後に、前記脈動振幅を徐々に増加させることを特徴とする。
第1から第5の発明のうちの何れか1つの電力変換装置において、
前記制御部(5)は、比例制御、積分制御、及び微分制御のうちの少なくとも1つの制御によって、前記電流(iu,iv,iw)の指令値(id *,iq *)と実電流値(id,iq)との偏差が小さくなるように制御する電流制御器(56)を備え、前記脈動振幅を低減させる際に、前記制御の制御ゲインを変化させることを特徴とする。
《構成》
図1は、本発明の実施形態1に係る電力変換装置(1)の構成を示すブロック図である。同図に示すように電力変換装置(1)は、コンバータ回路(2)、直流リンク部(3)、インバータ回路(4)、及び制御部(5)を備え、単相の交流電源(6)から供給された交流の電力を所定の周波数の電力に変換して、モータ(7)に供給するようになっている。なお、本実施形態のモータ(7)は、三相交流モータであり、空気調和機の冷媒回路に設けられた圧縮機を駆動するためのものである。
コンバータ回路(2)は、交流電源(6)に接続され、交流電源(6)が出力した交流を直流に全波整流する。この例では、コンバータ回路(2)は、複数(本実施形態では4つ)のダイオード(D1~D4)がブリッジ状に結線されたダイオードブリッジ回路である。これらのダイオード(D1~D4)は、交流電源(6)の交流電圧を全波整流して、直流電圧に変換する。
直流リンク部(3)は、コンデンサ(3a)を備えている。コンデンサ(3a)は、コンバータ回路(2)の出力に並列接続され、該コンデンサ(3a)の両端に生じた直流電圧(直流リンク電圧(vdc))がインバータ回路(4)の入力ノードに接続されている。コンデンサ(3a)は、例えばフィルムコンデンサによって構成されている。このコンデンサ(3a)は、インバータ回路(4)のスイッチング素子(後述)がスイッチング動作する際に、スイッチング周波数に対応して生じるリプル電圧(電圧変動)のみを平滑化可能な静電容量を有している。すなわち、コンデンサ(3a)は、コンバータ回路(2)によって整流された電圧(電源電圧に起因する電圧変動)を平滑化するような静電容量を有さない小容量のコンデンサである。そのため、直流リンク部(3)が出力する直流リンク電圧(vdc)は、その最大値がその最小値の2倍以上となるような大きな脈動を有している。
インバータ回路(4)は、入力ノードが直流リンク部(3)のコンデンサ(3a)に並列に接続され、直流リンク部(3)の出力をスイッチングして三相交流に変換し、接続されたモータ(7)に供給するようになっている。本実施形態のインバータ回路(4)は、複数のスイッチング素子がブリッジ結線されて構成されている。このインバータ回路(4)は、三相交流をモータ(7)に出力するので、6個のスイッチング素子(Su,Sv,Sw,Sx,Sy,Sz)を備えている。詳しくは、インバータ回路(4)は、2つのスイッチング素子を互いに直列接続してなる3つのスイッチングレグを備え、各スイッチングレグにおいて上アームのスイッチング素子(Su,Sv,Sw)と下アームのスイッチング素子(Sx,Sy,Sz)との中点が、それぞれモータ(7)の各相のコイル(図示は省略)に接続されている。また、各スイッチング素子(Su,Sv,Sw,Sx,Sy,Sz)には、還流ダイオード(Du,Dv,Dw,Dx,Dy,Dz)が逆並列に接続されている。そして、インバータ回路(4)は、これらのスイッチング素子(Su,Sv,Sw,Sx,Sy,Sz)のオンオフ動作によって、直流リンク部(3)から入力された直流リンク電圧(vdc)をスイッチングして三相交流電圧に変換し、モータ(7)へ供給する。なお、このオンオフ動作の制御は、制御部(5)が行う。
制御部(5)は、モータ(7)に流れる電流(モータ電流(iu,iv,iw))が、電源電圧(vin)の脈動に同期して脈動するように、インバータ回路(4)におけるスイッチング(オンオフ動作)を制御する。この例では、制御部(5)は、速度制御演算部(50)、電流指令生成部(51)、乗算器(52)、dq電流指令値生成部(54)、座標変換部(55)、dq軸電流制御部(56)、及びPWM演算部(57)を備えている。
速度制御演算部(50)は、減算器(50a)とPI演算部(50b)とを備えている。この速度制御演算部(50)では、減算器(50a)で、モータ(7)の機械角の回転角周波数(ωm)と、機械角の指令値(ωm *)との差を求めるとともに、PI演算部(50b)で、減算器(50a)の演算結果に比例・積分演算(PI演算)を行って第1の電流指令値(im *)を乗算器(52)に出力する。
電流指令生成部(51)は、電源電圧(vin)の位相角(θin)の正弦値(sin(θin))が入力され、前記入力値に基づいて下記の式(1)で表される変調係数(ripple)を求めて乗算器(52)に出力するようになっている。
乗算器(52)は、速度制御演算部(50)が出力した第1の電流指令値(im *)と、電流指令生成部(51)が出力した変調係数(ripple)とを乗算し、(駆動電流指令値(idq *))をdq電流指令値生成部(54)に出力する。駆動電流指令値(idq *)の値は、次の式(2)で表すことができる。
dq電流指令値生成部(54)は、駆動電流指令値(idq *)と、後述の電流位相指令値(β*)とから、次の式(3)に基づいてd軸電流指令値(id *)とq軸電流指令値(iq *)を求めて、dq軸電流制御部(56)に出力するようになっている。詳しくは、dq電流指令値生成部(54)は、駆動電流指令値(idq *)に対して所定値(β*)の負の正弦値(-sinβ*)と余弦値(cosβ*)とを乗じて、それぞれd軸電流指令値(id *)とq軸電流指令値(iq *)とを生成する。ここで、β*は、モータ(7)に流す電流の位相βの指令値である。
座標変換部(55)は、モータ(7)の回転子(図示は省略)の回転角(電気角(θe))と、モータ電流(iu,iv,iw)とから、d軸電流(id)とq軸電流(iq)を求めるようになっている。具体的には、座標変換部(55)は、次の式(4)に基づいて、d軸電流(id)とq軸電流(iq)とを求める。
dq軸電流制御部(56)は、本発明の電流制御器の一例である。dq軸電流制御部(56)は、モータ電流(iu,iv,iw)の指令値(id *,iq *)と実電流値との偏差が小さくなるように、PWM演算部(57)を介して、インバータ回路(4)の制御を行う。本実施形態では、dq軸電流制御部(56)には、比例制御器、積分制御器、及び微分制御器の3つの制御器を設けてある。すなわち、dq軸電流制御部(56)ではPID制御を行う。詳しくは、dq軸電流制御部(56)は、モータ(7)の速度である電気角の角速度(ωe)、d軸電流(id)、q軸電流(iq)、d軸電流指令値(id *)、及びq軸電流指令値(iq *)が入力され、次の式(5)に基づいてd軸電圧指令値(vd *)及びq軸電圧指令値(vq *)をPWM演算部(57)に出力する。ただし、式(5)では、Ld,Lqはそれぞれd軸及びq軸のモータインダクタンスであり、φaはモータ逆起電圧定数である。Raは、モータ巻線抵抗である。sは、微分演算子である。また、KPd、KId、KDdは、それぞれ、比例制御ゲイン、積分制御ゲイン、微分制御ゲインである。式(5)では、右辺の1項と2項が一般的なモータモデルに基づく項であり、3項がPID制御による項である。
PWM演算部(57)は、d軸電圧指令値(vd *)、q軸電圧指令値(vq *)、直流リンク電圧(vdc)、及び前記電気角(θe)が入力されており、これらの値に基づいて、各スイッチング素子(Su,Sv,Sw,Sx,Sy,Sz)のオンオフ動作を制御する指令値信号(Tu,Tv,Tw)を生成する。具体的には、PWM演算部(57)は、まず、次の式(6)に基づいて各相の相電圧指令値(vu *,vv *,vw *)を求める。
本実施形態では、直流リンク部に小容量のコンデンサ(3a)を設けているため、直流リンク電圧(vdc)がより大きく脈動する。そして、直流リンク電圧(vdc)の脈動により、コンバータ回路(2)のダイオード(D1~D4)の電流導通幅が広くなり、その結果力率が改善する。また制御部(5)は、モータ電流(iu,iv,iw)が、電源電圧(vin)の脈動に同期して脈動するように、インバータ回路(4)におけるスイッチングを制御する。これにより、交流電源(6)から電力変換装置(1)に入力される入力電流(iin)の高調波が低減される。 本実施形態は、モータ(7)の低速運転時などの軽負荷時におけるインバータ回路(4)の制御に特徴がある。そこで、以下では、軽負荷時における電力変換装置(1)の動作を説明する。
以上のように、本実施形態によれば、直流リンク部(3)において直流リンク電圧(vdc)を大きく脈動させて、コンバータ回路(2)における電流導通幅を広くすることで、力率を改善することが可能になる。また、軽負荷時には、モータ(7)に流れる電流の実効値を低減し、該モータ(7)の効率の改善が可能になる。
実施形態2では、モータ(7)の起動時における制御例を説明する。本実施形態でも電力変換装置(1)の回路構成自体は実施形態1の装置と同じである。
以上のように本実施形態によれば、モータ(7)が起動されて所定の回転数になるまでは、モータ電流(iu,iv,iw)が脈動しないように制御される。それゆえ、本実施形態では、起動時にはモータ(7)のトルクを一定に制御でき、安定的にモータ(7)の制御を行うことが可能になる。また、起動時における効率の低下も抑制することが可能になる。また、起動処理の終了後は、モータ電流(iu,iv,iw)の脈動振幅を徐々に大きくするので、起動後は、力率を改善することが可能になる。
なお、変調係数(ripple)の求め方(式(1))は例示である。例えば、式(1)において、位相角(θin)の正弦値の絶対値の代わりに、当該正弦値の2乗の値を用いるなど、種々の算定方法を採用できる。要は、負荷又はモータ(7)の運転状態に応じて、モータ電流(iu,iv,iw)の脈動振幅が変化するように変調係数(ripple)を設定すればよいのである。
2 コンバータ回路
3 直流リンク部
3a コンデンサ
4 インバータ回路
5 制御部
7 モータ
56 dq軸電流制御部(電流制御器)
Claims (6)
- 交流電源(6)の電源電圧(vin)を全波整流するコンバータ回路(2)と、
前記コンバータ回路(2)の出力に並列接続されたコンデンサ(3a)を有し、脈動する直流電圧(vdc)を出力する直流リンク部(3)と、
前記直流リンク部(3)の出力をスイッチングして交流に変換し、接続されたモータ(7)に供給するインバータ回路(4)と、
前記モータ(7)の電流(iu,iv,iw)が、前記電源電圧(vin)の脈動に同期して脈動するように、前記スイッチングを制御する制御部(5)とを備え、
前記制御部(5)は、前記モータ(7)の負荷、又は前記モータ(7)の運転状態に応じ、前記スイッチングを制御して前記電流(iu,iv,iw)の脈動振幅を低減させることを特徴とする電力変換装置。 - 請求項1の電力変換装置において、
前記制御部(5)は、前記モータ(7)の電流(iu,iv,iw)、電力、速度(ωm)、及びトルクの少なくとも1つに応じ、前記脈動振幅を低減させることを特徴とする電力変換装置。 - 請求項1又は請求項2の電力変換装置において、
前記制御部(5)は、前記直流電圧(vdc)がゼロよりも大きくなるように前記スイッチングを制御しつつ、前記脈動振幅を低減することを特徴とする電力変換装置。 - 請求項1の電力変換装置において、
前記制御部(5)は、前記モータ(7)の起動の際に、前記脈動振幅を低減させることを特徴とする電力変換装置。 - 請求項4の電力変換装置において、
前記制御部(5)は、前記モータ(7)が起動した後に、前記脈動振幅を徐々に増加させることを特徴とする電力変換装置。 - 請求項1の電力変換装置において、
前記制御部(5)は、比例制御、積分制御、及び微分制御のうちの少なくとも1つの制御によって、前記電流(iu,iv,iw)の指令値(id *,iq *)と実電流値(id,iq)との偏差が小さくなるように制御する電流制御器(56)を備え、前記脈動振幅を低減させる際に、前記制御の制御ゲインを変化させることを特徴とする電力変換装置。
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Cited By (3)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
AU2013204711B2 (en) * | 2013-02-08 | 2015-09-03 | Regal Beloit America, Inc. | Systems and methods for controlling electric machines |
WO2015146197A1 (ja) * | 2014-03-27 | 2015-10-01 | ダイキン工業株式会社 | 電力変換装置 |
JP2016127649A (ja) * | 2014-12-26 | 2016-07-11 | ダイキン工業株式会社 | 電力変換装置 |
Families Citing this family (26)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
DE102012209369A1 (de) * | 2012-06-04 | 2013-12-05 | Siemens Aktiengesellschaft | Regeleinrichtung zur Beseitigung von Störungen im Netz |
EP2922190B1 (en) * | 2012-11-14 | 2020-02-19 | Posco Energy Co. Ltd. | Apparatus for compensating for ripple and offset of inverter, and method therefor |
US20150229203A1 (en) * | 2014-02-12 | 2015-08-13 | Gholamreza Esmaili | Smart Resistor-Less Pre-Charge Circuit For Power Converter |
JP6435956B2 (ja) * | 2014-03-27 | 2018-12-12 | ダイキン工業株式会社 | 電力変換装置 |
JP6291996B2 (ja) * | 2014-04-21 | 2018-03-14 | ダイキン工業株式会社 | 電力変換装置 |
WO2016051797A1 (ja) * | 2014-09-30 | 2016-04-07 | ダイキン工業株式会社 | 電力変換装置 |
KR101589623B1 (ko) | 2015-04-13 | 2016-01-28 | 정민금속 주식회사 | 용접에 의한 이음부가 형성되는 사각파이프 단부의 확관장치 |
JP6520336B2 (ja) * | 2015-04-15 | 2019-05-29 | 富士電機株式会社 | 電力変換装置の制御装置 |
US10814470B2 (en) | 2016-03-05 | 2020-10-27 | Koki Holdings Co., Ltd. | Electrically powered tool |
EP3217522A1 (de) * | 2016-03-08 | 2017-09-13 | Siemens Aktiengesellschaft | Rückspeisefähige gleichrichtervorrichtung |
US10656026B2 (en) | 2016-04-15 | 2020-05-19 | Emerson Climate Technologies, Inc. | Temperature sensing circuit for transmitting data across isolation barrier |
US9933842B2 (en) | 2016-04-15 | 2018-04-03 | Emerson Climate Technologies, Inc. | Microcontroller architecture for power factor correction converter |
US10305373B2 (en) | 2016-04-15 | 2019-05-28 | Emerson Climate Technologies, Inc. | Input reference signal generation systems and methods |
US10320322B2 (en) | 2016-04-15 | 2019-06-11 | Emerson Climate Technologies, Inc. | Switch actuation measurement circuit for voltage converter |
US10763740B2 (en) | 2016-04-15 | 2020-09-01 | Emerson Climate Technologies, Inc. | Switch off time control systems and methods |
US10277115B2 (en) | 2016-04-15 | 2019-04-30 | Emerson Climate Technologies, Inc. | Filtering systems and methods for voltage control |
US11387729B2 (en) | 2016-04-15 | 2022-07-12 | Emerson Climate Technologies, Inc. | Buck-converter-based drive circuits for driving motors of compressors and condenser fans |
KR101857367B1 (ko) | 2016-11-25 | 2018-05-11 | 엘지전자 주식회사 | 공기조화기의 전동기 제어장치 및 그 제어 방법 |
KR101888842B1 (ko) * | 2017-01-02 | 2018-08-16 | 엘지전자 주식회사 | 모터 제어 장치 및 모터 제어 장치의 제어 방법 |
DE102017126150A1 (de) | 2017-11-08 | 2019-05-09 | Ebm-Papst Mulfingen Gmbh & Co. Kg | Kapazitätsreduzierung |
JP7335403B2 (ja) * | 2018-03-08 | 2023-08-29 | ナブテスコ株式会社 | Ac-ac電力変換装置 |
JP7154019B2 (ja) * | 2018-03-08 | 2022-10-17 | ナブテスコ株式会社 | Ac-ac電力変換装置 |
CN109995305B (zh) * | 2019-04-26 | 2020-11-10 | 深圳和而泰智能控制股份有限公司 | 压缩机的力矩输入控制方法、装置、设备和冰箱 |
US20230336090A1 (en) * | 2020-10-26 | 2023-10-19 | Mitsubishi Electric Corporation | Power conversion apparatus, motor drive apparatus, and refrigeration cycle apparatus |
CN112910357B (zh) * | 2021-02-06 | 2023-04-11 | 广东希塔变频技术有限公司 | 用于电机驱动的控制方法、装置、电路和变频空调器 |
CN113922664B (zh) * | 2021-09-30 | 2024-04-16 | 南京理工大学 | 低频大脉动电流输出无脉动电流输入的功率变换装置 |
Citations (4)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
JP2002051589A (ja) | 2000-07-31 | 2002-02-15 | Isao Takahashi | モータ駆動用インバータの制御装置 |
JP2002223599A (ja) * | 2000-11-22 | 2002-08-09 | Isao Takahashi | インバータ制御方法およびその装置 |
JP2004343993A (ja) * | 2003-04-22 | 2004-12-02 | Matsushita Electric Ind Co Ltd | モータ制御装置、圧縮機、空気調和機、及び冷蔵庫 |
JP2005130666A (ja) | 2003-10-27 | 2005-05-19 | Daikin Ind Ltd | インバータ制御方法及び多相電流供給回路 |
Family Cites Families (22)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
SU1577060A1 (ru) * | 1988-03-10 | 1990-07-07 | Волжское объединение по производству легковых автомобилей "АвтоВАЗ" | Электропривод переменного тока |
US5625548A (en) * | 1994-08-10 | 1997-04-29 | American Superconductor Corporation | Control circuit for cryogenically-cooled power electronics employed in power conversion systems |
CA2184663A1 (en) * | 1996-09-03 | 1998-03-04 | John C. Salmon | Harmonic correction of 3-phase rectifiers and converters |
RU2193814C2 (ru) * | 1997-03-19 | 2002-11-27 | Хитачи Лтд. | Устройство и способ управления асинхронным электродвигателем |
CN100438320C (zh) * | 1997-10-31 | 2008-11-26 | 株式会社日立制作所 | 电源转换设备 |
US6614991B2 (en) * | 1999-03-17 | 2003-09-02 | Diehl Ako Stiftung & Co. Kg | Inverter-fed three-phase motor for household appliance, especially for the direct drive of washing machines |
JP3540665B2 (ja) | 1999-04-21 | 2004-07-07 | 財団法人鉄道総合技術研究所 | 交流電気車駆動装置 |
US6313602B1 (en) * | 1999-04-30 | 2001-11-06 | Texas Instruments Incorporated | Modified space vector pulse width modulation technique to reduce DC bus ripple effect in voltage source inverters |
JP3699663B2 (ja) | 2001-05-24 | 2005-09-28 | 勲 高橋 | インバータ制御方法およびその装置 |
JP4060777B2 (ja) | 2003-09-03 | 2008-03-12 | 株式会社東芝 | 電気車制御装置 |
JP2006101675A (ja) * | 2004-09-30 | 2006-04-13 | Mitsubishi Electric Corp | モータ駆動装置 |
US7746024B2 (en) * | 2006-03-07 | 2010-06-29 | Hamilton Sundstrand Corporation | Electric engine start system with active rectifier |
JP5114387B2 (ja) * | 2006-04-03 | 2013-01-09 | パナソニック株式会社 | インバータ装置および空気調和機 |
JP4079178B2 (ja) * | 2006-04-19 | 2008-04-23 | ダイキン工業株式会社 | 電力変換器及びその制御方法並びに空気調和機 |
WO2008004294A1 (fr) * | 2006-07-06 | 2008-01-10 | Mitsubishi Electric Corporation | Dispositif de commande de vecteur de moteur à induction, procédé de commande de vecteur de moteur à induction, et dispositif de commande d'entraînement de moteur à induction |
US7495410B2 (en) * | 2007-01-30 | 2009-02-24 | Rockwell Automation Technologies, Inc. | Systems and methods for improved motor drive power factor control |
KR100886194B1 (ko) * | 2007-06-08 | 2009-02-27 | 한국전기연구원 | 계통 연계형 고압 권선형 유도 발전기 제어 장치 |
US7683568B2 (en) * | 2007-09-28 | 2010-03-23 | Rockwell Automation Technologies, Inc. | Motor drive using flux adjustment to control power factor |
US7957166B2 (en) * | 2007-10-30 | 2011-06-07 | Johnson Controls Technology Company | Variable speed drive |
JP4735638B2 (ja) * | 2007-11-13 | 2011-07-27 | パナソニック株式会社 | モータ駆動装置 |
US8736220B2 (en) * | 2008-04-28 | 2014-05-27 | Daikin Industries, Ltd. | Inverter control device and power conversion device |
US8503200B2 (en) * | 2010-10-11 | 2013-08-06 | Solarbridge Technologies, Inc. | Quadrature-corrected feedforward control apparatus and method for DC-AC power conversion |
-
2011
- 2011-01-18 JP JP2011007818A patent/JP5212491B2/ja active Active
-
2012
- 2012-01-18 US US13/980,241 patent/US9214881B2/en active Active
- 2012-01-18 CN CN201280005508.XA patent/CN103314513B/zh active Active
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- 2012-01-18 KR KR1020137021621A patent/KR101594662B1/ko active IP Right Grant
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- 2012-01-18 ES ES12736369T patent/ES2894604T3/es active Active
- 2012-01-18 BR BR112013017911A patent/BR112013017911A2/pt not_active Application Discontinuation
Patent Citations (4)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
JP2002051589A (ja) | 2000-07-31 | 2002-02-15 | Isao Takahashi | モータ駆動用インバータの制御装置 |
JP2002223599A (ja) * | 2000-11-22 | 2002-08-09 | Isao Takahashi | インバータ制御方法およびその装置 |
JP2004343993A (ja) * | 2003-04-22 | 2004-12-02 | Matsushita Electric Ind Co Ltd | モータ制御装置、圧縮機、空気調和機、及び冷蔵庫 |
JP2005130666A (ja) | 2003-10-27 | 2005-05-19 | Daikin Ind Ltd | インバータ制御方法及び多相電流供給回路 |
Non-Patent Citations (2)
Title |
---|
HAGA; SAITO; TAKAHASHI: "CONTROL OF HIGH-POWER FACTOR ELECTROLYTIC CAPACITORLESS INVERTER OF SINGLE- PHASE DIODE RECTIFIER CIRCUIT", THE INSTITUTE OF ELECTRICAL ENGINEERS OF JAPAN, pages: 99 |
See also references of EP2667502A4 |
Cited By (6)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
AU2013204711B2 (en) * | 2013-02-08 | 2015-09-03 | Regal Beloit America, Inc. | Systems and methods for controlling electric machines |
US9331614B2 (en) | 2013-02-08 | 2016-05-03 | Regal Beloit America, Inc. | Systems and methods for controlling electric machines |
EP2765703A3 (en) * | 2013-02-08 | 2017-10-25 | Regal Beloit America, Inc. | System and methods for controlling electric machines |
WO2015146197A1 (ja) * | 2014-03-27 | 2015-10-01 | ダイキン工業株式会社 | 電力変換装置 |
JP2015195714A (ja) * | 2014-03-27 | 2015-11-05 | ダイキン工業株式会社 | 電力変換装置 |
JP2016127649A (ja) * | 2014-12-26 | 2016-07-11 | ダイキン工業株式会社 | 電力変換装置 |
Also Published As
Publication number | Publication date |
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JP2012151962A (ja) | 2012-08-09 |
KR20140002736A (ko) | 2014-01-08 |
EP2667502A4 (en) | 2017-08-09 |
US20130300327A1 (en) | 2013-11-14 |
CN103314513A (zh) | 2013-09-18 |
EP3979490A1 (en) | 2022-04-06 |
EP2667502B1 (en) | 2021-10-06 |
EP2667502A1 (en) | 2013-11-27 |
AU2012208179B2 (en) | 2015-02-12 |
BR112013017911A2 (pt) | 2016-10-11 |
US9214881B2 (en) | 2015-12-15 |
RU2013138457A (ru) | 2015-02-27 |
CN103314513B (zh) | 2015-09-30 |
AU2012208179A1 (en) | 2013-08-15 |
KR101594662B1 (ko) | 2016-02-16 |
JP5212491B2 (ja) | 2013-06-19 |
RU2543502C1 (ru) | 2015-03-10 |
ES2894604T3 (es) | 2022-02-15 |
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