TWI499175B - 切換電源電路、用於操作其之方法及積體電路 - Google Patents

切換電源電路、用於操作其之方法及積體電路 Download PDF

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TWI499175B
TWI499175B TW099118779A TW99118779A TWI499175B TW I499175 B TWI499175 B TW I499175B TW 099118779 A TW099118779 A TW 099118779A TW 99118779 A TW99118779 A TW 99118779A TW I499175 B TWI499175 B TW I499175B
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circuit
power supply
current
current sensing
switching
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TW201110515A (en
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John L Melanson
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Cirrus Logic Inc
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
    • H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
    • H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0003—Details of control, feedback or regulation circuits
    • H02M1/0006—Arrangements for supplying an adequate voltage to the control circuit of converters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0003—Details of control, feedback or regulation circuits
    • H02M1/0009—Devices or circuits for detecting current in a converter

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Dc-Dc Converters (AREA)

Description

切換電源電路、用於操作其之方法及積體電路
本發明大致係關於切換電源轉換器電路，且更具體言之係關於一種其中一輔助繞組電源供應及一電流感測電路接收來自相同電流感測變壓器次級繞組之輸入之切換電源轉換器。
需要切換電源轉換器在連續傳導模式(CCM)中的操作以獲得效率及降低轉換器中的峰值電流位準而獲得可靠性及組件成本的降低。在CCM操作中，穿過磁耦合元件之電流不改變極性且通常不完全降為零。由於不允許電流達到零，若在各切換循環結束時磁耦合元件中逐漸累積一越來越多的磁通量，則可能發生磁耦合元件的飽和，一種有時被稱作「磁通走漏」之現象。最終，磁耦合元件的磁芯將飽和，導致磁耦合元件表現為一短路，造成切換電路故障。因此，在CCM操作中，需要偵測穿過藉由磁性儲存元件及切換電路所形成之串聯電路峰值電流或另一參考電流位準。峰值電流值決定使電感器放電所需的關閉循環週期。在不連續傳導模式(DCM)中，總是存在零電流在磁耦合元件中流動之一週期，且因此磁耦合元件的磁芯在各循環總是重設為零。
為了感測穿過磁耦合元件之電流，可將一感測電阻器插入串聯切換電路中，或可提供一額外電流感測變壓器。電流感測變壓器方法通常比添加一電流感測電阻器之方法更為有效，因為變壓器及電流感測電路係經設計以在電源切換電路中產生最少干擾及損耗。一電流感測變壓器初級繞組通常包含僅一些線圈，因此跨初級繞組之電壓很小。電流感測變壓器之次級繞組通常產生一伏或更小之量級之一電壓，從而可忽視電流感測變壓器之磁化電流(亦稱作磁化電流)。因此，典型電流感測變壓器之次級電流實質上與初級電流成比例，使得跨一電阻器(其跨電流感測變壓器之次級繞組連接)所產生之一電壓係與初級電流線性相關且提供穿越轉換器之主要磁耦合元件之初級繞組之電流之一量測。
為了供應電力給一切換電源轉換器之控制電路，需要一低電壓電源供應。當可用或方便的僅有電壓為高電壓電源供應時，或當需要輔助電源供應之隔離時，通常使用切換轉換器之主要磁耦合元件上之一輔助繞組以供應電力給控制電路。然而，包含一輔助繞組增加磁耦合元件的成本。與上述電流感測變壓器中的次級繞組之特性相比，由於輔助電源供應通常必須提供10V之量級之一電壓且亦產生數十或數百毫安之量級之大電流。因此，一輔助繞組通常具有大磁化電流且跨典型輔助繞組之電壓不提供流動穿過切換電源轉換器之主要磁耦合元件之初級繞組之電流之一準確指示。
因此，需要在具有一電流感測變壓器之一切換電源轉換器中提供一輔助電源供應而無需切換電源轉換器之主要磁耦合元件上之一輔助繞組。
提供一輔助電源供應電路及一電流感測電路而無需一切換轉換器之主要磁耦合元件上之一感測電阻器或一輔助繞組之上述目的係提供在一切換轉換器及該切換轉換器之操作之一方法中。
該切換轉換器具有與一切換電路及一電流感測變壓器串聯耦合之一磁耦合元件。該電流感測變壓器次級繞組係提供至一輔助電源供應電路且亦提供輸入給一電流感測電路。為了在面對歸因於輔助電源供應充電所需的較高電壓之一顯著磁化電流的情況下提供電流感測功能性，針對該磁化電流校正穿過該輔助繞組之電流，在輔助電源供應之充電停用的同時執行電流感測，使電流感測變壓器之電感變大，或藉由對一電路節點預充電為一反向偏移而補償歸因於磁化電流之偏移。
從下文(更特定言之，如隨附圖式中所繪示之本發明之較佳實施例之描述)可瞭解本發明之上述及其他目的、特徵及優點。
本發明包含具有從一電流感測變壓器之一繞組操作之一輔助電源供應之切換電源轉換器。該電流感測變壓器係與該轉換器之切換電路及主要磁耦合元件串聯耦合。本發明亦包含用於從一電流感測變壓器提供電力給一切換電源轉換器內部之控制電路及/或其他電路之方法。
現參考圖1，顯示根據本發明之一實施例之一切換電源轉換器8。一切換控制器10提供控制藉由一電晶體N1而實施之一切換電路之一切換控制信號CS。當電晶體N1處於作用中時，藉由跨電感器L1強加輸入電壓VIN 導致穿過電感器L1之一電流IL 線性增加而對藉由電感器L1而實施之一磁耦合元件充電。當電晶體N1停止時，電荷被推動穿過電感器L1及二極體D1進入電容器C1，提高在輸出終端OUT的電壓。一電流感測變壓器T1係與電晶體N1及電感器L1串聯連接以提供指示穿過電感器L1之電流IL 之量值及極性而不引入顯著損耗之一信號，若使用一串聯電阻器產生此一信號則可能存在此損耗。
切換電源轉換器8係可依照從終端OUT提供之一回饋電壓控制提供給輸出終端OUT之電壓之一升壓式轉換器電路。或者，可完全藉由電流模式回饋而控制切換電源轉換器8。在所繪示之應用中，該升壓式轉換器電路係從交流(AC)電源線輸入電壓VIN 提供一高電壓DC輸出之一功率因數校正器(PFC)。切換控制器10操作電晶體N1以維持輸入電壓VIN 與輸入電流之間之零度之一相位關係。一電流感測電路14提供衍生自從電流感測變壓器T1之次級繞組sec所接收之一輸入電壓之電流IL 之量值之一指示。一輔助電源供應12供應一電壓VDDH 給切換控制器10，且通常與切換控制器10及電流感測電路14整合於相同積體電路(IC)中。輔助電源供應12之輸入亦連接至電流感測變壓器T1之次級繞組sec。與典型電流感測變壓器不同，電流感測變壓器T1具有一較高圈數比，從而可藉由輔助電源供應12產生足以操作一控制器IC中之控制電路(包含切換控制器10，其含有控制電晶體N1之切換所需之閘極驅動電路)之一電壓VDDH 。因此電壓VDDH 通常在10 VDC至15 VDC之範圍中。
現參考圖2，根據本發明之一實施例顯示可用於實施圖1之輔助電源供應12之一輔助電源供應電路12A之細節及可用於實施圖1之電流感測電路14之一電流感測電路14A之細節。輔助電源供應12A之輸入係連接至電流感測變壓器T1之次級繞組。一二極體D10提供僅當從次級繞組sec提供的電流為正方向(即當電感器L1被充電且電晶體N1傳導時)傳導之一半波整流器。一電阻器R10確保當電晶體N1停止且電感器L1放電時，電流感測變壓器T1之磁化在各循環結束時重設。電流感測電路14A包含與次級繞組sec串聯連接以提供與電流Isec 成比例之一電壓VR11 給具有藉由一對電阻器R12及R13決定之一增益之一放大器A1之一電阻器R11。放大器A1之輸出係提供給切換控制器10，其在數位實施方案中通常將使用一類比至數位轉換器(ADC)量測放大器A1之輸出。然而，在根據本發明之一切換控制電路之其他類比實施例中，可使用一峰值偵測器及/或比較器偵測電流Isec 達到一預定臨限之一時間，用於將合適的切換週期指示給切換控制器10以維持CCM操作並避免磁通走漏。提供一齊納(Zener)二極體Z1以確保輸出電壓VDDH 不超過一最大位準，但是在輔助電源供應電路12A中通常不啟動齊納二極體Z1。通常決定電流感測變壓器T1之圈數比，使得電壓VDDH 維持低於一最大電壓位準而無須啟動齊納二極體Z1，但在異常操作條件下除外。
電流Isec 係藉由電流感測電路14A量測以提供穿過圖1之電感器L1之電流IL 之量值之一指示。然而，電流感測變壓器T1之磁化在電流Isec 對電流IL 之直接比例性中產生一誤差，其連同用以減少或校正誤差之根據本發明之各種實施例所提供之解決方案將在下文中詳細解釋。如上所述，在輔助電源供應12A中，與普通電流變壓器相比，變壓器T1具有一更高的次級對初級圈數比，使得操作切換控制器10所需的更高電壓在輔助電源供應12A之輸出產生為輸出電壓VDDH 。由於跨次級繞組sec產生之電壓VSEC 與電晶體N1處於作用中之週期之持續時間之乘積決定變壓器在切換循環之作用部分結束時的磁化。磁化導致使穿過次級繞組sec之電流Isec 之值減少至低於如從變壓器T1之圈數比所計算之一理想電流位準之值之一誤差。
上述誤差亦減少次級繞組sec提供給放大器A1的電流Isec 之指示之量值，因為穿過電阻器R11之電流將小於從變壓器T1之圈數比計算之一預期電流。電流的減少係歸因於變壓器T1之磁化電流，其係跨次級繞組sec之電壓乘以變壓器T1之相互電感(有時稱作磁化電感係數)之積分。由於電壓VSEC 在切換週期內係實質上恆定，積分減少至相互電感、電壓及脈衝持續時間之乘積：
其中Isec 為次級電流，Nsec /Npri 為次級對初級圈數比，IL 為初級繞組電流(即量測下的切換電流)且Imag 為磁化電流。磁化電流Imag 可由d*Vsec /LM 模擬，其中d為電晶體N1導通之時間週期，Vsec 為在次級繞組sec所產生之電壓，且LM 為變壓器T1之相互電感。在普通的電流感測變壓器電路中，d*Vsec /LM 之項可忽略，因為Vsec 歸因於較小的次級對初級圈數比而較小。在本發明之電流感測變壓器電路中，誤差一般無法忽略，除非藉由增加圈數及提供一足夠大小之磁芯而使相互電感變大，其需要更大空間且添加成本。替代例係提供消除誤差的技術，將其等之一者提供在輔助電源供應電路12A中。
輔助電源供應電路12A包含提供用於控制電晶體N10及P10之輸出信號之一控制電路16。當電流感測電路14A量測跨電阻器R11之電壓以產生提供至切換控制器10之電感器L1中電流IL 之指示時，電晶體N10被啟動。邏輯AND閘AND1控制電晶體N10之閘極使得當切換控制器處於CCM模式且信號ccm確證時且切換控制器10所產生之感測信號處於作用中時，電晶體N10接通。一般而言，在DCM操作期間亦可啟動電晶體N10，且未要求感測及充電操作之任何選擇取決於切換控制器10係操作於CCM模式或DCM模式。當啟動時，電晶體N10實質上將跨次級繞組sec之電壓降低至接近零，因為跨次級繞組sec將僅存在跨二極體D10之正向電壓降、跨電阻器R11所產生之電壓及電晶體N10之汲極源極電壓之總電壓。電阻器R11可選擇為一低電阻以減少其電壓降，且通常需要這樣做，因為在所描繪的電路中，電阻器R11降低提供用於對電容器C2充電之電壓且因此降低輸出電壓VDDH 之最大可能值。
在藉由從切換控制器10提供之信號sense決定之一時間週期後停止電晶體N10。信號sense可具有從切換控制器10之切換週期決定之一固定時序，或可依照如切換控制器10內之電路回應於從電流感測電路14A提供之信號所決定之電流量測已完成(例如，當電流IL 已達到一些臨限值時)之一決定而控制。在信號sense解確證後，允許輔助電源供應12A從次級繞組sec對電容器C2充電以提供輸出電壓VDDH 。電晶體P10係經啟動以允許根據藉由邏輯NAND閘NAND1所產生之一charge信號而對電容器C2充電。邏輯NAND閘NAND1組合從一反相器I1提供之來自邏輯AND閘AND1之輸出信號之一反相版本與一比較器K1(其僅當輸出電壓VDDH 低於一臨限電壓VTH 時啟動)之輸出，藉此藉由一比較器K1之動作而提供輸出電壓VDDH 之調節。只要當切換電晶體N1處於作用中且當信號sense不作用時，在切換轉換器8之工作循環之一些部分內，輸出電壓VDDH 處於或高於臨限電壓VTH ，將在該工作循環中對電容器C2充電。若控制器10及連接至VDDH 之其他電路之負載足夠且電容器C2相對較小，則電容器C2之充電一般將在各工作循環之全部或較遲部分期間發生。電阻器R11將具有指示在輔助電源供應12A開始對電容器C2充電前之工作循環之感測部分結束時電感器L1中之電流IL 之一電壓。可藉由切換控制器10在一預定時間對來自電流感測電路14A之輸出之指示進行取樣或對其進行峰值偵測。或者，多個取樣點可從電流感測電路14A之輸出收集並用於更好地將描述電流IL 之一電流波形之形狀指示給切換控制器10。
當電流感測電路14A首先量測電流IL ，且隨後允許輔助電源供應電路12A對電容器C2充電以維持輸出電壓VDDH 時，電流感測及輔助電源供應充電之順序通常不受限制。在本發明之其他實施例中，可在輔助電源供應輸出電壓VDDH 被補足後執行感測，只要用於電流IL 之量測之參考點無須為峰值電流或工作循環之較遲部分中之一些值。然而，在電流變壓器T1之大的磁化發生之前執行感測通常要求首先執行感測，除非採取其他方法對磁化進行校正或將其移除。
現參考圖3，根據本發明之一替代實施例顯示可用於實施圖1之輔助電源供應12之一輔助電源供應電路12B之細節及可用於實施圖1之電流感測電路14之一電流感測電路14B之細節。圖3之輔助電源供應電路12B及電流感測電路14B係類似於圖2之輔助電源供應電路12A及電流感測電路14A，且因此下文將僅描述它們之間之差異。在輔助電源供應12B中，控制信號sense係從控制電晶體N10及P10之切換控制器10提供。控制信號sense可以或無法藉由在CCM模式中操作的切換控制器10而鑑定，從而當切換控制器10操作於DCM模式中時不執行感測。雖然如上所述可首先在任一極性確證控制信號sense，但是通常可首先使用針對工作循環之第一部分所確證之控制信號sense執行感測，且可從切換控制器10內之切換信號決定時序。或者，量測電流感測電路14B之輸出之一結果可用於決定量測何時完成且輔助電源供應12B可開始對電容器C2充電。在此一實施例中，在一切換工作循環開始時確證信號sense，降低跨次級繞組sec之電壓且隨後電晶體N10接著停止且電晶體P10啟動以對電容器C2充電。由於切換控制器10控制電晶體N1之切換循環，所以可完全決定信號sense之操作之時序。因此，可取決於感測精確度及感測每一循環之電流與維持輔助電源供應輸出電壓VDDH 之低電壓變化之相對優先而以任一順序執行電流感測及輔助電源供應充電。
電流感測電路14B與圖2之電流感測電路14A之差異在於省略電阻器R11，且藉由電流Isec 而跨電晶體N10產生之電壓用於產生電流IL 之指示。消除額外電阻器R11之電壓降，減少電流變壓器T1在整個工作循環期間之磁化且因此減少歸因於磁化之誤差。消除跨電阻器R11之電壓降亦提供用於在工作循環之充電部分期間對電容器C2充電之一更高電壓。
現參考圖4，根據本發明之一替代實施例描繪可用於實施圖1之輔助電源供應12之一輔助電源供應電路12C之細節及可用於實施圖1之電流感測電路14之一電流感測電路14C之細節。輔助電源供應電路12C可用於實施圖1之輔助電源供應12。如下文更詳細描述，輔助電源供應電路12C繪示取決於包含或省略任選元件之本發明之多個替代實施例。圖4之輔助電源供應電路12C及電流感測電路14C係類似於圖3之輔助電源供應電路12B及電流感測電路14B，且因此下文將僅描述它們之間之差異。在輔助電源供應12C之一實施例中，繪示為一虛線方塊之一任選之預充電電路32係藉由從切換控制器10提供之一切換信號/CS而控制，該切換信號/CS係啟動圖1之切換轉換器8中之電晶體N1之控制信號CS之互補。在一工作循環開始時，即在控制信號CS確證前，預充電電路32對次級繞組sec充電至一磁化，其等於當電晶體N1處於作用中之工作循環期間藉由跨次級繞組sec所產生之電壓VSEC 而導致之磁化且具有與其相反之一極性。輔助電源供應12C中無需開關或電晶體，因為電流感測電路14C從如提供給電流感測電路14C之電流ISEC 直接接收電流IL 之指示之正確值，且可在從次級繞組sec提供之作用脈衝之整個持續時間內對電容器C2充電。
在亦繪示於圖4中之一替代實施例中，預充電電路32可省略且如虛線方塊所指示可在切換控制器10中提供一任選之校正方塊30。校正方塊30從變壓器T1之相互電感之一預定已知值或從在起動時或操作期間所進行的一相互電感量測計算電流IL 之指示之誤差。在另一實施例中，校正方塊30可藉由對比工作循環之感測及充電部分期間之Isec 的不同斜率而決定誤差以估計一實際磁化電流IMAG 。可藉由用一預定電壓驅動次級繞組sec並藉由觀察電流Isec 在電晶體N1停止後衰減的速率而決定電流Isec 之斜率而量測相互電感。或者，若提供電晶體，諸如圖2及圖3之電晶體N10及P10，則可對比DCM模式中之兩個等效循環期間(一期間電晶體N10處於作用中且另一期間電晶體P10處於作用中)之電流IL 的指示以決定誤差。在此一實施方案中，電晶體N10及P10係僅用於校準。在正常操作期間會停止電晶體N10並啟動電晶體P10，且校正方塊30會藉由從電流感測電路14所產生之電流IL 之指示中減去所量測之誤差值而直接補償歸因於變壓器T1之磁化之誤差。
電流感測電路14C與圖3之控制電路14B之不同在於一電流鏡M1係用於將電流Isec 反射進藉由放大器A1及電阻器R13所形成之一電流輸入放大器。因此，感測電路所引入之電壓降係類似於電流感測電路14B中之電晶體N10之電壓降。
現參考圖5，繪示包含圖2之一輔助電源供應12A之圖1之切換轉換器8內之信號波形。輔助電源供應之其他實施例具有類似輸出波形，但不直接繪示。在時間T2 前，切換轉換器8係操作於CCM模式中，且信號ccm被確證。電感器電流IL 在充電階段期間快速增加且隨電感器L1中的能量釋放進電容器C1而較慢地減少。電壓Vsec 由一正脈衝、一負轉變尖波及電感器L1之放電期間之一較低電壓負脈衝所組成。在正脈衝之第一部分期間，執行電流感測，如處於一作用狀態之信號sense所指示。電晶體N10將電壓Vsec 箝位在一相對較低之值直至信號sense解確證。若輸出電壓VDDH 低於臨限電壓VTH ，則正脈衝之第二部分在信號sense解確證且電壓Vsec 增至其如電流變壓器T1之圈數比所決定之完全電位後對電容器C2充電以恢復輸出電壓VDDH 。在時間T2 後，切換轉換器8操作於DCM模式且感測動作懸置，但若輸出電壓VDDH 低於臨限電壓VTH ，則仍對電容器C2充電。次級電流Isec 繪示工作循環之輔助供應充電部分期間之斜率之一改變。一電流誤差IMAG 表示用一非常低的磁化電流(即若電晶體N10在整個工作循環處於作用中)所產生之電流Isec 之一值與因電流變壓器T1之磁化而減少之Isec 之實際值之間之差。
雖然已參考本發明之較佳實施例特別顯示及描述本發明，但是熟悉此項技術者將瞭解可在不脫離本發明之精神與範圍的情況下對其中之形式及細節進行上述及其他改變。
8．．．切換電源轉換器
10．．．切換控制器
12．．．輔助電源供應
12A．．．輔助電源供應
12B．．．輔助電源供應
12C．．．輔助電源供應
14．．．電流感測電路
14A．．．電流感測電路
16．．．控制電路
30．．．校正方塊
32．．．預充電電路
/CS．．．切換信號
A1．．．放大器
AND1．．．邏輯AND閘
C1．．．電容器
C2．．．電容器
ccm．．．信號
CCM．．．連續傳導模式
Charge．．．信號
CS．．．控制信號
D1．．．二極體
D10．．．二極體
DCM．．．不連續傳導模式
I1．．．反相器
IL ．．．電流
IMAG ．．．磁化電流
Isec ．．．次級電流
K1．．．比較器
L1．．．電感器
M1．．．電流鏡
N1．．．電晶體
N10．．．電晶體
NAND1．．．邏輯NAND閘
OUT．．．輸出終端
P10．．．電晶體
pri．．．初級繞組
R10．．．電阻器
R11．．．電阻器
R12．．．電阻器
R13．．．電阻器
sec．．．次級繞組
sense．．．信號
T1．．．電流感測變壓器
VDDH ．．．電壓
VIN ．．．電壓
VR11 ．．．電壓
Vsec ．．．電壓
VTH ．．．臨限電壓
Z1．．．齊納二極體
圖1係描繪根據本發明之一實施例之一切換轉換器之一方塊圖。
圖2係描繪根據本發明之一實施例可各自用於實施圖1之電流感測電路14及輔助電源供應12之一電流感測電路14A及一輔助電源供應12A之細節之一示意圖。
圖3係描繪根據本發明之另一實施例可各自用於實施圖1之電流感測電路14及輔助電源供應12之一電流感測電路14B及一輔助電源供應12B之細節之一示意圖。
圖4係描繪根據本發明之又一實施例可各自用於實施圖1之電流感測電路14及輔助電源供應12之一電流感測電路14C及一輔助電源供應12C之細節之一示意圖。
圖5係描繪根據本發明之一實施例之圖1之切換轉換器之操作之細節之一信號波形圖。
8．．．切換電源轉換器
10．．．切換控制器
12．．．輔助電源供應
14．．．電流感測電路
C1．．．電容器
CS．．．控制信號
D1．．．二極體
IL ．．．電流
L1．．．電感器
N1．．．電晶體
OUT．．．輸出終端
Pri．．．初級繞組
sec．．．次級繞組
T1．．．電流感測變壓器
VDDH ．．．電壓
VIN ．．．電壓

Claims (19)

  1. 一種切換電源電路，其包括：一磁耦合元件，其用於耦合該切換電源電路之一輸入至該切換電源電路之一輸出且具有至少一繞組；一切換電路，其用於控制從連接至該切換電源電路之該輸入之一輸入電壓源對該磁耦合元件之一初級繞組之通電；一電流感測變壓器，其具有與該磁耦合元件之該至少一繞組及該切換電路串聯耦合之一初級繞組，且具有一次級繞組；一控制電路，其用於控制該切換電路之切換；一電流感測電路，其耦合至該電流感測變壓器之該次級繞組以提供透過該磁耦合元件之該至少一繞組傳導之電流之一量值之一指示，其中該電流感測電路校正該電流之該量值之該指示以補償該電流感測變壓器之一相互電感；及一輔助電源供應，其具有耦合至該電流感測變壓器之該次級繞組之一輸入及耦合至該控制電路以提供一供應電壓給該控制電路之一輸出。
  2. 如請求項1之切換電源電路，其中該電流感測電路從自跨該電流感測變壓器之該次級繞組之一電壓之一量測決定之一估計模擬該電流感測變壓器之該次級繞組之相互電感。
  3. 如請求項1之切換電源電路，其中該電流感測電路從該 電流感測變壓器之相互電感之一預定值模擬該電流感測變壓器之相互電感。
  4. 一種切換電源電路，其包括：一磁耦合元件，其用於耦合該切換電源電路之一輸入至該切換電源電路之一輸出且具有至少一繞組；一切換電路，其用於控制從連接至該切換電源電路之該輸入之一輸入電壓源對該磁耦合元件之一初級繞組之通電；一電流感測變壓器，其具有與該磁耦合元件之該至少一繞組及該切換電路串聯耦合之一初級繞組，且具有一次級繞組；一控制電路，其用於控制該切換電路之切換；一電流感測電路，其耦合至該電流感測變壓器之該次級繞組以提供透過該磁耦合元件之該至少一繞組傳導之電流之一量值之一指示，其中該電流感測電路進一步包括用於在決定該電流之該量值之該指示之一量測間隔期間選擇性地降低跨該電流感測變壓器之該次級繞組之一電壓，藉此實質上減少該電流感測變壓器之一磁化電流對該電流之該量值之該指示之一影響之一電路；及一輔助電源供應，其具有耦合至該電流感測變壓器之該次級繞組之一輸入及耦合至該控制電路以提供一供應電壓給該控制電路之一輸出。
  5. 如請求項4之切換電源電路，其中該輔助電源供應進一步包括用於在選擇性地降低跨該次級繞組之電壓時自該 電流感測變壓器之該次級繞組隔離該輔助電源供應之該輸出之一電路。
  6. 如請求項4之切換電源電路，其中若該切換電源電路係操作於連續傳導模式中，則僅在該量測間隔期間降低跨該電流感測變壓器之該次級繞組之電壓。
  7. 一種切換電源電路，其包括：一磁耦合元件，其用於耦合該切換電源電路之一輸入至該切換電源電路之一輸出且具有至少一繞組；一切換電路，其用於控制從連接至該切換電源電路之該輸入之一輸入電壓源對該磁耦合元件之一初級繞組之通電；一電流感測變壓器，其具有與該磁耦合元件之該至少一繞組及該切換電路串聯耦合之一初級繞組，且具有一次級繞組；一控制電路，其用於控制該切換電路之切換；一電流感測電路，其耦合至該電流感測變壓器之該次級繞組以提供透過該磁耦合元件之該至少一繞組傳導之電流之一量值之一指示；及一輔助電源供應，其具有耦合至該電流感測變壓器之該次級繞組之一輸入及耦合至該控制電路以提供一供應電壓給該控制電路之一輸出，其中該輔助電源供應進一步包括用於在一量測循環前磁化該電流感測變壓器之該次級繞組為與跨該次級繞組之電壓所導致之磁化電流相反之一值，藉此藉由磁化該次級繞組而補償該電流感測 變壓器之一磁化電流之一預充電電路。
  8. 一種操作一切換電源電路之方法，其包括：切換跨一磁耦合元件之至少一繞組之一輸入電壓源以輸送電力至該切換電源電路之一輸出；使用具有與該磁耦合元件之該至少一繞組串聯耦合之一初級繞組之一感測變壓器感測流動穿過該磁耦合元件之該至少一繞組之一電流；從該電流感測變壓器之一次級繞組產生一輔助電源供應以提供一供應電壓給該切換電源電路之一控制電路；及校正電流之一量值之一指示以補償該電流感測變壓器之一相互電感。
  9. 如請求項8之方法，其中該校正包括從藉由量測跨該電流感測變壓器之該次級繞組之一電壓而決定之一估計模擬該電流感測變壓器之該次級繞組之相互電感。
  10. 如請求項8之方法，其中該校正包括從該電流感測變壓器之相互電感之一預定值模擬該電流感測變壓器之相互電感。
  11. 一種操作一切換電源電路之方法，其包括：切換跨一磁耦合元件之至少一繞組之一輸入電壓源以輸送電力至該切換電源電路之一輸出；使用具有與該磁耦合元件之該至少一繞組串聯耦合之一初級繞組之一感測變壓器感測流動穿過該磁耦合元件之該至少一繞組之一電流； 從該電流感測變壓器之一次級繞組產生一輔助電源供應以提供一供應電壓給該切換電源電路之一控制電路；及在決定該電流之量值之指示之一量測間隔期間選擇性地降低跨該電流感測變壓器之該次級繞組之一電壓，藉此實質上減少該電流感測變壓器之一磁化電流對電流之該量值之該指示之一影響。
  12. 如請求項11之方法，其進一步包括在該選擇性降低期間隔離該輔助電源供應之該輸出。
  13. 如請求項11之方法，其中若該切換電源電路係操作於連續傳導模式中，則該選擇性降低僅在該量測間隔期間降低跨該電流感測變壓器之該次級繞組之該電壓。
  14. 一種操作一切換電源電路之方法，其包括：切換跨一磁耦合元件之至少一繞組之一輸入電壓源以輸送電力至該切換電源電路之一輸出；使用具有與該磁耦合元件之該至少一繞組串聯耦合之一初級繞組之一感測變壓器感測流動穿過該磁耦合元件之該至少一繞組之一電流；及從該電流感測變壓器之一次級繞組產生一輔助電源供應以提供一供應電壓給該切換電源電路之一控制電路；及在一量測循環前磁化該電流感測變壓器之該次級繞組為與跨該次級繞組之電壓所導致之磁化電流相反之一值，藉此藉由該次級繞組之磁化而補償該電流感測變壓 器之一磁化電流。
  15. 一種積體電路，其包括：一切換控制電路，其用於控制用於透過至少一初級繞組對一外部磁耦合元件充電之一開關；至少一輸入終端，其用於耦合至一電流感測變壓器之一次級繞組；一電流感測電路，其具有耦合至該至少一輸入終端之一輸入以提供透過該外部磁耦合元件之該至少一繞組而傳導之電流之一量值之一指示，其中該電流感測電路校正該電流之該量值之該指示以補償該電流感測變壓器之一相互電感；及一輔助電源供應，其具有耦合至該至少一輸入終端之一輸入及耦合至該切換控制電路以提供一供應電壓給該控制電路之一輸出。
  16. 一種積體電路，其包括：一切換控制電路，其用於控制用於透過至少一初級繞組對一外部磁耦合元件充電之一開關；至少一輸入終端，其用於耦合至一電流感測變壓器之一次級繞組；一電流感測電路，其具有耦合至該至少一輸入終端之一輸入以提供透過該外部磁耦合元件之該至少一繞組而傳導之電流之一量值之一指示，其中該電流感測電路進一步包括一電路，以用於在決定電流之該量值之該指示之一量測間隔期間選擇性地降低跨該電流感測變壓器之 該次級繞組之一電壓，藉此實質上減少該電流感測變壓器之一磁化電流對該電流之該量值之該指示之一影響；及一輔助電源供應，其具有耦合至該至少一輸入終端之一輸入及耦合至該切換控制電路以提供一供應電壓給該控制電路之一輸出。
  17. 如請求項16之積體電路，其中該輔助電源供應進一步包括一電路，以用於在選擇性地降低跨該次級繞組之該電壓時自該電流感測變壓器之該次級繞組隔離該輔助電源供應之該輸出。
  18. 如請求項16之積體電路，其中若該積體電路係操作於連續傳導模式中，則僅在該量測間隔期間降低跨該電流感測變壓器之該次級繞組之該電壓。
  19. 一種積體電路，其包括：一切換控制電路，其用於控制用於透過至少一初級繞組對一外部磁耦合元件充電之一開關；至少一輸入終端，其用於耦合至一電流感測變壓器之一次級繞組；一電流感測電路，其具有耦合至該至少一輸入終端之一輸入以提供透過該外部磁耦合元件之該至少一繞組而傳導之電流之一量值之一指示；及一輔助電源供應，其具有耦合至該至少一輸入終端之一輸入及耦合至該切換控制電路以提供一供應電壓給該控制電路之一輸出，其中該輔助電源供應進一步包括一 預充電電路，以用於在一量測循環前磁化該電流感測變壓器之該次級繞組為與跨該次級繞組之電壓所導致之該磁化電流相反之一值，藉此藉由該次級繞組之該磁化而補償該電流感測變壓器之一磁化電流。
TW099118779A 2009-06-30 2010-06-09 切換電源電路、用於操作其之方法及積體電路 TWI499175B (zh)

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