WO2016146000A1 - 一种高频隔离交直流变换电路及其控制方法 - Google Patents

一种高频隔离交直流变换电路及其控制方法 Download PDF

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Publication number
WO2016146000A1
WO2016146000A1 PCT/CN2016/075813 CN2016075813W WO2016146000A1 WO 2016146000 A1 WO2016146000 A1 WO 2016146000A1 CN 2016075813 W CN2016075813 W CN 2016075813W WO 2016146000 A1 WO2016146000 A1 WO 2016146000A1
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Prior art keywords
frequency
source
bridge inverter
circuit
inverter circuit
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PCT/CN2016/075813
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English (en)
French (fr)
Inventor
李伦全
刘嘉键
燕沙
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深圳市保益新能电气有限公司
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Priority to EP16764181.0A priority Critical patent/EP3273584A4/en
Publication of WO2016146000A1 publication Critical patent/WO2016146000A1/zh
Priority to US15/690,299 priority patent/US10050552B2/en

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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/42—Circuits or arrangements for compensating for or adjusting power factor in converters or inverters
    • H02M1/4208—Arrangements for improving power factor of AC input
    • H02M1/4233—Arrangements for improving power factor of AC input using a bridge converter comprising active switches
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H02M3/285—Single converters with a plurality of output stages connected in parallel
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/33569—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements
    • H02M3/33576—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements having at least one active switching element at the secondary side of an isolation transformer
    • H02M3/33584—Bidirectional converters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/33569—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements
    • H02M3/33576—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements having at least one active switching element at the secondary side of an isolation transformer
    • H02M3/33592—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements having at least one active switching element at the secondary side of an isolation transformer having a synchronous rectifier circuit or a synchronous freewheeling circuit at the secondary side of an isolation transformer
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/02—Conversion of ac power input into dc power output without possibility of reversal
    • H02M7/04—Conversion of ac power input into dc power output without possibility of reversal by static converters
    • H02M7/12—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/145—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a thyratron or thyristor type requiring extinguishing means
    • H02M7/155—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a thyratron or thyristor type requiring extinguishing means using semiconductor devices only
    • H02M7/162—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a thyratron or thyristor type requiring extinguishing means using semiconductor devices only in a bridge configuration
    • H02M7/1623—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a thyratron or thyristor type requiring extinguishing means using semiconductor devices only in a bridge configuration with control circuit
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0067—Converter structures employing plural converter units, other than for parallel operation of the units on a single load
    • H02M1/007—Plural converter units in cascade
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/02—Conversion of ac power input into dc power output without possibility of reversal
    • H02M7/04—Conversion of ac power input into dc power output without possibility of reversal by static converters
    • H02M7/12—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/21—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M7/217—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M7/219—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only in a bridge configuration
    • H02M7/2195—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only in a bridge configuration the switches being synchronously commutated at the same frequency of the AC input voltage
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes

Definitions

  • the invention relates to a switching power supply, in particular to an efficient high-frequency isolated AC/DC conversion circuit and a control method thereof.
  • the main object of the present invention is to provide a high-frequency isolated AC-DC conversion circuit and a control method thereof that can be switched between a rectification mode and an inverter mode, so as to solve the complicated design of the existing AC-DC bidirectional conversion circuit and difficult to achieve high-frequency isolation. And technical problems with low work efficiency.
  • An embodiment of the present invention provides a high frequency isolated AC/DC conversion circuit including a single phase AC source, a DC source, first to second capacitors, a high voltage energy storage filter, a high frequency full bridge inverter circuit, first to first a two-high frequency half-bridge inverter circuit, a driving circuit, first to third inductors, first to second high-frequency isolating transformers, first to second DC-side synchronous switches, and a control circuit connected to the driving circuit;
  • the first capacitor is connected in parallel with the single-phase AC source, and the second capacitor is connected in parallel with the DC source;
  • the high-frequency full-bridge inverter circuit and the first to second high-frequency half-bridge inverter circuits are all composed of a switch tube In the high frequency full bridge inverter circuit: 1.
  • the second AC end is respectively connected to the second end of the first inductor and the second end of the first capacitor, and the first and second DC ends are respectively connected to the positive pole and the negative pole of the high voltage energy storage filter
  • the first end of the first inductor is connected to the first end of the first capacitor; in the first high frequency half bridge inverter circuit, the first and second DC ends are respectively connected to the high voltage storage a positive electrode and a negative electrode of the filter, wherein the first AC terminal is connected to one end of the single-phase AC source side of the first high-frequency isolating transformer through the second inductor, and the second AC terminal is connected to the first high-frequency isolation
  • the first and second DC terminals are respectively connected to the positive pole and the negative pole of the high-voltage energy storage filter, and the first AC terminal Connected to one end of the single-phase AC source side of the second high-frequency isolating transformer by the third inductor,
  • Another embodiment of the present invention provides a control method for a high-frequency isolated AC/DC conversion circuit for controlling switching operation between a rectification mode and an inverter mode, the control method including: When the conversion circuit operates in the rectification mode: controlling the high-frequency full-bridge inverter circuit to operate in a PFC rectification state and boosting; controlling the first and second high-frequency half-bridge inverter circuits to operate in an inverter state; The absorption current of the DC source is greater than or equal to 0.1 times of the rated current, then: driving the first to fourth switch tubes to be turned on by a PWM signal, and the first and second switch tubes are turned on at the first high Offset based on the center of the turn-on sequence of the frequency half-bridge inverter circuit, and the turn-on timing of the third and fourth switch transistors is biased based on the center of the turn-on timing of the second high-frequency half-bridge inverter circuit Shifting, and adjusting the on-duty ratio according to the switching frequency to obtain high efficiency; when
  • Another embodiment of the present invention further provides a high frequency isolated AC/DC conversion circuit, including a single phase AC source, a DC source, first to third capacitors, a high voltage energy storage filter, and first to third high frequency full bridge inverter circuits.
  • a driving circuit first to second inductors, a high frequency isolation transformer, and a control circuit connected to the driving circuit;
  • the first capacitor is connected in parallel with the single phase AC source, and the second capacitor and the DC source Parallel;
  • the first to third high-frequency full-bridge inverter circuits are each formed by a switch tube; in the first high-frequency full-bridge inverter circuit, the first and second AC terminals are respectively connected to the second of the first inductor And a second end of the first capacitor, the first and second DC ends are respectively connected to the positive pole and the negative pole of the high voltage energy storage filter, the first end of the first inductor and the first capacitor The first end is connected; in the second high-frequency full-bridge inverter circuit, the first AC end is connected to the first end
  • Another embodiment of the present invention further provides a high frequency isolated AC/DC conversion circuit, including a three-phase AC source, a DC source, a high voltage energy storage filter, first to third high frequency full bridge inverter circuits, a driving circuit, a resonant inductor, a resonant capacitor, a DC side filter capacitor, a high frequency isolation transformer, and a control circuit connected to the driving circuit;
  • the three-phase AC source is coupled to an AC terminal of the first high frequency full bridge inverter circuit, the first high frequency
  • the first and second DC ends of the bridge inverter circuit are respectively connected to the positive pole and the negative pole of the high voltage energy storage filter, and the three-phase AC source and the AC end of the first high frequency full bridge inverter circuit are connected
  • An LC filter in the second high-frequency full-bridge inverter circuit, the first AC end is connected to the first end of the three-phase AC source side of the high-frequency isolating transformer through the resonant inductor, and the second AC end passes
  • the high-frequency isolated AC-DC conversion circuit and the control method thereof provided by the invention automatically switch between the rectification mode and the inverter mode according to the real-time voltage of the DC source with the set DC source reference voltage as a reference, and work at the same time.
  • the DC side high frequency inverter bridge is changed (including the first and the first mentioned above).
  • the frequency and duty ratio of the two-frequency high-frequency half-bridge inverter circuit and the DC-side synchronous switch are realized by the resonant state of the high-frequency inverter bridge topology,
  • the opening and closing stress of each switch tube in the bridge inverter circuit is reduced, the switching loss is reduced, the working frequency of the inverter circuit is improved or the efficiency is improved, thereby increasing the power density and reducing the volume; thereby achieving high power density. , high efficiency and high frequency electrical isolation.
  • the turn-on timing control of the high-frequency inverter bridge is used to realize the reverse conversion of a wide range of DC voltages, so that the topology achieves high efficiency in a similar application of a wide voltage range such as a battery, and is much more efficient than conventional converters. .
  • FIG. 1 is a schematic diagram of a high frequency isolated AC/DC conversion circuit according to Embodiment 1 of the present invention
  • FIG. 2 is a timing diagram of PWM driving when the conversion circuit of FIG. 1 operates in a rectification mode
  • FIG. 3 is a timing diagram of PWM driving when the conversion circuit of FIG. 1 operates in an inverter mode
  • FIG. 4 is a schematic diagram of a high frequency isolated AC/DC conversion circuit according to Embodiment 2 of the present invention.
  • FIG. 5 is a schematic diagram of a high frequency isolated AC/DC conversion circuit according to Embodiment 3 of the present invention.
  • V1 single-phase AC source
  • T RA first high frequency isolation transformer
  • T RB second high frequency isolation transformer
  • T R high frequency isolation transformer
  • A1 ⁇ A5 five ends of the first high frequency isolation transformer T RA
  • V1a, V1b, V1c three-phase AC source
  • the embodiment provides a high-frequency isolated AC-DC conversion circuit as shown in FIG. 1 , including a single-phase AC source V1, a DC source V2, a first capacitor C1, a second capacitor C2, a high-voltage energy storage filter C, and a high-frequency full bridge.
  • the high frequency full bridge inverter circuit 300 and the first to second high frequency half bridge inverter circuits 100 and 200 are each constituted by a switching tube.
  • the high-frequency full-bridge inverter circuit 300 has four input/output terminals, two AC terminals (for inputting or outputting an AC signal) and two DC terminals (for inputting or outputting a DC signal).
  • One of the AC ends is connected to the second end of the first inductor L1, and the other AC end is connected to the second end of the first capacitor C1.
  • the first end of the first inductor L1 is connected to the first end of the first capacitor C1.
  • the two DC terminals are respectively connected to the positive +BUS and negative-BUS of the high-voltage energy storage filter C.
  • the high-frequency full-bridge inverter circuit 300 includes four switching transistors Q5-Q8, wherein the source of the switching transistor Q5 is connected to the drain of the switching transistor Q7 and is led out to form an alternating current terminal to be connected to the first a second end of the inductor L1, the source of the switching transistor Q6 is connected to the drain of the switching transistor Q8 and is led out to form another alternating current terminal to be connected to the second end of the first capacitor C1, and the drains of the switching transistors Q5 and Q6 are connected And lead to form a DC terminal and connected to the positive electrode +BUS of the high-voltage energy storage filter C, the sources of the switching transistors Q7, Q8 are connected and lead to another DC terminal and connected to the negative electrode -BUS of the high-voltage energy storage filter C.
  • the high frequency full bridge inverter circuit 300 When the conversion circuit operates in a rectification mode, the high frequency full bridge inverter circuit 300 operates in a PFC (Power Factor Correction) rectification mode and functions as a boost switch, two AC terminals are signal inputs, and two DC terminals are signals.
  • the output terminal converts an AC signal passing through the LC filter (consisting of the first capacitor C1 and the first inductor L1) into a DC signal; and when the conversion circuit operates in the inverter mode, the high-frequency full-bridge inverter circuit 300 It is used as a high-frequency inverter switch.
  • the two DC terminals are signal input terminals, and the two AC terminals are signal output terminals.
  • the DC signals from the output terminals of the first and second high-frequency half-bridge inverter circuits are converted into AC signals. It should be noted that the operating frequency of the high frequency full bridge inverter circuit 300 is above 30 KHz.
  • the first high frequency half bridge inverter circuit 100 has four input/output terminals, which are two AC terminals (for inputting or outputting an AC signal) and two DC terminals (for inputting). Or outputting a DC signal), the two DC terminals are respectively connected to the positive electrode +BUS and the negative electrode -BUS of the high-voltage energy storage filter C, wherein one AC terminal is connected to the first high-frequency isolating transformer T RA through the second inductor L2
  • the AC source side here, the single-phase AC source side refers to one end A4 that outputs a signal to the AC side or the side that couples the signal from the AC side
  • the other AC terminal is connected to the first high frequency isolation.
  • the first high-frequency half-bridge inverter circuit 100 includes two switching tubes Q9 and Q10 and two capacitors C3 and C4, wherein a first end of the capacitor C3 is connected to a drain of the switch tube Q9 and is formed therein.
  • the DC terminal is connected to the positive electrode +BUS of the high-voltage energy storage filter C
  • the second end of the capacitor C3 is connected to the first end of the capacitor C4
  • the second end of the capacitor C4 is connected to the source of the switch Q10 Connected and led to form another DC terminal (the DC terminal is connected to the negative electrode -BUS of the high-voltage energy storage filter C)
  • the source of the switching transistor Q9 is connected to the drain of the switching transistor Q10 and leads to form an AC terminal (the AC terminal) Connected to the first end A4 of the single-phase AC source side of the first high-frequency isolating transformer T RA by connecting the second inductor L2 in series, the second end of the capacitor C3 (equivalent to the first end of the capacitor C4) is led out to form another An AC terminal is coupled to the second end A5 of the single-phase AC source side of the first high frequency isolation transformer T RA .
  • the connection and working principle of the second high frequency half bridge inverter circuit 200 is the same as that of the first high frequency half bridge inverter circuit 100 , and includes two switching tubes Q11 and Q12 and two capacitors C5. C6, two DC terminals are respectively connected to the positive electrode +BUS and the negative electrode-BUS of the high-voltage energy storage filter C, wherein one AC terminal is connected to the second high-frequency isolating transformer T RB single-phase AC source side through the third inductor L3 One end B4 and the other AC end are connected to the other end B5 of the single-phase AC source side of the second high-frequency isolating transformer T RB .
  • the first end of the capacitor C5 is connected to the drain of the switch Q11 and is led out to form one of the DC terminals.
  • the second end of the capacitor C5 is connected to the first end of the capacitor C6, and the second end of the capacitor C6 is connected to the source of the switch Q12.
  • the poles are connected and lead to form another DC terminal.
  • the source of the switch Q11 is connected to the drain of the switch Q12 and leads to form an AC terminal.
  • the second end of the capacitor C5 is led out to form another AC terminal connected to the second high frequency isolation.
  • the second end B5 of the transformer T RB on the AC source side.
  • the first DC-side synchronous switch 400 includes two switching tubes Q1 and Q2 , and the drains of the switching tubes Q1 and Q2 are respectively connected to the first high-frequency isolating transformer T RA on the DC source side.
  • the third terminals A1 and A3 are connected to the negative pole of the DC source V2 at the same time; the connection and working principle of the second DC-side synchronous switch 500 are the same as those of the first DC-side synchronous switch 400: the switching transistors Q3 and Q4
  • the drains are respectively connected to the first and third terminals B1 and B3 of the second high frequency isolation transformer T RB on the DC source side, and the sources of both are simultaneously connected to the negative electrode of the DC source V2.
  • the second ends A2 and B2 on the DC source side of the first and second high frequency isolation transformers T RA and T RB are both connected to the anode of the DC source V2.
  • the operating frequencies of the first and second high frequency half bridge inverter circuits and the first and second DC side synchronous switches are above 100 KHz.
  • the four capacitors C3 C C6 in the first and second high frequency half bridge inverter circuits are high frequency electrodeless capacitors.
  • the high-voltage energy storage filter C is an electrolytic capacitor, and the number of turns of the DC source side of the first and second high-frequency isolating transformers T RA and T RB is less than 4 ⁇ , and has a normal leakage. sense.
  • the synchronous switch on the DC side does not require an external freewheeling filter inductor.
  • the preferred application of the conversion circuit is when the magnitude of the DC source V2 is above 8V and below 45V, and the output power is between 200W and 2KW.
  • the embodiment further provides a control method of the above conversion circuit, configured to switch an operation mode (rectification mode or an inverter mode) of the circuit according to a real-time voltage value of the DC source V2, the control method comprising: when the conversion circuit operates on a rectification In mode: controlling the high-frequency full-bridge inverter circuit to operate in a PFC rectification state and boosting; controlling the first and second high-frequency half-bridge inverter circuits to operate in an inverter state; if the DC source sinks current If the current is greater than or equal to 0.1 times of the rated current, the first to fourth switch tubes are driven to be turned on by the PWM signal, and the first and second switch tubes are turned on according to the first high frequency half bridge inverter circuit.
  • the turn-on timing of the third and fourth switch transistors is shifted based on the center of the turn-on timing of the second high-frequency half-bridge inverter circuit, and according to the switching frequency Adjusting the on-duty ratio to obtain high efficiency; when the conversion circuit is operating in the inverter mode: controlling the first high-frequency half-bridge inverter circuit to the first DC according to the voltage of the DC source Turning on/off the basis of the center of the turn-on timing of the side synchronous switch, the second high frequency half-bridge inverter circuit is turned on/off based on the center of the turn-on timing of the second DC-side synchronous switch, and The offset is adjusted according to the voltage level of the DC source and the turn-on duty ratio is adjusted to obtain high efficiency.
  • the controller determines whether the conversion circuit should operate in a rectification mode or an inverter mode according to a relationship between a preset voltage value and a real-time voltage value of the DC source V2.
  • the controller determines that the conversion circuit needs to operate in a rectification mode, that is, the power is from the AC source side. Transfer to the DC source side.
  • the high-frequency full-bridge inverter circuit 300 operates in the PFC rectification state, and converts the AC input voltage into a stable value; the first and second high-frequency half-bridge inverter circuits operate in an inverter state, and the PWM signal is used to drive the switch tube Q9.
  • ⁇ Q12 inverts the DC voltage input from the DC terminal into a high-frequency pulse voltage (AC signal), and then transmits it to the first and second DC-side synchronous switches through the coupling of the first and second high-frequency isolation transformers, according to
  • the voltage of the DC source and the magnitude of the absorption current (or the absorption current) determine whether the switch tubes Q1 to Q4 need to be turned on. If the DC source sink current is less than 0.1 times the rated current, the switch tubes Q1 to Q4 are not turned on. The state of the parasitic diode is naturally rectified. If the DC source sinks current at 0.1 times or more of the rated current, the control switch tubes Q1 to Q4 are turned on, and the turn-on timing is referred to FIG.
  • the turn-on timing of the switch transistors Q1 and Q2 is controlled by the switch tubes Q9 and Q10.
  • the turn-on timing center is offset backward by 1/4 duty cycle, and a certain dead time is left between the switch tubes Q9 and Q10 to prevent the through-short circuit.
  • the switch tubes Q3 and Q4 are turned on. The timing is shifted back by 1/4 based on the turn-on timing center of the switching transistors Q11 and Q12, and a certain dead time is left between the switching transistors Q11 and Q12.
  • the resonance conversion process can be realized due to the resonance of the capacitors C3 to C6, and the load terminal (rectification mode) is used in the full working range.
  • the lower DC source is the voltage level and the current sink of the load terminal to change the operating frequency or duty cycle.
  • Q9 ⁇ Q12 can obtain soft switching to achieve high efficiency and high power density of the conversion circuit.
  • the controller determines that the conversion circuit needs to operate in the inverter mode, that is, the electric energy is transmitted from the DC source side to the AC source side.
  • the switch tubes Q1 to Q4 are turned on, and the turn-on timing is referred to FIG. 3, so that the first and second DC-side synchronous switches 400 and 500 operate in a high-frequency inverter state, and the DC voltage signal of the DC source is converted into an AC signal.
  • the first and second high-frequency isolating transformers are coupled to transmit the alternating current signal to the first and second high-frequency half-bridge inverter circuits 100 and 200 for rectification and boosting, and the turn-on timing of the switching transistors Q9 to Q12 is as shown in FIG.
  • the turn-on timing of the switch tubes Q1 and Q2 is shifted forward by 1/4 of the work based on the turn-on timing center of the switch tubes Q9 and Q10.
  • the turn-on timing of the switching transistors Q3 and Q4 is shifted forward by 1/4 duty cycle based on the turn-on timing center of the switching transistors Q11 and Q12.
  • the first and second DC side synchronous switches 400 and 500 are similar to the conventional push-pull structure, but since the DC source side of the transformer has a normal leakage inductance, the DC signal passes through the first and second DC side synchronous switches. There is a certain slow rising slope to avoid the conventional push-pull.
  • This embodiment provides a high-frequency isolated AC-DC conversion circuit similar to that of the first embodiment. As shown in FIG. 4, the difference from the first embodiment is that the first and second high-frequency half-bridge inverses in the first embodiment are reversed.
  • the variable circuits 100 and 200 are replaced by a full-bridge inverter circuit 600, and only one high-frequency isolating transformer T R is used , and the DC source side of the high-frequency isolating transformer T R is reduced by one coil, and the first and the first in the first embodiment are The two DC side synchronous switches 400, 500 are replaced by a full bridge inverter circuit 700.
  • the full-bridge inverter circuit 600 includes switching tubes Q9-Q12, and the drains of the switching tubes Q9 and Q10 are connected to form a DC terminal and connected to the positive electrode +BUS of the high-voltage energy storage filter C.
  • the sources of Q11 and Q12 are connected, another DC terminal is formed to be connected to the negative electrode -BUS of the high-voltage energy storage filter C, and the sources of the switching transistors Q9 and Q10 are respectively connected to the drains of the switching transistors Q11 and Q12, and
  • the two alternating current terminals are respectively led out, and the alternating current terminal drawn from the source of the switching transistor Q10 is connected to the first end 4 of the alternating current source side of the high frequency isolation transformer T R through the series inductor L2, and the alternating current is drawn from the source of the switching transistor Q9.
  • the terminal is connected to the first terminal 5 of the AC source side of the high frequency isolation transformer T R through a series capacitor C3.
  • the high-frequency full-bridge inverter circuit 700 includes switching tubes Q1 to Q4.
  • the drains of the switching tubes Q1 and Q2 are connected to form a DC terminal and connected to the anode of the DC source V2.
  • the sources of the switching tubes Q3 and Q4 are connected to form another
  • a DC terminal is connected to the negative pole of the DC source V2
  • the sources of the switching transistors Q1 and Q2 are respectively connected to the drains of the switching transistors Q3 and Q4, and are respectively led out to form two AC terminals, which are taken out from the source of the switching transistor Q2.
  • the AC terminal is connected to the first terminal 1 of the DC source side of the high frequency isolation transformer T R , and the AC terminal drawn from the source of the switching transistor Q1 is connected to the second terminal 2 of the DC source side of the high frequency isolation transformer T R .
  • the capacitor C3 in this embodiment preferably uses a high frequency electrodeless capacitor.
  • the control method of the conversion circuit of this embodiment is the same as that of the first embodiment, and details are not described herein again.
  • the conversion circuit of FIG. 4 provided by the embodiment when the voltage of the DC source V2 is high, the stress of the synchronous rectifier tube can be reduced, and when the current of the DC source V2 is large, the DC source side coil of the transformer can be reduced by one coil. The wire diameter can be large to reduce losses.
  • the optimum application of the conversion circuit provided by this embodiment is when the magnitude of the DC source V2 is higher than 45V and the output power is between 1KW and 5KW.
  • the present embodiment provides a high frequency isolated AC/DC conversion circuit as shown in FIG. 5.
  • a single-phase AC source is replaced with a three-phase AC source V1a, V1b, V1c, and LC filtering is connected to each phase.
  • the high-frequency full-bridge inverter circuit (including the switching tubes Q5 to Q8) in the second embodiment adopts a three-phase full-bridge inverter circuit
  • the road 800 switching tubes Q5 to Q8, Q13, Q14 in Fig. 5) is replaced.
  • the capacitor C3 in this embodiment is the same as the capacitor C3 in the second embodiment, and a high-frequency electrodeless capacitor is preferably used.
  • the three-phase AC source is used, and the control method of the conversion circuit in this embodiment is the same as that in the first embodiment. .
  • the optimum application of the conversion circuit provided by this embodiment is when the amplitude of the DC source V2 is higher than 80V and the output power is above 3KW.

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Abstract

一种高频隔离交直流变换电路及其控制方法。变换电路包括交流源（V1），直流源（V2），直流侧同步开关（400），高频隔离变压器（TRA，TRB），直流侧高频逆变桥（100，200），谐振电感（L2，L3，Lr），谐振电容(C3，Cr)，高压储能滤波电容（C），交流侧逆变桥，输出滤波器（C2），以预设直流侧电压为基准，根据外部电压参考，利用逆变桥的不同开通工作模式，使电路切换于整流和逆变两种工作模式，同时利用高频逆变桥拓扑的谐振模式实现软开关，降低开关损耗，有助于逆变电路的工作频率提高或者效率提高从而提高功率密度并减小体积。利用高频逆变桥的开通时序控制，实现宽范围直流电压的逆变，在蓄电池等较宽电压变化范围的应用中获得高效率。

Description

一种高频隔离交直流变换电路及其控制方法 技术领域
本发明涉及开关电源，尤其涉及一种高效的高频隔离交直流变换电路及其控制方法。
背景技术
在需要进行交直流双向变换(即充放电)的应用场合，如储能逆变器、离网逆变器、电池厂老化化成、检测等环节，大多以低频隔离方案为主，究其原因主要是高频隔离双向变换技术较为复杂，同时高频变换所引起的高频开关损耗导致效率低下，得不偿失。而低频变压器隔离技术相对成熟稳定，但相对高频隔离技术而言，其缺点也很明显：低频隔离的方法中变压器体积庞大且笨重，因此在很多应用场合难以推广，使用受限。因而，有人提出两种较为折衷的方案：一种是采用将充放电电路分离的办法，实现变压器隔离的高频化，体积有一定的缩小，效率也可以较高，但相对体积还是较大；另外一种是采用具有双向变换功能的电路，牺牲一定的效率，实现隔离的高频化，这样可以很大程度减小体积，并且相对于单向变换技术，功率密度和效率有一定的提高，但效率仍作出了一定的牺牲。
因此，有必要设计出一种新的电路，通过合理的变换电路以及合适的控制方法，可以实现高功率密度、高效率并且电气隔离，同时又可以满足不同电池类型的较宽电压范围的变换。
发明内容
本发明的主要目的在于提出一种可切换于整流模式和逆变模式工作的高频隔离交直流变换电路及其控制方法，以解决现有的交直流双向变换电路设计复杂、难以实现高频隔离且工作效率低的技术问题。
本发明的一种实施例提供一种高频隔离交直流变换电路，包括单相交流源、直流源、第一至第二电容、高压储能滤波器、高频全桥逆变电路、第一至第二高频半桥逆变电路、驱动电路、第一至第三电感、第一至第二高频隔离变压器、第一至第二直流侧同步开关以及与所述驱动电路连接的控制电路；所述第一电容与所述单相交流源并联，所述第二电容与所述直流源并联；所述高频全桥逆变电路、第一至第二高频半桥逆变电路均由开关管构成；在所述高频全桥逆变电路中：第 一、第二交流端分别连接至所述第一电感的第二端和所述第一电容的第二端，第一、第二直流端分别连接至所述高压储能滤波器的正极和负极，所述第一电感的第一端与所述第一电容的第一端相连；在所述第一高频半桥逆变电路中：第一、第二直流端分别连接至所述高压储能滤波器的正极和负极，第一交流端通过所述第二电感连接至所述第一高频隔离变压器单相交流源侧的其中一端，第二交流端连接至所述第一高频隔离变压器单相交流源侧的另外一端；在所述第二高频半桥逆变电路中：第一、第二直流端分别连接至所述高压储能滤波器的正极和负极，第一交流端通过所述第三电感连接至所述第二高频隔离变压器单相交流源侧的其中一端，第二交流端连接至所述第二高频隔离变压器单相交流源侧的另外一端；所述第一直流侧同步开关包括第一至第二开关管，所述第一、第二开关管的漏极分别连接至所述第一高频隔离变压器直流源侧的第一、第三端，所述第一、第二开关管的源极同时连接至所述直流源的负极；所述第二直流侧同步开关包括第三至第四开关管，所述第三、第四开关管的漏极分别连接至所述第二高频隔离变压器直流源侧的第一、第三端，所述第三、第四开关管的源极同时连接至所述直流源的负极；所述第一、第二高频隔离变压器直流源侧的第二端均连接至所述直流源的正极。
本发明的另一实施例提供一种前述的高频隔离交直流变换电路的控制方法，用于控制所述变换电路在整流模式和逆变模式之间切换工作，所述控制方法包括：当所述变换电路工作于整流模式时：控制所述高频全桥逆变电路工作于PFC整流状态并进行升压；控制所述第一、第二高频半桥逆变电路工作于逆变状态；若所述直流源的吸纳电流大于或等于额定电流的0.1倍，则：以PWM信号驱动所述第一至第四开关管开通，所述第一、第二开关管的开通时序以所述第一高频半桥逆变电路的开通时序的中心为基础进行偏移，所述第三、第四开关管的开通时序以所述第二高频半桥逆变电路的开通时序的中心为基础进行偏移，并且根据开关频率调整开通占空比大小以获取高效率；当所述变换电路工作于逆变模式时：根据所述直流源的电压：控制所述第一高频半桥逆变电路以所述第一直流侧同步开关的开通时序的中心为基础进行开通/关断，所述第二高频半桥逆变电路以所述第二直流侧同步开关的开通时序的中心为基础进行开通/关断，并且根据所述直流源的电压高低进行偏移及调整开通占空比大小以获取高效率。
本发明另一实施例还提供一种高频隔离交直流变换电路，包括单相交流源、直流源、第一至第三电容、高压储能滤波器、第一至第三高频全桥逆变电路、驱动电路、第一至第二电感、高频隔离变压器以及与所述驱动电路连接的控制电路；所述第一电容与所述单相交流源并联，所述第二电容与所述直流源并联；所述第一至第三高频全桥逆变电路均由开关管构成；在所述第一高频全桥逆变电路中：第一、第二交流端分别连接至所述第一电感的第二端和所述第一电容的第二端，第一、第二直流端分别连接至所述高压储能滤波器的正极和负极，所述第一电感的第一端与所述第一电容的第一端相连；在所述第二高频全桥逆变电路中：第一交流端通过所述第二电感连接至所述高频隔离变压器单相交流源侧的第一端，第二交流端通过所述第三电容连接至所述高频隔离变压器单相交流源侧的第二端，第一、第二直流端分别连接至所述高压储能滤波器的正极和负极；在所述第三高频全桥逆变电路中：第一、第二直流端分别连接至所述直流源的正极和负极，第一、第二交流端分别连接至所述高频隔离变压器直流源侧的第一端、第二端。
本发明另一实施例还提供一种高频隔离交直流变换电路，包括三相交流源、直流源、高压储能滤波器、第一至第三高频全桥逆变电路、驱动电路、谐振电感、谐振电容、直流侧滤波电容、高频隔离变压器以及与所述驱动电路连接的控制电路；所述三相交流源耦接至所述第一高频全桥逆变电路的交流端，所述第一高频全桥逆变电路的第一、第二直流端分别连接于所述高压储能滤波器的正极和负极，所述三相交流源和所述第一高频全桥逆变电路的交流端之间连接有LC滤波器；在所述第二高频全桥逆变电路中：第一交流端通过所述谐振电感连接至所述高频隔离变压器三相交流源侧的第一端，第二交流端通过所述谐振电容连接至所述高频隔离变压器三相交流源侧的第二端，第一、第二直流端分别连接至所述高压储能滤波器的正极和负极；在所述第三高频全桥逆变电路中：第一、第二直流端分别连接至所述直流源的正极和负极，第一、第二交流端分别连接至所述高频隔离变压器直流源侧的第一端、第二端。
本发明提供的上述高频隔离交直流变换电路及其控制方法，以设定的直流源参考电压为基准，根据对直流源的实时电压，自动切换工作于整流模式和逆变模式，并且在工作过程中根据直流源的实时电压及释放或吸收(逆变模式：释放；整流模式：吸收)电流大小，来改变直流侧的高频逆变桥(包括前述的第一、第 二高频半桥逆变电路)以及直流侧同步开关(包括前述的第一、第二直流侧同步开关)的频率和占空比大小，利用高频逆变桥拓扑的谐振状态实现软开关，降低了桥式逆变电路中各开关管的开通及关断应力，降低了开关损耗，有助于逆变电路的工作频率提高或者效率提高从而提高功率密度和减小体积；从而实现高功率密度，高效率以及高频电气隔离。此外，利用高频逆变桥的开通时序控制，实现宽范围直流电压的反向转换，从而使得该拓扑在蓄电池等较宽电压变化范围类似应用中获得高效率，比传统的变换器效率提高很多。
附图说明
图1是本发明实施例一提供的高频隔离交直流变换电路的示意图；
图2是图1的变换电路工作于整流模式时的PWM驱动时序图；
图3是图1的变换电路工作于逆变模式时的PWM驱动时序图；
图4是本发明实施例二提供的高频隔离交直流变换电路的示意图；
图5是本发明实施例三提供的高频隔离交直流变换电路的示意图。
附图标记说明：
V1：单相交流源
V2：直流源
C1～C6：电容
C：高压储能滤波器
L1～L3：电感
Q1～Q14：开关管
TRA：第一高频隔离变压器
TRB：第二高频隔离变压器
TR：高频隔离变压器
A1～A5：第一高频隔离变压器TRA的五个端
B1～B5：第二高频隔离变压器TRB的五个端
1、2、4、5：高频隔离变压器TR的四个端
V1a、V1b、V1c：三相交流源
L1a、L1b、L1c：电感
C1a、C1b、C1c：电容
具体实施方式
下面结合附图和具体的实施方式对本发明作进一步说明。
实施例一
本实施例提供一种如图1所示的高频隔离交直流变换电路，包括单相交流源V1、直流源V2、第一电容C1、第二电容C2、高压储能滤波器C、高频全桥逆变电路300、第一高频半桥逆变电路100、第二高频半桥逆变电路200、驱动电路、第一电感L1、第二电感L2、第三电感L3、第一高频隔离变压器TRA、第二高频隔离变压器TRB、第一直流侧同步开关400、第二直流侧同步开关500以及与所述驱动电路连接的控制电路；所述第一电容C1与所述单相交流源V1并联，所述第二电容C2与所述直流源V2并联；所述高频全桥逆变电路300、第一至第二高频半桥逆变电路100、200均由开关管构成。
如图1所示，所述高频全桥逆变电路300具有四个输入/输出端，分别为两个交流端(用于输入或输出交流信号)以及两个直流端(用于输入或输出直流信号)，其中一个交流端连接于第一电感L1的第二端，另一个交流端连接至第一电容C1的第二端，第一电感L1的第一端与第一电容C1的第一端相连；两个直流端分别连接至高压储能滤波器C的正极+BUS和负极-BUS。在一种具体的例子中，所述高频全桥逆变电路300包括四个开关管Q5～Q8，其中开关管Q5的源极和开关管Q7的漏极相连并引出形成一个交流端以连接至第一电感L1的第二端，开关管Q6的源极和开关管Q8的漏极相连并引出形成另一个交流端以连接至第一电容C1的第二端，开关管Q5、Q6的漏极相连并引出形成一个直流端而连接到高压储能滤波器C的正极+BUS，开关管Q7、Q8的源极相连并引出另一个直流端而连接至高压储能滤波器C的负极-BUS。当所述变换电路工作于整流模式时，所述高频全桥逆变电路300工作于PFC(功率因数矫正)整流模式并用作升压开关，两个交流端为信号输入端，两个直流端为信号输出端，将经过LC滤波器(由第一电容C1和第一电感L1构成)的交流信号变换为直流信号；而当所述变换电路工作于逆变模式时，所述高频全桥逆变电路300用作高频逆变开关，两个直流端为信号输入端，两个交流端为信号输出端，将来自第一、第二高频半桥逆变电路的输出端的直流信号变换为交流信号。需要说明：所述高频全桥逆变电路300的工作频率在30KHz以上。
如图1所示，所述第一高频半桥逆变电路100具有四个输入/输出端，分别为两个交流端(用于输入或输出交流信号)以及两个直流端(用于输入或输出直流信号)，两个直流端分别连接至所述高压储能滤波器C的正极+BUS和负极-BUS，其中一个交流端通过第二电感L2连接至第一高频隔离变压器TRA单相交流源侧(此处的单相交流源侧指的是向交流侧输出信号或将来自交流侧的信号耦合过去的一侧)的其中一端A4，另一交流端连接至第一高频隔离变压器TRA单相交流源侧的另外一端A5。具体地，所述第一高频半桥逆变电路100包括两个开关管Q9、Q10以及两个电容C3、C4，其中电容C3的第一端与开关管Q9的漏极相连并引出形成其中一个直流端(该直流端即连接至高压储能滤波器C的正极+BUS)，电容C3的第二端连接至电容C4的第一端，电容C4的第二端与开关管Q10的源极相连并引出形成另一个直流端(该直流端连接至高压储能滤波器C的负极-BUS)，开关管Q9的源极与开关管Q10的漏极相连并引出形成一个交流端(该交流端通过串联第二电感L2而连接到第一高频隔离变压器TRA的单相交流源侧的第一端A4)，电容C3的第二端(等效于电容C4的第一端)引出形成另一交流端连接至第一高频隔离变压器TRA的单相交流源侧的第二端A5。
如图1所示，所述第二高频半桥逆变电路200的连接和工作原理与第一高频半桥逆变电路100相同，包括两个开关管Q11、Q12以及两个电容C5、C6，两个直流端分别连接至所述高压储能滤波器C的正极+BUS和负极-BUS，其中一个交流端通过第三电感L3连接至第二高频隔离变压器TRB单相交流源侧的其中一端B4，另一交流端连接至第二高频隔离变压器TRB单相交流源侧的另外一端B5。其中电容C5的第一端与开关管Q11的漏极相连并引出形成其中一个直流端，电容C5的第二端连接至电容C6的第一端，电容C6的第二端与开关管Q12的源极相连并引出形成另一个直流端，开关管Q11的源极与开关管Q12的漏极相连并引出形成一个交流端，电容C5的第二端引出形成另一交流端连接至第二高频隔离变压器TRB的交流源侧的第二端B5。
如图1所示，第一直流侧同步开关400包括两个开关管Q1、Q2，开关管Q1、Q2的漏极分别连接至第一高频隔离变压器TRA在直流源侧的第一、第三端A1、A3，两者的源极同时连接至直流源V2的负极；第二直流侧同步开关500 的连接和工作原理与第一直流侧同步开关400相同：开关管Q3、Q4的漏极分别连接至第二高频隔离变压器TRB在直流源侧的第一、第三端B1、B3，两者源极同时连接至直流源V2的负极。另，第一、第二高频隔离变压器TRA、TRB的直流源侧的第二端A2、B2均连接至直流源V2的正极。
需要说明，第一、第二高频半桥逆变电路以及第一、第二直流侧同步开关的工作频率在100KHz以上。
在优选的实施方式中，第一、第二高频半桥逆变电路中的四个电容C3～C6为高频无极电容。
在优选的实施方式中，高压储能滤波器C为电解电容，所述第一、第二高频隔离变压器TRA、TRB直流源侧的线圈匝数低于4匝，且具有正常的漏感。直流侧的同步开关无需外加续流滤波电感。所述变换电路的最佳应用是当直流源V2的幅值高于8V且低于45V，以及输出功率在200W至2KW之间的时候。
本实施例还提供上述变换电路的控制方法，用于根据直流源V2的实时电压值来切换电路的工作模式(整流模式或逆变模式)，该控制方法包括：当所述变换电路工作于整流模式时：控制所述高频全桥逆变电路工作于PFC整流状态并进行升压；控制所述第一、第二高频半桥逆变电路工作于逆变状态；若所述直流源的吸纳电流大于或等于额定电流的0.1倍，则：以PWM信号驱动所述第一至第四开关管开通，所述第一、第二开关管的开通时序以所述第一高频半桥逆变电路的开通时序的中心为基础进行偏移，所述第三、第四开关管的开通时序以所述第二高频半桥逆变电路的开通时序的中心为基础进行偏移，并且根据开关频率调整开通占空比大小以获取高效率；当所述变换电路工作于逆变模式时：根据所述直流源的电压：控制所述第一高频半桥逆变电路以所述第一直流侧同步开关的开通时序的中心为基础进行开通/关断，所述第二高频半桥逆变电路以所述第二直流侧同步开关的开通时序的中心为基础进行开通/关断，并且根据所述直流源的电压高低进行偏移及调整开通占空比大小以获取高效率。
下面以图1的电路为例对上述控制方法进行更进一步的说明：
控制器根据预设的电压值和直流源V2的实时电压值的大小关系，判断所述变换电路应当工作于整流模式还是逆变模式。
假设，当控制器判断出所述变换电路需工作于整流模式，即电能从交流源侧 传送到直流源侧。此时：高频全桥逆变电路300工作在PFC整流状态，将交流输入电压变换为一个稳定值；第一、第二高频半桥逆变电路工作于逆变状态，采用PWM信号驱动开关管Q9～Q12，将其直流端输入的直流电压逆变成高频脉冲电压(交流信号)，再经过第一、第二高频隔离变压器的耦合，传送到第一、第二直流侧同步开关，根据直流源的电压大小以及吸收电流(或称吸纳电流)的大小，判断是否需开通开关管Q1～Q4，若直流源吸收电流小于额定电流的0.1倍，则开关管Q1～Q4不开通，工作于寄生二极管自然整流的状态，若直流源吸收电流在额定电流的0.1倍以上，则控制开关管Q1～Q4开通，且开通时序参考图2，开关管Q1、Q2的开通时序以开关管Q9、Q10的开通时序中心为基础向后偏移1/4个工作周期，同时开关管Q9、Q10之间留有一定的死区时间防止直通短路，同样地，开关管Q3、Q4的开通时序以开关管Q11、Q12的开通时序中心为基础向后偏移1/4，同时开关管Q11、Q12之间留有一定的死区时间。就第一、第二高频半桥逆变电路100、200的控制过程而言，由于电容C3～C6的谐振作用，因此可以实现谐振变换过程，在全工作范围内，根据负载端(整流模式下直流源即为负载端)的电压大小和吸收电流大小来改变工作频率或者占空比，吸收电流越大，占空比越大，开关频率越高，中心偏移越多，从而保证开关管Q9～Q12可以获得软开关，实现变换电路的高效率和高功率密度。
假设，当控制器判断出所述变换电路需工作于逆变模式，即电能从直流源侧传送到交流源侧。此时：开关管Q1～Q4开通，开通时序参考图3，使第一、第二直流侧同步开关400、500工作于高频逆变状态，将直流源的直流电压信号变换为交流信号，经过第一、第二高频隔离变压器的耦合，将交流信号传送到第一、第二高频半桥逆变电路100、200进行整流和升压，开关管Q9～Q12的开通时序参考图3，开关管Q1与Q2(Q3与Q4)之间留有一定的死区，此外，开关管Q1、Q2的开通时序以开关管Q9、Q10的开通时序中心为基础向前偏移1/4个工作周期，开关管Q3、Q4的开通时序以开关管Q11、Q12的开通时序中心为基础向前偏移1/4个工作周期。此时第一、第二直流侧同步开关400、500类似于传统的推挽式结构，但由于变压器中直流源侧存在正常的漏感，因此直流信号通过第一、第二直流侧同步开关后是有一定缓慢上升斜率的，避免的常规的推挽。
实施例二
本实施例提供一种与实施例一类似的高频隔离交直流变换电路，如图4所示，与实施例一的区别在于：将实施例一中的第一、第二高频半桥逆变电路100、200采用全桥逆变电路600替代，同时只采用一个高频隔离变压器TR，并且高频隔离变压器TR的直流源侧减少一个线圈，将实施例一中的第一、第二直流侧同步开关400、500采用全桥逆变电路700替代。在本实施例中，全桥逆变电路600包括开关管Q9～Q12，开关管Q9、Q10的漏极相连后引出形成一个直流端而连接到高压储能滤波器C的正极+BUS，开关管Q11、Q12的源极相连后引出形成另一个直流端而连接到高压储能滤波器C的负极-BUS，开关管Q9、Q10的源极分别对应连接到开关管Q11、Q12的漏极，并且分别引出形成两交流端，从开关管Q10的源极引出的交流端通过串联电感L2连接到高频隔离变压器TR的交流源侧的第一端4，从开关管Q9的源极引出的交流端通过串联电容C3连接到高频隔离变压器TR的交流源侧的第一端5。高频全桥逆变电路700包括开关管Q1～Q4，开关管Q1、Q2的漏极相连后引出形成一个直流端而连接到直流源V2的正极，开关管Q3、Q4的源极相连后引出形成另一个直流端而连接到直流源V2的负极，开关管Q1、Q2的源极分别对应连接到开关管Q3、Q4的漏极，并且分别引出形成两交流端，从开关管Q2的源极引出的交流端连接到高频隔离变压器TR的直流源侧的第一端1，从开关管Q1的源极引出的交流端连接到高频隔离变压器TR的直流源侧的第二端2。
本实施例中的电容C3优选采用高频无极电容。
本实施例的变换电路的控制方法与实施例一相同，在此不再赘述。本实施例提供的图4的变换电路，直流源V2的电压较高时同步整流管的应力可以降低，同时当直流源V2的电流较大时，由于变压器的直流源侧线圈可以减少一个从而线圈线径可以较大，以减少损耗。本实施例提供的所述变换电路的最佳应用是当直流源V2的幅值高于45V，以及输出功率在1KW至5KW时。
实施例三
本实施提供一种如图5所示的高频隔离交直流变换电路，在本实施例中，将单相交流源替换为三相交流源V1a、V1b、V1c，并且各相都连接有LC滤波器(分别为电感L1a、电容C1a，电感L1b、电容C1b，以及电感L1c、电容C1c)。将实施例二中的高频全桥逆变电路(包括开关管Q5～Q8)采用三相全桥逆变电路 路800(图5中的开关管Q5～Q8、Q13、Q14)替代。本实施例中的电容C3与实施例二中的电容C3一样，优选采用高频无极电容。本实施例由于采用三相交流源，可以满足功率较大场合或对交流侧配电平衡度要求很高的场合，本实施例的变换电路的控制方法与实施例一相同，在此不再赘述。本实施例提供的所述变换电路的最佳应用是当直流源V2的幅值高于80V，以及输出功率在3KW以上时。
以上内容是结合具体的优选实施方式对本发明所作的进一步详细说明，不能认定本发明的具体实施只局限于这些说明。对于本发明所属技术领域的技术人员来说，在不脱离本发明构思的前提下，还可以做出若干等同替代或明显变型，而且性能或用途相同，都应当视为属于本发明的保护范围。

Claims (10)

  1. 一种高频隔离交直流变换电路，其特征在于：包括单相交流源(V1)、直流源(V2)、第一至第二电容、高压储能滤波器(C)、高频全桥逆变电路、第一至第二高频半桥逆变电路、驱动电路、第一至第三电感、第一至第二高频隔离变压器、第一至第二直流侧同步开关以及与所述驱动电路连接的控制电路；所述第一电容(C1)与所述单相交流源并联，所述第二电容(C2)与所述直流源并联；所述高频全桥逆变电路、第一至第二高频半桥逆变电路均由开关管构成；
    在所述高频全桥逆变电路中：第一、第二交流端分别连接至所述第一电感(L1)的第二端和所述第一电容(C1)的第二端，第一、第二直流端分别连接至所述高压储能滤波器(C)的正极(+BUS)和负极(-BUS)，所述第一电感(L1)的第一端与所述第一电容(C1)的第一端相连；
    在所述第一高频半桥逆变电路中：第一、第二直流端分别连接至所述高压储能滤波器(C)的正极(+BUS)和负极(-BUS)，第一交流端通过所述第二电感(L2)连接至所述第一高频隔离变压器(TRA)单相交流源侧的其中一端(A4)，第二交流端连接至所述第一高频隔离变压器(TRA)单相交流源侧的另外一端(A5)；
    在所述第二高频半桥逆变电路中：第一、第二直流端分别连接至所述高压储能滤波器(C)的正极(+BUS)和负极(-BUS)，第一交流端通过所述第三电感(L2)连接至所述第二高频隔离变压器(TRB)单相交流源侧的其中一端(B4)，第二交流端连接至所述第二高频隔离变压器(TRB)单相交流源侧的另外一端(B5)；
    所述第一直流侧同步开关包括第一至第二开关管，所述第一、第二开关管(Q1、Q2)的漏极分别连接至所述第一高频隔离变压器(TRA)直流源侧的第一、第三端(A1、A3)，所述第一、第二开关管(Q1、Q2)的源极同时连接至所述直流源(V2)的负极；
    所述第二直流侧同步开关包括第三至第四开关管，所述第三、第四开关管(Q3、Q4)的漏极分别连接至所述第二高频隔离变压器(TRB)直流源侧的第一、第三端(B1、B3)，所述第三、第四开关管(Q3、Q4)的源极同时连接至所述直流源(V2)的负极；
    所述第一、第二高频隔离变压器(TRA、TRB)直流源侧的第二端(A2、B2) 均连接至所述直流源(V2)的正极。
  2. 如权利要求1所述的高频隔离交直流变换电路，其特征在于：所述第一高频半桥逆变电路包括第三至第四电容(C3、C4)，所述第二高频半桥逆变电路包括第五至第六电容(C5、C6)，并且，所述第三至第六电容(C3～C6)为高频无极电容。
  3. 如权利要求1所述的高频隔离交直流变换电路，其特征在于：所述第一、第二高频隔离变压器(TRA、TRB)直流源侧的线圈匝数低于4匝，且具有漏感。
  4. 一种如权利要求1所述的高频隔离交直流变换电路的控制方法，其特征在于：用于控制所述变换电路在整流模式和逆变模式之间切换工作，包括：
    当所述变换电路工作于整流模式时：控制所述高频全桥逆变电路工作于PFC整流状态并进行升压；控制所述第一、第二高频半桥逆变电路工作于逆变状态；若所述直流源的吸纳电流大于或等于额定电流的0.1倍，则：以PWM信号驱动所述第一至第四开关管开通，所述第一、第二开关管的开通时序以所述第一高频半桥逆变电路的开通时序的中心为基础进行偏移，所述第三、第四开关管的开通时序以所述第二高频半桥逆变电路的开通时序的中心为基础进行偏移，并且根据开关频率调整开通占空比大小以获取高效率；
    当所述变换电路工作于逆变模式时：根据所述直流源的电压：控制所述第一高频半桥逆变电路以所述第一直流侧同步开关的开通时序的中心为基础进行开通/关断，所述第二高频半桥逆变电路以所述第二直流侧同步开关的开通时序的中心为基础进行开通/关断，并且根据所述直流源的电压高低进行偏移及调整开通占空比大小以获取高效率。
  5. 如权利要求4所述的控制方法，其特征在于：所述变换电路工作于所述整流模式和所述逆变模式时，所述第一直流侧同步开关与所述第一高频半桥逆变电路的时序相位相差1/4个工作周期，所述第二直流侧同步开关与所述第二高频半桥逆变电路的时序相位相差1/4个工作周期。
  6. 如权利要求4所述的控制方法，其特征在于：当所述变换电路工作于整流模式时，若所述直流源的吸纳电流小于所述额定电流的0.1倍，则控制所述第一至第四开关管关断以使所述第一、第二直流侧同步开关工作于二极管整流状态。
  7. 一种高频隔离交直流变换电路，其特征在于：包括单相交流源(V1)、直流源(V2)、第一至第三电容、高压储能滤波器(C)、第一至第三高频全桥逆变电路、驱动电路、第一至第二电感、高频隔离变压器(TR)以及与所述驱动电路连接的控制电路；所述第一电容(C1)与所述单相交流源并联，所述第二电容(C2)与所述直流源并联；所述第一至第三高频全桥逆变电路均由开关管构成；
    在所述第一高频全桥逆变电路中：第一、第二交流端分别连接至所述第一电感(L1)的第二端和所述第一电容(C1)的第二端，第一、第二直流端分别连接至所述高压储能滤波器(C)的正极(+BUS)和负极(-BUS)，所述第一电感(L1)的第一端与所述第一电容(C1)的第一端相连；
    在所述第二高频全桥逆变电路中：第一交流端通过所述第二电感(L2)连接至所述高频隔离变压器(TR)单相交流源侧的第一端(4)，第二交流端通过所述第三电容(C3)连接至所述高频隔离变压器(TR)单相交流源侧的第二端(5)，第一、第二直流端分别连接至所述高压储能滤波器(C)的正极(+BUS)和负极(-BUS)；
    在所述第三高频全桥逆变电路中：第一、第二直流端分别连接至所述直流源的正极和负极，第一、第二交流端分别连接至所述高频隔离变压器(TR)直流源侧的第一端(1)、第二端(2)。
  8. 如权利要求7所述的高频隔离交直流变换电路，其特征在于：所述第三电容(C3)为高频无极电容。
  9. 一种高频隔离交直流变换电路，其特征在于：包括三相交流源、直流源(V2)、高压储能滤波器(C)、第一至第三高频全桥逆变电路、驱动电路、谐振电感(L2)、谐振电容(C3)、直流侧滤波电容(C2)、高频隔离变压器(TR)以及与所述驱动电路连接的控制电路；所述三相交流源耦接至所述第一高频全桥逆变电路的交流端，所述第一高频全桥逆变电路的第一、第二直流端分别连接于所述高压储能滤波器(C)的正极和负极，所述三相交流源和所述第一高频全桥逆变电路的交流端之间连接有LC滤波器；
    在所述第二高频全桥逆变电路中：第一交流端通过所述谐振电感(L2)连接至所述高频隔离变压器(TR)三相交流源侧的第一端(4)，第二交流端通过所 所述谐振电容(C3)连接至所述高频隔离变压器(TR)三相交流源侧的第二端(5)，第一、第二直流端分别连接至所述高压储能滤波器(C)的正极(+BUS)和负极(-BUS)；
    在所述第三高频全桥逆变电路中：第一、第二直流端分别连接至所述直流源的正极和负极，第一、第二交流端分别连接至所述高频隔离变压器(TR)直流源侧的第一端(1)、第二端(2)。
  10. 如权利要求9所述的高频隔离交直流变换电路，其特征在于：所述谐振电容(C3)为高频无极电容。
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