WO2015056491A1 - Dispositif de conversion de puissance et procédé de conversion de puissance - Google Patents

Dispositif de conversion de puissance et procédé de conversion de puissance Download PDF

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Publication number
WO2015056491A1
WO2015056491A1 PCT/JP2014/073171 JP2014073171W WO2015056491A1 WO 2015056491 A1 WO2015056491 A1 WO 2015056491A1 JP 2014073171 W JP2014073171 W JP 2014073171W WO 2015056491 A1 WO2015056491 A1 WO 2015056491A1
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Prior art keywords
voltage
power
circuit
phase
voltage conversion
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PCT/JP2014/073171
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English (en)
Japanese (ja)
Inventor
祐輔 図子
ジョン シー クレア
アラン ワトソン
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日産自動車株式会社
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Priority to JP2015542538A priority Critical patent/JP6168155B2/ja
Publication of WO2015056491A1 publication Critical patent/WO2015056491A1/fr

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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
    • H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
    • H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/483—Converters with outputs that each can have more than two voltages levels
    • H02M7/49—Combination of the output voltage waveforms of a plurality of converters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
    • H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
    • H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/4807—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode having a high frequency intermediate AC stage
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
    • H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
    • H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/4815—Resonant converters
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes

Definitions

  • the present invention relates to a power conversion device and a power conversion method for converting DC power output from a DC power source into AC power.
  • a distributed module power supply has been proposed as a power supply device for driving a load such as an AC motor (see Patent Document 1).
  • the distributed module power supply includes a plurality of DC power supplies, and converts the DC voltage output from each DC power supply into an AC voltage using an inverter. And the alternating voltage output from each inverter is added in series, the alternating voltage of a desired level is produced
  • a conventional power conversion device requires a large-capacitance capacitor as a smoothing capacitor, which increases the overall size of the device.
  • the present invention can cancel the ripple currents of the respective phases, so that the smoothing capacitor can be reduced and the apparatus can be reduced in size and power conversion method.
  • the purpose is to provide.
  • the power conversion device is a power conversion device that converts a DC voltage into an AC voltage and supplies the converted AC voltage to a load having a plurality of phases, the plurality of DC power supplies, A smoothing capacitor connected in parallel to each of a plurality of DC power supplies and a number of phases corresponding to each of the plurality of DC power supplies so as to cancel each other out ripple currents generated when converting DC voltage to AC voltage
  • a plurality of voltage conversion means for converting a DC voltage from the connected DC power supply to an AC voltage; a control means for controlling the plurality of voltage conversion means; and an output of the voltage conversion means connected to a different DC power supply.
  • a plurality of output terminals that are connected in series, add the AC voltage from each voltage conversion means, and output to each phase of the load, respectively.
  • a smoothing capacitor is connected in parallel to each of a plurality of DC power supplies, and a plurality of voltage conversion means are connected in parallel to each of the plurality of DC power supplies by the number of the plurality of phases.
  • the output of the voltage conversion means connected to the different DC power supply is connected in series, the DC voltage is converted into an AC voltage, and the power converter that supplies the converted AC voltage to a load having a plurality of phases is used.
  • a power conversion method in which a plurality of voltage conversion means converts a DC voltage from a plurality of DC power supplies into an AC voltage, and an AC voltage from a voltage conversion means connected to a different DC power supply is added in series. Output to each phase of the load, and for each voltage conversion means connected in parallel, cancel each other ripple currents generated when the DC voltage is converted into the AC voltage. And wherein the door.
  • FIGS. 7A to 7C are timing charts showing an example of the ripple current waveform of each phase, and FIG.
  • FIG. 7D shows an example of the waveform obtained by adding the ripple current of each phase. It is a timing chart. It is a graph showing the relationship between the frequency and gain which concern on embodiment of this invention. It is the schematic for demonstrating the feedforward control of the DC / DC converter which concerns on embodiment of this invention. It is a timing chart which shows an example of the signal waveform in PWM of the level shift system which concerns on the 1st modification of embodiment of this invention. It is a circuit diagram which shows an example of the power converter device which concerns on the 2nd modification of embodiment of this invention. It is a circuit diagram which shows an example of the DC / DC converter which concerns on the 3rd modification of embodiment of this invention. It is a circuit diagram which shows an example of the DC / DC converter which concerns on the 4th modification of embodiment of this invention. It is a circuit diagram which shows an example of the DC / DC converter which concerns on the 5th modification of embodiment of this invention.
  • FIG. 1 a device that drives a motor M1 using a load as a three-phase AC motor (hereinafter simply referred to as “motor”) M1 as a load.
  • motor a three-phase AC motor
  • the power conversion device according to the embodiment of the present invention drives motor M1 by supplying AC voltages that are 120 ° different from each other to each of a plurality of phases (U phase, V phase, W phase) of motor M1. .
  • the power conversion device is arranged in a row direction and a column direction with a plurality (n; n is a natural number of 2 or more) of DC power supplies VB1, VB2, VB3.
  • a control device (control means) 31 for controlling the operation.
  • a plurality (n) of voltage conversion modules 11-1, 11-2,... 11-n arranged in the same column supply an AC voltage to the U phase.
  • a plurality (n) of voltage conversion modules 12-1, 12-2,... 12-n arranged in the same column supply an AC voltage to the V phase.
  • a plurality (n) of voltage conversion modules 13-1, 13-2,... 13-n arranged in the same column supply an AC voltage to the W phase.
  • the voltage conversion modules 11-1, 12-1, and 13-1 arranged in the same row are connected in parallel to the DC power supply VB1 and commonly use the DC power supply VB1.
  • the voltage conversion modules 11-2, 12-2, and 13-2 arranged in the same row are connected in parallel to the DC power supply VB2, and use the DC power supply VB2 in common.
  • the voltage conversion modules 11-n, 12-n, 13-n arranged in the same row are connected in parallel to the DC power source VBn, and commonly use the DC power source VBn.
  • the uppermost voltage conversion modules 11-1, 12-1, and 13-1 are set to the high potential side, and the lowermost voltage conversion modules 11-n, 12-n, and 13-n are set to the low potential side.
  • the potential is set step by step.
  • the output terminals of the lowest voltage conversion modules 11-n, 12-n, 13-n are connected to the reference potential.
  • the outputs of the voltage conversion modules 11-1 to 11-n arranged in the same column are connected in series.
  • the AC voltages output from the voltage conversion modules 11-1 to 11-n are added in series and output to the U phase via the output terminal N1.
  • the outputs of the voltage conversion modules 12-1 to 12-n arranged in the same column are connected in series.
  • the AC voltages output from the voltage conversion modules 12-1 to 12-n are added in series and output to the V phase via the output terminal N2.
  • the outputs of the voltage conversion modules 13-1 to 13-n arranged in the same column are connected in series.
  • the AC voltages output from the voltage conversion modules 13-1 to 13-n are added in series and output to the W phase via the output terminal N3.
  • one voltage conversion module 11-1 among the voltage conversion modules 11-1 to 11-n, 12-1 to 12-n, and 13-1 to 13-n will be described as a representative.
  • the other voltage conversion modules 11-2 to 11-n, 12-1 to 12-n, and 13-1 to 13-n have the same configuration as that of the voltage conversion module 11-1.
  • the voltage conversion module 11-1 includes a DC / DC converter (transformer means) 21 whose input side is connected to the DC power source VB1, an inverter circuit 22 whose input side is connected to the DC / DC converter 21, and a positive electrode of the DC power source VB1.
  • a harmonic removing capacitor C1 connected between the negative electrodes and a smoothing capacitor C2 connected between the DC / DC converter 21 and the inverter circuit 22 are provided.
  • the harmonic removing capacitor C1 removes harmonics of the DC voltage from the DC power supply VB1.
  • the smoothing capacitor C ⁇ b> 2 suppresses voltage fluctuations that occur due to the switching operation of the inverter circuit 22 and smoothes the output voltage of the DC / DC converter 21.
  • the smoothing capacitor C2 may not be included in the voltage conversion module 11-1, but may be provided separately from the voltage conversion module 11-1.
  • the DC / DC converter 21 boosts or steps down the DC voltage from the DC power supply VB1.
  • the DC / DC converter 21 includes a primary circuit (full bridge (H bridge) circuit) 21a having four switching elements Q11 to Q14 and four switching elements Q21 to Q24, as shown in FIG.
  • Such a DC / DC converter 21 is also called a dual active bridge (DAB) circuit.
  • DAB dual active bridge
  • the switching elements Q11 to Q14 and Q21 to Q24 are constituted by, for example, insulated gate bipolar transistors (IGBT).
  • IGBT insulated gate bipolar transistors
  • the transformer TR1 is an insulating transformer that boosts or steps down the DC voltage from the primary circuit 21a and transmits it to the secondary circuit 21b, and insulates the primary circuit 21a and the secondary circuit 21b.
  • the transformer TR1 has a transformation ratio of m: n (m and n are integers).
  • the transformer TR1 may have a transformation ratio of 1: 1. In other words, the DC voltage may be transmitted as it is without being transformed.
  • the DC / DC converter 21 is an insulation type converter having an insulation transformer TR1
  • the control device 31 includes a primary side voltage detection unit 33, a secondary side voltage detection unit 34, a secondary side current detection unit 36, a main control unit 32, and a drive circuit 35.
  • the primary side voltage detector 33 detects the voltage V1 on the primary circuit 21a side and outputs it to the main controller 32.
  • the secondary side voltage detector 34 detects the voltage V ⁇ b> 2 on the secondary circuit 21 b side and outputs it to the main controller 32.
  • the main control unit 32 is configured as an integrated computer including a central processing unit (CPU) and storage means such as a RAM, a ROM, and a hard disk.
  • CPU central processing unit
  • storage means such as a RAM, a ROM, and a hard disk.
  • the main control unit 32 observes the input voltage V1 and the output voltage V2 so as to follow the command voltage value (target output voltage value) Vref by the master controller 41, which is the host device, and switches the switching elements Q11 to Q14, Q21 to Q24.
  • the on / off command signal is output to the drive circuit 35.
  • the drive circuit 35 outputs drive signals to the control terminals (bases) of the switching elements Q11 to Q14 and Q21 to Q24 based on the on / off command signal from the main control unit 32.
  • the switching elements Q11 and Q14 on the primary circuit 21a side of the DC / DC converter 21 and the switching elements Q12 and Q13 are alternately turned on and off periodically based on a drive signal from the drive circuit 35. Further, the switching elements Q21 and Q24 on the secondary circuit 21b side of the DC / DC converter 21 and the switching elements Q22 and Q23 are alternately turned on and off periodically based on a drive signal from the drive circuit 35.
  • the inverter circuit 22 is a full bridge (H bridge) circuit having four switching elements Q31 to Q34.
  • the switching elements Q31 to Q34 are composed of, for example, an IGBT.
  • a diode is connected between the two terminals of the switching elements Q31 to Q34.
  • the output of the inverter circuit 22 of the voltage conversion module 11-1 is connected in series with the output of the inverter circuits of the voltage conversion modules 11-2 to 11-n arranged in the same column as the voltage conversion module 11-1. .
  • the inverter circuit 22 is a PWM circuit that turns on / off the switching elements Q31 to Q34 by performing phase shift type pulse width modulation (PWM).
  • PWM phase shift type pulse width modulation
  • the drive signals are compared by comparing the signal values of the carrier waves W1 to W6 and the signal wave (sine wave) W0 while shifting the phases of the carrier waves (triangular waves) W1 to W6. Is generated.
  • the switching elements Q31 and Q34 are turned on when the carrier waves W1 to W6 are smaller than the signal wave W0, and the switching elements Q32 and Q33 are turned on when the carrier waves W1 to W6 are larger than the signal wave W0.
  • the switching frequency of the DC / DC converter 21 is set higher than the switching frequency of the inverter circuit 22.
  • the ripple current Iu As shown in FIG. 4, in the voltage conversion module 11-1, voltage fluctuation occurs due to the switching operation of the inverter circuit 22 and the like, and a ripple current Iu corresponding to the voltage fluctuation that cannot be absorbed by the smoothing capacitor C2 flows.
  • the ripple current Iu is transmitted from the secondary circuit 21b side to the primary circuit 21a side via the transformer TR1.
  • the ripple current Iu has a pulse waveform as shown in FIG.
  • the fundamental frequency of the ripple waveform of the ripple current is the switching frequency of the inverter circuit 22.
  • the amplitude of the ripple waveform of the ripple current oscillates (changes) at the phase current frequency.
  • the maximum value of the amplitude of the ripple waveform of the ripple current is the maximum value Imax of the phase current.
  • the ripple currents Iu, Iv, and Iw are transmitted from the secondary circuit 21b side to the transformer TR1. Are respectively transmitted to the primary circuit 21a side.
  • the periods are 120 ° out of phase with each other.
  • the DC power supply VB1 is shared by the U-phase, V-phase, and W-phase voltage conversion modules 11-1, 12-1, and 13-1, as shown in FIG.
  • the phase current fundamental wave components of the ripple currents Iu, Iv, and Iw flowing in the respective phases are added and canceled.
  • the switching frequency fs of the inverter circuit 22 is always higher than the maximum value fp of the phase current frequency.
  • the ripple currents Iu, Iv, and Iw themselves contain a higher order frequency than the switching frequency of the inverter circuit 22, but transmit the phase current frequency component from the secondary circuit 21b side of the DC / DC converter 21 to the primary circuit 21a side. Includes only the fundamental wave component of the switching frequency fs of the inverter circuit 22. Therefore, the cut-off frequency of the DC / DC converter 21 may be equal to or higher than the switching frequency fs of the inverter circuit 22. Therefore, the voltage control band of the DC / DC converter 21 is set to a frequency higher than the switching frequency fs of the inverter circuit 22.
  • the final output of the main control unit 32 is a PWM signal.
  • the PWM signal is a square wave with a duty ratio of approximately 50%, the phase of which is shifted by ⁇ on the primary circuit 21a side and the secondary circuit 21b side.
  • the PI controller included in the main control unit 32 is configured so that the voltage V2 on the secondary circuit 21b side follows the command voltage value Vref while referring to the voltage V2 on the secondary circuit 21b side and the voltage V1 on the primary circuit 21a side.
  • the phase difference ⁇ is controlled.
  • the average value of current i 2 of the secondary circuit 21b side can be obtained by the following equation (1).
  • phase difference (shift amount) ⁇ for achieving the actual current i 2 on the secondary circuit 21b side can be obtained by the following equation (2).
  • the nominal value i 2 (nom) of the current on the secondary circuit 21b side is used as in equations (3) and (4), and the phase shift amount ⁇ (nom) is set.
  • a PWM signal is generated by adding the phase shift amount ⁇ (nom) obtained by the FF control term to the output of the PI controller.
  • the plurality of voltage conversion modules 11-1 to 11-n, 12-1 to 12-n, and 13-1 to 13-n shown in FIG. 1 convert the DC voltages from the plurality of DC power sources VB1 to VBn to AC. Convert to voltage. Specifically, in each of the voltage conversion modules 11-1 to 11-n, 12-1 to 12-n, and 13-1 to 13-n, the DC / DC converter 21 is based on a control signal from the control device 31. By switching the switching elements Q11 to Q14 and Q21 to Q24, the DC voltage from the DC power sources VB1 to VBn is transformed. Further, the inverter circuit 22 converts the DC voltage output from the DC / DC converter 21 into an AC voltage by switching the switching elements Q31 to Q34 based on a control signal from the control device 31.
  • AC voltages output from the voltage conversion modules 11-1 to 11-n are added in series and output to the U phase. Also, the AC voltages output from the voltage conversion modules 12-1 to 12-n are added in series and output to the V phase. Further, AC voltages output from the voltage conversion modules 13-1 to 13-n are added in series and output to the U phase.
  • the U-phase, V-phase, and W-phase voltage conversion modules 11-1, 12-1, and 13-1 arranged in the same row are connected in common to the DC power supply VB1, so that the ripple current of each phase is obtained.
  • the phase current fundamental wave components of Iu, Iv, and Iw can be added together and canceled.
  • the phase current fundamental wave components of the ripple currents Iu, Iv, and Iw of each phase can be added and canceled.
  • the U-phase, V-phase, and W-phase voltage conversion modules 11-1, 12-1, and 13-1 arranged in the same row are connected to the DC power supply VB1.
  • the phase current fundamental wave components of the ripple currents Iu, Iv, Iw of each phase can be added together and canceled. Therefore, in each of the voltage conversion modules 11-1 to 11-n, 12-1 to 12-n, and 13-1 to 13-n, the smoothing capacitor C2 can be reduced, and the overall size of the device can be reduced. be able to.
  • the U-phase, V-phase, and W-phase voltage conversion modules 11-1, 12-1, and 13-1 arranged in the same row are commonly connected to the DC power supply VB1, thereby reducing the power between the phases. Even if the balance occurs, the energy consumption of the DC power supply VB1 can be made uniform.
  • the voltage conversion modules 11-1, 12-1, 13-1 of each phase can be insulated from each other, and the voltage conversion modules 11-1, 12-1 and 13-1 can be connected to a common DC power supply VB1.
  • the use of DAB as the DC / DC converter 21 can reduce the size and increase the efficiency of the apparatus. Further, by making the switching frequency of DAB higher than the switching frequency of the inverter circuit 22, the responsiveness of DAB can be improved. Further, by making the DAB cutoff frequency higher than the switching frequency of the inverter circuit 22, the responsiveness of the DAB can be improved. Further, DAB responsiveness can be improved by feedforward control of DAB. Further, by controlling the inverter circuit 22 with the phase shift type PWM, the energy consumption of all the batteries can be made uniform.
  • the inverter circuit 22 according to the first modification is controlled by level shift type PWM.
  • level shift method as shown in FIG. 10, voltage levels of carrier waves (triangular waves) W1 to W6 are modulated.
  • the magnitudes of the carrier waves W1 to W6 and the signal wave (sine wave) W0 on / off of the switching elements Q31 to Q34 of the inverter circuit 22 is controlled.
  • the first modification high efficiency can be achieved by controlling the inverter circuit 22 with level shift PWM. Further, since the number of turn-offs and ons is small even at the same switching frequency as compared with the phase shift method, the same effect as the embodiment of the present invention can be obtained even with a low response DC / DC converter (DAB).
  • DAB low response DC / DC converter
  • the inverter circuit 22 (Second modification) Another example of the inverter circuit 22 will be described as a second modification. As shown in FIG. 11, the inverter circuit 22 according to the second modification is different in that it includes a half bridge circuit having two switching elements Q31 and Q32 instead of the H bridge circuit. Further, in order to generate a negative voltage, DC power sources VB (n ⁇ 1) and VBn on the reference potential side are connected in the reverse direction. Also in the second modification, for example, phase shift type PWM control is possible as in the embodiment of the present invention.
  • each of the voltage conversion modules 11-1 to 11-n, 12-1 to 12-n is compared with the case of the H-bridge circuit. , 13-1 to 13-n, the number of switching elements can be reduced by two, and the circuit configuration can be simplified.
  • the DC / DC converter 21 according to the third modified example uses a metal oxide semiconductor field effect transistor (MOSFET) instead of the IGBT as the switching elements Q11 to Q14 and Q21 to Q24.
  • MOSFET metal oxide semiconductor field effect transistor
  • the MOSFET has a built-in output capacitance.
  • soft switching can be performed using the built-in output capacitance of the MOSFET without providing capacitors at both ends of the IGBT as shown in FIG. 1, and noise generated during switching can be suppressed. Can do.
  • the DC / DC converter 21 according to the fourth modification is different in that a capacitor is connected in parallel to the IGBT in each of the switching elements Q11 to Q14 and Q21 to Q24.
  • soft switching can be performed by using the capacitors of the switching elements Q11 to Q14 and Q21 to Q24, and noise generated during switching can be suppressed.
  • the DC / DC converter 21 may have an LC series resonance type primary circuit 21a.
  • the DC / DC converter 21 may include an LLC series resonance type primary circuit 21a.
  • the DC / DC converter 21 may have the LCC series resonance type primary circuit 21a.
  • the DC / DC converter 21 may have the LC parallel resonance type primary circuit 21a.
  • the present invention is not limited to this, and a single-phase AC voltage is generated. It is also applicable to.
  • the configuration in which the power conversion apparatus includes the DC / DC converter 21 has been described.
  • the DC / DC converter 21 may not necessarily be included.
  • the harmonic component removing capacitor C1 is not necessarily provided.
  • the present invention can be used to reduce the smoothing capacitor of the power conversion device and to reduce the size of the device.

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Inverter Devices (AREA)
  • Dc-Dc Converters (AREA)

Abstract

L'invention concerne un dispositif de conversion de puissance dans lequel la taille d'un condensateur de lissage peut être réduite puisque les courants ondulatoires dans les phases respectives peuvent être compensés entre eux, de sorte que la taille du dispositif peut être réduite. Le dispositif de conversion de puissance comprend : une pluralité d'alimentations électriques en CC (VB1 à VBn) ; un condensateur de lissage (C2) connecté à chacune des alimentations électriques en CC (VB1 à VBn) en parallèle ; une pluralité de circuits onduleurs (22) connectés à chacune des alimentations électriques en CC (VB1 à VBn) par le nombre de phases en parallèle de sorte que les courants ondulatoires se produisant pendant la conversion de tension de CC en CA sont compensés entre eux et convertissant les tensions en CC produites par les alimentations électriques en CC (VB1 à VBn) connectées en tensions en CA ; et un moyen de commande (31) permettant de commander les circuits onduleurs (22). Dans le dispositif de conversion de puissance, les sorties des circuits onduleurs (22) connectés aux différentes alimentations électriques en CC (VB1 à VBn) sont connectées en série et transférées à chaque phase d'une charge.
PCT/JP2014/073171 2013-10-17 2014-09-03 Dispositif de conversion de puissance et procédé de conversion de puissance WO2015056491A1 (fr)

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WO2018019944A1 (fr) * 2016-07-29 2018-02-01 Rheinisch-Westfälische Technische Hochschule Aachen (RWTH) Convertisseur d'entraînement pour machine à reluctance commutée
JP2019154142A (ja) * 2018-03-02 2019-09-12 株式会社豊田中央研究所 電力変換装置
US20210203241A1 (en) * 2018-09-06 2021-07-01 TRiiiON Holdings Pty Ltd Variable and auto regulated three phase power source
KR20210088244A (ko) * 2020-01-06 2021-07-14 서울대학교산학협력단 듀얼 액티브 하프브리지 컨버터
WO2022097538A1 (fr) * 2020-11-06 2022-05-12 株式会社安川電機 Système de conversion de puissance
JP2022187724A (ja) * 2021-06-08 2022-12-20 本田技研工業株式会社 電源システム及び移動体

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KR102180639B1 (ko) * 2018-11-14 2020-11-19 한국전력공사 저주파 리플 제거를 위한 양방향 컨버터의 디커플링 제어 장치 및 이를 포함하는 dc-ac 전력 변환 시스템

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