WO2012009998A1 - Convertisseur résonnant monté en série llc et son procédé d'excitation - Google Patents

Convertisseur résonnant monté en série llc et son procédé d'excitation Download PDF

Info

Publication number
WO2012009998A1
WO2012009998A1 PCT/CN2011/073148 CN2011073148W WO2012009998A1 WO 2012009998 A1 WO2012009998 A1 WO 2012009998A1 CN 2011073148 W CN2011073148 W CN 2011073148W WO 2012009998 A1 WO2012009998 A1 WO 2012009998A1
Authority
WO
WIPO (PCT)
Prior art keywords
switch
signal
transformer
turn
resonant converter
Prior art date
Application number
PCT/CN2011/073148
Other languages
English (en)
Chinese (zh)
Inventor
范杰
王静
Original Assignee
中兴通讯股份有限公司
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by 中兴通讯股份有限公司 filed Critical 中兴通讯股份有限公司
Publication of WO2012009998A1 publication Critical patent/WO2012009998A1/fr

Links

Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/337—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only in push-pull configuration
    • H02M3/3376—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only in push-pull configuration with automatic control of output voltage or current
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0048—Circuits or arrangements for reducing losses
    • H02M1/0054—Transistor switching losses
    • H02M1/0058—Transistor switching losses by employing soft switching techniques, i.e. commutation of transistors when applied voltage is zero or when current flow is zero
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02P—CLIMATE CHANGE MITIGATION TECHNOLOGIES IN THE PRODUCTION OR PROCESSING OF GOODS
    • Y02P80/00—Climate change mitigation technologies for sector-wide applications
    • Y02P80/10—Efficient use of energy, e.g. using compressed air or pressurized fluid as energy carrier

Definitions

  • FIG. 1 is a circuit diagram of a related art LLC series resonant converter composed of a synchronous rectification transistor, as shown in FIG. 1, wherein an inductor-inductor-capacitor (LLC) series resonant converter (Series-Parallel Resonance)
  • LLC inductor-inductor-capacitor
  • SPRC series-Parallel Resonance
  • the bridge circuit 110 uses a symmetrical half-bridge control method, and the upper and lower tubes are complementarily turned on, and the duty ratio is 50%;
  • the resonant circuit 120 is composed of a resonant capacitor Cr, a resonant inductor Lr, and a magnetizing inductance Lm to form a resonant body, and Lr can be used as a leakage of the transformer.
  • the sense circuit is composed of a pair of synchronous rectification transistors Q1 and Q2 connected to the output capacitor Co.
  • the converter 100 is a converter having a double resonance point. When Lr, Cr participates in resonance only, the high-frequency resonance point fr is generated, and Lm does not participate in resonance.
  • the frequency modulation controller 140 is also required.
  • the operating frequency of the converter, fin is the low frequency resonance point of the LLC series resonant converter, and fr is the high frequency resonance point of the LLC series resonant converter.
  • FIG. 2 is a schematic diagram showing the voltage and current waveforms of the main components of the prior art LLC series resonant converter operating in the fin ⁇ fs ⁇ fr region.
  • &81 and ⁇ , 82 are the gate drive signals of the two FETs S1 and S2 in the bridge circuit 110, respectively, i r , respectively the resonant inductor Lr and the magnetizing inductance
  • the current of Lm, i Q1 , i Q2 and Vg, SR1 , Vg, S R2 are the current waveform and the driving voltage waveform of the two synchronous rectifying transistors Q1 and Q2 in the rectifying circuit 130, respectively.
  • the resonant current i r increases inversely from zero, the field effect transistor S 1 begins to conduct forward, the primary side of the transformer is clamped, and the field current changes linearly.
  • the resonant current i r flows through S 1 and gradually rises in a sinusoidal form.
  • i r flows through Lm and the primary side of the transformer, transfers energy to the secondary side of the transformer, and outputs Vo.
  • the resonant current i r and the exciting current i m are equal, the current at the output is zero, that is, at time 11, the phase ends.
  • the resonant current i r and the exciting current i m are equal, and at this time, the two synchronous rectifying transistors Q1 and Q2 on the secondary side are both in an off state, and the output voltage Vo is supplied from the output capacitor Co.
  • the output voltage is no longer clamped to the primary side of the transformer, and the magnetizing inductance Lm begins to participate in resonance, forming a series resonance with Lr and Cr.
  • the period of this resonance is much larger than the period of resonance of Lr and Cr, and the slope of the resonant current is much smaller, so the primary current can be approximately constant during this process.
  • the synchronous rectifying transistor Q1 should be turned off at time t1.
  • FETs S1 and S2 are turned off and enter dead time.
  • the resonant current i r charges the parasitic capacitance of S1 and the parasitic capacitance of S2 discharges.
  • the output voltage clamps the primary side of the transformer, and the magnetizing inductance Lm is discharged at a constant voltage.
  • the diode of S2 is turned on, and the field effect transistor S2 is turned on under the condition of Zero Voltage Switching (ZVS).
  • ZVS Zero Voltage Switching
  • the same working process can be analyzed in the time interval of t3 ⁇ t ⁇ t4 and t4 ⁇ t ⁇ t5.
  • the same operating state and current waveform i Q2 as the synchronous rectification transistor Q1 also occurs on the synchronous rectification transistor Q2, and current 1 (21 and i Q2 constitute the output rectified current i rec . Because at t1 to t2 and t4 to t5, synchronization rectification transistor Q1 or Q2 the current decreases to zero, and all occurred in the FETs S1 or pre-S2 is turned off, so that their wave guide width TONGMAI Vg, Q1, Vg, Q 2 than the small FET S1 and S2.
  • the synchronous rectification drive signals V g , Q1 , Vg , Q 2 must refer to the corresponding half bridge FET control signals V & S1 , Vg , S2 , and Vg , sl , Vg , S2 behind or Cut in advance This ensures that the circuit can block the secondary side energy back to the primary side during the dead time by using the body diode inside the synchronous rectification transistor.
  • 3 is a waveform timing diagram of a prior art LLC series resonant converter in a state where a switching frequency is greater than or equal to a resonant frequency, as shown in FIG.
  • the side switch tube can realize zero voltage switch (ZVS) under any load, but the transformer magnetizing inductance Lm is clamped by the output voltage and does not participate in the whole resonance process. Therefore, the current on the secondary side synchronous rectifier of the transformer is continuous.
  • the output rectified current i rec is a quasi-sinusoidal absolute value waveform which is synchronized with the driving permanent waves of the synchronous rectifying transistors Q1 and Q2.
  • FIG. 4 is a circuit diagram of a synchronous rectification driving method of a prior art LLC series resonant converter.
  • the LLC series resonant converter 400 is provided with two reference voltages and two comparators. And 2 with the door.
  • the synchronous rectification transistor Q2 flows a current from the source to the drain, a channel resistance voltage drop is generated in its channel resistance.
  • the channel resistance voltage drop V ds ( .n ) is compared by the comparator 410 and the reference voltage V ref to generate the pulse wave signal Ve . m . V e .
  • the m signal and the drive signal V g , s2 of the FET S2 are processed by the AND gate 420 to obtain a drive signal of the synchronous rectification transistor Q2.
  • the synchronous rectifying transistors Q1 and Q2 of the rectifying circuit are driven by the same signals for driving the FETs S1, S2, respectively.
  • FIG. 5 it is a circuit diagram of another synchronous rectification driving method of the prior art LLC series resonant converter, compared with FIG.
  • the LLC series resonant converter 500 is equipped with two synchronous circuits (Syn) 510, two constant pulse width generators (ie, Forced Oscillation Technique, referred to as FOT) 520, and two OR gates 530.
  • FOT Forced Oscillation Technique
  • the synchronous circuit 510 and the fixed pulse width are generated.
  • the 520 generates a constant pulse width signal V FOT , which is determined by the resonance parameters Lr, Cr, and the rising edge of the pulse wave is synchronized with the signal V SYN through the synchronization circuit 510. Constant pulse width signal V FOT and pulse wave signal V e .
  • the FET driving signal S2 V g, s2 After treatment with the gate drive signal 420 synchronous rectification transistor Q2 is obtained.
  • the channel resistance voltage V ds (. n ) for the synchronous rectifying transistors Q1 and Q2 is compared with the reference voltage V ref .
  • the pulse wave signal V e generated after comparison is performed on the device 410. m is used to drive the synchronous rectification transistors Q1 and Q2 of the rectifier circuit.
  • the synchronous rectifying transistors Q1 and Q2 of the rectifying circuit are driven by the same signals for driving the FETs S1, S2, respectively.
  • the scheme of FIG. 5 is based on the scheme of FIG. 4, and the synchronous rectification driving device of the LLC series resonant converter at the time of light load is added, that is, when the operating frequency is less than the resonant frequency and the converter is connected to the light load, the resonance of the resonant circuit is utilized.
  • the parameter drives the synchronous rectification transistor to determine a constant pulse width signal.
  • the output rectification current of the resonant converter is intermittent at light load.
  • a primary object of the present invention is to provide an LLC series resonant converter and a driving method thereof to solve at least the above-mentioned problem of low reliability.
  • an LLC series resonant converter comprising: a bridge circuit connected to an input voltage and composed of at least two first switches; and a resonant circuit coupled to the bridge circuit, The first switch is driven; a transformer is coupled to the resonant circuit; and a rectifier circuit includes two sub-driving circuits, each of which includes: a second switch coupled to both ends of the secondary side of the transformer, configured to provide LLC series resonance a voltage output of the converter; a shutdown circuit configured to provide a shutdown signal to the second switch, comprising a current transformer connected in series between the secondary side of the transformer and the two second switches, configured to measure the flow through a current of the source-drain branch of the second switch to generate a turn-off signal; a pulse width processor configured to reduce a duty cycle of a power switch drive signal of the transformer primary side of the control terminal of the first switch to obtain an open signal Provided to the second switch.
  • a driving method of an LLC series resonant converter includes: a bridge circuit coupled to an input voltage and composed of at least two first switches; The circuit is coupled to the bridge circuit and is driven by the first switch; a transformer coupled to the resonant circuit; and a rectifier circuit including two sub-drive circuits, each comprising: a second switch coupled to the secondary side of the transformer Both ends are arranged to provide a voltage output of the LLC series resonant converter; a shutdown circuit is provided to provide a shutdown signal to the second switch, which includes a current transformer connected in series with the secondary side of the transformer and two Between the two switches, the current flowing through the source-drain branch of the second switch is measured to generate a turn-off signal; a pulse width processor is provided to reduce the primary power switch of the transformer at the control end of the first switch After the duty cycle of the signal, the turn-on signal is supplied to the second switch; the driving method includes: when the LLC series resonant converter
  • FIG. 1 A diagrammatic representation of the LLC series resonant converter of the present invention and the driving method thereof, because the current transformer is used to measure the current flowing through the source-drain branch of the second switch, so that the related art LLC series resonant converter achieves reliable current backflow.
  • the problem of lower sex improves the reliability at light loads.
  • FIG. 1 is a circuit diagram of a related art LLC series resonant converter composed of a synchronous rectification transistor
  • FIG. 2 is a prior art LLC series resonant converter operating in a fin ⁇ fs ⁇ fr region.
  • FIG. 3 is a waveform timing diagram of a prior art LLC series resonant converter in a state where a switching frequency is greater than or equal to a resonant frequency;
  • FIG. 4 is a prior art LLC series resonant converter
  • FIG. 6 is a circuit diagram of a synchronous rectification driving scheme of the LLC series resonant converter 600 according to the present invention, comprising: a bridge circuit 110 coupled to an input voltage Vin, which is composed of two first switches SI, S2; The oscillating circuit 120 is connected to the bridge circuit 110 and is driven by the first switches S1, S2; a transformer TX is coupled to the resonant circuit 120; and a rectifying circuit 60 includes two sub-driving circuits 601, 602, respectively: A second switch Q1, or Q2, coupled to both ends of the secondary side of the transformer Tx, is configured to provide a voltage output Vo of the LLC series resonant converter; a shutdown circuit configured to provide a switch to the second switch Q1 or Q2 Break signal V e .
  • m comprising a current transformer CT1 , CT2 , connected in series between the secondary side of the transformer Tx and the two second switches Q1 or Q2 , configured to measure the source-drain branch flowing through the second switch Q1 or Q2 Current to generate a turn-off signal V c . m; a pulse processor 610, to provide a reduced set transformer primary side power switch signal v driving the control terminal of the first switch S1 or S2, g, sl, v g, the duty ratio s2 to obtain Pulse ON signal v Give the second switch Q1 or Q2.
  • Method of driving the LLC series resonant converter comprising: when the LLC series resonant converter operation over the entire operating frequency range, the shutdown circuit to provide off signal V c to the second switch Q1 or Q2.
  • the pulse width processor 610 supplies an on signal V pulse to the second switch Q1 or Q2 (eg, V pulsel and V pulse2 in FIG. 6 ).
  • the rising edge of the output signal of the pulse width processor is synchronized with the rising edge of the corresponding driving signals of the power switches S1, S2.
  • the output rectified current i rec does not have a dead zone, so the on-time of the synchronous rectification transistor Q1 or Q2 corresponds to the on-time of the FETs S1 and S2, respectively.
  • the LLC series resonant converter uses the current transformers CT1 and CT2 to measure the current flowing through the source-drain branches of the second switches Q1, Q2, so that the related art LLC series resonant converter current inrush is reliable.
  • the problem of lower sex improves the reliability at light loads.
  • the bridge circuit 110 is a half bridge circuit or a full bridge circuit.
  • the resonant circuit 120 is composed of a resonant capacitor Cr, a resonant inductor Lr, and a magnetizing inductance Lm in series.
  • the resonant inductor is an independent external inductor Lr or a leakage inductance of the transformer Tx.
  • each of the shutdown circuits includes: a reference voltage source Vref, a current transformer CT1, CT2, a magnetic reset resistor R1, R3, a sample resistor R2, R4, and a diode D1.
  • a comparator 410 an OR gate 530
  • the primary input of the current transformers CT1, CT2 is connected to the input of the second switch Q1 or Q2, and the primary output is connected to the secondary side of the transformer Tx
  • the current transformer CT1, CT2 are connected with magnetic reset resistor R1 or R3 at both ends
  • magnetic reset resistors Rl, R3 are connected to the anode of diode D1 or D2 at one end, and the other end is grounded
  • parallel resistor R2 is connected between the cathode of diodes D1 and D2 and ground.
  • a reference voltage source Vref is connected in series between the first input terminal of the comparator 410 and the output terminal of the second switch Q1 or Q2, the second input terminal of the comparator 410 is connected to the negative electrode of the diode D1 or D2, and the comparator 410 is set to Comparing the voltage V c outputted by the diode D1 or D2 with the voltage Vref output by the reference voltage source Vref generates a turn-off signal
  • the pulse width processor 610 makes the duty ratio of the turn-on signal V pulse equal to or smaller than the turn-off signal V c .
  • the duty cycle of m the pulse between the first input of the OR gate 530 and the control terminal of the first switch S1 or S2
  • the wide processor 610, the second input of the OR gate 530 is coupled to the output of the comparator 410, and the output of the OR gate 530 is coupled to the control terminal of the second switch Q1 or Q2.
  • the driving mode of the second switch Q1 is: when the LLC series resonant converter operates over the entire frequency range, the current transformer CT1 (or CT2) is The current signal is converted to a voltage signal by a sample resistor R2 (or R4), and is output as a voltage V e via a diode D1 (or D2), and is compared with a voltage Vref of the reference voltage source Vref by a comparator 410 to generate a turn-off signal V e . m , turn off the signal V e . m and another turn-on signal V pu i se are processed by OR gate 530 to obtain a complete drive signal to drive second switch Q1 (or Q2).
  • the present embodiment uses two OR logic gates 530 to implement adaptive control of the synchronous rectification drive signals
  • the implementation of the specific circuit is not limited to such logic gate structures, and any logic function that can implement this OR logic function.
  • Circuit architecture is within the scope of the present invention.
  • the rectifier circuit has a simple structure and is easy to implement.
  • 7 and 8 are main waveform timing diagrams of an embodiment of the LLC series resonant converter proposed by the present invention. As shown in FIG. 7 and FIG. 8, the synchronous rectification driving timing operation diagram of the LLC series resonant converter of the present embodiment is between the frequency of fin and fr and the operating frequency is higher than fr. Wherein, the output signal V pulse of the monthly Yongkuan processor and the output signal V c of the comparator.
  • the turn-on of the drive signal is determined by the drive signal of the primary power switch, and the turn-off is determined by the output signal of the comparator.
  • the first switch S1 or S2 is a field effect transistor
  • the second switch Q1 or Q2 is a field effect transistor.
  • the input, output and control terminals of the first switch S1 (or S2) and the second switch Q1 (or Q2) are the drain, the source and the gate of the FET, respectively. FETs are low cost and easy to implement.
  • the LLC series resonant converter of the present invention and the driving method thereof have the advantages that the driving signal of the synchronous rectifier is completely synchronized with the current signal, the duty ratio is lost less, and the efficiency of the converter is improved.
  • the transformer amplifies the current signal into a large voltage signal, which is not easily disturbed by the ground voltage peak, thereby effectively avoiding the pulse converter V c at the light load.
  • An error occurs in m , which causes the switches in the synchronous rectification circuit to be driven incorrectly. Therefore, the scheme is more resistant to interference.
  • the synchronous rectification driving method uses the output current of the converter to realize the driving control of the synchronous rectification transistor, which not only simplifies the design of the conventional driving circuit, but also effectively prevents the synchronous rectifier from passing through or output voltage backflow. Further improved reliability.

Landscapes

  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Dc-Dc Converters (AREA)
  • Rectifiers (AREA)

Abstract

La présente invention a trait à un convertisseur résonnant monté en série LLC qui inclut : un circuit à pont qui est couplé à une tension d'entrée (Vin) et qui est constitué d'au moins deux premiers commutateurs (S1, S2), un circuit résonnant qui est couplé au circuit à pont et qui est excité par les premiers commutateurs (S1, S2), un transformateur (Tx) qui est couplé au circuit résonnant, et un circuit de redressement (60) qui comprend deux circuits d'excitation secondaires (601, 602). Les deux circuits d'excitation secondaires (601, 602) incluent respectivement : un second commutateur (Q1, Q2) qui est couplé aux deux bornes de l'enroulement secondaire du transformateur (Tx) et qui fournit la tension de sortie (Vo) du convertisseur résonnant monté en série LLC, un circuit de blocage qui fournit au second commutateur (Q1, Q2) un signal de blocage (VCOM1, VCOM2) et qui comprend un transformateur de courant (CT1, CT2), et un processeur de largeur d'impulsion (610) permettant de générer un signal d'activation (Vpulse1, Vpulse2) et de fournir le signal d'activation au second commutateur (Q1, Q2) après avoir réduit le facteur de marche du signal d'excitation de commutateur d'énergie primaire de transformateur (Vg,s1, Vg,s2) de la borne de commande du premier commutateur (S1, S2). Le transformateur de courant (CT1, CT2) est monté en série entre l'enroulement secondaire du transformateur (Tx) et le second commutateur (Q1, Q2) et mesure le courant circulant dans la branche d'électrode source-drain du second commutateur (Q1, Q2) de manière à générer le signal de blocage (VCOM1, VCOM2).
PCT/CN2011/073148 2010-07-23 2011-04-21 Convertisseur résonnant monté en série llc et son procédé d'excitation WO2012009998A1 (fr)

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
CN201010238057.7 2010-07-23
CN201010238057.7A CN101895201B (zh) 2010-07-23 2010-07-23 Llc串联谐振变换器及其驱动方法

Publications (1)

Publication Number Publication Date
WO2012009998A1 true WO2012009998A1 (fr) 2012-01-26

Family

ID=43104306

Family Applications (1)

Application Number Title Priority Date Filing Date
PCT/CN2011/073148 WO2012009998A1 (fr) 2010-07-23 2011-04-21 Convertisseur résonnant monté en série llc et son procédé d'excitation

Country Status (2)

Country Link
CN (1) CN101895201B (fr)
WO (1) WO2012009998A1 (fr)

Cited By (7)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN107196520A (zh) * 2017-07-27 2017-09-22 桐庐恒英电子有限公司 一种谐振电路
CN108418436A (zh) * 2018-04-27 2018-08-17 合肥博鳌电气科技有限公司 一种基于半桥三电平结构的双向llc直流变换器及其控制方法
CN109995242A (zh) * 2019-04-08 2019-07-09 深圳市航嘉驰源电气股份有限公司 一种谐振变换器
CN113162441A (zh) * 2020-01-22 2021-07-23 杭州必易微电子有限公司 隔离电源电路、原副边通讯控制电路及控制方法
CN113381614A (zh) * 2021-06-21 2021-09-10 深圳中瀚蓝盾电源有限公司 控制电路、llc谐振电路的控制系统及开关电源
CN114123789A (zh) * 2021-11-12 2022-03-01 深圳市卓芯微科技有限公司 一种同步整流转换器
CN115313836A (zh) * 2022-07-11 2022-11-08 西北工业大学 一种llc谐振变换器软启动控制方法

Families Citing this family (22)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN101895201B (zh) * 2010-07-23 2015-06-10 中兴通讯股份有限公司 Llc串联谐振变换器及其驱动方法
US9312746B2 (en) 2011-04-25 2016-04-12 Fairchild Semiconductor Corporation Switching techniques to reduce current overshoot in a DC to DC converter
CN103078492A (zh) * 2011-10-26 2013-05-01 中兴通讯股份有限公司 谐振变换器的控制方法和装置
CN103138590B (zh) * 2011-12-02 2017-02-08 中兴通讯股份有限公司 谐振电路限流保护方法和装置
CN102590580B (zh) * 2012-01-10 2014-05-14 南京航空航天大学 一种对集成变压器励磁电感电流进行采样的电路及方法
CN103219705B (zh) 2013-03-12 2016-02-24 中兴通讯股份有限公司 半桥谐振变换器的短路保护方法及装置
CN103280774B (zh) * 2013-05-17 2015-09-09 华为技术有限公司 功率转换电路及其驱动装置、开关管保护装置和方法
CN103326581B (zh) * 2013-06-24 2016-04-13 成都芯源系统有限公司 Llc谐振变换器、控制电路及驱动方法
CN103546048B (zh) * 2013-10-30 2018-03-06 华为技术有限公司 电流采样方法
CN104201893A (zh) * 2014-09-19 2014-12-10 北京新雷能科技股份有限公司 多级联变换器预偏置电路及预偏置方法
CN105652062A (zh) * 2014-11-21 2016-06-08 中国航空工业集团公司雷华电子技术研究所 一种全桥变换器功率回路的电流检测电路
AT516903B1 (de) * 2015-03-09 2020-10-15 Fronius Int Gmbh Schaltungsanordnung mit Transformator mit Mittelpunktanzapfung und Messung der Ausgangsspannung
CN107659127B (zh) * 2016-07-25 2021-05-28 中兴通讯股份有限公司 一种同步整流自驱电路的控制方法及装置
CN107276190B (zh) * 2017-05-27 2020-02-21 华为技术有限公司 一种轻载纹波的发波方法及装置、设备
CN108667307B (zh) * 2018-06-08 2020-11-24 苏州舜唐新能源电控设备有限公司 Llc同步整流装置及其控制方法、电子设备、存储介质
CN109586581A (zh) * 2018-12-15 2019-04-05 华南理工大学 用于全桥dc/dc变换器同步整流的数字化实现装置
TWI694670B (zh) * 2019-02-15 2020-05-21 群光電能科技股份有限公司 諧振式電源轉換裝置
US11038430B2 (en) 2019-08-02 2021-06-15 Analog Devices International Unlimited Company LLCC secondary overtone resonant power converter
CN111490577A (zh) * 2020-05-27 2020-08-04 深圳威迈斯新能源股份有限公司 一种双端输出充电电路及其辅路开关控制方法
CN114337290A (zh) * 2021-02-07 2022-04-12 华为数字能源技术有限公司 功率电路中副边整流电路的驱动电路
CN113014112B (zh) * 2021-03-25 2023-06-30 矽力杰半导体技术(杭州)有限公司 控制电路、控制方法以及功率变换器
CN113098286B (zh) * 2021-04-23 2022-04-01 北京机械设备研究所 一种lclcl谐振变换器同步整流方法

Citations (5)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JPH10243647A (ja) * 1997-02-27 1998-09-11 Sony Corp 電源装置
US20070008757A1 (en) * 2003-09-02 2007-01-11 Hiroshi Usui Synchronous commutation dc-dc converter
CN101521463A (zh) * 2008-02-25 2009-09-02 崇贸科技股份有限公司 柔性切换电源转换器的同步整流电路
CN101667783A (zh) * 2008-09-05 2010-03-10 艾默生网络能源系统北美公司 一种用于变换器的同步整流驱动装置及方法
CN101895201A (zh) * 2010-07-23 2010-11-24 中兴通讯股份有限公司 Llc串联谐振变换器及其驱动方法

Family Cites Families (2)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN100424975C (zh) * 2005-02-25 2008-10-08 台达电子工业股份有限公司 Llc串联谐振变换器与其同步整流功率开关驱动方法
CN101154891B (zh) * 2006-09-28 2010-08-25 台达电子工业股份有限公司 谐振转换器及其同步整流驱动方法

Patent Citations (5)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JPH10243647A (ja) * 1997-02-27 1998-09-11 Sony Corp 電源装置
US20070008757A1 (en) * 2003-09-02 2007-01-11 Hiroshi Usui Synchronous commutation dc-dc converter
CN101521463A (zh) * 2008-02-25 2009-09-02 崇贸科技股份有限公司 柔性切换电源转换器的同步整流电路
CN101667783A (zh) * 2008-09-05 2010-03-10 艾默生网络能源系统北美公司 一种用于变换器的同步整流驱动装置及方法
CN101895201A (zh) * 2010-07-23 2010-11-24 中兴通讯股份有限公司 Llc串联谐振变换器及其驱动方法

Cited By (10)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN107196520A (zh) * 2017-07-27 2017-09-22 桐庐恒英电子有限公司 一种谐振电路
CN107196520B (zh) * 2017-07-27 2024-02-20 英飞特电子（杭州）股份有限公司 一种谐振电路
CN108418436A (zh) * 2018-04-27 2018-08-17 合肥博鳌电气科技有限公司 一种基于半桥三电平结构的双向llc直流变换器及其控制方法
CN109995242A (zh) * 2019-04-08 2019-07-09 深圳市航嘉驰源电气股份有限公司 一种谐振变换器
CN113162441A (zh) * 2020-01-22 2021-07-23 杭州必易微电子有限公司 隔离电源电路、原副边通讯控制电路及控制方法
CN113381614A (zh) * 2021-06-21 2021-09-10 深圳中瀚蓝盾电源有限公司 控制电路、llc谐振电路的控制系统及开关电源
CN114123789A (zh) * 2021-11-12 2022-03-01 深圳市卓芯微科技有限公司 一种同步整流转换器
CN114123789B (zh) * 2021-11-12 2023-07-07 深圳市卓芯微科技有限公司 一种同步整流转换器
CN115313836A (zh) * 2022-07-11 2022-11-08 西北工业大学 一种llc谐振变换器软启动控制方法
CN115313836B (zh) * 2022-07-11 2024-03-08 西北工业大学 一种llc谐振变换器软启动控制方法

Also Published As

Publication number Publication date
CN101895201A (zh) 2010-11-24
CN101895201B (zh) 2015-06-10

Similar Documents

Publication Publication Date Title
WO2012009998A1 (fr) Convertisseur résonnant monté en série llc et son procédé d'excitation
US8988901B2 (en) Switching power supply device
US8625311B2 (en) Switching power supply apparatus including a plurality of switching elements
KR101865062B1 (ko) 2단 공진 컨버터
JP5463759B2 (ja) スイッチング電源装置およびスイッチング電源制御回路
US9906147B2 (en) Adaptive dead time control apparatus and method for switching power converters
US7961482B2 (en) Bi-directional HEMT/GaN half-bridge circuit
CN101154891B (zh) 谐振转换器及其同步整流驱动方法
US11770076B2 (en) System and method for controlling active clamp flyback converter
US8619438B2 (en) Resonant converter
CN110798075B (zh) 控制电路以及应用其的开关变换器
Zhang et al. A high-frequency dual-channel isolated resonant gate driver with low gate drive loss for ZVS full-bridge converters
US20080297248A1 (en) Class d amplifier circuit with bi-directional power switch
KR101000561B1 (ko) 직렬 공진형 컨버터
WO2022170954A1 (fr) Dispositif de commande pour convertisseur cc/cc et son système de commande
WO2020228818A1 (fr) Système et procédé de commande de redressement synchrone pour convertisseur indirect quasi-résonant
WO2005101635A1 (fr) Convertisseur de puissance a commutation flexible equipe de moyens d'economie de puissance
US10014788B2 (en) Method of control for synchronous rectifiers
CN103441680A (zh) 一种减小环流损耗的软开关全桥直流变换器
US9484841B2 (en) Inverter device
CN113676057B (zh) 一种基于二次电流模拟的llc同步整流电路
CN108667304B (zh) 同步整流反激式直流-直流电源转换装置及控制方法
TW202247587A (zh) 適用於寬範圍輸出電壓的變換器及其控制方法
CN113541503A (zh) 一种零电流开关有源钳位电流型推挽直流变换器
JP2002199719A (ja) 複合共振型スイッチング電源装置

Legal Events

Date Code Title Description
121 Ep: the epo has been informed by wipo that ep was designated in this application

Ref document number: 11809187

Country of ref document: EP

Kind code of ref document: A1

NENP Non-entry into the national phase

Ref country code: DE

122 Ep: pct application non-entry in european phase

Ref document number: 11809187

Country of ref document: EP

Kind code of ref document: A1