EP2181500B1 - Amplifier circuit - Google Patents

Amplifier circuit Download PDF

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Publication number
EP2181500B1
EP2181500B1 EP08776120.1A EP08776120A EP2181500B1 EP 2181500 B1 EP2181500 B1 EP 2181500B1 EP 08776120 A EP08776120 A EP 08776120A EP 2181500 B1 EP2181500 B1 EP 2181500B1
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Prior art keywords
signal
amplifier
envelope
input
control signal
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EP08776120.1A
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German (de)
English (en)
French (fr)
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EP2181500A1 (en
Inventor
John Paul Lesso
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Cirrus Logic International Semiconductor Ltd
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Cirrus Logic International Semiconductor Ltd
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Priority to EP12194839.2A priority Critical patent/EP2568599B1/en
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
    • H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
    • H02M3/06—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using resistors or capacitors, e.g. potential divider
    • H02M3/07—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using resistors or capacitors, e.g. potential divider using capacitors charged and discharged alternately by semiconductor devices with control electrode, e.g. charge pumps
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03G—CONTROL OF AMPLIFICATION
    • H03G3/00—Gain control in amplifiers or frequency changers
    • H03G3/20—Automatic control
    • H03G3/30—Automatic control in amplifiers having semiconductor devices
    • H03G3/3005—Automatic control in amplifiers having semiconductor devices in amplifiers suitable for low-frequencies, e.g. audio amplifiers
    • H03G3/301—Automatic control in amplifiers having semiconductor devices in amplifiers suitable for low-frequencies, e.g. audio amplifiers the gain being continuously variable
    • H03G3/3015—Automatic control in amplifiers having semiconductor devices in amplifiers suitable for low-frequencies, e.g. audio amplifiers the gain being continuously variable using diodes or transistors
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03F—AMPLIFIERS
    • H03F1/00—Details of amplifiers with only discharge tubes, only semiconductor devices or only unspecified devices as amplifying elements
    • H03F1/02—Modifications of amplifiers to raise the efficiency, e.g. gliding Class A stages, use of an auxiliary oscillation
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03F—AMPLIFIERS
    • H03F1/00—Details of amplifiers with only discharge tubes, only semiconductor devices or only unspecified devices as amplifying elements
    • H03F1/02—Modifications of amplifiers to raise the efficiency, e.g. gliding Class A stages, use of an auxiliary oscillation
    • H03F1/0205—Modifications of amplifiers to raise the efficiency, e.g. gliding Class A stages, use of an auxiliary oscillation in transistor amplifiers
    • H03F1/0211—Modifications of amplifiers to raise the efficiency, e.g. gliding Class A stages, use of an auxiliary oscillation in transistor amplifiers with control of the supply voltage or current
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03F—AMPLIFIERS
    • H03F1/00—Details of amplifiers with only discharge tubes, only semiconductor devices or only unspecified devices as amplifying elements
    • H03F1/02—Modifications of amplifiers to raise the efficiency, e.g. gliding Class A stages, use of an auxiliary oscillation
    • H03F1/0205—Modifications of amplifiers to raise the efficiency, e.g. gliding Class A stages, use of an auxiliary oscillation in transistor amplifiers
    • H03F1/0211—Modifications of amplifiers to raise the efficiency, e.g. gliding Class A stages, use of an auxiliary oscillation in transistor amplifiers with control of the supply voltage or current
    • H03F1/0216—Continuous control
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03F—AMPLIFIERS
    • H03F1/00—Details of amplifiers with only discharge tubes, only semiconductor devices or only unspecified devices as amplifying elements
    • H03F1/02—Modifications of amplifiers to raise the efficiency, e.g. gliding Class A stages, use of an auxiliary oscillation
    • H03F1/0205—Modifications of amplifiers to raise the efficiency, e.g. gliding Class A stages, use of an auxiliary oscillation in transistor amplifiers
    • H03F1/0211—Modifications of amplifiers to raise the efficiency, e.g. gliding Class A stages, use of an auxiliary oscillation in transistor amplifiers with control of the supply voltage or current
    • H03F1/0216—Continuous control
    • H03F1/0222—Continuous control by using a signal derived from the input signal
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03F—AMPLIFIERS
    • H03F1/00—Details of amplifiers with only discharge tubes, only semiconductor devices or only unspecified devices as amplifying elements
    • H03F1/02—Modifications of amplifiers to raise the efficiency, e.g. gliding Class A stages, use of an auxiliary oscillation
    • H03F1/0205—Modifications of amplifiers to raise the efficiency, e.g. gliding Class A stages, use of an auxiliary oscillation in transistor amplifiers
    • H03F1/0211—Modifications of amplifiers to raise the efficiency, e.g. gliding Class A stages, use of an auxiliary oscillation in transistor amplifiers with control of the supply voltage or current
    • H03F1/0216—Continuous control
    • H03F1/0222—Continuous control by using a signal derived from the input signal
    • H03F1/0227—Continuous control by using a signal derived from the input signal using supply converters
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03F—AMPLIFIERS
    • H03F1/00—Details of amplifiers with only discharge tubes, only semiconductor devices or only unspecified devices as amplifying elements
    • H03F1/02—Modifications of amplifiers to raise the efficiency, e.g. gliding Class A stages, use of an auxiliary oscillation
    • H03F1/0205—Modifications of amplifiers to raise the efficiency, e.g. gliding Class A stages, use of an auxiliary oscillation in transistor amplifiers
    • H03F1/0211—Modifications of amplifiers to raise the efficiency, e.g. gliding Class A stages, use of an auxiliary oscillation in transistor amplifiers with control of the supply voltage or current
    • H03F1/0244—Stepped control
    • H03F1/025—Stepped control by using a signal derived from the input signal
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03F—AMPLIFIERS
    • H03F1/00—Details of amplifiers with only discharge tubes, only semiconductor devices or only unspecified devices as amplifying elements
    • H03F1/02—Modifications of amplifiers to raise the efficiency, e.g. gliding Class A stages, use of an auxiliary oscillation
    • H03F1/0205—Modifications of amplifiers to raise the efficiency, e.g. gliding Class A stages, use of an auxiliary oscillation in transistor amplifiers
    • H03F1/0261—Modifications of amplifiers to raise the efficiency, e.g. gliding Class A stages, use of an auxiliary oscillation in transistor amplifiers with control of the polarisation voltage or current, e.g. gliding Class A
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03F—AMPLIFIERS
    • H03F1/00—Details of amplifiers with only discharge tubes, only semiconductor devices or only unspecified devices as amplifying elements
    • H03F1/02—Modifications of amplifiers to raise the efficiency, e.g. gliding Class A stages, use of an auxiliary oscillation
    • H03F1/0205—Modifications of amplifiers to raise the efficiency, e.g. gliding Class A stages, use of an auxiliary oscillation in transistor amplifiers
    • H03F1/0261—Modifications of amplifiers to raise the efficiency, e.g. gliding Class A stages, use of an auxiliary oscillation in transistor amplifiers with control of the polarisation voltage or current, e.g. gliding Class A
    • H03F1/0266—Modifications of amplifiers to raise the efficiency, e.g. gliding Class A stages, use of an auxiliary oscillation in transistor amplifiers with control of the polarisation voltage or current, e.g. gliding Class A by using a signal derived from the input signal
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03F—AMPLIFIERS
    • H03F1/00—Details of amplifiers with only discharge tubes, only semiconductor devices or only unspecified devices as amplifying elements
    • H03F1/30—Modifications of amplifiers to reduce influence of variations of temperature or supply voltage or other physical parameters
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03F—AMPLIFIERS
    • H03F3/00—Amplifiers with only discharge tubes or only semiconductor devices as amplifying elements
    • H03F3/181—Low-frequency amplifiers, e.g. audio preamplifiers
    • H03F3/183—Low-frequency amplifiers, e.g. audio preamplifiers with semiconductor devices only
    • H03F3/185—Low-frequency amplifiers, e.g. audio preamplifiers with semiconductor devices only with field-effect devices
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03F—AMPLIFIERS
    • H03F3/00—Amplifiers with only discharge tubes or only semiconductor devices as amplifying elements
    • H03F3/189—High-frequency amplifiers, e.g. radio frequency amplifiers
    • H03F3/19—High-frequency amplifiers, e.g. radio frequency amplifiers with semiconductor devices only
    • H03F3/193—High-frequency amplifiers, e.g. radio frequency amplifiers with semiconductor devices only with field-effect devices
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03F—AMPLIFIERS
    • H03F3/00—Amplifiers with only discharge tubes or only semiconductor devices as amplifying elements
    • H03F3/20—Power amplifiers, e.g. Class B amplifiers, Class C amplifiers
    • H03F3/21—Power amplifiers, e.g. Class B amplifiers, Class C amplifiers with semiconductor devices only
    • H03F3/213—Power amplifiers, e.g. Class B amplifiers, Class C amplifiers with semiconductor devices only in integrated circuits
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03G—CONTROL OF AMPLIFICATION
    • H03G3/00—Gain control in amplifiers or frequency changers
    • H03G3/001—Digital control of analog signals
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03G—CONTROL OF AMPLIFICATION
    • H03G3/00—Gain control in amplifiers or frequency changers
    • H03G3/002—Control of digital or coded signals
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03F—AMPLIFIERS
    • H03F1/00—Details of amplifiers with only discharge tubes, only semiconductor devices or only unspecified devices as amplifying elements
    • H03F1/26—Modifications of amplifiers to reduce influence of noise generated by amplifying elements
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03F—AMPLIFIERS
    • H03F2200/00—Indexing scheme relating to amplifiers
    • H03F2200/03—Indexing scheme relating to amplifiers the amplifier being designed for audio applications
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03F—AMPLIFIERS
    • H03F2200/00—Indexing scheme relating to amplifiers
    • H03F2200/504—Indexing scheme relating to amplifiers the supply voltage or current being continuously controlled by a controlling signal, e.g. the controlling signal of a transistor implemented as variable resistor in a supply path for, an IC-block showed amplifier

Definitions

  • This invention relates to amplifier circuits, and in particular but not exclusively to amplifier circuits that include power amplifiers.
  • FIG. 1 shows a basic Class AB amplifier 10.
  • a bipolar (i.e. split level) power supply outputs the voltages V + , V - and these output voltages are applied across the amplifier 10, which amplifies the input signal S in and outputs a ground-referenced amplified output signal S out to a load 20.
  • the amplifier 10 has a substantially linear amplification (ignoring crossover effects). That is, the voltages V + , V - output from the power supply must be adequate so as to avoid output signal "clipping", i.e. attenuation of the output when the signal nears, equals or exceeds the voltages V + , V - output from the power supply to the amplifier. This is avoided by having "headroom" between the maximum output signal S outmax and the power supply rails.
  • Figure 2 is a graph showing S out where S in is a sine wave.
  • V + and V - are set sufficiently high so that the input sine wave is linearly amplified. That is, there is a small amount of headroom between V + and V - and the maximum output signal, so that the signal is not clipped.
  • the shaded region of the graph is representative of the power wasted in the amplifier 10; it can be seen that the amplifier 10 is very efficient when the output is close to V + or V_, but very inefficient when the output is close to 0 V (GND). That is, a large amount of power is still being expended by the amplifier 10 even when the output signal S out is small.
  • the maximum theoretical efficiency for a class AB amplifier is 78.5%.
  • Class G amplifiers overcome this limitation on efficiency by providing more than one set of power supply rails, i.e. supply voltages. That is, as shown in Figure 3 , the amplifier may run off one power supply V + -V - if the output signal S out is reasonably large, or another smaller power supply V p -V n if the output signal S out is small. Ideally, an infinite number of power supply rails would be provided, such that the voltage supplied to the amplifier effectively "tracks" the input signal, always providing just enough voltage so that there is no clipping.
  • Figure 4 shows an example of a Class G amplifier 50.
  • a digital signal S in to be amplified is input to the amplifier 50.
  • the digital input signal is first converted to an analogue signal by a digital-to-analogue converter (DAC) 51.
  • the resulting analogue signal is fed to an envelope detector 52.
  • the envelope detector 52 detects the size of the envelope of the analogue output signal of the DAC 51, and outputs a control signal to a switching DC-DC converter 54.
  • the control signal is indicative of the size of the envelope of the analogue output of the DAC 51.
  • the DC-DC converter 54 then supplies voltages V + and V - to a power amplifier 56 by charging respective capacitors 58, 60.
  • the voltages V + and V - supplied by the DC-DC converter 54 vary with the control signal from the envelope detector 52, such that a relatively large envelope will lead to a relatively high voltage supplied to the power amplifier 56; conversely, a small envelope will lead to a relatively small voltage being supplied to the power amplifier 56, so that less power is wasted.
  • V + is supplied to one terminal of a first capacitor 58
  • V - is supplied to one terminal of a second capacitor 60.
  • the second terminals of the respective capacitors 58, 60 are connected to ground.
  • the DC-DC converter 54 is switched on and off at a fixed frequency F s , so that the capacitors 58, 60 are alternately charged and discharged, with an approximately constant voltage being applied to the power amplifier 56 provided the envelope of the analogue signal does not change.
  • Figure 5 is a schematic graph illustrating the voltage across one of the capacitors 58, 60 (in practice the charge and discharge profiles of the capacitor will be exponential curves).
  • the DC-DC converter 54 is switched on and the capacitor begins to charge.
  • the DC-DC converter 54 is switched off and the capacitor begins to discharge.
  • the DC-DC converter 54 is switched on and the capacitor begins to charge again. This action repeats, such that the voltage across the capacitor is maintained at an approximately constant level, with a small amount of variation known as the "ripple voltage".
  • the time period between to and t 2 therefore, is 1/F s .
  • the analogue output signal of the DAC 51 in Figure 4 is fed through an analogue delay 62 to a preamplifier 63, typically a programmable gain amplifier (PGA), which amplifies the delayed signal by a gain set in accordance with a received control signal (i.e. the volume).
  • a preamplifier 63 typically a programmable gain amplifier (PGA)
  • the output from the preamplifier 63 is fed to the power amplifier 56, where it is amplified and output to a load 64.
  • the analogue delay 62 is necessary so that the power modulation achieved by the envelope detection is synchronized with the signal arriving at the power amplifier 56.
  • an amplifier circuit comprising: an input, for receiving an input signal to be amplified; a preamplifier, for amplifying the input signal based on a variable gain; a power amplifier for amplifying the signal output from the preamplifier; a variable voltage power supply for supplying power to the power amplifier, said power being adjusted based on the variable gain.
  • the power supply is of the charge pump type.
  • FIG 6 shows an amplifier 100 for use in amplifying audio signals according to one aspect of the present invention.
  • the amplifier 100 can be used for amplifying many other types of signal.
  • the amplifier 100 receives a digital input signal to be amplified.
  • the digital input signal is input to an envelope detector 102.
  • the envelope detector 102 detects the size of the envelope of the digital input signal and outputs a control signal 103 to a variable voltage power supply (WPS) 104.
  • the control signal 103 output to the WPS 104 is indicative of the size of the detected envelope.
  • the VVPS 104 in turn provides two voltages V + and V - to a power amplifier 106 by charging respective capacitors 108, 110.
  • the voltages V + and V - supplied by the WPS 104 vary such that a control signal indicative of a relatively large envelope will lead to a relatively high voltage supplied to the power amplifier 106; conversely, a control signal indicative of a relatively small envelope will lead to a relatively small voltage being supplied to the power amplifier 106, so that less power is wasted.
  • V + is supplied to one terminal of a first capacitor 108
  • V - is supplied to one terminal of a second capacitor 110.
  • the second terminals of the respective capacitors 108, 110 are connected to ground.
  • the WPS 104 is switched on and off at a frequency F s , so that the capacitors 108, 110 are alternately charged and discharged, with an approximately constant voltage being supplied to the power amplifier 106 provided, the envelope of the digital input signal does not change.
  • the control signal 103 may have a high number of bits, for representing the size of the envelope with a high degree of accuracy. Alternatively, the control signal 103 may have only a single bit.
  • the digital input signal is input to a digital filter 112.
  • the filtered signal is then input to a sigma-delta ( ⁇ ) modulator 114.
  • the modulated filtered signal is input to a digital-to-analogue converter (DAC) 116, and converted to an analogue signal.
  • DAC digital-to-analogue converter
  • the effect of the filter 112, sigma-delta modulator 114 and DAC 116 is to convert the digital signal to an analogue signal so that it may be amplified, and to delay the signal so that its arrival at the power amplifier 106 is synchronized with the correct voltage levels as determined by the envelope detector 102.
  • a digital delay and a DAC are all that is required.
  • the delay is primarily introduced in the digital filter 112, although the sigma-delta modulator 114 and DAC 116 also have inherent delays.
  • the sigma-delta modulator 114 reduces the word length of the input signal as will be familiar to those skilled in the art.
  • the design of the DAC 116 is greatly simplified.
  • the sigma-delta modulator 114 requires that the signal be upsampled, and this is the purpose of the digital filter 112.
  • the analogue output signal of the DAC 116 is input to a preamplifier 118 that amplifies the signal by a variable gain.
  • the variable gain is set by a control signal, which in this particular example is the volume signal. In the majority of audio applications, the variable gain will typically be an attenuation, in order to improve the signal to noise ratio (SNR).
  • SNR signal to noise ratio
  • the preamplified signal is output from the preamplifier 118 to the power amplifier 106, where it is amplified and output to a load 120, such as, for example, a speaker, a set of headphones, or a line-out connector.
  • a load 120 such as, for example, a speaker, a set of headphones, or a line-out connector.
  • the amplifier 100 has a number of advantages over the amplifier 50 described with respect to Figure 4 .
  • the amplifier 100 can make use of digital delays to delay the signal in parallel to the envelope detection. Digital delays are easy to implement and do not lead to distortion of the signal. Further, the digital delay can be easily adapted so the VVPS 104 need not operate as quickly as in the prior art, and so no tones are generated that may be audible to the user.
  • the digital delay can be realized using one or more processes that have an inherent delay.
  • the arrangement shown in Figure 6 i.e. the combination of the digital filter 112 and the sigma-delta modulator 114 simplifies the DAC 116 and also delays the signal; however, equalizer circuitry could be used to modulate and delay the signal; alternatively stereo or 3D processing would also delay the signal.
  • This list is not exhaustive, however; any process or combination of processes that delays the signal could be used. It will also be appreciated that the delay could be provided by the DAC 116 alone.
  • the envelope detector 102 may take a number of forms that would be familiar to a person skilled in the art.
  • the envelope detector 102 may detect the envelope and compare it with some threshold value.
  • the envelope detector 102 may comprise a comparator, that compares the envelope with a threshold value. If the envelope is below the threshold, the WPS 104 will provide a relatively low voltage; if the envelope is above the threshold, the WPS 104 will provide a relatively high voltage.
  • control signal 103 may be derived directly from the digital input signal, for example based on a certain bit, such as the most significant bit (MSB) of the input signal.
  • MSB most significant bit
  • control signal 103 may be provided, for example when using multiple power supply rails or voltage levels for powering the power amplifier 106, by using additional comparators and corresponding threshold values.
  • WPS 104 is a charge pump. Also, the WPS 104 shown in Figure 6 provides a positive and a negative voltage output to the power amplifier; however, this is not necessary. The WPS may supply only one voltage to the power amplifier.
  • Figures 14 and 15 illustrated below, illustrate two charge pumps that may be used as the WPS 104.
  • Figure 7 shows an amplifier 200 according to another aspect of the present invention.
  • the amplifier 200 is similar to the amplifier 100 described with respect to Figure 6 , with the exception of a number of components which will be described in more detail below. Components which are common to both amplifiers 100, 200 have retained their original reference numerals and will not be described further.
  • the envelope detector 202 and WPS 204 act in a similar way to their counterparts in the amplifier 100; however, the operation of either or both may be adjusted as described below.
  • control signal i.e. volume signal
  • the control signal which is applied to the preamplifier 118 in order to set the variable gain in the preamplifier 118, is also used to adjust the voltages supplied to the power amplifier 106.
  • variable gain applied in the preamplifier 118 is typically an attenuation in order to improve the signal-to-noise ratio.
  • the envelope detection, and therefore the voltages supplied to the power amplifier 106 is based on the full input signal. All of the gain in the system is present after the envelope detection. Thus, in the event that the volume results in an attenuation, there will be power wastage; if the volume results in a gain, there will be clipping of the signal output from the power amplifier 106.
  • the input signal may be modified by the volume control signal before entering the envelope detector 202, such that the volume is already accounted for in the detected envelope (for example, the input signal may be multiplied by the volume signal).
  • control signal output from the envelope detector 202 to the WPS 204 may be modified by the volume, such that the WPS 204 can adjust its voltage output accordingly (for example, the control signal may be multiplied by the volume).
  • This latter method has the advantage of increasing the resolution of the system; the envelope detector 202 can use the full input signal to detect the envelope.
  • the detecting mechanism of the envelope detector 202 may be adapted by the volume, in order to output a control signal that is adjusted for the volume.
  • the output of the WPS 204 may be adapted by the volume, so that the voltages supplied to the power amplifier 106 are adjusted for the volume.
  • the discussion above has described the application of the volume control signal not only to the pre-amplifier 118, as is conventional in order to set the variable gain within the pre-amplifier 118, but also to the envelope detection of the input signal.
  • the variable gain itself may be applied to the envelope detection of the input signal.
  • References above and below to adapting or modifying a quantity or signal "based on the volume” also therefore cover adapting that quantity or signal based on the variable gain; the variable gain in the pre-amplifier by definition varies in accordance with the volume control signal, and thus varying or modifying a quantity or signal based on the variable gain is equivalent to indirectly varying or modifying that quantity or signal based on the volume.
  • volume gain to envelope detection will equally have benefits in a system with an analogue input signal and an analogue amplifier, as described with reference to Figure 4 .
  • the volume may be applied either before, during or after the envelope detection in envelope detector 52, as described earlier with reference to amplifier 200 and Figure 7 .
  • Figure 8 shows an amplifier 300 according to another aspect of the invention.
  • the amplifier 300 is similar to the amplifier 100 described with respect to Figure 6 , with the exception of a number of components which will be described in more detail below. Components which are common to both amplifiers 100, 300 have retained their original reference numerals and will not be described further.
  • the envelope detector 302 and WPS 304 act in a similar way to their counterparts in the amplifier 100; however, the operation of either or both may be adjusted as described below.
  • the capacitors 108, 110 are charged when the WPS 104 is switched on, and discharged when the WPS 104 is switched off.
  • the magnitude of the rise and fall of the voltage across the capacitors 108, 110 is known as the "ripple voltage" (see Figure 5 ).
  • the switching frequency of the WPS 304, F s may be increased so that the capacitors 108, 110 do not discharge as much before being recharged.
  • increasing the switching frequency F s will result in greater power consumption within the WPS 304 itself, as it will be switched on a greater number of times in a given period.
  • the rate of discharge of the capacitors 108, 110 is dependent on the amount of power that is dissipated in the load 120, which is in turn dependent on the signal amplified by the power amplifier 106.
  • a variable gain (as set by the volume control signal) is applied to the input signal of the pre-amplifier 118. Both of these factors (i.e. the signal envelope and the volume) have an effect on the signal that is input to the power amplifier 106.
  • the amplifier 300 comprises a clock generator 306, that receives the volume control signal and generates a clock signal with a frequency F s '.
  • the frequency F s 'of the clock signal is adapted to be relatively high when the volume is relatively high, and relatively low when the volume is relatively low.
  • the clock signal is output to the WPS 304, such that the WPS 304 switches at the frequency F s '. Therefore, at higher volumes, where the current drawn in the load 120 is high, and thus the capacitors 108, 110 discharge relatively rapidly, the switching frequency F s ' of the WPS 304 is also high. This means the voltage across the capacitors 108, 110 is maintained at an adequate level.
  • Figure 9 shows an amplifier 400 according to another aspect of the invention.
  • the amplifier 400 is similar to the amplifier 100 described with respect to Figure 6 , with the exception of a number of components which will be described in more detail below. Components which are common to both amplifiers 100, 400 have retained their original reference numerals and will not be described further.
  • the envelope detector 402 and WPS 404 act in a similar way to their counterparts in the amplifier 100; however, the operation of either or both may be adjusted as described below.
  • the amplifier 400 comprises a clock generator 406 that receives a further control signal from the envelope detector 402.
  • the clock generator 406 generates a clock signal with a frequency F s '.
  • the clock signal is output to the WPS 404, such that the VVPS 404 switches at the frequency F s '. Therefore, when the signal envelope is large, the current drawn in the load 120 will be high, and thus the capacitors 108, 110 will discharge relatively rapidly. Therefore, the switching frequency F s ' of the WPS 404 is also high, such that the voltage across the capacitors 108, 110 is maintained at an adequate level.
  • Both amplifiers 300, 400 may be adapted so that the switching frequency of the WPS 304, 404 takes into account both the signal envelope and the volume.
  • the volume may be applied to the envelope detector 302, 402 as described with reference to Figure 7 . That is, in amplifier 400 the signal may be modified by the volume before the envelope is detected in the envelope detector 402 (for example, the signal may be multiplied by the volume); or the control signal output from the envelope detector 402 to the clock generator 406 may be modified by the volume (for example, the control signal may be multiplied by the volume).
  • the envelope detector 302 may output a control signal to the clock generator 306 such that both the envelope and the volume are taken into account when generating the clock signal.
  • the volume, the envelope, and their combination may be used to alter the switching frequency of the VVPS.
  • an analogue amplifier for example as described with reference to Figure 4 , would comprise a clock generator as described with reference to Figures 8 and 9 , and operate in essentially the same way.
  • Conduction losses relate to the power dissipated by each switch of the switching power supply
  • switching losses relate to the power dissipated in switching, i.e. driving, each switch.
  • switching power supplies use MOSFETs as the switching elements.
  • a large MOSFET has a lower channel resistance, i.e. drain-source resistance R DS , than a relatively smaller MOSFET for a given current.
  • R DS drain-source resistance
  • a large MOSFET will require a higher gate charge which results in greater switch driver current losses, i.e. switching losses, than smaller MOSFETs, for a given frequency of operation. While switching losses are typically less significant than conductive losses at high output currents, switching losses lead to significant inefficiencies at low output currents.
  • the internal switches of the charge pump for example, typically used to adjust the output voltage of the charge pump, expend some energy.
  • This switching-loss energy is equal to 1 ⁇ 2 CV 2 , where C is the capacitance of the switch, and V the voltage across the switch.
  • the MOSFET switches in the WPS have an inherent gate capacitance and an inherent channel resistance R DS .
  • Resistance R DS is proportional to L / W , where L is the channel length of the MOSFET switch and W its channel width.
  • the gate capacitance is proportional to the product WL. R ⁇ L / W C ⁇ WL
  • VVPS voltage regulator
  • NMOS complementary metal-oxide-semiconductor
  • PMOS complementary metal-oxide-semiconductor
  • the basic principle stated above is the same for each MOS switch type.
  • the energy expended in operating the MOS switch is 1 ⁇ 2 CV 2
  • the capacitance is proportional to the gate area ( WL ) of the switch.
  • Figure 10 shows a further amplifier 500.
  • the amplifier 500 is similar to the amplifier 100 described with respect to Figure 6 , with the exception of a number of components which will be described in more detail below. Components which are common to both amplifiers 100, 500 have retained their original reference numerals and will not be described further.
  • the envelope detector 502 and WPS 504 act in a similar way to their counterparts in the amplifier 100; however, the operation of either or both may be adjusted as described below.
  • the amplifier 500 further comprises a switch select block 506 that receives the volume control signal and outputs a control signal 505 to the WPS 504.
  • the control signal 505 directs the WPS 504 to adapt its switches as will be described in more detail below with reference to Figures 11 and 12 .
  • FIG 11 shows one example of the switches that may be used in VVPS 504.
  • Two switches 550, 552 are connected in parallel between an input voltage V ln and an output voltage V out .
  • the first switch 550 is comparatively wide, and therefore has a comparatively low resistance and a high capacitance.
  • the second switch 552 is narrower, and so has a higher resistance but a lower capacitance.
  • the wide switch 550 is used in this instance. A greater amount of energy is expended as capacitance C is high, but this is necessary in order to achieve an adequate V out .
  • Figure 12 shows one possible implementation of the switches 550 and 552.
  • a single switch 560 may be split unevenly as shown, into regions 562 and 564. This arrangement gives three possible switch widths: the smallest region 564; the larger region 562; and a region combining both 562 and 564.
  • multiple switches may be provided, and different numbers of switches turned on in order to adapt the overall resistance and capacitance to desired values.
  • the switch select block 506 in the amplifier 500 operates to reduce the power consumption of the amplifier 500. If the volume is high, a greater amount of voltage will be required in the capacitors 108, 110. Therefore, in this instance, the switch select block 506 directs the WPS 504 to use relatively wide switches. If the volume is low, less voltage is required in the capacitors 108,110. In this instance, the switch select block 506 directs the WPS 504 to use relatively narrow switches, such that the switching losses in the WPS 504 are minimized.
  • Figure 13 shows a further amplifier 600.
  • the amplifier 600 is similar to the amplifier 100 described with respect to Figure 6 , with the exception of a number of components which will be described in more detail below. Components which are common to both amplifiers 100, 600 have retained their original reference numerals and will not be described further.
  • the envelope detector 602 and WPS 604 act in a similar way to their counterparts in the amplifier 100; however, the operation of either or both may be adjusted as described below.
  • the amplifier 600 further comprises a switch select block 606 that receives a control signal from the envelope detector 602 and outputs a control signal 605 to the VVPS 604.
  • the switch select block 606 may receive the same control signal as is output to the WPS 604.
  • the control signal 605 directs the WPS 604 to adapt its switches as described previously with reference to Figures 11 and 12 .
  • the switch select block 606 directs the WPS 604 to use relatively wide switches. If the signal envelope is low, less voltage is required in the capacitors 108, 110. In this instance, the switch select block 606 directs the WPS 604 to use relatively narrow switches, such that the switching losses in the VVPS 604 are minimized. As above, it will be appreciated that multiple switches may be used, each having a different "width".
  • Both amplifiers 500, 600 may be adapted so that the switch select block 506, 606 takes into account both the signal envelope and the volume.
  • the volume may be applied to the envelope detector 502, 602 as described with reference to Figure 7 . That is, in the amplifier 600 the input signal may be modified by the volume before it is detected in the envelope detector 602 (for example, the signal may be multiplied by the volume); or the control signal output from the envelope detector 602 to the switch select block 606 may be modified by the volume (for example, the control signal may be multiplied by the volume); or the control signal 605 output from the switch select block 606 may be modified by the volume signal.
  • the envelope detector 502 may output a further control signal, indicative of the detected input signal envelope, to the switch select block 506 such that both the envelope and the volume are taken into account when generating the switch select control signal.
  • a further control signal indicative of the detected input signal envelope
  • an analogue amplifier for example as described with reference to Figure 4 , would comprise a switch select block as described with reference to Figures 10 and 13 , and operate in essentially the same way.
  • Figure 14a shows a charge pump 1400 that is suitable for use as the WPS 104, 204, 304, 404, 504, 606 in any of Figures 6 , 7 , 8 , 9 , 10 and 13 respectively. Further, the charge pump 1400 is also suitable for use as the VVPS in any of the analogue equivalents of the amplifiers 200, 300, 400, 500, 600.
  • FIG 14a is a block diagram of a novel inverting charge pump circuit, which we shall call a "Level Shifting Charge-Pump" (LSCP) 1400.
  • LSCP Level Shifting Charge-Pump
  • neither of the reservoir capacitors CR1, CR2 are connected directly to the input supply voltage VDD, but only via the switch array 1410.
  • LSCP 1400 is configured as an open-loop charge-pump, although a closed-loop arrangement would be readily appreciated and understood by those skilled in the art.
  • LSCP 1400 relies on the respective loads (not illustrated) connected across each output N12-N11, N13-N11 remaining within predetermined constraints.
  • the LSCP 1400 outputs two voltages Vout+, Vout- that are referenced to a common voltage supply (node N11), i.e. ground.
  • node N11 i.e. ground.
  • a load 1450 Connected to the outputs Vout+, Vout-, N11, and shown for illustration only, is a load 1450. In reality this load 1450 may be wholly or partly located on the same chip as the power supply, or alternatively it may be located off-chip.
  • the load 1450 is a combination of the power amplifier 106 and the load 120.
  • LSCP 1400 operates such that, for an input voltage +VDD, the LSCP 1400 generates outputs of magnitude +VDD/2 and -VDD/2 although when lightly loaded, these levels will, in reality, be +/-VDD/2 - Iload.Rload, where Iload equals the load current and Rload equals the load resistance.
  • Iload equals the load current
  • Rload equals the load resistance
  • FIG. 14b shows a more detailed version of the LSCP 1400 and, in particular, detail of the switch array 1410 is shown.
  • the switch array 1410 comprises six switches S1-S6 each controlled by corresponding control signal CS1-CS6 from the switch controller 1420.
  • the switches are arranged such that first switch S1 is connected between the positive plate of the flying capacitor Cf and the input voltage source, the second switch S2 between the positive plate of the flying capacitor and first output node N12, the third switch S3 between the positive plate of the flying capacitor and common terminal N11, the fourth switch S4 between the negative plate of the flying capacitor and first output node N12, the fifth switch S5 between the negative plate of the flying capacitor and common terminal N11 and the sixth switch S6 between the negative plate of the flying capacitor and second output terminal N13.
  • the switches can be implemented in a number of different ways (for example, MOS transistor switches or MOS transmission gate switches) depending upon, for example, an integrated circuits process technology or the input and output voltage requirements.
  • Figure 15a shows a further charge pump 2400 that is suitable for use as the VVPS 104, 204, 304, 404, 504, 606 in any of Figures 6 , 7 , 8 , 9 , 10 and 13 respectively. Further, the charge pump 2400 is also suitable for use as the VVPS in any of the analogue equivalents of the amplifiers 200, 300, 400, 500, 600.
  • FIG 15a is a block diagram of a novel inverting charge pump circuit, which we shall call a "Dual Mode Charge Pump” (DMCP) 2400.
  • DMCP Dual Mode Charge Pump
  • reservoir capacitors CR1 and CR2 a flying capacitor Cf and a switch array 2410 controlled by a switch control module 420 (which may be software or hardware implemented).
  • switch control module 420 which may be software or hardware implemented.
  • neither of the reservoir capacitors CR1, CR2 are connected directly to the input supply voltage VDD, but rather via the switch array 2410.
  • DMCP 2400 is configured as an open-loop charge-pump, although a closed-loop arrangement would be readily appreciated and understood by those skilled in the art. Therefore, DMCP 2400 relies on the respective loads (not illustrated) connected across each output N12-N11, N13-N11 remaining within predetermined constraints.
  • the DMCP 2400 outputs two voltages Vout+, Vout- that are referenced to a common voltage supply (node N11). Connected to the outputs Vout+, Vout-, N11, and shown for illustration only, is a load 2450. In reality this load 2450 may be wholly or partly located on the same chip as the power supply, or alternatively it may be located off-chip.
  • the load 2450 is a combination of the power amplifier 106 and the load 120.
  • DMCP 2400 is operable in two main modes.
  • a first mode the DMCP 400 operates such that, for an input voltage +VDD, the DMCP 2400 generates outputs each of a magnitude which is a mathematical fraction of the input voltage VDD.
  • the outputs generated in this first mode are of magnitude +VDD/2 and -VDD/2, although when lightly loaded, these levels will, in reality, be +/-VDD/2 - Iload.Rload, where Iload equals the load current and Rload equals the load resistance.
  • the magnitude (VDD) of output voltage across nodes N12 & N13 is the same, or is substantially the same, as that of the input voltage (VDD) across nodes N10 & N11.
  • a second mode the DMCP 400 produces a dual rail output of +/-VDD.
  • FIG. 15b shows a more detailed version of the DMCP 2400 and, in particular, detail of the switch array 2410 is shown.
  • the switch array 2410 comprises six main switches S1-S6 each controlled by corresponding control signal CS1-CS6 from the switch control module 2420.
  • first switch S1 is connected between the positive plate of the flying capacitor Cf and the input voltage source
  • second switch S2 between the positive plate of the flying capacitor and first output node N12
  • third switch S3 between the positive plate of the flying capacitor and common terminal N11
  • fourth switch S4 between the negative plate of the flying capacitor and first output node N12
  • fifth switch S5 between the negative plate of the flying capacitor and common terminal N11
  • sixth switch S6 between the negative plate of the flying capacitor and second output node N13.
  • seventh switch S7 shown dotted
  • control module 2420 which comprises mode select circuit 2430 for deciding which controller 2420a, 2420b or control program to use, thus determining which mode the DMCP operates in.
  • the mode select circuit 2430 and the controllers 2420a, 2420b can be implemented in a single circuit block (not illustrated).
  • switches S1-S6 are used and the DMCP 2400 operates in a similar manner to the LSCP 1400.
  • switches S1-S3 and S5-S6/S7 are used, and switch S4 is redundant.
  • switches can be implemented in a number of different ways (for example, MOS transistor switches or MOS transmission gate switches) depending upon, for example, an integrated circuit's process technology or the input and output voltage requirements.
  • the amplifiers described herein are preferably incorporated in an integrated circuit.
  • the integrated circuit may be part of an audio and/or video system, such as an MP3 player, a mobile phone, a camera or a satellite navigation system, and the system can be portable (such as a battery-powered handheld system) or can be mains-powered (such as a hi-fi system or a television receiver) or can be an in-car, in-train, or in-plane entertainment system.
  • the signals amplified in the amplifier may represent ambient noise for use in a noise cancellation process.
  • processor control code for example on a carrier medium such as a disk, CD- or DVD-ROM, programmed memory such as read only memory (firmware), or on a data carrier such as an optical or electrical signal carrier.
  • a carrier medium such as a disk, CD- or DVD-ROM, programmed memory such as read only memory (firmware), or on a data carrier such as an optical or electrical signal carrier.
  • embodiments of the invention will be implemented on a DSP (digital signal processor), ASIC (application specific integrated circuit) or FPGA (field programmable gate array).
  • the code may comprise conventional program code or microcode or, for example code for setting up or controlling an ASIC or FPGA.
  • the code may also comprise code for dynamically configuring re-configurable apparatus such as re-programmable logic gate arrays.
  • the code may comprise code for a hardware description language such as Verilog TM or VHDL (very high speed integrated circuit hardware description language).
  • Verilog TM or VHDL very high speed integrated circuit hardware description language
  • the code may be distributed between a plurality of coupled components in communication with one another.
  • the embodiments may also be implemented using code running on a field-(re-)programmable analogue array or similar device in order to configure analogue/digital hardware.

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Multimedia (AREA)
  • Microelectronics & Electronic Packaging (AREA)
  • Amplifiers (AREA)
  • Control Of Amplification And Gain Control (AREA)
EP08776120.1A 2007-08-03 2008-08-04 Amplifier circuit Active EP2181500B1 (en)

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GBGB0715254.9A GB0715254D0 (en) 2007-08-03 2007-08-03 Amplifier circuit
GB0716922.0A GB2451527B (en) 2007-08-03 2007-08-30 Amplifier circuit
GB0716917.0A GB2451524B (en) 2007-08-03 2007-08-30 Amplifier circuit
GB0716919.6A GB2451525B (en) 2007-08-03 2007-08-30 Amplifier circuit
GB0716926.1A GB2451529B (en) 2007-08-03 2007-08-30 Amplifier circuit
PCT/GB2008/002641 WO2009019459A1 (en) 2007-08-03 2008-08-04 Amplifier circuit

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TW200908546A (en) 2009-02-16
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GB2451530B (en) 2012-03-21
US20120242413A1 (en) 2012-09-27
TWI458257B (zh) 2014-10-21
KR101466935B1 (ko) 2014-12-03
CA2711022A1 (en) 2009-02-12
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US9252729B2 (en) 2016-02-02
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US20110221533A1 (en) 2011-09-15
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US20150162885A1 (en) 2015-06-11
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EP2568599A1 (en) 2013-03-13
GB2451526B (en) 2012-04-25
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GB2451528B (en) 2012-10-17
GB0716922D0 (en) 2007-10-10
CN101828333B (zh) 2014-08-20
US20130300508A1 (en) 2013-11-14
KR20100059826A (ko) 2010-06-04
GB2451527A (en) 2009-02-04
CN104135235B (zh) 2018-01-19
WO2009019459A1 (en) 2009-02-12
GB2451529A (en) 2009-02-04
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US8988149B2 (en) 2015-03-24
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US20140159816A1 (en) 2014-06-12
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WO2009019460A1 (en) 2009-02-12
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KR101467508B1 (ko) 2014-12-10
US9473098B2 (en) 2016-10-18

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