EP0206160B1 - Alimentation de courant pour filtre électrostatique - Google Patents

Alimentation de courant pour filtre électrostatique Download PDF

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Publication number
EP0206160B1
EP0206160B1 EP86108075A EP86108075A EP0206160B1 EP 0206160 B1 EP0206160 B1 EP 0206160B1 EP 86108075 A EP86108075 A EP 86108075A EP 86108075 A EP86108075 A EP 86108075A EP 0206160 B1 EP0206160 B1 EP 0206160B1
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EP
European Patent Office
Prior art keywords
current
voltage
filter
power supply
supply according
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Expired - Lifetime
Application number
EP86108075A
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German (de)
English (en)
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EP0206160A1 (fr
Inventor
Hermann Dipl.-Ing. Mickal
Franz Dipl.-Ing. Neulinger
Hartmut Dipl.-Ing. Gaul
Helmut Dipl.-Ing. Schummer
Walter Dipl.-Ing. Schmidt
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Siemens AG
MG Technologies AG
Original Assignee
Metallgesellschaft AG
Siemens AG
MG Technologies AG
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Publication of EP0206160A1 publication Critical patent/EP0206160A1/fr
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    • B—PERFORMING OPERATIONS; TRANSPORTING
    • B03—SEPARATION OF SOLID MATERIALS USING LIQUIDS OR USING PNEUMATIC TABLES OR JIGS; MAGNETIC OR ELECTROSTATIC SEPARATION OF SOLID MATERIALS FROM SOLID MATERIALS OR FLUIDS; SEPARATION BY HIGH-VOLTAGE ELECTRIC FIELDS
    • B03C—MAGNETIC OR ELECTROSTATIC SEPARATION OF SOLID MATERIALS FROM SOLID MATERIALS OR FLUIDS; SEPARATION BY HIGH-VOLTAGE ELECTRIC FIELDS
    • B03C3/00—Separating dispersed particles from gases or vapour, e.g. air, by electrostatic effect
    • B03C3/34—Constructional details or accessories or operation thereof
    • B03C3/66—Applications of electricity supply techniques
    • B03C3/68—Control systems therefor
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y10—TECHNICAL SUBJECTS COVERED BY FORMER USPC
    • Y10S—TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y10S323/00—Electricity: power supply or regulation systems
    • Y10S323/903—Precipitators

Definitions

  • the invention relates to a power supply for an electrostatic filter with the features of the preamble of claim 1 (DE-AS 19 23 952).
  • electrostatic filters are often used, the plates and spray wires of which are supplied with such a high DC voltage that in the medium passed between the plates and spray wires ionization of the foreign substances contained and their separation on the plates occurs.
  • the DC voltage (supply voltage) of the plates and spray wires is chosen to be as high as possible.
  • ionization processes also take place in the gas itself, which lead to a constant discharge of the filter up to a corona discharge on the spray wires.
  • the filter discharges via short breakdowns or even voltage breakdowns up to a stationary arc if the direct current supplied by the voltage supply is not interrupted. No significant foreign matter separation is then possible until the subsequent reconstruction of a high DC voltage. In addition, these processes cause wear on the filter, in particular its spray wires, and short downtimes of the entire device.
  • the ionization processes and thus the limit value of the supply voltage mentioned depend on the distribution of the electric field strength between the plates of the electrostatic filter. Insulating layers of foreign substances deposited on the plates must be knocked off, collected and removed at certain intervals - if necessary with the supply voltage switched off for as short a time as possible. Furthermore, ionization forms space charges with strong distortions in the potential course between the plates, whereby the voltage gradient and the spray direction can even be reversed between plates and space charges.
  • the limit value mentioned is therefore not constant during operation.
  • the supply voltage of the filter should be kept as close as possible to this practically uncontrollably changing limit value.
  • electrostatic precipitators contain a voltage supply that is connected to two phases of a three-phase network and takes an alternating current from the network via an electronic steepener.
  • the output voltage of the actuator is controlled by the firing angle and supplies a line-frequency alternating current which is phase-shifted with respect to the input voltage and which then feeds the electrostatic filter as a pulsating continuous current after step-up and rectification.
  • DE-AS 19 23 952 To approximate the optimal working conditions of the filter it is proposed in DE-AS 19 23 952 to start up the voltage on the electrostatic precipitator after the start-up control via the cut control in the actuator until the limit value corresponding to the current state of the filter is reached and there is a voltage breakdown or a similar sudden discharge of the filter occurs.
  • the AC power controller must first be blocked after a breakdown in order to avoid an arc and to wait for the deionization of the plasma formed.
  • the currentless minimum pause is determined by the frequency of the actuator, i.e. the mains frequency.
  • the result of this is that the filter is fed by a direct current which flows practically without gap with a ripple corresponding to the mains frequency and which is interrupted after a breakdown.
  • the filter voltage fed by this current results in an undulating course which rises until it breaks down.
  • Electrostatic precipitators have also been proposed in which the filter is not supplied with such a practically seamless direct current which is taken from the supply network by a mains-frequency alternating current regulator, is highly transformed and rectified. Rather, the filter is charged by a sequence of individual voltage or direct current pulses.
  • the frequency and / or duration of the individual pulses are specified in such a way that the average current intensity of these isolated direct current pulses assumes a filter current setpoint value that is adapted to the respective filter condition. This creates a filter voltage that is rippled in accordance with the pulse repetition frequency, the value of which is as far as possible below the breakdown limit.
  • a combination is currently striven for as an optimal method in which the filter is initially biased via a rectifier with an already relatively high, practically constant basic DC voltage, which is then superimposed on an AC voltage or isolated individual voltage pulses in order to generate a rippled filter voltage.
  • the height of the filter is said to be considerably above the breakdown voltage of the filter, but a very short pulse duration means that no arc is formed when the filter is discharged.
  • the duration, shape and pulse repetition frequency of these isolated individual pulses are adapted to the respective load condition of the filter.
  • insulated current pulses are fed to the filter biased to the constant basic DC voltage, the maximum amplitude of which is controlled in accordance with a setpoint value for the filter current so that the filter is thereby pulsed to a maximum voltage below the breakdown voltage.
  • These current pulses are taken from an intermediate circuit fed by a rectifier by means of a resonant circuit converter dimensioned to the desired pulse width or a frequency-controlled converter with forced quenching and are transformed up.
  • the ripple of the filter voltage is also ensured in that a diode suppresses one polarity of the highly transformed current impulse.
  • DE-OS 27 13 675 proposes a simple power supply in which the basic voltage is supplied by a gate-controlled AC power controller connected to two phases of a three-phase network with a transformer and rectifier connected downstream.
  • the electrodes supplied with the basic direct voltage are connected to the secondary winding of a high-voltage transformer via a coupling capacitor, the primary winding of which is fed by a controllable rectifier device via an inverter in the center point circuit.
  • the DC link makes it possible to adapt the power consumption from the grid to the requirements of the grid largely independently of the operation of the inverter and to shield it from the commutation perturbations of the inverter.
  • the inverter can be operated at high frequency, which results in a favorable design of the power unit on the one hand, and an optimal adaptation to the deposition process on the other hand.
  • F denotes the electrostatic filter, between the plates of which the medium represented by an arrow M (for example flue gas or another exhaust gas) is passed and which has a voltage U, which is detected by a measuring element MU, from a supply network N.
  • M for example flue gas or another exhaust gas
  • U which is detected by a measuring element MU
  • the intermediate circuit of a converter is fed by the voltage of the supply network N with a network-side controllable rectifier arrangement and a filter-side inverter with a controllable freewheeling path for the intermediate circuit current.
  • WP denotes the primary winding of a high-voltage transformer connected to the AC (or three-phase) output of the converter, the secondary winding WS of which feeds the electrodes of the filter F via a high-voltage rectifier GRH, preferably an uncontrolled rectifier bridge.
  • the controlled rectifier arrangement is, as shown in FIG. 1, an uncontrolled rectifier GR which is followed by a current actuator for the intermediate circuit direct current I which can be measured by means of a measuring element MI.
  • a DC regulator containing a free-wheeling diode FD with the control valve ST and a high-frequency operating frequency, preferably about 5 kHz, is used as the actuator, the downstream intermediate circuit choke ZI (together with an intermediate circuit capacitor ZK) need only be matched to the smoothing of this high frequency and decouples this Network N connected to the rectifier GR from possible repercussions of the inverter and the filter.
  • there is practically only a symmetrical three-phase active load (cos ⁇ 1).
  • the intermediate circuit current which can be regulated by a current controller IR and the control set SSt of the actuator ST to a setpoint l *, flows through the choke ZI - with the valve ST ignited from the mains and with the valve blocked via the freewheeling diode FD - practically constant, regardless of the switching state of the inverter.
  • Such a circuit is customary as a pulse-controlled inverter, which connects a DC voltage impressed via correspondingly large DC link capacitors within a half cycle of a sinusoidal, low-frequency target output voltage in the form of sinusoidally pulse-width-modulated, high-frequency voltage pulses with alternating signs to the AC voltage outputs.
  • a pulse-controlled inverter which connects a DC voltage impressed via correspondingly large DC link capacitors within a half cycle of a sinusoidal, low-frequency target output voltage in the form of sinusoidally pulse-width-modulated, high-frequency voltage pulses with alternating signs to the AC voltage outputs.
  • this known circuit is operated here for the direct current impressed by the choke ZI and the controller IR in order to generate a high-frequency alternating current (working cycle preferably 1 to 3 kHz) by alternating switching of the direct current to the alternating current outputs.
  • valves Tr1 and Tr4 or Tr2 and Tr3 are simultaneously fired after a half cycle, current pulses flow through the connected winding WP, the length of which is equal to the half cycle and the amplitude is equal to the direct current.
  • Such "cross firings”, which temporarily release the freewheeling path of the direct current, are carried out according to FIG. 1 at least whenever a breakdown in the filter is detected. This can e.g. recognize a threshold value element SG from a breakdown of the filter voltage U. At the same time, the normal ignition pulses are blocked via the control rate WSt of the inverter.
  • a program part "program” controls the re-enabling of the inverter, in addition the ramping up of the AC amplitude and / or the inverter frequency itself, e.g. depending on the penetration frequency. and on the foreign matter content of the inflowing and outflowing medium can be controlled by the program part.
  • the current flowing into the transformer is always limited to the impressed direct current, even if there is a breakdown in the filter, but is also maintained during an inverter lock, so that the inverter feed into the transformer can be resumed as quickly as desired.
  • the transformer itself has to be tuned to the high frequency of the inverter and is therefore very inexpensive.
  • an additional voltage limitation control is preferably provided, which limits the filter voltage to the filter voltage setpoint belonging to the specified operating point.
  • the voltage setpoint U * set in the setpoint generator SS is compared with the actual voltage value U measured by the voltage measuring element MU and fed via a limiting regulator BR to a limiting circuit BG at the input of the current regulator IR.
  • the foreign substance raw gas content (content of the inflowing medium of foreign substances) and / or foreign substance pure gas content (foreign substance content of the outflowing medium) can be used as input signals.
  • the supply voltage and / or supply current of the filter can be optimized, in particular they can be controlled according to a predefined voltage / current characteristic. This characteristic can be dependent on the raw material gas content, i.e. the load state of the filter.
  • the controller can react very quickly to any voltage drop and to the start and end of a knocking process and the ripple of the voltage, i.e. the fluctuation of the voltage between an upper and lower limit value can be specified and optimized.
  • controllable rectifier arrangement is shown schematically as a controllable three-phase rectifier bridge DR, which already contains the necessary means to change the intermediate circuit current I (measuring element MI) of an intermediate circuit converter and thus the amplitude of the high-frequency actuator output current with a certain control behavior regulate.
  • the intermediate circuit contains an intermediate circuit choke ZI, which is designed to smooth the intermediate circuit current and is optionally supplemented by an intermediate circuit capacitor.
  • the downstream inverter AR generates the high-frequency alternating current.
  • the suitable inverter shown in FIG. 2 is known as an inverter with "phase sequence deletion".
  • a two-phase bridge is sufficient, although in principle three-phase and multi-phase bridges can also be possible and possibly also advantageous in order to obtain a direct current that is as complete as possible after step-up transformation and rectification.
  • valves ignite in the normal phase sequence TH1 and TH4 and the valves TH2 and TH3 each simultaneously and delete the previously ignited valves by reloading the commutation capacitors K1 and K2.
  • the transverse thyristor TQ is provided as a means for cross-ignition.
  • the specified intermediate circuit current continues to flow through the choke ZI, but is passed via the freewheeling path TQ past the primary winding WP, which therefore quickly de-energizes in every phase position of the inverter and, after blocking any number of converter clock pulses, is excited again with the full intermediate circuit current can be. After a breakdown, the required separation voltage can be quickly built up again.
  • cross-firings can also be carried out by firing valves in series. They can also be provided in order to shorten the current carrying time of the valves fired in the normal clock sequence compared to a half period of the inverter output current. The impressed intermediate circuit current itself is practically not affected by these switching operations.
  • the operating point of the power supply is determined in that a setpoint generator SS specifies a setpoint I for the intermediate circuit current or the amplitude of the alternating output current, the control deviation of which controls the control rate SDR for the controlling means of the controllable rectifier arrangement via a current controller SR.
  • the setpoint I * can in particular be determined on the basis of a current / voltage characteristic stored in the setpoint generator SS, to which the value for the optimum voltage U * is specified by a current control program part PS.
  • U * can be changed periodically, for example as a function of the foreign substance content measured on a flue gas probe RG, in order to generate the aforementioned ripple in the filter supply voltage.
  • the optimal basic level for U * can be determined by a flue gas probe EG depending on the raw material gas content or can be changed in an iterative search procedure so that on the one hand a high degree of separation, on the other hand a low frequency of breakdowns and voltage dips occur on the measuring element MU.
  • limiting the voltage to the predetermined value U * is advantageous.
  • the setpoint / actual value difference of the supply voltage U is applied to a limit controller BR, which operates on a limit circuit BG which limits the current setpoint.
  • a ramp generator HG is provided at the setpoint input of the limiting controller PR, the final value (for example depending on the frequency of the voltage breakdowns detected on the voltage measuring element MU) can be changed by a pulse program part PI.
  • the pulse program part PI also has the task of specifying the AC output frequency and thus the high frequency of the inverter AR by means of a corresponding, operationally dependent control signal for the inverter tax rate WSt. It also generates the switching signal for the freewheeling path (valve TQ) and the temporary stopping and restarting of the inverter after a breakdown.
  • the DC current drawn from the high-voltage rectifier GRH can be interrupted by periodic blocking ("packet formation") and thus a voltage ripple on the filter can also be forced.
  • the coupling capacitor KK shown in FIG. 2 also facilitates the additional connection of such pulses which can be applied to the corresponding input terminals HFI of the filter.

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  • Engineering & Computer Science (AREA)
  • Automation & Control Theory (AREA)
  • Inverter Devices (AREA)
  • Electrostatic Separation (AREA)
  • Dc-Dc Converters (AREA)

Claims (10)

1. Dispositif d'alimentation en courant pour un électrofiltre (F), comportant un transformateur, dont l'enroulement primaire (WP) est raccordé au réseau d'alimentation (N) par l'intermédiaire d'un convertisseur statique (Tr1 ... Tr4, D1, ... D4, GR) et dont l'enroulement secondaire (WS) alimente l'électrofiltre par l'intermédiaire d'un redresseur (GRH) monté sur le filtre, caractérisé par le fait que le convertisseur statique est un convertisseur à circuit intermédiaire constitué par un dispositif redresseur commandé (GR, ST), installé sur le côté réseau et servant à produire un courant injecté (I) du circuit intermédiaire, qui continue à circuler en permanence même dans le cas d'un claquage du filtre, et par un onduleur (Tr1, D1, ..., Tr4, D4) comportant une voie commandable de transmission unidirectionnelle pour le courant du circuit intermédiaire, qui continue à circuler lors d'un claquage du filtre (figure 1).
2. Dispositif d'alimentation en courant suivant la revendication 1, caractérisé par le fait que le dispositif redresseur commandé est constitué par un redresseur non commandé (GR) et par un circuit (ST) branché en aval, de réglage du courant du circuit intermédiaire (figure 1).
3. Dispositif d'alimentation en courant suivant la revendication 2, caractérisé par le fait que le circuit de réglage du courant est un régulateur de courant continu (ST), qui contient une diode à effet unidirectionnel (FD) et possédant une fréquence élevée de travail, de préférence environ 5 kHz, et qu'une bobine d'arrêt (ZI) du circuit intermédiaire, réglée sur le lissage de cette haute fréquence, est branchée en amont de l'entrée de l'onduleur (figure 1).
4. Dispositif d'alimentation en courant suivant l'une des revendications 1 à 3, caractérisé par le fait que l'onduleur est un régulateur, notamment un circuit en pont, formé respectivement d'une valve commandable (Tr1, ..., Tr4), avec laquelle est branchée, selon un montage antiparallèle, une diode (D1, ..., D4), dont la voie de transmission unidirectionnelle peut être commutée au moyen de l'envoi du courant de branches du pont (Tr1, Tr2 ou Tr3, Tr4) susceptible d'être branchées en série (figure 1).
5. Dispositif d'alimentation en courant suivant l'une des revendications 1 à 3, caractérisé par le fait que l'onduleur est conçu pour une extinction de la succession des phases et que la voie de transmission unidirectionnelle est une valve transversale (TQ) située entre les entrées à courant continu de l'onduleur (figure 2).
6. Dispositif d'alimentation en courant suivant l'une des revendications 1 à 5, caractérisé par un générateur de valeurs de consigne (SS) pour une valeur de consigne (1*) du courant du circuit intermédiaire, déterminé sur la base d'une courbe caractéristique courant/tension à partir d'une valeur de consigne optimale prédéterminée de la tension, et par un régulateur de courant (IR) pour la commande du courant (I) du circuit intermédiaire (figure 1).
7. Dispositif d'alimentation en courant suivant la revendication 6, caractérisé par un régulateur (BR) de limitation de la tension, qui limite la valeur actuelle de consigne du courant, en fonction de l'écart de réglage de la tension (U) du filtre par rapport à une valeur de tension (U*) réglée sur la valeur optimale de consigne du courant (figure 1 ).
8. Dispositif d'alimentation en courant suivant l'une des revendications 1 à 7, caractérisé par le fait que l'onduleur raccorde l'enroulement primaire du transformateur au circuit intermédiaire à courant continu, respectivement pendant une alternance d'une cadence de travail prédéterminée à haute fréquence, de préférence une cadence de travail à une fréquence comprise entre environ 1 et 3 kHz, pour une durée prédéterminée d'impulsion, et que le transformateur est dimensionné en fonction de la haute fréquence de la cadence de travail (figure 1).
9. Dispositif d'alimentation en courant suivant l'une des revendications 1 à 8, caractérisé par le fait que dans le cas d'un court-circuit à l'intérieur du filtre, le courant circulant dans le transformateur peut être bloqué temporairement.
10. Dispositif d'alimentation en courant suivant l'une des revendications 1 à 9, caractérisé par le fait que le redresseur (GR) monté sur le filtre est un pont redresseur non commandé.
EP86108075A 1985-06-24 1986-06-12 Alimentation de courant pour filtre électrostatique Expired - Lifetime EP0206160B1 (fr)

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
DE19853522569 DE3522569A1 (de) 1985-06-24 1985-06-24 Stromversorgung fuer ein elektrofilter
DE3522569 1985-06-24

Publications (2)

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EP0206160A1 EP0206160A1 (fr) 1986-12-30
EP0206160B1 true EP0206160B1 (fr) 1990-09-05

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EP86108075A Expired - Lifetime EP0206160B1 (fr) 1985-06-24 1986-06-12 Alimentation de courant pour filtre électrostatique

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US (1) US4779182A (fr)
EP (1) EP0206160B1 (fr)
JP (1) JP2641164B2 (fr)
AU (1) AU582864B2 (fr)
DE (2) DE3522569A1 (fr)
ZA (1) ZA864663B (fr)

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JPS621464A (ja) 1987-01-07
AU5920186A (en) 1987-01-08
DE3522569A1 (de) 1987-01-02
AU582864B2 (en) 1989-04-13
ZA864663B (en) 1987-02-25
JP2641164B2 (ja) 1997-08-13
US4779182A (en) 1988-10-18
DE3673883D1 (de) 1990-10-11
EP0206160A1 (fr) 1986-12-30

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