WO2002049197A2 - Procede d'alimentation d'une charge inductive au moyen d'onduleurs montes en parallele, a commutation progressive - Google Patents

Procede d'alimentation d'une charge inductive au moyen d'onduleurs montes en parallele, a commutation progressive Download PDF

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Publication number
WO2002049197A2
WO2002049197A2 PCT/DE2001/004533 DE0104533W WO0249197A2 WO 2002049197 A2 WO2002049197 A2 WO 2002049197A2 DE 0104533 W DE0104533 W DE 0104533W WO 0249197 A2 WO0249197 A2 WO 0249197A2
Authority
WO
WIPO (PCT)
Prior art keywords
inverter
inverters
resonance
parallel
voltage
Prior art date
Application number
PCT/DE2001/004533
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German (de)
English (en)
Other versions
WO2002049197A3 (fr
Inventor
Andreas SCHÖNKNECHT
Rik W. De Doncker
Original Assignee
Otto Junker Gmbh
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Otto Junker Gmbh filed Critical Otto Junker Gmbh
Priority to EP01270944A priority Critical patent/EP1342310A2/fr
Publication of WO2002049197A2 publication Critical patent/WO2002049197A2/fr
Publication of WO2002049197A3 publication Critical patent/WO2002049197A3/fr

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Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
    • H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
    • H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
    • H02M3/158—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load
    • H02M3/1584—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load with a plurality of power processing stages connected in parallel
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0048—Circuits or arrangements for reducing losses
    • H02M1/0054—Transistor switching losses
    • H02M1/0058—Transistor switching losses by employing soft switching techniques, i.e. commutation of transistors when applied voltage is zero or when current flow is zero
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes

Definitions

  • the invention relates to a method for supplying an inductive load with any number of parallel-connected soft-switching inverters, which are fed by at least one rectifier, each inverter being connected in parallel with at least one capacitor bank, which is connected to at least one voltage intermediate circuit, and the outputs of the inverters to the inductive Load can be coupled.
  • the L f C ⁇ R parallel resonant circuit topology described there has some advantages over topologies with only two energy stores (series resonant circuit or parallel resonant circuit).
  • the resonance choke Z_ ⁇ and the resonance capacitor Ci By adapting the resonance choke Z_ ⁇ and the resonance capacitor Ci, the input impedance Zi of the L 1 C1 2 R parallel resonant circuit (see FIG. 3) can be optimally adapted to the specifications of the inverter, which means the use of a high-frequency transformer at the output of the inverter and means considerable cost savings.
  • the parallel resonant circuit without inductor Li the inductance of the lines from the inverter to the L ⁇ C ⁇ L 2 R parallel resonant circuit in this topology . which inevitably arise when inverters are connected in parallel, not critical.
  • the maximum power available at the load in the L1C 1 L2R parallel resonant circuit topology has so far been limited by the maximum power of an individual inverter unit, consisting of an inverter and an associated resonance choke.
  • EP 0 511 344 B1 shows a method and a device for connecting inverters in parallel.
  • the output chokes of the inverters used there are only balancing chokes, which only serve to avoid cross currents between the individual inverters and ensure an even distribution of the currents.
  • a complex control algorithm is usually required to achieve this. Basically, this means additional work that is caused by the parallel connection. A compromise must be found between the size and thus the effort of the balancing choke and the even distribution of the power or the size of the cross currents.
  • DE 196 51 666 A1 describes a method with which a uniform current distribution can be achieved by means of a special type of balancing choke in the case of several inverters connected in parallel.
  • the method is characterized by a special connection of the balancing chokes with which Ferrite core material can be saved.
  • this method has the disadvantage that the balancing chokes used involve additional expenditure and lead to higher costs.
  • the object of the invention is to provide a method for feeding an ohmic-inductive load in the form of an inductor or induction furnace with a high frequency power product with inverters connected in parallel, which is characterized in that any number of inverters can be connected in parallel without additional hardware expenditure and is possible without complex control technology.
  • the chokes at the output of the individual inverter WR are not balancing chokes but part of the Li Ci L 2 R parallel resonant circuit.
  • the current distribution of the inverters WR is proportional to the value of the inductances of the respective resonance chokes L ⁇ n , which are arranged at the output of the WR. A uniform current distribution is guaranteed if all output chokes L ⁇ n have the same inductance.
  • any number of inverters can be connected in parallel.
  • the inductive coupling of the inverter units to a common capacitor bank i.e. a group of capacitors that are connected to each other by busbars, so that lead inductances usually do not play a major role.
  • the method according to the invention can be used to feed inductors or induction furnaces with a high frequency power product, for example so that steel strips are inductively heated with the help of an inductor with powers of several MW at frequencies of more than 20 kHz.
  • the method is therefore particularly suitable for inductive loads with a low power factor, which have to be supplied with alternating currents at a fixed frequency and with powers of approx. 100 kW to a few MW.
  • powers of several MW at frequencies of approximately 100 kHz are required.
  • the parallel connection of the inverter units ie the inverter together with the associated resonance chokes, is required.
  • Inverters are understood to mean the power semiconductors with drivers and control.
  • the output power is distributed evenly across the inverter units.
  • the inverter units are switched non-synchronously, there are no impermissibly high cross currents between the inverter units.
  • the cost of materials increases only slightly due to the parallel connection compared to a single-inverter system. Additional protective mechanisms that are implemented in the controller are required. However, these play a subordinate role in relation to the total costs of the system.
  • a relatively expensive high-frequency transformer can be dispensed with.
  • a device operating according to this system can be modular, i.e. the number of inverter units can be adapted to the required output power. The power loss is minimized due to the soft switching inverters.
  • the rectifiers can be of any topology.
  • a rectifier is designed for an inverter and forms a module with it. You just switch like that many of these standard modules in parallel as necessary until the required performance is achieved.
  • each WR Since each WR has its own GR, each WR has its own
  • MOSFET power semiconductors For A4: The use of MOSFET power semiconductors is conceivable for (higher) frequencies from approx. 100 kHz to approx. 1 MHz. IGCT power semiconductors are more likely to be used at lower frequencies. Some companies implement 100 kHz converters with MOSFET semiconductors. The IGBT has only recently entered this high frequency range.
  • Re A5 If a defective inverter is a short circuit, it must be ensured that it is disconnected from the DC link. This can be done during operation by power semiconductors (such as IGCTs) or after the system has been switched off by mechanical disconnection. The separation from the intermediate circuit can e.g. by attaching fuses that automatically trip in the event of a short circuit.
  • Another option is to supply the inverter units with independent rectifiers.
  • a short circuit e.g. at the output of one or more inverter units is not critical for the continued operation of the intact inverter units.
  • the power semiconductors of the inverter itself and the intermediate circuit capacitor can also be short-circuited due to a defect. If one inverter fails, the associated rectifier can be switched off and the circuit can be operated with the remaining inverters.
  • Re A6 In the event of an inverter failure, disconnection from the L 1 C 1 L 2 R parallel resonant circuit is always required. After the system has been switched off, it can be disconnected mechanically and also in operation (and then, of course, after the system has been switched off) electrically, ie with a power semiconductor. The electrical separation can take place in such a way that the corresponding Circuit breaker is not switched on when the system is switched on again, provided that the relevant inverter is to remain separated from the others. This means that when switching on, only the inverters that work perfectly are connected to the L ⁇ C-
  • one inverter unit consisting of an inverter and assigned resonance choke including the controller, fails, the operation of the remaining intact units can be continued (redundancy).
  • a reserve inverter can be provided, which can be switched on. Inverters of 200 kW each are conceivable. Since most of the work is in the megawatt range, a requirement of at least 10 inverters can be expected. If an inverter fails until it is repaired, e.g. If the desired performance is not achieved in a belt heating system, this can be temporarily compensated for by slowing down the belt speed.
  • a device can be controlled decentrally, i.e. without a master circuit. Communication between the controls of the inverter units that is necessary for operation does not take place. This makes the overall system less susceptible to interference. If one of the individual controls fails during operation, the remaining controls can continue to work unhindered.
  • the control has the following tasks:
  • A11-A18 In principle, it is a standard control procedure. The special thing is that with this standard control method with the design selected here, decentralized control is possible without communication between the individual controls and without a master. In the past, such control was always carried out by a master, which controls the individual inverters simultaneously. The advantage of this regulation is that no interference-prone communication is necessary. Control redundancy is also achieved. This means that the operation of the inverters 1 with a functioning controller can be continued if any controller fails.
  • a mains transformer can be connected upstream of the rectifier.
  • FIG. 7 a control concept.
  • Figure 1 shows the basic structure of the power section. This consists of N IGBT inverters 1 connected in parallel (three of which are explicitly shown), each with an individually assigned capacitor bank 3 and a common voltage intermediate circuit, which are fed by a rectifier 2 with any topology. Of course, the use of several rectifiers 2 is also conceivable.
  • FIG. 2 shows the topology for an IGBT inverter unit with a voltage intermediate circuit (and capacitor bank) 3.
  • An L f CrZ - ⁇ - parallel resonant circuit is connected to the output of the inverter 1 (see FIG. 3), since a LyCr element applies an ohmic-inductive load 11 adapts the inverter 1, whereby of course several ohmic-inductive loads can also be provided.
  • the total inductance of the resonance chokes 6 was divided between the N inverters 1 connected in parallel.
  • the respective resonance inductor 7 must be arranged symmetrically, for example resonance inductor 7 is divided into two partial inductors, each with L n / 2.
  • the inverters 1 are operated in the vicinity of the resonance frequency fo of the L 1 C1L2R parallel resonant circuit 5 with the switching frequency f s , which results from the parallel connection of the total inductance 6 of the resonance reactors and the total inductance 9 of the ohmic-inductive load 11 with the resonance capacitor 8 7 (see Figure 3). Neglecting the damping, the following applies to this frequency:
  • of the L 1 C1L2R parallel resonant circuit a local minimum.
  • FIG. 4 shows the voltage and current profiles at the outputs of two inverters 1 connected in parallel due to the resulting bandpass character at this operating point, for example, with ideally simultaneous switching and with identical resonance chokes.
  • the respective output current In and I 12 of the inverter 1 is sinusoidal due to the bandpass character of the f C ⁇ ft parallel resonant circuit despite the respective rectangular output voltages Un and U ⁇ 2 -
  • the output power of the inverter system i.e. All inverters connected in parallel are controlled by the rectifier 2 via the voltage Udc of the DC voltage intermediate circuit or on the capacitor 3.
  • FIG. 5 shows that in the case of non-synchronous switching, the output currents n , here In and I- I2 , of the individual inverter units are in phase and only have different amplitudes.
  • Figure 6 shows the principle of the decentralized control concept.
  • the control In order to achieve a high level of reliability and modularity of the system, the control should be set up decentrally and there should be no communication between controls 13 of different inverters 1.
  • Each controller 13 therefore only measures quantities within the associated inverter 1, that is the output voltage and the output current ⁇ n of the inverter 1.
  • the voltage U 2 at the ohmic-inductive load 11 can also be used for improved control properties.
  • a rectifier 2 with an upstream transformer 14 feeds a DC voltage intermediate circuit U dC or a capacitor 3 to which N inverters 1 connected in parallel are connected.
  • the transformer 14 is a mains transformer 14, which has the task of transforming the mains voltage down to a value that is reasonable for the rectifier 2. Depending on the type of rectifier and the power supply, this transformer 14 can be omitted become. All inverters 1 are connected to a common resonance capacitor 8 via resonance chokes 7, which are also connected in parallel and which, for reasons of symmetry, have to be divided into two resonance chokes with inductance L- / n / 2.
  • Each of these inverters 1 has its own DC link in the form of a capacitor 3, which is connected to the inverter 1 in a low-inductance manner. All inverters 1 are controlled independently of one another without the controls of different inverters 1 communicating with one another. For this purpose, the individual controls 13 record the output voltage of the respective inverter U ⁇ n , the output current of the respective inverter U n and the voltage U 2 at the ohmic-inductive load 11. With the aid of these variables, each controller 13 controls its respective inverter 11 with the frequency s at which the angle ⁇ has the respective desired value ⁇ *.
  • FIG. 7 presents an example of the control concept from FIG. 6, with which the respective controller 13 is able to switch the assigned inverter 1 in the vicinity of the resonance frequency f 0 with the switching frequency f s and simultaneously with the other inverters 1 synchronize so that they switch at the same time.
  • the controlled variable is the frequency fo with which the inverter 1 is controlled.
  • This frequency can be recognized, for example, by the fact that the inverter output voltage (Jin and the inverter output current ⁇ n are in phase. Since there are two resonance frequencies for which this is the case, it makes sense to add a further measured variable, e.g. the angular shift between the Voltages l / ⁇ n and U.
  • the task of the control is to control the inverter 1 with the switching frequency f s , which is in the vicinity of the operating frequency f 0 , so that the angle ⁇ "between the inverter output voltage U- ⁇ and current assumes a predetermined setpoint value ⁇ " *.
  • a control system with two superimposed control loops was developed, which is based on the principle of a so-called phase-locked loop (PLL).
  • PLL phase-locked loop
  • the inverter output voltages t / ⁇ n and the voltage U 2 at the ohmic-inductive load 11 and the inverter output current ⁇ are detected by means of voltage and current transformers. From this, angle detectors 16 determine the angle ⁇ n , ie the angular displacement between -J ⁇ "and U 2 , and the angle ⁇ n , ie the angular displacement between U ⁇ and / ⁇ ".
  • An inner control loop subtracts the detected angle ⁇ "from the target value ⁇ " * given by the outer control loop. The resulting difference is given to the input of a PI controller 21, at whose output the setpoint for the switching frequency fs is present.
  • a voltage-controlled oscillator (VCO, "Voltage Controlled Oscillator”) 18 converts this setpoint into switching signals which are transmitted to the drivers 12 of the inverter 1.
  • VCO Voltage Controlled Oscillator
  • An external control loop serves to track ⁇ "* when the ohmic-inductive load 11 changes, so that the angle ⁇ " * set by the user is established.
  • the detected angle ⁇ " is subtracted from the target value ⁇ " * and passed to a further PI controller or an I controller 17.
  • the setpoint ⁇ mein* is present at the output, which is transferred to the inner control loop.
  • the outer control loop can be omitted.
  • VCO Voltage Controlled Oscillator

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Inverter Devices (AREA)
  • General Induction Heating (AREA)

Abstract

L'invention concerne un procédé et un dispositif d'alimentation d'une charge inductive sous la forme d'un inducteur ou d'un four à induction présentant un produit fréquence-rendement élevé. Ceci est obtenu au moyen d'onduleurs en un nombre quelconque, montés en parallèle, à commutation progressive, qui sont alimentés par au moins un redresseur, à chaque onduleur étant associé au moins un condensateur monté en parallèle et en amont, et connecté à au moins un circuit intermédiaire de tension. Les sorties des onduleurs sont couplées à au moins un circuit oscillant en parallèle L1C1L2R comprenant une charge inductive ohmique L2R, un condensateur à résonance C1 et l'inductivité globale L1 des bobines de résonance. Les onduleurs sont montés synchrone et sont commandés par la fréquence de résonance (f0) du circuit oscillant en parallèle L1C1L2R, ou légèrement au-dessus ou au-dessous de la fréquence de résonance (f0) de la fréquence de commutation (fs).
PCT/DE2001/004533 2000-12-14 2001-12-05 Procede d'alimentation d'une charge inductive au moyen d'onduleurs montes en parallele, a commutation progressive WO2002049197A2 (fr)

Priority Applications (1)

Application Number Priority Date Filing Date Title
EP01270944A EP1342310A2 (fr) 2000-12-14 2001-12-05 Procede d'alimentation d'une charge inductive au moyen d'onduleurs montes en parallele, a commutation progressive

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
DE10062317.4 2000-12-14
DE10062317 2000-12-14

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WO2002049197A3 WO2002049197A3 (fr) 2003-03-13

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Cited By (6)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
EP1870994A1 (fr) * 2006-06-23 2007-12-26 ALSTOM Technology Ltd Alimentation électrique pour précipitateur électrostatique
WO2009147551A1 (fr) * 2008-06-02 2009-12-10 Philips Intellectual Property & Standards Gmbh Système d'alimentation électrique modulable pour alimenter un dispositif de tomodensitométrie en énergie électrique
GB2477171A (en) * 2009-08-28 2011-07-27 Gen Electric Push-pull inverter device
CN103368404A (zh) * 2013-08-02 2013-10-23 陶顺祝 一种集成电感谐振变换器
CN113316888A (zh) * 2019-01-21 2021-08-27 索尤若驱动有限及两合公司 具有第一变流器和至少一个第二变流器的驱动系统
CN113972849A (zh) * 2021-10-27 2022-01-25 珠海格力电器股份有限公司 感应加热电源的频率自适应装置、方法及相关设备

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US5081409A (en) * 1989-11-13 1992-01-14 Performance Controls, Inc. Pulse-width modulated circuit for driving a load
JPH09289979A (ja) * 1996-04-26 1997-11-11 Hitachi Medical Corp 磁気共鳴イメージング装置用電源装置

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Publication number Priority date Publication date Assignee Title
US5081409A (en) * 1989-11-13 1992-01-14 Performance Controls, Inc. Pulse-width modulated circuit for driving a load
JPH09289979A (ja) * 1996-04-26 1997-11-11 Hitachi Medical Corp 磁気共鳴イメージング装置用電源装置

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Cited By (10)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
EP1870994A1 (fr) * 2006-06-23 2007-12-26 ALSTOM Technology Ltd Alimentation électrique pour précipitateur électrostatique
JP2008011697A (ja) * 2006-06-23 2008-01-17 Alstom Technology Ltd 静電集塵器用の電源
US7649753B2 (en) 2006-06-23 2010-01-19 Alstom Technology Ltd Power supply for electrostatic precipitator
AU2007202910B2 (en) * 2006-06-23 2011-06-30 General Electric Technology Gmbh Power supply for electrostatic precipitator
WO2009147551A1 (fr) * 2008-06-02 2009-12-10 Philips Intellectual Property & Standards Gmbh Système d'alimentation électrique modulable pour alimenter un dispositif de tomodensitométrie en énergie électrique
GB2477171A (en) * 2009-08-28 2011-07-27 Gen Electric Push-pull inverter device
GB2477171B (en) * 2009-08-28 2012-03-07 Gen Electric Switching inverters and converters for power conversion
CN103368404A (zh) * 2013-08-02 2013-10-23 陶顺祝 一种集成电感谐振变换器
CN113316888A (zh) * 2019-01-21 2021-08-27 索尤若驱动有限及两合公司 具有第一变流器和至少一个第二变流器的驱动系统
CN113972849A (zh) * 2021-10-27 2022-01-25 珠海格力电器股份有限公司 感应加热电源的频率自适应装置、方法及相关设备

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EP1342310A2 (fr) 2003-09-10
WO2002049197A3 (fr) 2003-03-13

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