CN110463033B - 增强型线性混频器 - Google Patents

增强型线性混频器 Download PDF

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CN110463033B
CN110463033B CN201880020736.1A CN201880020736A CN110463033B CN 110463033 B CN110463033 B CN 110463033B CN 201880020736 A CN201880020736 A CN 201880020736A CN 110463033 B CN110463033 B CN 110463033B
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CN110463033A (zh
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威廉·斯蒂芬·哈恩
阿尔弗雷德·里德尔
厄尼·兰迪
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Qualcomm Inc
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Kumu Networks Inc
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    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B1/00—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission
    • H04B1/38—Transceivers, i.e. devices in which transmitter and receiver form a structural unit and in which at least one part is used for functions of transmitting and receiving
    • H04B1/40—Circuits
    • H04B1/54—Circuits using the same frequency for two directions of communication
    • H04B1/56—Circuits using the same frequency for two directions of communication with provision for simultaneous communication in two directions
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B1/00—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission
    • H04B1/38—Transceivers, i.e. devices in which transmitter and receiver form a structural unit and in which at least one part is used for functions of transmitting and receiving
    • H04B1/40—Circuits
    • H04B1/44—Transmit/receive switching
    • H04B1/48—Transmit/receive switching in circuits for connecting transmitter and receiver to a common transmission path, e.g. by energy of transmitter
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L5/00—Arrangements affording multiple use of the transmission path
    • H04L5/14—Two-way operation using the same type of signal, i.e. duplex
    • H04L5/1461—Suppression of signals in the return path, i.e. bidirectional control circuits
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B1/00—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission
    • H04B1/005—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission adapting radio receivers, transmitters andtransceivers for operation on two or more bands, i.e. frequency ranges
    • H04B1/0067—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission adapting radio receivers, transmitters andtransceivers for operation on two or more bands, i.e. frequency ranges with one or more circuit blocks in common for different bands
    • H04B1/0075—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission adapting radio receivers, transmitters andtransceivers for operation on two or more bands, i.e. frequency ranges with one or more circuit blocks in common for different bands using different intermediate frequencied for the different bands
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L5/00—Arrangements affording multiple use of the transmission path
    • H04L5/14—Two-way operation using the same type of signal, i.e. duplex
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L5/00—Arrangements affording multiple use of the transmission path
    • H04L5/14—Two-way operation using the same type of signal, i.e. duplex
    • H04L5/1423—Two-way operation using the same type of signal, i.e. duplex for simultaneous baseband signals

Abstract

一种用于增强型线性混频的系统，包括：输入源信号耦合器；本地振荡器(LO)信号耦合器；主混频器，其通过外差法将主混频器输入信号和主混频器LO信号组合，以生成主混频器输出信号；失真源混频器，其通过外差法将失真混频器输入信号和失真混频器LO信号组合，以生成失真混频器输出信号；以及输出信号耦合器，其将主混频器输出信号和失真混频器输出信号组合，以生成非线性度减小的输出信号。

Description

增强型线性混频器
相关申请的交叉引用
本申请要求于2017年3月27日提交的序列号为62/477,346的美国临时申请和于2017年12月14日提交的序列号为62/598,739的美国临时申请的权益，这两者都通过引用以其整体并入。
技术领域
本发明大体上涉及模拟电路领域，并且更具体地涉及用于增强型线性混频的新的且有用的系统和方法。
背景
传统的无线通信系统是半双工的；也就是说，它们不能够在单个无线通信信道上同时发射信号和接收信号。最近，在无线通信领域的工作带来了在开发全双工无线通信系统中的进步；如果这些系统被成功地实现，则可以给无线通信领域提供巨大的益处。例如，蜂窝网络使用全双工通信可以将频谱需求减半。成功实现全双工通信的一个主要障碍是自干扰的问题。
解决自干扰的许多解决方案依赖于混频电路(例如，作为模拟自干扰消除器的一部分)，但是由于传统混频器固有的限制，这些解决方案在性能上可能会受到影响。因此，在无线通信领域中需要建立用于增强型线性混频的新的且有用的系统以及方法。本发明提供了这样的新的且有用的系统以及方法。
当然，这种用于增强型线性混频的系统和方法可以应用于模拟电路的多种应用中。
附图的简要说明
图1是发明实施例的系统的视图；
图2是混频器的输出信号的示例视图；
图3是发明实施例的系统的信号组合的示例视图；
图4是发明实施例的系统的信号组合的示例视图；
图5是发明实施例的系统的信号组合的示例视图；
图6是发明实施例的系统的信号组合的示例视图；和
图7是发明实施例的系统的视图。
发明实施例的描述
本发明的发明实施例的以下描述并非旨在将本发明限制于这些发明实施例，而是旨在使本领域的任何技术人员能够制造并且使用本发明。
1.全双工无线通信系统
无线通信系统已经彻底改变了世界通信的方式，并且使用这样的系统的通信的快速增长已经在所有地区和行业中提供了更多的经济和教育机会。不幸的是，通信所需的无线频谱是有限的资源，并且无线通信的快速增长也使该资源的可用性变成更为稀缺。其结果是，频谱效率对于无线通信系统已经变得越来越重要。
在全双工无线通信系统中发现了一种用于增加频谱效率的有希望的解决方案；即，能够在同一时间在同一无线信道上发射无线信号并且接收无线信号的无线通信系统。与标准半双工无线通信系统相比，此技术允许频谱效率的加倍。
虽然全双工无线通信系统对于无线通信领域具有实质价值，但是已知这样的系统由于自干扰而面临挑战；因为接收和发射在同一时间在同一信道上发生，所以在全双工收发机处所接收的信号可以包括来自从该收发机发射的信号的不期望的信号分量。其结果是，全双工无线通信系统通常包括减少自干扰的模拟和/或数字自干扰消除电路。
全双工收发机优选地采样作为基带数字信号、中频(IF)模拟信号或作为射频(RF)模拟信号的传输输出，但是全双工收发机可以附加地或可替代地以任何合适的方式(例如，作为IF数字信号)对传输输出进行采样。此被采样的传输输出可以由全双工收发机使用以消除来自所接收的无线通信数据(例如，作为RF/IF模拟信号或基带数字信号)的干扰。在许多全双工收发机中，模拟自干扰消除系统与数字自干扰消除系统配对。模拟自干扰消除系统通过对RF发射信号的延迟版本、相移版本和缩放版本求和，以产生RF自干扰消除信号，然后从RF接收信号中减去该信号，来去除自干扰的第一部分。可选地，模拟消除系统可以在中频处完成类似的工作。RF(或IF)接收信号减去RF/IF自干扰消除信号后，RF(或IF)接收信号通过接收机的模数转换器(并且成为数字接收信号)。在这个阶段之后，然后从数字接收信号中减去(通过转换数字发射信号而产生的)数字自干扰消除信号。
本文描述的系统和方法可以通过实现高线性混频来提高全双工收发器(和其他可适用的系统)的性能，而没有在电路复杂度和/或成本方面过度增加。其他可适用的系统包括主动感测系统(例如，雷达)、有线通信系统、无线通信系统、信道仿真器、反射计、PIM分析仪和/或任何其他以模拟电子器件为特征的系统(包括发射频带和接收频带在频率上相近但不重叠的通信系统)。
2.用于增强型线性混频的系统
如图1所示，用于增强型线性混频的系统100包括主混频器110、失真源混频器120和信号耦合器150。系统100可以另外包括移相器130、缩放器140和/或谐波短路电路160。
系统100用于提高混频器(或者更一般地，包括混频器的电路和线路(line-ups))的线性度。高线性度电路对于各种模拟电子系统非常重要，特别是在通信系统中。传统上，模拟电路设计人员可以通过提供(sourcing)更高线性度的部件(这可能会产生显著的成本)、降低功率电平(这可能会对信噪比等级或其他方面产生负面影响)或通过显著增加电路复杂性和功耗来提高线性度。
根据类似于章节1中讨论的自干扰消除技术的一般原理运行，系统100利用部件(例如，失真源混频器120)来对存在于主混频器110(或包括主混频器110的更一般的电路)的输出中的失真建模并减去该失真，从而建立比单独的主混频器110的输出更线性的系统100的输出。
主混频器110用于将输入信号从第一频率转换成第二频率；例如从射频(RF)到中频(IF)或基带，或者从基带到RF或IF，或者从IF到基带或RF。
主混频器110优选地是有源混频器，但是可附加地或者可选择地是无源混频器。主混频器110可以包括分立部件、模拟集成电路(IC)、数字IC和/或任何其他合适的部件。主混频器110优选地用于将两个或更多个电输入信号组合为一个或更多个复合输出，其中每个输出都包括至少两个输入信号的一些特征。
主混频器110优选地接收输入信号以及频移信号，频移信号优选地由本地振荡器(LO)提供。本地振荡器优选地是PLL(锁相环)操纵的数字晶体可变频振荡器(VFO)，但是附加地或者可选择地可以是模拟VFO或者任何其他合适类型的振荡器。本地振荡器优选地具有可调谐振荡频率，但是可附加地或者可选择地具有静态振荡频率。
给定以频率f1为中心的输入信号和频率f2处的频移信号，主混频器110可以在以下频率中每一个处产生输出信号(每个信号是输入信号和频移信号的乘积)：f＝nf1+mf2，其中n和m是整数。例如，f1为900MHz，f2为750MHz，并且期望的输出频率为150MHz。在本例中，有问题的输出是150MHz附近的输出，而不是来自处于f1-f2的主输出。在本例中，除了接近期望频率的主输出之外的输出处于{{n,m}}＝{{-4,5},{6,-7}}(对于大多数混频器来说，这几乎不存在)。
不幸的是，当主混频器110同时遇到多个紧密间隔的信号时(这在通信中是常见的)，情况更加复杂。现在假设两个输入信号在f1和f2处，频移在f3处；现在乘积可以在全部的f＝nf1+mf2+of3处产生。现在假设f1为900.00MHz，f2为900.050MHz，f3为750MHz，并且期望的输出频率为150.000MHz和150.050MHz。现在，存在一些令人困扰的输出：{{n,m,o}}＝{{2,-1,-1},{-1,2,-1}}(三阶项)、{{n,m,o}}＝{{3,-2,-1},{-2,3,-1}}(五阶项)和{{n,m,o}}＝{{4,-3,-1},{-3,4,-1}}(七阶项)。这些输出示于图2中。
失真源混频器120用于对主混频器110的失真建模(例如，如图2所示)。然后可以从主混频器110的输出中减去失真源混频器120的这个输出，以减少存在于主混频器110的输出中的失真。
因为失真混频器输出中的一阶分量与高阶分量(即，阶>1的分量，也被称为非线性分量)的信号功率比优选地高于主混频器输出中的一阶分量与高阶分量的信号功率比，因此从主混频器输出中减去失真混频器输出，与其减少一阶分量相比更多地减少了高阶分量，所以主混频器110的输出中存在的失真被降低。
失真源混频器120优选地基本上类似于主混频器110，但是失真源混频器120可以是具有不同于主混频器110的基本特征的混频器(可选地，它们可以是相同的)。
在第一配置中，主混频器110和失真源混频器120具有基本相同的配置和特征(例如，输入参考的三阶截取点(IIP3)、转换增益、本底噪声、频率响应)以及基本相同的输入信号。在该实施例中，失真源混频器120的输出可以(通过缩放器140)相对于主混频器110衰减并(通过移相器130)反相，然后与主混频器110的输出组合。然而，如图3所示，在本发明实施例中，主混频器110中失真的任何减小都伴随着期望信号中的相等减小(例如，期望信号和失真都减小了12dB)。这种配置是不希望的。
在第二配置中，主混频器110和失真源混频器120具有基本上相同的特征(例如，IIP3、转换增益、本地噪声、频率响应)，但是不同的输入信号。在这种配置中，失真源混频器120的输入信号具有比主混频器110更高的功率(通过分离、衰减和/或增益的某种组合)。因为三阶互调产物大致随着三阶输入功率增加(对于五阶和七阶产物，依此类推)，所以在这种配置中，增加的输入功率意味着失真源混频器120产生的信号比主混频器110产生的信号更非线性。然后失真源混频器120的输出可以在相减之前被衰减(或者主混频器110的信号可以被放大)。这可能是系统100的期望配置。如图4所示的示例。如图5所示，要注意的是，这种技术可能受到高阶互调产物的限制；也就是说，如果失真源混频器120输入端上的信号(增益)增加得足够多，则其可能会导致噪声的增加。
要注意的是，由于制造差异，基本相似的特征可能意味着混频器共用相同的特征规格(例如，每个特征参数具有相同的中心值和相同的误差范围)，但实际上并不相同(例如，两个混频器的插入损耗可能为3dB加或减0.5dB，这意味着一个混频器的插入损耗可能为3.1dB，而另一个混频器的插入损耗为2.7dB)。
第二配置的一种变型是使用相同的输入信号但不同的LO信号电平。当失真源混频器使用较低的LO电平时，它的非线性度会增加，并且互调产物也会增加。结果类似于图4(或图5)所示的曲线图。
对于第二配置所描述的两种方法可以组合起来，以优化线性度、插入损耗、电路复杂性和噪声系数。
在第三配置中，主混频器110和失真源混频器120具有不相同的配置和/或特征(例如，IIP3、转换增益、本底噪声、频率响应、运行模式)，但是基本上相同的输入信号。例如，主混频器110和失真源混频器120可以具有相似的转换增益和本底噪声，但是具有不同的IIP3。在这个示例中，失真源混频器120优选地表现出在形式上类似但幅度大于主混频器110的非线性度的非线性度，从而允许与第二配置类似的效果，但不一定遭受第二配置的相同限制(例如，需要更高的功率和混频器来处理它)。事实上，在一些混频器中，“低功率”模式使混频器能够以较低的运行功率运行，但具有较低的IIP3；在这种情况下，系统100可以使用处于“正常模式”的主混频器110和处于“低功率”模式的失真源混频器120。这可能是系统100的期望配置。如图6所示的示例。
系统100可以附加地或替代地使用具有不同特征、不同输入信号和不同LO信号的两个混频器110/120。混频器110/120可以以任何方式配置，并且不限于给出的示例。
要注意的是，如图1所示，主混频器110和失真源混频器120共用本地振荡器源；附加地或替代地，主混频器110和失真源混频器120可以利用不同的本地振荡器信号。
移相器130优选地用于移动主混频器110和失真源混频器120中的一个的相位，使得在信号相加之前失真源混频器120的输出与主混频器110反相180度。可选地，移相器130可以被用于任何相移目的。
移相器130可以在其输入端和输出端处包括阻抗匹配网络，该阻抗匹配网络补偿移相器130的输入阻抗和输出阻抗(和/或相移量)中由于信号分量频率的变化而产生的变化，或者仅仅将阻抗变换到适当的阻抗水平和将阻抗从适当的阻抗水平变换，以用于移相器的核心到标准阻抗水平(50ohm)。可替代地，移相器130可以不包括阻抗匹配网络。阻抗匹配网络优选地是可调谐的(例如，连续地或离散可变的)，但是可以附加地或可替代地是静态的(即，通过使用网络实现的阻抗变换是不可变的)。
移相器130优选被分成一组相移级(phase shifting stage)。基于控制信号，这些相移级优选地可以被“接通”(例如，在信号路径中)或“断开”(例如，旁路，在信号路径之外)。所得的相移由哪些级接通和哪些级断开来确定；例如，具有90度相移级和10度相移级“接通”的移相器130可能导致信号相位100度的移动。
每个相移级优选地引起设定量(即，不可变量)的相移。可替换地，相移级可以包括可调谐的相移元件。例如，相移级可以包括变容二极管；通过改变变容二极管的控制电压，可以改变变容二极管的电容(并因此改变通过该级的信号经受的相移量)。
移相器130优选地由调谐电路控制，但是可以附加地或替代地以任何合适的方式控制。
要注意的是，移相器130可以位于系统100中的任何点处；例如，在LO和主混频器110关于LO信号的输入端之间；在LO和失真源混频器120关于LO信号的输入端之间；在系统输入端和主混频器110关于输入信号的输入端之间；在系统输入端和失真源混频器120关于输入信号的输入端之间；在主混频器110的输出端和系统输出端之间；和/或在失真源混频器120的输出端和系统输出端之间。
缩放器140用于缩放发射信号分量；具体地，缩放器140有效地将发射信号分量乘以比例因子。例如，34％的衰减可以被表示为0.66的比例因子；20％的增益可以被表示为1.20的比例因子；10％的衰减和反相可以被表示为-0.90的比例因子。比例因子可能很复杂；例如，比例因子可以表示为90度的相移。
缩放器140可以包括衰减器、放大器、反相器和/或用于缩放模拟信号分量的任何其他合适的部件。衰减器可以是电阻衰减器(T型、Pi型)、单位增益以下的放大器或任何其他合适类型的衰减器。放大器可以是晶体管放大器、真空管放大器、运算放大器或任何其他合适类型的放大器。反相器可以是任何反相器件，包括NPN/PNP反相电路、变压器和/或反相放大器。
缩放器140优选地能够衰减、增益和反相，但是可选地可能仅能够实现所述能力的子集。每个缩放器140优选地在单个设备中包括所有三种能力(例如，具有可调谐增益和两个输出端的放大器，一个反相和一个非反相)，但是可以附加地或替代地将能力分成不同的部分(例如，具有可调谐增益但没有反相能力的放大器，以及单独的反相电路、衰减器)。缩放器140优选地由调谐电路控制，但是可以附加地或替代地以任何合适的方式控制。
类似于移相器130，缩放器140可以位于电路中的任何点处。例如，如图1所示，衰减缩放器140可被用于衰减失真源混频器120的输出。附加地或替代地，放大缩放器140可以被用于放大主混频器110的输出。
要注意的是，在一些情况下，功能(例如，反相)可以由移相器130和缩放器140中的任一个或两个来实现。
信号耦合器150用于允许模拟信号被分离和/或组合。信号耦合器150可以使用不同的功率量来耦合和/或分离信号；例如，打算对信号进行采样的信号耦合器150可以具有输入端口、输出端口和采样端口，并且耦合器150可以将大部分功率从输入端口路由到输出端口，其中少量功率来自采样端口(例如，输出端口和采样端口之间分离的功率为99.9％/0.1％，或者任何其他合适的分流)。
信号耦合器150优选是短截面定向传输线耦合器，但是附加地或替代地可以是任何功率分配器、功率组合器、定向耦合器或其他类型的信号分离器。信号耦合器150优选是无源耦合器，但是附加地或替代地可以是有源耦合器(例如，包括增益块和功率放大器)。例如，信号耦合器150可以包括耦合传输线耦合器、支线耦合器、兰格(Lange)耦合器、威尔金森(Wilkinson)功率分配器、混合耦合器、混合环耦合器、多输出分配器、波导定向耦合器、波导功率耦合器、混合变压器耦合器、交叉连接变压器耦合器、T形电阻(resistive tee)和/或电阻桥式混合耦合器。
例如，信号耦合器150可以将输入源信号(系统100的输入)分成两个输入信号，其中一个将作为主混频器110的输入(主混频器输入信号)，另一个将作为失真源混频器120的输入(失真混频器输入信号)。同样地，另一个信号耦合器150可以将本地振荡器信号分成两个信号，其中一个将作为主混频器110的LO信号(主混频器LO信号)，而其中另一个将作为失真源混频器120的LO信号(失真混频器LO信号)。
谐波短路电路160用于减少谐波对系统100输出的贡献(并因此用于增加输出的线性度)。谐波短路电路优选地是调谐到特定谐波频率(例如，3f、5f)处的谐振的串联LC谐振器，但是可以附加地或替代地是能够在特定期望频率下短路系统100的信号路径的任何电路。类似于移相器130和缩放器140，谐波短路电路160可以设置在系统100中的任何点处。例如，可以在失真源混频器120的输出路径中设置三次谐波短路(如图5所示，这减少了在失真源混频器120的输出中的五阶互调(IM5)产物和/或七阶互调(IM7)产物的存在，并且防止了这些分量在相减之后的增长)。谐波短路电路160可以附加地或替代地设置在主混频器110的输入端或输出端、失真源混频器120的输出端或任何其他位置。要注意的是，多个谐波短路电路160可以被并联设置(或者以其他方式可以位于系统100中)，以减少多个频率处谐波的存在。
优选实施例及其变型的方法可以被至少实现部分地体现和/或实现为被配置成接收存储计算机可读指令的计算机可读介质的机器。指令优选地由优选地与用于增强型线性混频的系统集成的计算机可执行部件来执行。计算机可读介质可存储在任何合适的计算机可读媒介上，诸如RAM、ROM、闪存、EEPROM、光学设备(CD或DVD)、硬盘驱动器、软盘驱动器或任何合适的设备。计算机可执行部件优选地是通用或专用处理器，但任何合适的专用硬件或硬件/固件组合设备可替代地或另外地可执行指令。
如本领域中的技术人员将从先前的详细描述以及从附图和权利要求中认识到的，可在不偏离在所附权利要求中限定的本发明的范围的情况下对本发明的优选实施例进行修改和改变。

Claims (22)

1.一种用于增强型线性混频的系统，包括：
输入源信号耦合器，所述输入源信号耦合器将第一输入信号分成主混频器输入信号和失真混频器输入信号；
本地振荡器(LO)信号耦合器，所述本地振荡器(LO)信号耦合器将第一LO信号分成主混频器LO信号和失真混频器LO信号；
主混频器，所述主混频器通过外差法将所述主混频器输入信号和所述主混频器LO信号组合，以生成主混频器输出信号，所述主混频器输出信号包括一阶主混频器输出信号分量和高阶主混频器输出信号分量；其中，所述主混频器输出信号的特征在于所述高阶主混频器输出信号分量与所述一阶主混频器输出信号分量的第一信号功率比；
失真源混频器，所述失真源混频器通过外差法将所述失真混频器输入信号和所述失真混频器LO信号组合，以生成失真混频器输出信号，所述失真混频器输出信号包括一阶失真混频器输出信号分量和高阶失真混频器输出信号分量；其中，所述失真混频器输出信号的特征在于所述高阶失真混频器输出信号分量与所述一阶失真混频器输出信号分量的第二信号功率比；其中，所述第二信号功率比大于所述第一信号功率比；
谐波短路电路，所述谐波短路电路减少所述失真混频器输出信号中的五阶互调(IM5)产物或七阶互调(IM7)产物中的至少一个；和
输出信号耦合器，所述输出信号耦合器将所述主混频器输出信号和所述失真混频器输出信号组合以生成输出信号，所述输出信号包括一阶输出信号分量和高阶输出信号分量；其中，所述输出信号的特征在于所述高阶输出信号分量与所述一阶输出信号分量的第三信号功率比；其中，所述第三信号功率比小于所述第一信号功率比并且小于所述第二信号功率比。
2.根据权利要求1所述的系统，还包括移相器；其中，所述移相器将所述主混频器输入信号、所述失真混频器输入信号、所述主混频器LO信号和所述失真混频器LO信号中的一个反相；其中，反相导致在所述输出信号耦合器处所述主混频器输出信号相对于所述失真混频器输出信号反相。
3.根据权利要求2所述的系统，其中，所述移相器将所述主混频器输入信号反相。
4.根据权利要求2所述的系统，其中，所述移相器将所述主混频器LO信号反相。
5.根据权利要求2所述的系统，其中，所述移相器将所述失真混频器输入信号反相。
6.根据权利要求2所述的系统，其中，所述移相器将所述失真混频器LO信号反相。
7.根据权利要求1所述的系统，其中，高阶信号分量是三阶互调产物。
8.根据权利要求1所述的系统，其中，高阶信号分量是五阶互调产物。
9.根据权利要求1所述的系统，其中，所述失真源混频器和所述主混频器具有相同的特征规格。
10.根据权利要求9所述的系统，其中，所述失真混频器输入信号具有比所述主混频器输入信号更高的信号功率，这将导致所述失真混频器输出信号具有比所述主混频器输出信号更高的非线性度。
11.根据权利要求10所述的系统，还包括第一缩放器，所述第一缩放器衰减所述主混频器输入信号或者放大所述失真混频器输入信号。
12.根据权利要求11所述的系统，还包括第二缩放器，所述第二缩放器衰减所述失真混频器输出信号或放大所述主混频器输出信号，使得所述一阶主混频器输出信号分量具有比所述一阶失真混频器输出信号分量更高的功率。
13.根据权利要求9所述的系统，其中，所述失真混频器LO信号具有比所述主混频器LO信号更低的信号功率，这将导致所述失真混频器输出信号具有比所述主混频器输出信号更高的非线性度。
14.根据权利要求10所述的系统，还包括第一缩放器，所述第一缩放器放大所述主混频器LO信号或者衰减所述失真混频器LO信号。
15.根据权利要求14所述的系统，还包括第二缩放器，所述第二缩放器衰减所述失真混频器输出信号或放大所述主混频器输出信号，使得所述一阶主混频器输出信号分量具有比所述一阶失真混频器输出信号分量更高的功率。
16.根据权利要求9所述的系统，其中，所述失真源混频器以不同于所述主混频器的运行模式运行，这将导致所述失真混频器输出信号具有比所述主混频器输出信号更高的非线性度。
17.根据权利要求16所述的系统，其中，所述失真源混频器以低功率模式运行。
18.根据权利要求8所述的系统，其中，所述失真源混频器和所述主混频器具有不同的特征规格。
19.根据权利要求18所述的系统，其中，所述失真源混频器和主混频器具有不同的输入参考的三阶截取点(IIP3)值。
20.根据权利要求1所述的系统，其中，所述谐波短路电路耦合到所述失真源混频器的输出端。
21.根据权利要求1所述的系统，其中，所述谐波短路电路包括调谐至五次谐波频率的至少一个LC谐振器。
22.根据权利要求1所述的系统，其中，所述谐波短路电路包括调谐至七次谐波频率的至少一个LC谐振器。
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