WO2022254508A1 - 電力変換装置 - Google Patents
電力変換装置 Download PDFInfo
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- WO2022254508A1 WO2022254508A1 PCT/JP2021/020656 JP2021020656W WO2022254508A1 WO 2022254508 A1 WO2022254508 A1 WO 2022254508A1 JP 2021020656 W JP2021020656 W JP 2021020656W WO 2022254508 A1 WO2022254508 A1 WO 2022254508A1
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- 238000006243 chemical reaction Methods 0.000 title claims abstract description 21
- 238000001514 detection method Methods 0.000 claims abstract description 61
- 230000009466 transformation Effects 0.000 claims description 51
- 239000004065 semiconductor Substances 0.000 claims description 13
- 230000003247 decreasing effect Effects 0.000 abstract 1
- 238000004804 winding Methods 0.000 description 34
- 239000003990 capacitor Substances 0.000 description 24
- 230000001131 transforming effect Effects 0.000 description 12
- 230000001172 regenerating effect Effects 0.000 description 5
- 230000007423 decrease Effects 0.000 description 4
- 238000010586 diagram Methods 0.000 description 4
- 230000007274 generation of a signal involved in cell-cell signaling Effects 0.000 description 4
- 238000003745 diagnosis Methods 0.000 description 3
- 230000001360 synchronised effect Effects 0.000 description 3
- 238000000844 transformation Methods 0.000 description 3
- 230000008878 coupling Effects 0.000 description 2
- 238000010168 coupling process Methods 0.000 description 2
- 238000005859 coupling reaction Methods 0.000 description 2
- 238000000034 method Methods 0.000 description 2
- 238000012545 processing Methods 0.000 description 2
- 238000012935 Averaging Methods 0.000 description 1
- HBBGRARXTFLTSG-UHFFFAOYSA-N Lithium ion Chemical compound [Li+] HBBGRARXTFLTSG-UHFFFAOYSA-N 0.000 description 1
- 230000008859 change Effects 0.000 description 1
- 239000000284 extract Substances 0.000 description 1
- 238000001914 filtration Methods 0.000 description 1
- 229910001416 lithium ion Inorganic materials 0.000 description 1
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- 238000012805 post-processing Methods 0.000 description 1
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Classifications
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/0003—Details of control, feedback or regulation circuits
- H02M1/0009—Devices or circuits for detecting current in a converter
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/32—Means for protecting converters other than automatic disconnection
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
- H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
- H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
- H02M3/158—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load
- H02M3/1584—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load with a plurality of power processing stages connected in parallel
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/0064—Magnetic structures combining different functions, e.g. storage, filtering or transformation
Definitions
- the present invention relates to a power converter.
- Patent Literature 1 discloses a power conversion device including a multiphase converter in which a plurality of chopper circuits each having a switching element and a reactor connected to the switching element are connected in parallel. , a single current sensor that detects the phase current flowing in each reactor in both the ON state and the OFF state of each switching element, and a phase current drift in each chopper circuit based on the phase current detected by the current sensor.
- a power conversion device is described that includes a drift detector for detecting.
- the above-mentioned conventional power converter detects phase current drift by comparing the phase current peaks of each chopper circuit, so when the phase current becomes small, the drift detection accuracy decreases. As a result, there is an increased risk of erroneous detection of a failure in a chopper circuit (multiphase transformer circuit) having a polyphase configuration.
- the present invention has been made in view of the circumstances described above, and an object thereof is to provide a power converter capable of reducing erroneous detection of failures in a polyphase transformer circuit more than before.
- a power conversion device includes a multiphase transformer circuit in which a plurality of chopper circuits are connected in parallel according to the number of phases, a current sensor that detects a phase current of the chopper circuit, and a current sensor that detects the phase current.
- a deviation detection unit for detecting a deviation value, and a failure detection threshold value variably set according to the state quantity of the polyphase transformer circuit, and the deviation value is compared with the failure detection threshold value to detect the chopper circuit. and a failure determination unit that determines a failure.
- the current sensor detects the total amount of the phase currents
- the failure determination unit detects the failure based on the state quantity obtained from the total amount.
- a threshold value may be set.
- a second current sensor that detects an input current or an output current of the multiphase transformer circuit is further provided, and the failure determination unit includes the The failure detection threshold may be set based on the value detected by the second current sensor.
- the failure determination unit divides into a plurality of current ranges according to the magnitude of the state quantity, and sets the failure detection threshold for each division. good too.
- the power conversion device may further include a failure identification unit that identifies the failed chopper circuit.
- the failure identifying unit includes a plurality of temperature sensors that detect temperatures of semiconductor switching elements that constitute the chopper circuit, and a failure based on the detected values of the temperature sensors. and a judgment unit for judging the semiconductor switching element.
- the failure determination unit may set the failure detection threshold to be smaller as the state quantity is smaller.
- the state quantity may be an average value or an effective value of the phase current.
- the state quantity may be the transformation ratio of the multiphase transformer circuit.
- the polyphase transformer circuit may be a step-up/step-down conversion circuit with a polyphase configuration.
- FIG. 1 is a block diagram showing the overall configuration of a power converter A according to a first embodiment of the present disclosure
- FIG. FIG. 4 is a characteristic diagram showing a method of setting a failure detection threshold value R according to the first embodiment of the present disclosure
- FIG. 4 is a schematic diagram showing reliability of failure diagnosis according to reactor current I, drift value H, and step-up ratio in the first embodiment of the present disclosure
- It is a block diagram which shows the whole structure of power converter device A1 which concerns on 2nd Embodiment of this indication.
- FIG. A power conversion device A according to the first embodiment is provided between an assembled battery P and a traction motor M as shown in FIG. 1, and converts DC power and three-phase AC power mutually.
- the power converter A includes a step-up/step-down converter D1, an inverter D2, and a control drive circuit D3 as shown.
- Such a power conversion device A is mounted, for example, in an electric vehicle such as a hybrid vehicle or an electric vehicle.
- the assembled battery P has a positive electrode connected to the primary side input terminal of the buck-boost converter D1, and a negative electrode connected to the primary side GND terminal of the buck-boost converter D1.
- This assembled battery P is a secondary battery such as a lithium ion battery, and charges and discharges DC power.
- the traveling motor M is a three-phase synchronous motor that generates the traveling power of the electric vehicle, and is the load of the inverter D2.
- the traveling motor M is rotationally driven by three-phase drive power (U-phase drive power, V-phase drive power, and W-phase drive power) input from the inverter D2, and rotates the drive wheels of the electric vehicle.
- the power converter A according to the first embodiment is provided between such an assembled battery P and the motor M, and converts the DC power supplied from the assembled battery P into three-phase AC power to drive the motor M. and a charging function of converting the regenerated power (three-phase AC power) of the motor M into DC power and supplying it to the assembled battery P.
- the buck-boost converter D1 corresponds to the multiphase transformer circuit of the present disclosure
- the control drive circuit D3 is: It is a component corresponding to the drift detection section and the failure determination section of the present disclosure.
- the buck-boost converter D1 is a multi-phase buck-boost conversion circuit called a magnetically coupled interleaved chopper circuit. 3d, a second capacitor 4, a primary voltage sensor 5, a secondary voltage sensor 6 and a current sensor 7;
- the step-up/down converter D1 is a power conversion circuit that steps up or steps down DC power based on the transformation gate signal input from the control drive circuit D3 and inputs/outputs the DC power. That is, the step-up/step-down converter D1 steps up the DC power input from the assembled battery P to the primary side and outputs it to the inverter D2. It alternatively performs a step-down operation to output.
- the inverter D2 has three switching legs corresponding to three phases (a total of six running IGBTs), and each running IGBT is turned ON/OFF based on a running gate signal input from the control drive circuit D3. By doing so, power conversion between DC power and three-phase AC power is performed. That is, the inverter D2 converts the DC power input from the buck-boost converter D1 into three-phase AC power and supplies it to the traction motor M, and converts the three-phase AC power input from the traction motor M into DC power. , and output to the step-up/step-down converter D1.
- the first capacitor 1 has one end connected to the positive electrode of the assembled battery P and the transformer 2, and the other end connected to the positive electrode of the assembled battery P. Both ends of the first capacitor 1 are primary input/output terminals of the step-up/step-down converter D1.
- the first capacitor 1 is connected in parallel to the assembled battery P, and suppresses high-frequency noise that may be contained in the DC power (battery power) input from the assembled battery P to the buck-boost converter D1 during boosting operation. Also, the ripple contained in the DC power input from the transformer 2 during the step-down operation is smoothed.
- the transformer 2 has a primary winding 2a and a secondary winding 2b, and one end of the primary winding 2a and one end of the secondary winding 2b are connected to one end of the first capacitor 1.
- the other end of the primary winding 2a is connected to the emitter terminal of the first transformation IGBT 3a and the collector terminal of the second transformation IGBT 3b, and the other end of the secondary winding 2b is connected to the third transformation IGBT 3c. and the collector terminal of the fourth transformer IGBT 3d.
- the primary winding 2a and the secondary winding 2b are electromagnetically coupled with a predetermined coupling coefficient k. That is, the primary winding 2a has a predetermined first self-inductance La corresponding to its own number of turns, etc., and the secondary winding 2b has a predetermined second self-inductance Lb corresponding to its own number of turns, etc. is doing. Also, the primary winding 2a and the secondary winding 2b have mutual inductance based on the above-described first self-inductance La, second self-inductance Lb, and coupling coefficient k.
- the first transforming IGBT 3a and the second transforming IGBT 3b constitute an A-phase switching leg in the step-up/step-down converter D1.
- the third transformation IGBT 3c and the fourth transformation IGBT 3d constitute a B-phase switching leg in the buck-boost converter D1.
- Such an A-phase switching leg and a B-phase switching leg are switching arms that perform ON/OFF operations in phases opposite to each other.
- the first transformation IGBT 3a is an upper arm switch in the A-phase switching leg
- the second transformation IGBT 3b is a lower arm switch in the A-phase switching leg
- the third transformation IGBT 3c is an upper arm switch in the B-phase switching leg
- the fourth transformation IGBT 3d is a lower arm switch in the B-phase switching leg.
- the first transformer IGBT 3a has a collector terminal commonly connected to the collector terminal of the third transformer IGBT 3c and one end of the second capacitor 4, and has an emitter terminal connected to the other end of the primary winding 2a and the second transformer IGBT 3c.
- the collector terminal of the IGBT 3b is connected in common, and the gate terminal is connected to the first transformer output terminal of the control drive circuit D3.
- Such a first transformation IGBT 3a is a semiconductor switching element whose ON/OFF duty ratio is controlled based on the first transformation gate signal input from the first transformation output terminal.
- the second transformer IGBT 3b has a collector terminal commonly connected to the other end of the primary winding 2a and the emitter terminal of the first transformer IGBT 3a, and has an emitter terminal connected to the emitter terminal of the fourth transformer IGBT 3d and the first capacitor 1. and the other end of the second capacitor 4, and the gate terminal is connected to the second transformer output terminal of the control drive circuit D3.
- Such a second transformation IGBT 3b is a semiconductor switching element whose ON/OFF duty ratio is controlled based on the second transformation gate signal input from the second transformation output terminal.
- the third transformer IGBT 3c has a collector terminal commonly connected to the collector terminal of the first transformer IGBT 3a and one end of the second capacitor 4, and an emitter terminal connected to the other end of the secondary winding 2b and the fourth transformer IGBT 3d. , and the gate terminal is connected to the third transformer output terminal of the control drive circuit D3.
- Such a third transformation IGBT 3c is a semiconductor switching element whose ON/OFF duty ratio is controlled based on the third transformation gate signal input from the third transformation output terminal.
- the fourth transformer IGBT 3d has a collector terminal commonly connected to the other end of the secondary winding 2b and the emitter terminal of the third transformer IGBT 3c, and an emitter terminal connected to the emitter terminal of the first transformer IGBT 3a and the first capacitor. 1 and the other end of the second capacitor 4, and the gate terminal is connected to the fourth transformer output terminal of the control drive circuit D3.
- Such a fourth transformation IGBT 3d is a semiconductor switching element whose ON/OFF duty ratio is controlled based on the fourth transformation gate signal input from the fourth transformation output terminal.
- Each of the first to fourth transformer IGBTs 3a to 3d is provided with a free wheel diode as shown. That is, the freewheeling diode has the cathode terminal connected to the collector terminal and the anode terminal connected to the emitter terminal for each IGBT. Such a freewheeling diode allows a freewheeling current to flow from the anode terminal to the cathode terminal when the IGBT is in the OFF state.
- the second capacitor 4 has one end connected to the collector terminal of the first IGBT 3a for transformation and the collector terminal of the third IGBT 3c for transformation, and the other end connected to the emitter terminal of the second IGBT 3b for transformation and the fourth IGBT 3d for transformation. and the other end of the first capacitor 1 are connected in common. Both ends of the second capacitor 4 are secondary input/output terminals of the step-up/step-down converter D1.
- Such a second capacitor 4 smoothes ripples that may be included in the DC power (boosted power) input from the A-phase switching leg and the B-phase switching leg in the boost operation. Further, the second capacitor 4 smoothes ripples that may be included in the DC power (regenerative power) input from the inverter D2 during step-down operation.
- the first capacitor 1 the primary winding 2a and the secondary winding 2b of the transformer 2
- the four transforming IGBTs Insulated Gate Bipolar Transistors 3a to 3d and the second capacitor 4
- the first capacitor 1 , primary winding 2a, first and second transforming IGBTs 3a and 3b (A-phase switching leg), and second capacitor 4 constitute a first chopper circuit.
- first capacitor 1, the secondary winding 2b, the third and fourth transformer IGBTs 3c, 3d (B-phase switching leg), and the second capacitor 4 constitute a second chopper circuit.
- Such a first chopper circuit and a second chopper circuit constitute a two-phase transformer circuit (multiphase transformer circuit) corresponding to the number of phases of two, and a plurality of (2) are connected in parallel.
- the primary voltage sensor 5 is a voltage sensor that detects the primary voltage V1 on the primary side of the buck-boost converter D1, that is, the primary voltage V1 on the battery pack P side, and outputs the primary voltage V1, which is the state quantity of the buck-boost converter D1, to the control drive circuit D3. .
- This primary voltage V1 is the input voltage in the step-up operation of the buck-boost converter D1, and is the output voltage in the step-down operation of the buck-boost converter D1.
- the secondary voltage sensor 6 is a voltage sensor that detects a secondary voltage V2 on the secondary side of the buck-boost converter D1, that is, on the inverter D2 side. output to This secondary voltage V2 is the output voltage in the step-up operation of buck-boost converter D1, and is the input voltage in the step-down operation of buck-boost converter D1.
- the current sensor 7 is a current sensor that detects the total amount (total current) of the primary current flowing through the primary winding 2a and the secondary current flowing through the secondary winding 2b of the transformer 2 as a reactor current I.
- the current sensor 7 outputs the reactor current I to the control drive circuit D3.
- the primary current is the A-phase current Ia that flows through the primary winding 2a by the ON/OFF operation of the A-phase switching leg connected to the primary winding 2a. It is a current or a regenerated current that flows from the secondary side to the primary side of the buck-boost converter D1.
- the secondary current is the B-phase current Ib that flows through the secondary winding 2b due to the ON/OFF operation of the B-phase switching leg connected to the secondary winding 2b. It is a powering current flowing to the secondary side or a regenerative current flowing from the secondary side to the primary side of the buck-boost converter D1.
- each of the three-phase power lines connecting the inverter D2 and the traveling motor M is provided with a current sensor. That is, a U-phase power line is provided with a U-phase current sensor 8 , a V-phase power line is provided with a V-phase current sensor 9 , and a W-phase power line is provided with a W-phase current sensor 10 .
- the U-phase current sensor 8 detects a U-phase drive current or a U-phase regenerative current flowing in the U-phase power line, and outputs a U-phase current detection signal indicating the detected value to the control drive circuit D3.
- the V-phase current sensor 9 detects a V-phase driving current or a V-phase regenerative current flowing through the V-phase power line, and outputs a V-phase current detection signal indicating the detected value to the control drive circuit D3.
- the W-phase current sensor 10 detects a W-phase driving current or W-phase regenerative current flowing in the W-phase power line, and outputs a W-phase current detection signal indicating the detected value to the control drive circuit D3.
- the control drive circuit D3 includes a drift detector 11, an average current detector 12, a controller 13, and two gate signal generators 14 and 15, as shown.
- the drift detection unit 11 detects the drift value H based on the ripple component contained in the reactor current I input from the current sensor 7 . That is, the drift detector 11 extracts a ripple component from the reactor current I and outputs the difference between the two peak values included in the ripple component as the drift value H to the controller 13 .
- the reactor current I is the total current of the A-phase current Ia flowing through the primary winding 2a of the transformer 2 and the B-phase current Ib flowing through the secondary winding 2b.
- the A-phase current Ia is a DC current containing a phase ripple synchronized with the ON/OFF operation of the A-phase switching leg
- the B-phase current Ib is a phase ripple synchronized with the ON/OFF operation of the B-phase switching leg.
- the ripple component of the A-phase current Ia is in opposite phase to the ripple component of the B-phase current Ib.
- the ripple component of the reactor current I is the A-phase current
- a relatively small value is obtained by summing (adding) the ripple component of Ia and the ripple component of the B-phase current Ib.
- the drift value H of the reactor current I is a state quantity that varies according to the ratio between the magnitude of the A-phase current Ia and the magnitude of the B-phase current Ib, that is, whether the A-phase switching leg or the B-phase switching leg is selected. It can be said that it is a state quantity indicating that one of them is in a failure state.
- the average current detection unit 12 Based on the reactor current I input from the current sensor 7, the average current detection unit 12 detects the average value of the reactor current I (current average value G). That is, the average current detection unit 12 performs moving average processing, which is a kind of filtering processing, on the reactor current I, and outputs the current value obtained by averaging the ripple component (deviation) to the control unit 13 as the current average value G. do.
- the control unit 13 receives a primary voltage V1 input from the primary voltage sensor 5, a secondary voltage V2 input from the secondary voltage sensor 6, a reactor current I input from the current sensor 7, and a control input from the host controller. Based on the command or the like, the duty command values for the first to fourth transformations required for generating the gate signals for the first to fourth transformations are generated.
- These first to fourth transformation duty command values are signals that specify the duty ratios of the first to fourth transformation gate signals, which are PWM signals.
- the control unit 13 outputs such first to fourth transformation duty command values to the first gate signal generation unit 14 .
- the control unit 13 also controls the secondary voltage V2 input from the secondary voltage sensor 6, the U-phase current detection signal input from the U-phase current sensor 8, and the V-phase current detection signal input from the V-phase current sensor 9. , based on the W-phase current detection signal input from the W-phase current sensor 10 and the control command input from the host controller, etc., the first to fourth driving gate signals necessary for generating the first to fourth driving gate signals are detected. Generate a Duty command value for
- These first to fourth driving duty command values are signals that designate the duty ratios of the first to fourth driving gate signals, which are PWM signals.
- the control unit 13 outputs such first to fourth driving duty command values to the second gate signal generation unit 15 .
- control unit 13 has a failure diagnosis function for the step-up/step-down converter D1. That is, the control unit 13 controls the drift value H input from the drift detection unit 11, the average current value G input from the average current detection unit 12, and the transformation ratio, which is one of the operation states of the buck-boost converter D1. , it is diagnosed whether one of the A-phase switching leg and the B-phase switching leg is in a fault state.
- the control unit 13 sequentially takes in the primary voltage V1, the secondary voltage V2, the reactor current I, the control command, etc. at predetermined time intervals, thereby generating the first to fourth transformation duty command values at each time, and stepping up and stepping up Output to converter D1. Further, the control unit 13 sequentially takes in the secondary voltage V2, the U-phase current detection signal, the V-phase current detection signal, the W-phase current detection signal, the control command, and the like at predetermined time intervals, so that the first to the first 6 A driving Duty command value is generated and output to the inverter D2.
- the controller 13 controls the first to fourth transformations so that the buck-boost converter D1 has a predetermined step-up ratio.
- the first to sixth driving duty command values are generated so that the inverter D2 converts the DC power input from the buck-boost converter D1 into three-phase AC power with a predetermined drive current value. do.
- the traveling motor M rotates at the torque and the number of revolutions designated by the control command, causing the electric vehicle to travel.
- the first gate signal generation unit 14 generates the first to fourth transformation gate signals based on the first to fourth transformation duty command values input from the control unit 13, and supplies them to the buck-boost converter D1. Output. Further, the second gate signal generation unit 15 generates first to sixth driving gate signals based on the first to sixth driving duty command values input from the control unit 13, and outputs the first to sixth driving gate signals to the inverter D2. .
- the first and second transforming gate signals for driving the first and second transforming IGBTs 3a and 3b that constitute the A-phase switching leg are the third and fourth transforming IGBTs 3c that constitute the B-phase switching leg. , 3d are 180° out of phase with respect to the third and fourth transforming gate signals. Therefore, the first and second transforming IGBTs 3a, 3b and the third and fourth transforming IGBTs 3c, 3d are turned on/off while being out of phase with each other by 180 degrees.
- the A-phase current Ia flowing through the primary winding 2a of the transformer 2 and the B-phase current Ib flowing through the secondary winding 2b of the transformer 2 have a relationship in which the phases of the ripple components differ by 180°.
- the current sensor 7 always detects the reactor current I, which is the total current of the A-phase current Ia and the B-phase current Ib, and outputs it to the drift detector 11 and the average current detector 12 .
- the drift detection unit 11 sequentially detects the drift value H based on the reactor current I and outputs it to the control unit 13, and the average current detection unit 12 sequentially detects the current average value G based on the reactor current I. and output to the control unit 13. Then, based on the drift value H and the current average value G, the control unit 13 diagnoses whether or not one of the A-phase switching leg and the B-phase switching leg is in a failure state as follows.
- the control unit 13 variably sets the failure detection threshold value R of the A-phase switching leg and the B-phase switching leg according to the drift value H and the current average value G, as shown in FIG. Then, when the drift value H is equal to or greater than the failure detection threshold value R, the control unit 13 determines that one of the A-phase switching leg and the B-phase switching leg is in a failure state. If the failure detection threshold value R is not exceeded, it is determined that both the A-phase switching leg and the B-phase switching leg are normal.
- the flow direction of the reactor current I differs depending on whether the buck-boost converter D1 is performing a step-up operation or a step-down operation.
- the failure detection threshold value R is the same for the two flow directions of the reactor current, that is, the vertical axis (the axis of the drift value H) where the current average value G is "0". It is set so as to be symmetrical to the left and right.
- the failure detection threshold value R is set to a smaller value as the magnitude (absolute value) of the current average value G decreases, and the magnitude (absolute value) of the current average value G increases. set to a moderately large value.
- the failure detection threshold value R is divided into three current regions (large region, medium region, and small region) of large, medium, and small currents (large region, medium region, and small region) according to the magnitude of the average current value G. Individually set for the current range.
- the method for setting the failure detection threshold value R is such that the smaller the reactor current I, that is, the smaller the absolute value of the current average value G, the smaller the reactor current. This is because the ripple component of I becomes smaller, so the reliability of failure determination of the A-phase switching leg or the B-phase switching leg is lowered.
- the ripple component of the reactor current I becomes smaller as the step-up ratio S becomes smaller when the same reactor current I is compared. That is, the reliability of failure determination of the A-phase switching leg or the B-phase switching leg tends to decrease as the step-up ratio S decreases. Taking this into consideration, the failure detection threshold value R may be set to a smaller value as the step-up ratio S becomes smaller.
- the average current value G and the step-up ratio S in the first embodiment correspond to the state quantities of the present disclosure. That is, the average current value G and the step-up ratio S are quantities that indicate the operating state of the step-up/step-down converter D1.
- the reactor current I is small, that is, when the absolute value of the current average value G is small, the drift value H when either one of the A-phase switching leg and the B-phase switching leg is in a failure state, There is concern that there will be no significant difference from the drift value H when both the A-phase switching leg and the B-phase switching leg are normal.
- the region Tm is set to be smaller and narrower than the region Ts in terms of the current average value G as shown in the figure, and the step-up ratio is set to be large, medium or small.
- This is a non-diagnostic area that is set when the area is divided into three areas and is medium or higher.
- the region Ts includes the region Tm in the current average value G and is set to a region wider than the region Tm, and is a diagnostic non-execution region set when the step-up ratio is small.
- the boost ratio is small, the drift value H tends to be smaller than when the boost ratio is medium or higher. Stop diagnostics on a wider scale.
- the failure detection threshold value R is variably set according to the state quantities of the first and second chopper circuits, and the drift value H is compared with the failure detection threshold value R. Since the failure of the A-phase switching leg or the B-phase switching leg that constitutes the first and second chopper circuits is determined by the above, it is possible to reduce erroneous detection of failures in the A-phase switching leg and the B-phase switching leg more than before. It is possible.
- FIG. 4 shows the overall configuration of the power converter A1 according to the second embodiment, and the same components as in FIG. 1 showing the overall configuration of the power converter A according to the first embodiment are assigned the same reference numerals. attached.
- the power conversion device A1 according to the second embodiment has four temperature sensors 16 to 19 added to the power conversion device A according to the first embodiment. 13 A of control parts are provided instead of the control part 13 of the power converter device A which concerns on a form.
- the four temperature sensors 16 to 19 and the control section 13A constitute the failure identification section of the present disclosure. Further, among the four temperature sensors 16 to 19 and the control section 13A, the four temperature sensors 16 to 19 correspond to the temperature sensors of the present disclosure, and the control section 13A corresponds to the determination section of the present disclosure.
- the four temperature sensors 16 to 19 and the control unit 13A specify which switching leg of the A-phase switching leg of the first chopper circuit or the B-phase switching leg of the second chopper circuit has failed. .
- the four temperature sensors 16 to 19 and the controller 13A identify the failed switch (semiconductor switching element) of the upper arm switch and the lower arm switch for the switching leg of the failed chopper circuit.
- the four temperature sensors 16 to 19 are used for the first to fourth transforming IGBTs 3a to 3d constituting the first and second chopper circuits. (Semiconductor switching element) temperature is detected.
- the first temperature sensor 16 is a sensor that detects the operating temperature of the first transformation IGBT 3a, and outputs the detected value to the control section 13A as a first temperature detection signal.
- the second temperature sensor 17 is a sensor that detects the operating temperature of the second transformation IGBT 3b, and outputs the detected value to the controller 13A as a second temperature detection signal.
- the third temperature sensor 18 is a sensor that detects the operating temperature of the third transformation IGBT 3c, and outputs the detected value to the control section 13A as a third temperature detection signal.
- the fourth temperature sensor 19 is a sensor that detects the operating temperature of the fourth transformation IGBT 3d, and outputs the detected value to the controller 13A as a fourth temperature detection signal.
- control unit 13A has a function of identifying the faulty transformer IGBT.
- the control unit 13A determines which of the semiconductor switching elements, that is, the first to fourth transformation IGBTs 3a to 3d has failed based on the values detected by the four (plurality) temperature sensors 16 to 19.
- FIG. 1 the control unit 13A determines which of the semiconductor switching elements, that is, the first to fourth transformation IGBTs 3a to 3d has failed based on the values detected by the four (plurality) temperature sensors 16 to 19.
- control unit 13A determines failure of the A-phase switching leg or the B-phase switching leg by comparing the drift value H with the failure detection threshold value R, the control unit 13A configures the switching leg determined as failure as post-processing. Which one of the two transformation IGBTs has failed is determined based on the first to fourth temperature detection signals.
- the first transformation IGBT 3a constituting the A-phase switching leg has a failure (open failure) in which it is fixed in the OFF state (open state)
- the first transformation IGBT 3a is energized with the A-phase current Ia. Therefore, the operating temperature is much lower than normal.
- the operating temperatures of the second to fourth transformer IGBTs 3b to 3d that are not out of order do not change significantly.
- the control unit 13A identifies the failed IGBT for transformation by evaluating the operating temperatures of the first to fourth IGBTs for transformation 3a to 3d based on the first to fourth temperature detection signals. Then, the controller 13A notifies the host controller of the failed IGBT for transformation.
- the buck-boost converter D1 can be easily repaired.
- the present disclosure is not limited to the above-described embodiments, and for example, the following modifications are conceivable.
- the current average value G is used as the state quantity indicating the operation state of the first and second chopper circuits, but the present disclosure is not limited to this.
- the average current value G that is, the average value of the reactor current I
- the effective value of the reactor current I and the transformation ratio are determined according to the states of the first and second chopper circuits.
- the failure detection threshold value R may be variably set according to such a state quantity.
- the current average value G generated by the average current detection unit 12 is used as the state quantity, but the present disclosure is not limited to this.
- a current sensor (second current sensor) is provided separately for detecting the input current of the buck-boost converter D1 during the boost operation, that is, the output current (battery current) of the assembled battery P, and the detected value of the second current sensor is It may be used as a state quantity. Since the ripple component of the battery current is sufficiently smaller than that of the reactor current I, it can be used as a state quantity for variably setting the failure detection threshold R.
- a current sensor for detecting the output current of the buck-boost converter D1 during the boost operation, that is, the input current of the inverter D2 may be provided separately, and the detected value of the second current sensor may be used as the state quantity. . Since the ripple component of the output current is sufficiently smaller than that of the reactor current I, it can be used as a state quantity for variably setting the failure detection threshold R.
- a current sensor 7 is employed to detect the total amount with the phase current Ib. That is, the current sensor 7 detects, as the reactor current I, a combined current of two phase currents, the A-phase current Ia and the B-phase current Ib.
- the current sensor in the present disclosure is not limited to current sensor 7 .
- two current sensors that individually detect the A-phase current Ia and the B-phase current Ib may be employed.
- the present disclosure is not limited to this. That is, the present disclosure can be applied to multi-phase transformer circuits other than two-phase transformer circuits, such as three-phase transformer circuits, four-phase transformer circuits, and transformer circuits having five or more phases.
- the present disclosure is applied to the buck-boost converter D1, which is a type of multiphase transformer circuit, has been described, but the present disclosure is not limited to this.
- the present disclosure can also be applied to a multiphase booster circuit that only performs a boost operation and a multiphase step-down circuit that only performs a step-down operation.
- the present disclosure can be used for power converters.
- A A1 Power converter D1 Buck-boost converter D2 Inverter D3 Control drive circuit 1 First capacitor 2 Transformer 2a Primary winding 2b Secondary winding 3a to 3d IGBT for transformation 4 second capacitor 5 primary voltage sensor 6 secondary voltage sensor 7 current sensor 8 U-phase current sensor 9 V-phase current sensor 10 W-phase current sensor 11 drift detector 12 average current detector 13 controller 14, 15 gate signal generator
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Abstract
Description
〔第1実施形態〕
最初に、本開示の第1実施形態について図1~図3を参照して説明する。第1実施形態に係る電力変換装置Aは、図1に示すように組電池Pと走行モータMとの間に設けられ、直流電力と三相交流電力とを相互に変換する装置である。この電力変換装置Aは、図示するように昇降圧コンバータD1、インバータD2及び制御駆動回路D3を備えている。このような電力変換装置Aは、例えばハイブリッド自動車や電気自動車等の電動車両に搭載される。
次に、本開示の第2実施形態について図4を参照して説明する。この図4は、第2実施形態に係る電力変換装置A1の全体構成を示しており、第1実施形態に係る電力変換装置Aの全体構成を示す図1と同一の構成要素については同一符号を付している。
(1)上記各実施形態では、第1、第2のチョッパ回路の動作状態を示す状態量として電流平均値Gを採用したが、本開示はこれに限定されない。電流平均値Gつまりリアクトル電流Iの平均値に代えてあるいは電流平均値Gに加えて、リアクトル電流Iの実効値や変圧比(昇圧比あるいは降圧比)を第1、第2のチョッパ回路の状態量とし、このような状態量に応じて故障検知しきい値Rを可変設定してもよい。
D1 昇降圧コンバータ
D2 インバータ
D3 制御駆動回路
1 第1コンデンサ
2 トランス
2a 一次巻線
2b 二次巻線
3a~3d 変圧用IGBT
4 第2コンデンサ
5 一次電圧センサ
6 二次電圧センサ
7 電流センサ
8 U相電流センサ
9 V相電流センサ
10 W相電流センサ
11 偏流検出部
12 平均電流検出部
13 制御部
14、15 ゲート信号生成部
Claims (10)
- チョッパ回路が相数に応じて複数並列に接続された多相変圧回路と、
前記チョッパ回路の相電流を検出する電流センサと、
前記相電流の偏流値を検出する偏流検出部と、
前記多相変圧回路の状態量に応じて故障検知しきい値を可変設定し、前記偏流値を前記故障検知しきい値と比較することにより前記チョッパ回路の故障を判定する故障判定部と
を備える電力変換装置。 - 前記電流センサは、前記相電流の合計量を検出し、
前記故障判定部は、前記合計量から得られる前記状態量に基づいて前記故障検知しきい値を設定する請求項1に記載の電力変換装置。 - 前記電流センサに代えて、前記多相変圧回路の入力電流あるいは出力電流を検出する第2の電流センサをさらに備え、
前記故障判定部は、前記第2の電流センサの検出値に基づいて前記故障検知しきい値を設定する請求項1に記載の電力変換装置。 - 前記故障判定部は、前記状態量の大小に応じて複数の電流範囲に区分し、当該区分毎に前記故障検知しきい値を設定する請求項1~3のいずれか一項に記載の電力変換装置。
- 故障した前記チョッパ回路を特定する故障特定部をさらに備える請求項1~4のいずれか一項に記載の電力変換装置。
- 前記故障特定部は、
前記チョッパ回路を構成する半導体スイッチング素子の温度を各々検出する複数の温度センサと、
該温度センサの検出値に基づいて故障した前記半導体スイッチング素子を判定する判定部と
を備える請求項5に記載の電力変換装置。 - 前記故障判定部は、前記状態量が小さい程、前記故障検知しきい値を小さく設定する請求項1~6のいずれか一項に記載の電力変換装置。
- 前記状態量は、前記相電流の平均値あるいは実効値である請求項1~7のいずれか一項に記載の電力変換装置。
- 前記状態量は、前記多相変圧回路の変圧比である請求項1~8のいずれか一項に記載の電力変換装置。
- 前記多相変圧回路は、多相構成の昇降圧変換回路である請求項1~9のいずれか一項に記載の電力変換装置。
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JP2013046541A (ja) * | 2011-08-26 | 2013-03-04 | Mitsubishi Electric Corp | 電源装置 |
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JP2019169997A (ja) * | 2018-03-22 | 2019-10-03 | 株式会社オートネットワーク技術研究所 | 車載用の多相コンバータ |
WO2019244614A1 (ja) * | 2018-06-18 | 2019-12-26 | 株式会社ケーヒン | 電力変換装置 |
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JP2013046541A (ja) * | 2011-08-26 | 2013-03-04 | Mitsubishi Electric Corp | 電源装置 |
JP2019024283A (ja) * | 2017-07-24 | 2019-02-14 | 三菱電機株式会社 | 電力変換装置および電力変換装置の制御方法 |
JP2019169997A (ja) * | 2018-03-22 | 2019-10-03 | 株式会社オートネットワーク技術研究所 | 車載用の多相コンバータ |
WO2019244614A1 (ja) * | 2018-06-18 | 2019-12-26 | 株式会社ケーヒン | 電力変換装置 |
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