WO2019073904A1 - Ac-acコンバータ回路 - Google Patents
Ac-acコンバータ回路 Download PDFInfo
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- WO2019073904A1 WO2019073904A1 PCT/JP2018/037260 JP2018037260W WO2019073904A1 WO 2019073904 A1 WO2019073904 A1 WO 2019073904A1 JP 2018037260 W JP2018037260 W JP 2018037260W WO 2019073904 A1 WO2019073904 A1 WO 2019073904A1
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M5/00—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases
- H02M5/40—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc
- H02M5/42—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters
- H02M5/44—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters using discharge tubes or semiconductor devices to convert the intermediate dc into ac
- H02M5/453—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters using discharge tubes or semiconductor devices to convert the intermediate dc into ac using devices of a triode or transistor type requiring continuous application of a control signal
- H02M5/458—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters using discharge tubes or semiconductor devices to convert the intermediate dc into ac using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M5/4585—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters using discharge tubes or semiconductor devices to convert the intermediate dc into ac using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only having a rectifier with controlled elements
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
- H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
- H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M5/00—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases
- H02M5/40—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc
- H02M5/42—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters
- H02M5/44—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters using discharge tubes or semiconductor devices to convert the intermediate dc into ac
- H02M5/453—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters using discharge tubes or semiconductor devices to convert the intermediate dc into ac using devices of a triode or transistor type requiring continuous application of a control signal
- H02M5/458—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters using discharge tubes or semiconductor devices to convert the intermediate dc into ac using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/14—Arrangements for reducing ripples from dc input or output
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/42—Circuits or arrangements for compensating for or adjusting power factor in converters or inverters
- H02M1/4208—Arrangements for improving power factor of AC input
- H02M1/4225—Arrangements for improving power factor of AC input using a non-isolated boost converter
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
- H02P27/00—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage
- H02P27/04—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage
- H02P27/06—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage using dc to ac converters or inverters
- H02P27/08—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage using dc to ac converters or inverters with pulse width modulation
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/42—Circuits or arrangements for compensating for or adjusting power factor in converters or inverters
- H02M1/4208—Arrangements for improving power factor of AC input
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/42—Circuits or arrangements for compensating for or adjusting power factor in converters or inverters
- H02M1/4208—Arrangements for improving power factor of AC input
- H02M1/425—Arrangements for improving power factor of AC input using a single converter stage both for correction of AC input power factor and generation of a high frequency AC output voltage
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- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
Definitions
- the present invention relates to an AC-AC converter circuit that converts power from an AC power supply into AC power.
- Patent Document 1 describes a power conversion circuit in which an impedance source circuit and a three-phase inverter are combined.
- the power conversion circuit described in Patent Document 1 generates DC power by inputting DC power from a secondary battery (rechargeable battery) to a three-phase inverter via an impedance source circuit.
- this power conversion circuit uses a normally on type transistor as a switching element.
- Patent Document 2 describes a power converter including a power supply, a main converter circuit, and an impedance network.
- the impedance network is coupled to the power supply and the main converter circuit, and the main converter circuit is coupled to the load.
- the impedance network is configured such that the main converter circuit performs both step-down and step-up conversion.
- PFC Power Factor Correction
- the present inventors examined an AC-AC converter circuit for converting power from an AC power source into AC power, and obtained the following recognition. It is conceivable to use an AC-AC converter circuit to drive a motor driven by three-phase AC power with a single-phase AC power supply.
- the AC-AC converter circuit may include a rectifier circuit that converts power from an AC power supply into DC power, and a DC-AC conversion circuit that converts rectified DC power into AC power of a desired specification. Conceivable.
- the rectified voltage which is particularly rectified from single-phase AC voltage, contains large pulsations.
- the rectifier circuit often includes a PFC circuit using a large capacity smoothing capacitor to smooth the rectified voltage. It is considered that the size of the capacitor increases as the capacitance and the withstand voltage increase.
- a rectifier circuit having a large capacity capacitor has a problem that a current containing a large amount of harmonics flows in the power supply current. From this, the inventors have recognized that the AC-AC converter circuit has a problem to be improved in terms of downsizing the entire circuit and reducing harmonics of the power supply current.
- Such problems are not limited to single-phase to three-phase AC-AC converter circuits, but may also occur to other types of AC-AC converter circuits.
- the present invention has been made in view of these problems, and an object thereof is to provide an AC-AC converter circuit that can achieve miniaturization of the entire circuit.
- an AC-AC converter circuit is an AC-AC converter circuit that converts an AC voltage to another AC voltage, the rectifier circuit rectifying an AC voltage, and And an inverter circuit that generates an AC voltage of Z.
- any combination of the above-described components, or any of the components or expressions of the present invention mutually replaced by a method, an apparatus, a program, a temporary or non-temporary storage medium recording a program, a system, etc. are also effective as an aspect of the present invention.
- FIG. 1 is a circuit diagram showing an example of an AC-AC converter circuit according to an embodiment. It is a circuit diagram showing an AC-AC converter circuit concerning a comparative example.
- FIG. 3 is a circuit diagram for illustrating the operation of the AC-AC converter circuit of FIG. 2;
- FIG. 5 is a waveform diagram showing voltage and current waveforms of the circuit of FIG. 3; It is a graph which shows the high-order harmonic of the input current of the circuit of FIG.
- FIG. 6 is another circuit diagram for explaining the operation of the AC-AC converter circuit of FIG. 2;
- FIG. 7 is yet another circuit diagram for illustrating the operation of the AC-AC converter circuit of FIG. 2;
- FIG. 2 is a circuit diagram showing an example of an equivalent circuit of the AC-AC converter circuit of FIG.
- FIG. 1; 5 is a timing chart showing an example of a rectified voltage of the AC-AC converter circuit of FIG. 1 and switching of a switching element.
- FIG. 2 is a block diagram showing an example of a control circuit of the AC-AC converter circuit of FIG. 1; 5 is a timing chart showing an example of the operation of each switching element at the time of step-down operation of the AC-AC converter circuit of FIG. 1; 5 is a timing chart showing an example of the operation of each switching element at the time of the step-up operation of the AC-AC converter circuit of FIG. 1; It is a circuit diagram showing an example of T source circuit concerning the 1st modification, and an eyebrows source circuit.
- FIG. 13 (a) shows an example of a T source circuit
- FIG. 13 (a) shows an example of a T source circuit
- FIG. 13 (b) shows an example of a ⁇ source circuit.
- An equivalent circuit 80 in the active mode is shown.
- An equivalent circuit 80 is shown when in the buck mode.
- the equivalent circuit 80 is shown when in boost mode.
- 17 shows input current i G and inductor current i L when control is performed using step-down operation and step-up operation.
- An example of an operation mode is shown.
- the inductor current i L shows the result of executing a control to minimize.
- the carrier signal and U-phase voltage waveform of the converter which concern on a comparative example are shown.
- FIG. 20A shows a carrier signal of the converter according to the comparative example.
- FIG. 20 (b) shows the U-phase voltage waveform of the converter according to the comparative example.
- 7 shows a carrier signal and a U-phase voltage waveform of the converter according to Method 1.
- FIG. FIG. 21A shows a carrier signal of the converter according to method 1.
- FIG. 21 (b) shows the U-phase voltage waveform of the converter according to method 1.
- 7 shows carrier signals and U-phase voltage waveforms of the converter according to method 2.
- FIG. FIG. 22 (a) shows the carrier signal of the converter according to method 2.
- FIG. FIG. 22 (b) shows the U-phase voltage waveform of the converter according to method 2.
- FIG. 1 is a circuit diagram showing an example of an AC-AC converter circuit 100 according to an embodiment of the present invention.
- the AC-AC converter circuit 100 functions as a power converter that generates three-phase power based on the power from the single-phase power supply 12.
- the AC-AC converter circuit 100 can be used to drive various devices such as pumps, compressors, motorized actuators for ships and airplanes, robot arms and the like.
- the AC-AC converter circuit 100 includes a filter 14, a rectifier circuit 16, a step-down circuit 18, a Z source circuit 20, a three-phase inverter circuit 22, and a control circuit 24.
- the upstream side may be referred to as the former stage or input, and the downstream side as the latter stage or the output.
- the single phase power source 12 may be, for example, a commercial power source or a generator.
- the single-phase power supply 12 outputs an AC voltage V12 to the first end 12b and the second end 12c.
- the filter 14 is connected between the single phase power supply 12 and the rectifier circuit 16 and functions as an EMI filter.
- the filter 14 includes an inductor L3 and a capacitor C3.
- the input end of the inductor L 3 is connected to the first end 12 b of the single phase power supply 12, and the output end of the inductor L 3 is connected to the input end of the rectifier circuit 16.
- One end of the capacitor C3 is connected to the output end of the inductor L3, and the other end of the capacitor C3 is connected to the second end 12c of the single-phase power supply 12.
- the rectifier circuit 16 is connected to the rear stage of the filter 14.
- the rectifier circuit 16 includes four diodes D1 to D4 connected in a bridge.
- the AC voltage V12 from the single-phase power supply 12 is input to the input terminals 16b and 16c of the rectifier circuit 16 through the filter 14.
- the rectifier circuit 16 full-wave rectifies the AC voltage V12 from the single-phase power supply 12 to generate a rectified voltage V16.
- the rectifier circuit 16 outputs a rectified voltage V16 between the positive side output end 16p and the negative side output end 16m.
- the waveform of the rectified voltage 16v is a pulsating waveform including large peaks and dips.
- the step-down circuit 18 is connected to the rear stage of the rectifier circuit 16.
- the step-down circuit 18 steps down the rectified voltage V16 from the rectifier circuit 16 to generate a step-down voltage V18.
- Step-down circuit 18 includes a switching element T7 and a diode D5 connected to the output side of switching element T7.
- the switching element T7 may be various known elements. In this example, the switching element T7 is an n-type MOSFET.
- the drain of the switching element T7 is connected to the positive output end 16p of the rectifier circuit 16, the source of the switching element T7 is connected to the positive output end 18p of the step-down circuit 18, and the gate of the switching element T7 is connected to the control circuit 24.
- the cathode of the diode D5 is connected to the output end 18p, and the anode 18m of the diode D5 is connected to the output end 16m of the rectifier circuit 16.
- the Z source circuit 20 is connected to the subsequent stage of the step-down circuit 18.
- the Z source circuit 20 generates a supply voltage V20 to be supplied to the inverter circuit 22 based on the step-down voltage V18 from the step-down circuit 18.
- the Z source circuit 20 generates the supply voltage V20 from the rectified voltage V16 according to the switching operation of the inverter circuit 22 and the switching operation of the step-down circuit.
- the Z source circuit 20 outputs the supply voltage V20 between the positive side output end 20p and the negative side output end 20m. The configuration of the Z source circuit 20 will be described later.
- the inverter circuit 22 is connected to the rear stage of the Z source circuit 20.
- the inverter circuit 22 generates an AC voltage V22 based on the supply voltage V20 from the Z source circuit 20.
- the inverter circuit 22 is a three-phase inverter circuit.
- An AC voltage V22 is a three-phase AC voltage including an X phase voltage Vox, a Y phase voltage Voy, and a Z phase voltage Voz.
- the voltages Vox, Voy and Voz may be alternating voltages with a phase difference of 2 ⁇ / 3.
- the AC voltage V22 from the inverter circuit 22 is supplied to, for example, the motor 6.
- Various known circuit configurations can be adopted as the inverter circuit 22.
- the inverter circuit 22 includes six switching elements T1 to T6.
- the switching elements T1 to T6 may be various known elements.
- the switching elements T1 to T6 are n-type MOSFETs.
- the switching elements T1 and T2 are connected in series with each other to form an X-phase arm.
- the switching elements T3 and T4 are connected in series with each other to constitute a Y-phase arm.
- the switching elements T5 and T6 are connected in series with each other to constitute a Z-phase arm.
- Each of the switching elements T1, T3 and T5 has its drain connected to the positive-side output end 20p of the Z source circuit 20, and functions as an upper switching element.
- Each of the switching elements T2, T4 and T6 has its source connected to the negative output end 20m of the Z source circuit 20, and functions as a lower switching element.
- the sources of the switching elements T1, T3 and T5 are connected to the drains of the switching elements T2, T4 and T6, and output voltages Vox, Voy and Voz from the connection points Xc, Yc and Zc.
- the gates of the switching elements T1 to T6 are connected to the control circuit 24.
- the inverter circuit 22 is controlled by the control circuit 24 to turn on / off the switching elements T1 to T6.
- the control circuit 24 controls the supply voltage V20 by controlling the gate voltage of the switching element T7.
- the control circuit 24 can control the supply voltage V20 high by increasing the on-state duty ratio of the switching element T7 and can decrease the supply voltage V20 by reducing the duty ratio.
- the control circuit 24 controls the AC voltage V22 from the inverter circuit 22 by controlling the on / off of the switching elements T1 to T6.
- the control circuit 24 can control the voltages Vox, Voy, Voz from the respective arms of the inverter circuit 22 by controlling the gate voltages of the switching elements T1 to T6.
- the configuration of the control circuit 24 will be described later.
- FIG. 2 is a circuit diagram showing an AC-AC converter circuit 200 according to a comparative example.
- the AC-AC converter circuit 200 according to the comparative example has a configuration in which the Z source circuit 20 is removed from the AC-AC converter circuit 100 according to the embodiment, and a PFC circuit 218 and a smoothing capacitor C8 are added. Have. The redundant description will be omitted, and the operation of the PFC circuit 218 and the smoothing capacitor C8 will be mainly described.
- the AC-AC converter circuit 200 includes the filter 14, the rectifier circuit 16, the step-down circuit 18, the PFC circuit 218, the smoothing capacitor C8, the inverter circuit 22, and the control circuit 24. It contains.
- the filter 14, the rectifier circuit 16, the step-down circuit 18, and the inverter circuit 22 are the same as those of the AC-AC converter circuit 100, and the description thereof will be omitted.
- FIG. 3 is a circuit diagram for explaining the operation of AC-AC converter circuit 200.
- FIG. 3 shows a circuit without the step-down circuit 18 and the PFC circuit 218.
- FIG. 4 is a waveform diagram showing voltage and current waveforms of the circuit of FIG. 3 (http://seppotl.web.fc2.com/zht03/acdc.html).
- FIG. 4 shows the rectified voltage V16, the smoothed voltage V8, and the input current Ip.
- the horizontal axis in FIG. 4 is time.
- the vertical axis in FIG. 4 indicates the magnitude of voltage and current.
- the rectified voltage V16 is a waveform before smoothing and shows a pulsating waveform which is obtained by full-wave rectifying a single-phase alternating current.
- the smoothed voltage V8 is a waveform after smoothing, and shows a waveform with reduced pulsation.
- the smoothed voltage V8 includes the ripple voltage Vr as shown in FIG.
- FIG. 5 is a graph showing harmonics obtained by frequency analysis of the input current Ip of FIG. 4 (http://www.jeea.or.jp/course/contents/01130/).
- the horizontal axis of FIG. 5 indicates the order of harmonics.
- the vertical axis in FIG. 5 shows the amplitudes of the respective harmonics in proportion, with the amplitude of the fundamental wave (shown as primary) being 100%.
- the input current Ip contains many high-order harmonics. It is desirable that the higher harmonics be suppressed because they cause unwanted radiation.
- the AC-AC converter circuit 200 includes a PFC circuit 218 to improve power factor and suppress higher harmonics.
- the PFC circuit 218 functions as a circuit that controls the flow time of the input current to improve the power factor.
- the PFC circuit 218 suppresses harmonic components of the input current.
- the PFC circuit 218 shapes the rectified voltage V16 from the rectifier circuit 16 to generate a shaped voltage.
- the smoothing capacitor C8 is connected in parallel to the rear stage of the PFC circuit 218.
- the smoothing capacitor C8 smoothes the shaped voltage from the PFC circuit 218 to generate a smoothed voltage V8.
- the smoothing capacitor C ⁇ b> 8 desirably has a capacitance corresponding to the magnitude of the charge / discharge current and a withstand voltage corresponding to the applied voltage. For this reason, the size of the smoothing capacitor C8 often increases.
- FIG. 6 is a circuit diagram for explaining the operation of the PFC circuit 218 of the AC-AC converter circuit 200.
- FIG. 6 shows a circuit in which a PFC circuit 218 is added to the circuit of FIG.
- the PFC circuit 218 includes an inductor L8, a switching element T8, and a diode D8.
- the switching element T8 is an n-type MOSFET.
- the input end of the inductor L8 is connected to the output end 16p of the rectifier circuit 16.
- the drain of the switching element T8 is connected to the output end of the inductor L8, and the source of the switching element T8 is connected to the output end 16m of the rectifier circuit 16.
- the anode of the diode D8 is connected to the output end of the inductor L8, and the cathode of the diode D8 is connected to the positive end of the smoothing capacitor C8.
- the diode D8 is connected so as to prevent the backflow from the smoothing capacitor C8.
- the rapid increase of the input current Ip is suppressed by the action of the inductor L8.
- the switching element T8 When the switching element T8 is turned on, the output end of the inductor L8 and the output end 16m on the negative side of the rectifier circuit 16 are short-circuited, and the short circuit current flows to the inductor L8.
- the switching element T8 switches from on to off, the voltage at the output end of the inductor L8 rises by the action of the inductor L8, and a rapid drop in the input current Ip is suppressed.
- the PFC circuit 218 can improve the power factor of the input current Ip and suppress the harmonic components of the input current Ip.
- FIG. 7 is a circuit diagram for explaining the operation of the PFC circuit 218 in which the step-down circuit 18 is combined.
- the step-down circuit 18 includes the switching element T7 and the diode 5.
- the smoothing capacitor C8 is charged through the switching element T7, and the smoothed voltage V8 rises.
- the switching element T7 is turned off, a current based on the magnetic energy stored in the inductor L8 flows through the diode 5.
- the step-down circuit 18 can lower the smoothed voltage V8 in accordance with the on-state duty ratio of the switching element T7.
- the step-down circuit 18 can reduce the duty ratio of the switching element T7 to reduce the smoothed voltage V8 and reduce the switching loss of the inverter circuit 22.
- the AC-AC converter circuit 200 of the comparative example configured as described above includes a large-sized smoothing capacitor C8, and uses eight switching elements and six diodes. Therefore, AC-AC converter circuit 200 has a problem that it is difficult to miniaturize the entire circuit.
- the description will return to the description of the AC-AC converter circuit 100 according to the embodiment.
- the inverter circuit is operated based on the rectified voltage rectified from the AC voltage
- problems of current factor and higher harmonics This problem can not occur in a configuration in which the inverter circuit is operated based on a direct current voltage such as a storage battery with almost no voltage fluctuation. Therefore, the present inventors have devised a configuration in which a Z source circuit is provided in the subsequent stage of the rectifier circuit by repeating research and trial and error on this subject. In this configuration, it is possible to miniaturize the entire circuit by reducing or miniaturizing the smoothing capacitor and reducing the number of switching elements and diodes.
- the Z source circuit 20 is provided between the rectifier circuit 16 and the inverter circuit 22.
- the Z source circuit 20 is provided on the downstream side of the step-down circuit 18 and on the upstream side of the inverter circuit 22.
- the Z source circuit 20 includes two inductors L1 and L2 and two capacitors C1 and C2.
- the input end of the inductor L1 and the positive end of the capacitor C1 are connected to the positive-side output end 18p of the step-down circuit 18.
- the input end of the inductor L2 and the negative end of the capacitor C2 are connected to the output end 16m of the rectifier circuit 16.
- the output end of the inductor L1 and the positive end of the capacitor C2 are connected to the output end 20p on the positive side of the Z source circuit 20.
- the inductances of the inductors L1, L2 may be different but are equal in this example.
- the capacitances of the capacitors C1, C2 may be different but are equal in this example.
- the switching elements T1 to T6 perform switching operation of the inductors L1 and L2 to generate a step-up function to suppress a sharp drop in the current of the inductor.
- the capacitors C1 and C2 negatively feed back voltage changes of the output ends 20p and 20m on the output side of the Z source circuit 20 to the input side of the Z source circuit 20, and suppress abrupt voltage changes on the output ends 20p and 20m. By acting in this manner, the Z source circuit 20 can improve the power factor of the input current Ip and reduce high-order harmonics.
- FIG. 8 is a circuit diagram showing an example of the equivalent circuit 80 of the AC-AC converter circuit 100.
- the equivalent circuit 80 includes a voltage source 26, a diode D 28, a step-down circuit 18, a Z source circuit 20, a switching element T 30, and a bidirectional current source 32.
- the voltage source 26 is an element equivalent to a circuit including the single-phase power supply 12, the filter 14, and the rectifier circuit 16, and is a voltage source that outputs an absolute value of a sine wave as the rectified voltage V16.
- the diode D28 is an element equivalent to the backflow prevention function of the rectifier circuit 16.
- the switching element T30 is an element equivalent to a part of the switching elements T1 to T6.
- the bidirectional current source 32 is an element equivalent to the load of the inverter circuit 22 and is a current source capable of generating a source current and a sink current.
- each circuit element is connected as follows.
- the positive end of the voltage source 26 is connected to the anode of the diode D28.
- the cathode of the diode D28 is connected to the drain of the switching element T7 of the step-down circuit 18.
- the negative end of the voltage source 26 is connected to the cathode of the diode D28, the input end of the inductor L2, and the negative end of the capacitor C2.
- the step-down circuit 18 and the Z source circuit 20 are as described above.
- the positive-side output terminal 20p of the Z source circuit 20 is connected to the drain D30 of the switching element T30 and the positive terminal 32p of the bidirectional current source 32.
- the negative output terminal 20m of the Z source circuit 20 is connected to the source of the switching element T30 and the negative terminal 32m of the bidirectional current source 32.
- FIG. 9 is a timing chart showing an example of the rectified voltage V16 and the switching of the switching elements T7 and T30.
- FIG. 9 shows one cycle Tac of the AC voltage V12 from the single-phase power supply 12.
- the rectified voltage V16 alternately repeats a large peak and a dip every Tac / 2.
- the virtual DC voltage Vg functions as a threshold that serves as a reference for switching between the boosting operation and the bucking operation.
- Virtual DC voltage Vg may be set corresponding to desired supply voltage V20.
- the rectified voltage V16 can be divided into periods S1 to S5 based on the virtual DC voltage Vg.
- the AC-AC converter circuit 100 performs a step-down operation and cuts the peak of the rectified voltage V16 as indicated by an arrow P.
- the rectified voltage V16 exceeds the virtual DC voltage Vg, and the AC-AC converter circuit 100 performs a step-down operation to remove the peak of the rectified voltage V16 as shown by the arrow P.
- the rectified voltage V16 is equal to or lower than the virtual DC voltage Vg, and the AC-AC converter circuit 100 performs a boosting operation to fill the dip E of the rectified voltage V16 as shown by arrow D.
- the waveform indicated by reference numeral T7s indicates the operating state of the switching element T7, and indicates level 1 at on and level 0 at off.
- a waveform indicated by a symbol T30s indicates the operating state of the switching element T30, and indicates level 1 at on and level 0 at off.
- the step-down operation will be described.
- the switching element T30 is maintained in the OFF state, and the switching element T7 is controlled to perform the switching operation of periodically repeating ON and OFF.
- the switching element T7 is on, current from the voltage source 26 flows to the inductors L1 and L2 and the bidirectional current source 32, and magnetic energy is accumulated in the inductors L1 and L2.
- the switching element T7 is turned off, a current based on the magnetic energy stored in the inductors L1 and L2 flows to the inductors L1 and L2 and the bidirectional current source 32 through the diode D28.
- the boosting operation will be described.
- the switching element T7 is maintained in the on state, and the switching element T30 is controlled to perform the switching operation in which the on and off are periodically repeated.
- the switching element T30 is on, a current flowing through the switching element T30 flows to the inductors L1 and L2, and magnetic energy is accumulated in the inductors L1 and L2.
- the switching element T30 is turned off, a current based on the magnetic energy stored in the inductors L1 and L2 flows to the inductors L1 and L2 and the bidirectional current source 32.
- a voltage boosted according to the switching duty ratio of the switching element T30 can be obtained as the supply voltage V20 of the Z source circuit 20.
- FIG. 10 is a block diagram showing an example of the configuration of AC-AC converter circuit 100. Referring to FIG. FIG. 10 omits and shows some elements which are not important in the explanation.
- Each block of the control circuit 24 shown in FIG. 10 can be realized by hardware as an electronic element or mechanical component including a CPU of a computer, and as software as a computer program or the like. , The functional block realized by those cooperation is drawn. Therefore, it is understood by those skilled in the art that these functional blocks can be realized in various forms by a combination of hardware and software.
- the control circuit 24 includes an AC voltage acquisition unit 24b, a rectified voltage acquisition unit 24c, a capacitor voltage acquisition unit 24d, a peak voltage identification unit 24e, an inductor current identification unit 24f, an inductor voltage identification unit 24h, a gate control unit 24g, and a simultaneous on control unit. Includes 24j.
- the AC voltage acquisition unit 24 b acquires an AC voltage V ⁇ b> 12 from the single phase power supply 12.
- the rectified voltage acquisition unit 24 c acquires the rectified voltage V 16 from the rectifier circuit 16.
- the capacitor voltage acquisition unit 24d acquires the voltage across the capacitor from the capacitors C1 and C2.
- the peak voltage identification unit 24e identifies the peak of the rectified voltage V16 from the acquired rectified voltage V16.
- the simultaneous on control unit 24 j specifies the simultaneous on timing as the short control signal TST according to the rectified voltage V 16. The short control signal TST will be described later (see FIGS. 12 and 11).
- the inductor current identification unit 24 f identifies the target inductor current to be supplied to the inductors L 1 and L 2 from the acquired voltages of the capacitors C 1 and C 2.
- the inductor voltage specification unit 24h specifies the voltage across the inductors L1 and L2 as the inductor voltage from the specified inductor current.
- the gate control unit 24g specifies the on / off timings of the switching elements T1 to T6 and T7 based on the specified inductor voltage and the short control signal TST, and outputs the specified results as gate control signals G1 to G6 and G7. .
- the gate control signals G1 to G6 and G7 are supplied to the gates of the switching elements T1 to T6 and T7 to control on / off of the switching elements T1 to T6 and T7.
- the switching elements T1 to T6 and T7 are controlled by the control circuit 24 and operate as follows.
- FIG. 11 is a timing chart showing an example of the operation of each switching element at the time of step-down operation.
- FIG. 12 is a timing chart showing an example of the operation of each switching element at the time of the boosting operation.
- the waveforms indicated by reference symbols T1s to T6s and T7s indicate the operating states of the switching elements T1 to T6 and T7, and indicate on at level 1 and off at level 0.
- TST indicates a short control signal, and is a signal that controls the upper and lower switching elements to be simultaneously turned on at level 1.
- Car indicates a carrier signal.
- the carrier signal Car is a triangular wave with one repetition period of 20 ⁇ s (50 kHz).
- the step-down operation will be described.
- the other is off, and when one is off, the other is on.
- the switching elements T3 and T4 is on, the other is off, and when one is off, the other is on.
- one of the switching elements T5 and T6 is on, the other is off, and when one is off, the other is on. That is, the upper switching element and the lower switching element constituting the phase arm of each phase are controlled such that the other is turned off when one is on.
- the short control signal TST is maintained at level 0, and the upper and lower switching elements are controlled not to be turned on simultaneously.
- the switching elements T1 and T2 are provided with a period in which the other is simultaneously turned on when one is turned on.
- the switching elements T3 and T4 are provided with a period in which the other is simultaneously turned on when one is turned on.
- the switching elements T5 and T6 are provided with a period in which the other is simultaneously turned on when one is turned on. That is, the upper switching element and the lower switching element that constitute the phase arm of each phase are provided with a period in which the other is also turned on simultaneously when one is turned on.
- the AC-AC converter circuit 100 is an AC-AC converter circuit (100) that converts an AC voltage (V12) into another AC voltage (V22), and performs rectification to rectify the AC voltage (V12).
- a Z source circuit (20) is provided between the circuit (16) and an inverter circuit (22) that generates another alternating voltage (V22).
- the switching element T8 and the diode D8 can be reduced. Therefore, the reliability of the AC-AC converter circuit 100 due to the life of the semiconductor element used It is possible to suppress the decrease. Further, since the number of semiconductor elements to be used can be reduced, downsizing of the entire AC-AC converter circuit 100 is facilitated.
- the Z source circuit 20 suppresses pulsation of the rectified voltage V16, it is possible to replace or eliminate the large smoothing capacitor C8 with a small one, so that the entire AC-AC converter circuit 100 is miniaturized. It will be possible.
- a step-down circuit (18) is provided between the rectifier circuit (16) and the Z source circuit (20).
- the peak of the rectified voltage V16 can be suppressed by the step-down circuit 18, the voltage of the supply voltage V20 of the Z source circuit 20 and the pulsation thereof can be reduced, and the entire AC-AC converter circuit 100 can be miniaturized.
- the voltage applied to the inverter circuit 22 can be reduced, the load on each element can be reduced and heat generation can be reduced. Therefore, the member for heat dissipation of the inverter circuit 22 can be miniaturized, and the entire AC-AC converter circuit 100 can be reduced. Can be miniaturized.
- the inverter circuit (22) includes a first switching element (T1, T3, T5) and a second switching element (T2, T4, T6) connected in series with each other. A period during which the second switching elements (T2, T4, T6) are turned on when the first switching elements (T2, T4, T6) are turned on to generate another alternating voltage (V22) There is. According to this configuration, by providing a period during which the second switching element (T2, T4, T6) is turned on, the inductors L1 and L2 of the Z source circuit 20 are caused to perform a boosting operation to alleviate the dip of the rectified voltage V16. Thus, the fluctuation of the supply voltage V20 of the Z source circuit 20 can be suppressed.
- the Z source circuit 20 is provided between the rectifier circuit 16 that rectifies an AC voltage and the inverter circuit 22 that generates another AC voltage, but the present invention is not limited to this.
- any impedance network circuit may be provided as an alternative to the Z source circuit.
- a T source circuit and a ⁇ source circuit can be mentioned as an example.
- a T source circuit 20 (B) or a negative source circuit 20 (C) may be provided between the rectifier circuit 16 and the inverter circuit 22 instead of the Z source circuit 20.
- FIG. 13 is a circuit diagram showing an example of the T source circuit 20 (B) and the negative source circuit 20 (C) according to the first modification.
- FIG. 13 (a) shows an example of the T source circuit 20 (B)
- FIG. 13 (b) shows an example of the source circuit 20 (C).
- the configurations and operations of the T source circuit 20 (B) and the negative source circuit 20 (C) will be described with reference to FIG.
- T source circuit 20 (B) includes inductors L1 (B) and L2 (B), and a capacitor C1 (B).
- the inductors L1 (B) and L2 (B) are magnetically coupled to one another to create an interaction.
- the input of the T source circuit 20 (B) is connected to the output of the step-down circuit 18.
- the output of the T source circuit 20 (B) is connected to the input of the inverter circuit 22.
- the input end of the inductor L1 (B) is connected to the positive input end of the T source circuit 20 (B).
- the output end of the inductor L1 (B) is connected to the input end of the inductor L2 (B).
- the output end of the inductor L2 (B) is connected to the positive side output end of the T source circuit 20 (B).
- the positive end of the capacitor C1 (B) is connected to the output end of the inductor L1 (B).
- the negative end of the capacitor C1 (B) is connected to the negative input end of the T source circuit 20 (B).
- the negative side output terminal of the T source circuit 20 (B) is connected to the negative side input terminal of the T source circuit 20 (B).
- the source circuit 20 (C) includes inductors L1 (C) and L2 (C) and a capacitor C1 (C).
- the inductors L1 (C), L2 (C) are magnetically coupled to one another to create an interaction.
- the input of the source circuit 20 (C) is connected to the output of the step-down circuit 18.
- the output of the source circuit 20 (C) is connected to the input of the inverter circuit 22.
- the input end of the inductor L2 (C) is connected to the input end of the source circuit 20 (C).
- the output end of the inductor L2 (C) is connected to the positive output end of the source circuit 20 (C).
- the input end of the inductor L1 (C) is connected to the input end of the source circuit 20 (C).
- the output end of the inductor L1 (C) is connected to the positive end of the capacitor C1 (C).
- the negative end of the capacitor C1 (C) is connected to the negative input of the source circuit 20 (C).
- the negative output terminal of the source circuit 20 (C) is connected to the negative input terminal of the source circuit 20 (C).
- the T source circuit (20 (B)) or the negative source circuit (20 (C)) is between the rectifier circuit (16) and the inverter circuit (22). Provided in According to this configuration, the same function and effect as those of the AC-AC converter circuit 100 according to the embodiment can be obtained.
- diodes D1 to D5 are semiconductor diodes that can be energized in one direction
- the present invention is not limited to this. All or part of the diodes D1 to D5 may be replaced by switching elements that can be energized in the reverse direction like MOSFETs. This modification exhibits the same effects as the AC-AC converter circuit 100 according to the embodiment.
- switching elements T1 to T7 are n-type MOSFETs in the description of the embodiment, the present invention is not limited to this.
- the type of switching elements T1 to T6 and T7 is not particularly limited, and various known switching elements such as bipolar transistors, IGBTs (Insulated Gate Bipolar Transistors), SiC devices, and GaN devices can be applied. This modification exhibits the same effects as the AC-AC converter circuit 100 according to the embodiment.
- the operation for controlling the voltage of the AC-AC converter circuit includes only the step-down operation and the step-up operation.
- the present invention is not limited to this.
- the AC-AC converter circuit of one embodiment of the present invention may further include performing the buck-boost operation near the zero of the input voltage v G in addition to the above-mentioned step-down operation and step-up operation.
- the step-up / step-down operation will be described.
- the operation state of equivalent circuit 80 in FIG. 8 is set to three modes of a first operation mode, a second operation mode, and a third operation mode.
- the first operation mode, the second operation mode, and the third operation mode may be referred to as an “active mode”, a “step-down mode”, and a “boost mode”, respectively.
- the switching elements T7 and T30 may also be referred to as "step-down circuit switching element” and "inverter circuit switching element", respectively.
- the equivalent circuit 80 is in the active mode when the step-down circuit switching element T7 is on and the inverter circuit switching element T30 is off.
- FIG. 14 shows the equivalent circuit 80 in the active mode.
- a positive input voltage v G is applied to the anode. Therefore, a positive input current i T7,1 flows through the step-down circuit switching element T7 (“T7” on the left side of the subscript indicates the switching element T7, and “1” on the right side of the subscript is the first Indicates the operation mode (active mode) of the same.
- T7 on the left side of the subscript indicates the switching element T7
- “1” on the right side of the subscript is the first Indicates the operation mode (active mode) of the same.
- the diode D5 no current flows because the positive input voltage v G is applied to the cathode.
- I Q is an output peak current. That is, the inductor current i L, 1 is always 1/2 or more of the output peak current I Q.
- V G is an input peak voltage. That is, the capacitor voltage v C, 1 is always larger than 1/2 of the input peak voltage V G.
- step-down circuit switching element T7 When the step-down circuit switching element T7 is off and the inverter circuit switching element T30 is off, it is defined that the equivalent circuit 80 is in the step-down mode.
- the diode current i D5,2 is positive, i L, 2 I I Q / 2 (14) It is understood that That is, the inductor current i L, 2 is always 1/2 or more of the output peak current I Q.
- the inverter circuit switching element T30 When the inverter circuit switching element T30 is on, it is defined that the equivalent circuit 80 is in the step-up mode. At this time, the step-down circuit switching element T7 may be either on or off.
- v D5,3 applied to the diode D5 is calculated as follows.
- the inverter circuit switching element T30 is maintained in the OFF state, and the step-down circuit switching element T7 is controlled to perform the switching operation periodically repeating ON and OFF.
- control is performed so that the active mode and the step-down mode are periodically and repeatedly used.
- the step-down circuit switching element T7 is maintained in the on state, and the inverter circuit switching element T30 is controlled to perform the switching operation periodically repeating on and off.
- control is performed so that the active mode and the boosting mode are periodically and repeatedly used.
- d A the proportion of time in which the active mode is used
- d 0 the proportion of time in which the buck mode is used
- d B the proportion of time in which the boost mode is used.
- d A + d B 1
- D 0 0.
- the output voltage vPN can be controlled by changing the values of the duties d A , d 0 and d B in each of these modes.
- the duties d A , d 0 and d B of each mode are compared with the duties D A , D 0 and D B when the circuit is in the steady state, and minute variations d ' A , d' 0 and d 'from the steady state.
- d A D A + d ' A
- d 0 D 0 + d ′ 0
- d B D B + d ′ B (26) It is.
- the duties D A , D 0 and D B when the circuit is in steady state are calculated.
- the inductor current i L in order to avoid energy loss due to Joule heat or the like generated in the inductor, it is desirable to suppress the inductor current i L to be as small as possible. That is, by minimizing the inductor current i L , the efficiency of the device can be maximized.
- the goal is to define a duty that minimizes i L within the range that satisfies the given constraints.
- each duty is determined by the equations (32), (34), (35), (36), and (37). Allows the inductor current i L to be minimized. This is the end of the description of the method of calculating the optimum duty in the embodiment in which only the step-down operation and the step-up operation are included in the voltage control of the AC-AC converter device of the present invention.
- the inductor current i L must be 1/2 or more of the peak current I Q. That is, i L ((1/2) ⁇ I Q (38) It is.
- FIG. 17 shows the input current i G and the inductor current i L when control is performed using the step-down operation and the step-up operation.
- Duty D A in the step-down operation and the step-up operation BU, D B, BU, D 0, BU, D A, B0, D B, BO, D 0, B0 respectively, formula (32) (33) (33) ( 34) Determined by (35) and (36).
- formula (32) (33) (33) ( 34) Determined by (35) and (36).
- the present inventors have result of further studies, in addition to the control by the step-down operation and the step-up operation only, by the input voltage v G performs control by step-up and step-down operations in the vicinity of zero, to be able to solve the aforementioned problems I noticed.
- the step-up / step-down operation is to ensure that the condition of equation (38) is satisfied even when the input voltage v G is near zero.
- (2 ⁇ i L ⁇ ⁇ i Q >) ⁇ D A, BB (44) far.
- D A, BB
- the duty DA , BB of the active mode at the time of buck-boost operation may be defined in the following range.
- the optimal duty DA , BB of the active mode at the time of buck-boost operation becomes a value proportional to the modulation factor m.
- the proportionality factor k at this time is determined by equation (55).
- Steady-state duty DA and BU / BO are effective during step-down operation and step-up operation, and are associated with the minimum value of duty DA and BU in active mode during step-down operation.
- BB step-up and step-down operation
- BU step-down operation
- FIG. 19 shows the result of execution of control for minimizing the inductor current i L based on the method described above. From the rectified input voltage
- and the output voltage ⁇ v PN > ( capacitor voltage ⁇ v C >), the duty D A, BU , D A, BO , D A, BU / BO of the active mode in the steady state The optimal D A and D B can be obtained by determining As a result, as shown in FIG. 19, it can be seen that a completely rectified input current ⁇ i TA > and an inductor current i L can be obtained during one cycle of the input power.
- d 0 and BB are determined as values that minimize the inductor current i L. Therefore d A, variation d from the steady state of BB 'A, BB is not generated, d B, variation d from the steady state of BB' B, only BB occurs.
- the PWM carrier waveform of the switching signal can be made asymmetric with respect to the time axis by precisely controlling and changing the output voltage. Thereby, the short period can be properly distributed.
- the duty d A , d 0 , d B of each mode and the inverter duty d U , d V , d W are the control signals S A , S 1 , S 2 , S 3 , S 4 , S 5 of the actual transistor switches. , S 6 .
- FIG. 20A shows a carrier signal of the converter according to the comparative example.
- FIG. 20 (b) shows the U-phase voltage waveform of the converter according to the comparative example.
- FIG. 20 (a) shows a phase voltage waveform of the U phase, but the same applies to the V phase and the W phase.
- FIG. 20 (b) shows a phase voltage waveform of the U phase, but the same applies to the V phase and the W phase.
- d X where X ⁇ ⁇ U, V, W ⁇
- the other phase outputs are 0.
- the average X-phase voltage ⁇ v XN > is v DC ⁇ d X.
- ⁇ V XN > v DC ⁇ d X (64)
- ) and in the buck mode (v PN , 1 2 ⁇ v C ) You need to get in between. Method 1 achieves this by asymmetrizing the PWM carrier waveform. Specifically, the carrier waveform is changed as follows according to the state of the mode.
- FIG. 21A shows the carrier signal of the converter according to method 1.
- FIG. 21 (b) shows the U-phase voltage waveform of the converter according to method 1.
- a shoot through period t SH at which both half bridges turn on is provided in the dead time period. In other words, the shoot through period is integrated into the switching procedure. Therefore, the number of switches does not increase.
- the upper and lower duties d H and d L of the half bridge satisfy the following relationship.
- d H d L + d SH (68)
- t AN + t 0 N 1 (73) Is true.
- the shoot through periods t SH, A and t SH, 0 are the duty d x, H of the high side switch and the duty d x, L of the low side switch of each half bridge x ⁇ ⁇ a, b, c ⁇ .
- a duty cycle difference t SH (1/3) ⁇ d B between them.
- d x, H d x, L and + (1/3) d B, x (78)
- the minimum duty half bridge output d a min (d U , d V , d W ) (79)
- d b mid (d U , d V , d W ) (80)
- d c max (d U , d V , d W ) (81)
- min () indicates that the minimum value in () is taken
- mid () indicates that the intermediate value in () is taken
- max () indicates that the maximum value in () is taken.
- the minimum duty d a, L of d U , d V , d W is first determined.
- FIG. 22 (a) shows a carrier signal of the converter according to method 2.
- FIG. 22 (b) shows the U-phase voltage waveform of the converter according to method 2.
- the high side and low side duties of the second phase and the third phase are calculated as follows from the relationship with the front phase.
- d a, L (1-d B ) d a (86)
- d b, L d a, H + (1-d B ) (d b- d a ) (87)
- d c, L d b, H + (1-d B) ⁇ (d c -d b) ⁇ (88)
- the PWM carrier waveform of the switching signal is asymmetric with respect to the time axis.
- the short through period can be properly distributed.
- an AC-AC converter circuit includes a control circuit that controls the step-down circuit and the inverter circuit.
- the step-down circuit includes a step-down circuit switching element.
- the inverter circuit includes a switching element for the inverter circuit.
- the first operation mode in which the step-down circuit switching element is on and the inverter circuit switching element is off, the step-down circuit switching element is off, and the inverter circuit switching element is off Control is performed using a certain second operation mode and a third operation mode in which the inverter circuit switching element is on.
- a further embodiment of the present invention is characterized in that the control circuit performs control such that the duty D3 of the third operation mode satisfies the following equation.
- D 3 6 M ⁇ cos ⁇ / (4-3 M ⁇ cos ⁇ ) ⁇ (v c / V G ) 2 ⁇ m
- the PWM carrier waveform of the switching signal is asymmetric with respect to the time axis.
- the present invention relates to an AC-AC converter circuit that converts power from an AC power source into AC power, and can be used in the power industry.
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Abstract
Description
三相交流電力によって駆動されるモータを単相交流電源で駆動するためにAC-ACコンバータ回路を用いることが考えられる。AC-ACコンバータ回路は、交流電源からの電力を直流電力に変換する整流回路と、整流された直流電力を所望の仕様の交流電力に変換するDC-AC変換回路とを含んで構成することが考えられる。
このことから、本発明者らは、AC-ACコンバータ回路には回路全体を小型化し、電源電流の高調波を少なくする観点から改善すべき課題があることを認識した。
このような課題は、単相-三相のAC-ACコンバータ回路に限られず、他の種類のAC-ACコンバータ回路についても生じうる。
図1は、本発明の実施形態に係るAC-ACコンバータ回路100の一例を示す回路図である。AC-ACコンバータ回路100は、単相電源12からの電力に基づき三相電力を生成する電力変換装置として機能する。一例として、AC-ACコンバータ回路100は、ポンプ、コンプレッサ、船や飛行機の電動アクチュエータ、ロボットアームなど多様な装置を駆動するために使用することができる。AC-ACコンバータ回路100は、フィルタ14と、整流回路16と、降圧回路18と、Zソース回路20と、三相のインバータ回路22と、制御回路24と、を含んでいる。本明細書において、単相電源12から三相電力の出力に向かう電力の流れに沿って、上流側を前段または入力と、下流側を後段または出力と表記することがある。
スイッチング素子T7は公知の様々な素子であってもよい。この例では、スイッチング素子T7はn型MOSFETである。スイッチング素子T7のドレインは整流回路16のプラス側の出力端16pに接続され、スイッチング素子T7のソースは降圧回路18のプラス側の出力端18pに接続され、スイッチング素子T7のゲートは制御回路24に接続される。ダイオードD5のカソードは出力端18pに接続され、ダイオードD5のアノード18mは整流回路16の出力端16mに接続される。
実施の形態の説明では、交流電圧を整流する整流回路16と、別の交流電圧を生成するインバータ回路22との間にZソース回路20を設けたが、本発明はこれに限られない。例えば、Zソース回路の代替として、いかなるインピーダンスネットワーク回路を設けても良い。このようなインピーダンスネットワーク回路としては、一例として、Tソース回路とΓソース回路があげられる。本発明のAC-ACコンバータは、Zソース回路20に代えて、整流回路16とインバータ回路22との間にTソース回路20(B)またはΓソース回路20(C)が設けられてもよい。図13は、第1変形例に係るTソース回路20(B)とΓソース回路20(C)の一例を示す回路図である。図13(a)はTソース回路20(B)の一例を示し、図13(b)はΓソース回路20(C)の一例を示す。以下、図1も参照しながら、Tソース回路20(B)とΓソース回路20(C)の構成と動作を説明する。
実施の形態の説明では、ダイオードD1-D5が1方向に通電可能な半導体ダイオードである例について説明したが、これに限られない。ダイオードD1-D5の全部または一部は、MOSFETのように逆方向に通電可能なスイッチング素子に置き換えられてもよい。この変形例は、実施の形態に係るAC-ACコンバータ回路100と同様の作用効果を奏する。
実施の形態の説明では、スイッチング素子T1~T7がn型MOSFETである例について説明したが、これに限られない。スイッチング素子T1~T6、T7の種類は特に限定されず、バイポーラトランジスタ、IGBT(Insulated Gate Bipolar Transistor)、SiCデバイス、GaNデバイスなどの公知の各種スイッチング素子を適用することができる。この変形例は、実施の形態に係るAC-ACコンバータ回路100と同様の作用効果を奏する。
ダイオードD28では、アノードに正の入力電圧vGが印加される。従って、降圧回路用スイッチング素子T7には、正の入力電流iT7,1が流れる(下付き添字の左側の「T7」はスイッチング素子T7を示し、下付き添字の右側の「1」は第1の動作モード(アクティブモード)を示す。以下同様)。一方ダイオードD5は、カソードに正の入力電圧vGが印加されるため、電流が流れない。
iT7,1=iC,1+iL、1 ・・・(1)
インダクタL1を流れた電流iL,1は2つに分岐し、一方はコンデンサC2に入力する電流iC,1となり、他方は出力電流iQ,1となる。すなわち、
iQ=iL、1-iC,1 ・・・(2)
上記の2つの式から、インダクタ電流iL、1は以下のように算出される。
iL、1=iQ/2+iT7,1/2 ・・・(3)
iL、1≧IQ/2 ・・・(4)
であることが分かる。ここでIQは、出力ピーク電流である。
すなわち、インダクタ電流iL、1は、常に出力ピーク電流IQの1/2以上である。
|vG|=vC,1+vL,1 ・・・(5)
また出力電圧vPN,1は、コンデンサC2に印加される電圧(キャパシタ電圧)vC,1と、インダクタL2に印加される電圧VL,1との和であるため、以下の式が成り立つ。
vPN,1=vC,1-vL,1 ・・・(6)
従って、
vC,1=|vG|/2+vPN,1/2 ・・・(7)
となる。
ここでダイオードD28があることにより、出力電圧vPN,1は常に正である。従って、
vC,1≧VG/2 ・・・(8)
であることが分かる。ここでVGは、入力ピーク電圧である。
すなわち、キャパシタ電圧vC,1は、入力ピーク電圧VGの1/2より常に大きい。
降圧回路用スイッチング素子T7がオフであるため、降圧回路用スイッチング素子T7には入力電流iT7,2が流れない。すなわち、
iT7,2=0 ・・・(9)
ダイオードD5には正の電流iD5,2が流れる。すなわち、
iD5,2>0 ・・・(10)
iD5,2=iC,2+iL,2 ・・・(11)
iQ=iL,2-iC,2 ・・・(12)
であることが分かる。
式(11)(12)から、インダクタ電流iL1,2は以下のように算出される。
iL,2=iQ/2+iD5,2/2 ・・・(13)
iL,2≧IQ/2 ・・・(14)
であることが分かる。
すなわち、インダクタ電流iL,2は、常に出力ピーク電流IQの1/2以上である。
vD5,2=vC,2+vL,2=0 ・・・(15)
すなわちvL,2=-vC,2となる。これは、キャパシタ電圧と大きさが同じであって逆符号の電圧が、インダクタに印加されることを意味する。
また出力電圧vPN,2は、
vPN,2=vC,2-vL,2=2・vC,2 ・・・(16)
となることが分かる。
インバータ回路用スイッチング素子T30がオンであるため、電流は双方向電源32の手前でインバータ回路用スイッチング素子T30をシュートスルーし、出力電圧vPN、3はゼロとなる。従って、このときモータ等の負荷には電力が供給されない。すなわち、
vPN,3=vC,3-vL,3=0 ・・・(17)
となる。
式(17)よりvL,3=vC,3となることが分かる。これは、キャパシタ電圧と大きさが同じであって同符号の電圧が、インダクタに印加されることを意味する。
vD5,3=vC,3+vL,3=2・vC,3 ・・・(18)
また、「キャパシタ電圧vC,3が、入力ピーク電圧VGの1/2より常に大きい」という条件、すなわち、
vC,3>VG/2 ・・・(19)
が満たされている限り、vD5,3>|vG|が成立するため、たとえ降圧回路用スイッチング素子T7がオンになっていても、降圧回路用スイッチング素子T7には電流が流れない。
以上の説明から分かる通り、昇圧モードでは、電流路はZソース回路にのみ形成される。
降圧動作時は、インバータ回路用スイッチング素子T30がオフ状態に維持され、降圧回路用スイッチング素子T7がオンとオフを周期的に繰り返すスイッチング動作を行うように制御される。換言すれば、降圧動作時には、アクティブモードと降圧モードとが周期的に繰り返して使用されるように制御がされる。
一方昇圧動作時は、降圧回路用スイッチング素子T7がオン状態に維持され、インバータ回路用スイッチング素子T30がオンとオフを周期的に繰り返すスイッチング動作を行うように制御される。換言すれば、昇圧動作時には、アクティブモードと昇圧モードとが周期的に繰り返して使用されるように制御がされる。
降圧動作時は、アクティブモードが使用される時間tAはtA=dA・TSW、降圧モードが使用される時間t0はt0=d0・TSW、ただしdA+d0=1、dB=0である。
昇圧動作時は、アクティブモードが使用される時間tAはtA=dA・TSW、昇圧モードが使用される時間tBはtB=dB・TSW、ただしdA+dB=1、d0=0である。
これらの各モードのデューティdA、d0、dBの値を変えることにより、出力電圧vPNを制御することができる。
<vPN>=2・vC・(1-dB)-|vG|・dA ・・・(20)
<vL>=|vG|・dA-vC・(1-2・dB) ・・・(21)
<iQ>=PM/<vPN> ・・・(22)
<iT7>=|iG|=(2・iL-<iQ>)・dA ・・・(23)
dA=DA+d'A ・・・(24)
d0=D0+d'0 ・・・(25)
dB=DB+d'B ・・・(26)
である。
一般にAC-ACコンバータ装置では、インダクタで発生するジュール熱等によるエネルギー損失を回避するために、インダクタ電流iLがなるべく小さくなるように抑制することが望ましい。すなわち、インダクタ電流iLを最小化することにより、装置の効率を最大化することができる。そこで与えられた拘束条件を満たす範囲で、iLを最小化するようなデューティを定めることを目標とする。
<vPN>=<vC>=|vG|・DA/(1-2・DB) ・・・(27)
ただし、式(8)(19)から
<vPN>=<vC> > VG/2 ・・・(28)
を満たす必要がある。
m=|vG|/<vPN>=(1-2・DB)/DA ・・・(29)
ただし、|vG|>0および式(8)の条件から、
0≦m≦2 ・・・(30)
を満たす必要がある。
iL=(1/2)・(<iQ>+|iG|/DA) ・・・(31)
これより、アクティブモードのデューティDAが大きければ大きいほど、インダクタ電流iLの値が小さくなることが分かる。
DA、BU=1/m ・・・(32)
DB,BU=0 ・・・(33)
D0,BU=1-1/m=(m-1)/m ・・・(34)
となる(下付き添字の右側のBUは降圧(Buck)を示す)。
このとき、式(32)で表されるdA、BUが、1≦m≦2におけるDA、BUの最大値となる。
DA、BO=1/(2-m) ・・・(35)
DB,BO=1-1/(2-m)=(1-m)/(2-m)・・・(36)
D0,BO=0 ・・・(37)
となる(下付き添字の右側のBOは昇圧(Boost)を示す)。
このとき、式(35)で表されるDA、BOが、0≦m≦1におけるDA、BOの最大値となる。なお式(32)と式(35)は、まとめて以下の式で表すことができる。
DA、BU/BO=min(1/m、1/(2-m)) ・・・(37)
ただしmin()は()内の小さい方の値を取ることを示す。
以上で、本発明のAC-ACコンバータ装置の電圧制御に降圧動作と昇圧動作のみが含まれる実施形態における、最適なデューティの算出方法の説明を終える。
iL≧(1/2)・IQ ・・・(38)
である。
降圧動作と昇圧動作におけるデューティDA、BU、DB、BU、D0、BU、DA、B0、DB,BO、D0、B0はそれぞれ、式(32)(33)(33)(34)(35)(36)により定めた。降圧動作と昇圧動作のみを用いて制御を行った場合、図17に示されるように、iG=0の近傍で、入力電流iGに正弦波形からの乱れが生じていることが分かる。すなわちこの場合、入力電流iGがゼロの近傍では、目的とする力率=1の制御が実現できない。本発明者らは、これが、降圧動作と昇圧動作のみによる制御では、入力電流iGがゼロの近傍で式(38)の条件が満たされないことに起因することを認識した。
DA、BU+DB,BU=1 ・・・(39)
D0,BU=0 ・・・(40)
である。
また昇圧動作時は、アクティブモードと昇圧モードのみが使用される。すなわち、
DA、BO+D0,BO=1 ・・・(41)
DB,BO=0 ・・・(42)
である。
これに対し、昇降圧動作では、アクティブモード、降圧モードおよび昇圧モードの3つのモードが使用される。すなわち、
DA、BB+DB,BB+D0,BB=1 ・・・(43)
である(下付き添字の右側のBBは昇降圧(Buck-Boost)を示す)。
前述のように、昇降圧動作は、入力電圧vGがゼロの近傍でも式(38)の条件が成立することを保証することにある。式(23)において、アクティブモードのデューティDAを、昇降圧動作時のアクティブモードのデューティDA、BBで置き換えたものを、
|iG|=(2・iL-<iQ>)・DA、BB ・・・(44)
とおく。
これより、
DA、BB=|iG|/(2・iL-<iQ>) ・・・(45)
となる。
ここで式(38)が成立しているとして、iL=(1/2)・IQとおく(IQは出力ピーク電流)。従って、昇降圧動作時のアクティブモードのデューティDA、BBは、
DA、BB=|iG|/(IQ-<iQ>) ・・・(46)
となる。
iG=2・PM・vG/VG 2 ・・・(47)
<vPN>=<vC> ・・・(48)
m=|vG|/<vPN> ・・・(49)
PM=(3/2)・VQ・IQ・cosφ ・・・(50)
M=2・VM/vc ・・・(51)
とおくと、
DA、BB=(6M・cosφ/(4-3M・cosφ))・(vC/VG)2・m=k・m ・・・(52)
と表される。
ただし、
M<Mmax=2/√3 ・・・(53)
cosφ<1 ・・・(54)
が成り立つ。
ここで、PMは出力電力、Mはインバータ変調率である。
すなわち、
k=6M・cosφ/(4-3M・cosφ) ・・・(55)
と定義する。
DA=min(DA,BU/BO、DA,BB) ・・・(56)
DB=(1/2)・(1-m・DA) ・・・(57)
DA、BB≧(6M・cosφ/(4-3M・cosφ))・(vC/VG)2・m=k・m ・・・(58)
DA、BBを式(58)で定められる範囲で規定することにより、本技術分野における規格で定められる許容歪率を含む範囲をカバーすることができる。
動作モードの別の例として、図18(b)に、k=k2>1のときの動作モードを示す。
図18(a)に示される通り、k=k1では、昇降圧動作(BB)と降圧動作(BU)のみが用いられる。
また図18(b)に示される通り、k=k2では、昇降圧動作(BB)と降圧動作(BU)と昇圧動作(BO)とが用いられる。
整流された入力電圧|vG|と出力電圧<vPN>(=キャパシタ電圧<vC>)から、定常状態におけるアクティブモードのデューティDA,BU、DA,BO、DA,BU/BOを求めることにより、最適なDA、DBを得ることができる。その結果、図19に示されるように、完全に整流された入力電流<iTA>とインダクタ電流iLが、入力電力の1周期の間で得られることが分かる。
式(24)(25)を式(21)に代入し、定常状態からの変動分を取り出すと、以下の式が得られる。
vL'=|vG|・d'A+2・vC・d'B ・・・(59)
ただしvL'は、インダクタ電圧vLの定常状態からの変動を表す。
降圧動作時は、シュートスルーのため、d0,BU=0である。またD0,BU=0であることからd'0、BU=0であることが分かる。
昇圧動作時は、d0、BO=0、dA,BO+dB,BO=1から、d'A,BO=-d'B,BOとなる。
昇降圧動作時は、d0、BBはインダクタ電流iLを最小にする値として決定される。従ってdA,BBの定常状態からの変動d'A,BBは発生せず、dB,BBの定常状態からの変動d'B,BBのみが発生する。
(d'A、BU、d'B、BU)=(vL'、0) ・・・(60)
(d'A、BO、d'B、BO)=(vL'/(|vG|-2・vC)、-vL'/(|vG|-2・vC)) ・・・(61)
(d'A、BB、d'B、BB)=(0、vL'/2・vC) ・・・(62)
図20(a)に、比較例に係るコンバータのキャリア信号を示す。
図20(b)に、比較例に係るコンバータのU相電圧波形を示す。
図20(b)は、U相の相電圧波形を示すが、V相、W相についても同様である。
図20(b)に示されるように、キャリア波形がdXより小さいとき(ただし、X∈{U、V、W}、各相電圧vXNはDCリンク電圧VDCとなる。
すなわちこの場合、
vXN=VDC ・・・(63)
である。
それ以外の相出力は0となる。
換言すれば、平均X相電圧<vXN>は、vDC・dXとなる。
<vXN>=vDC・dX ・・・(64)
本発明に係るインバータにおいても、同じ平均相電圧の出力を得る必要がある。
これを実現するための手法として、以下の2つの方法が考えられる。
シュートスルーの時の出力電圧vPNはゼロである。このため,平均U相相電<vUN>は、アクティブモード(すなわち、vPN、1=2・vC-|vG|)と降圧モード(vPN、1=2・vC)との間に得る必要がある。
方法1は、PWMキャリア波形を非対称化することにより、これを実現するものである。具体的には、モードの状態に応じてキャリア波形を以下のように変更する。
アクティブモードの間(tA=dA・TSW):0から1に変化
降圧モードの間(t0=d0・TSW):0から1に変化
昇圧モード(シュートスルー)(tB=dB・TSW):0を維持
図21(b)に、方法1に係るコンバータのU相電圧波形を示す。
すなわち、
tU,A=dU・TA=dU・dA・TSW ・・・(65)
tU,0=dU・T0=dU・d0・TSW ・・・(66)
となる。
これにより、平均相電圧は以下のように算出される。
<vUN>=vPN,1・tU,A/TSW+vPN,2・tU,0/TSW
=(2・vC-|vG|)・dU・dA+2・vC・dU・d0
=<vPN>・dU ・・・(67)
方法2は、シュートスルー期間(tB=dB・TSW)のスイッチングを統合するものである。
従来のスイッチング手順では、一方のハーフブリッジがターンオンする前に、他方が必ずターンオフするデッドタイム期間が設けられている。
方法2では、両方のハーフブリッジがターンオンするシュートスルー期間tSHをデッドタイム期間に設ける。換言すれば、シュートスルー期間をスイッチング手順に統合する。従ってスイッチ回数が増加することはない。
dH=dL+dSH ・・・(68)
シュートスルー期間(tB=dB・TSW)を、以下のようにアクティブモードと降圧モードとに比例分配する。
tB,A=dB,A・TSW=dB・dA/(dA+d0)・TSW ・・・(69)
tB,0=dB,0・TSW=dB・d0/(dA+d0)・TSW ・・・(70)
また、
tAN=dAN・TSW=(dA+dB,A)・TSW ・・・(71)
t0N=d0N・TSW=(dA+dB,0)・TSW ・・・(72)
tAN+t0N=1 ・・・(73)
が成り立つ。
これより、
dAN=dA+tB,A/TSW=dA/(1-dB) ・・・(74)
d0N=dA+tB,0/TSW=d0/(1-dB) ・・・(75)
が得られる。
すなわち、
tSH、A=(1/3)・tB、A ・・・(76)
tSH、0=(1/3)・tB、0 ・・・(77)
アクティブモードの間(tA、N=dAN・TSW):0から1に変化
降圧モードの間(t0、N=d0N・TSW):0から1に変化
昇圧モード(シュートスルー)(tB=dB・TSW):0を維持
dx、H=dx、Lと+(1/3)・dB,x ・・・(78)
ただしx∈{a、b、c}
da=min(dU、dV、dW) ・・・(79)
db=mid(dU、dV、dW) ・・・(80)
dc=max(dU、dV、dW) ・・・(81)
ただしmin()は()内の最小値を取ることを示し、mid()は()内の中間値を取ることを示し、max()は()内の最大値を取ることを示す。
シュートスルー期間中はDCリンク電圧が0(出力電圧が0)となる点に留意されたい。
dA,N=dA+tB、A/TSW=dA/dA,N=1-dB ・・・(82)
である点に留意すると、これは
dA/dA,N=1-dB ・・・(83)
の係数から求めることができる。
従って、
da,L=(1-dB)・da ・・・(84)
となる。
また、ハイサイドデューティda,Hは、
da,H=da,L+(1/3)・dB ・・・(85)
となる。
図22(b)に、方法2に係るコンバータのU相電圧波形を示す。
da,L=(1-dB)・da ・・・(86)
db,L=da,H+(1-dB)・(db-da) ・・・(87)
dc,L=db,H+(1-dB)・(dc-db) ・・・(88)
M<2/√3、
cosφ<1、
D3≧6M・cosφ/(4-3M・cosφ)・(vc/VG)2・m
D3=6M・cosφ/(4-3M・cosφ)・(vc/VG)2・m
Claims (8)
- 交流電圧を別の交流電圧に変換するAC-ACコンバータ回路であって、
前記交流電圧を整流する整流回路と、前記別の交流電圧を生成するインバータ回路と、の間にZソース回路が設けられていることを特徴とするAC-ACコンバータ回路。 - 前記整流回路と、前記Zソース回路と、の間に降圧回路が設けられていることを特徴とする請求項1に記載のAC-ACコンバータ回路。
- 前記Zソース回路に代えて、Tソース回路またはΓソース回路が前記整流回路と前記インバータ回路との間に設けられていることを特徴とする請求項1または2に記載のAC-ACコンバータ回路。
- 前記インバータ回路は、互いに直列接続された第1スイッチング素子および第2スイッチング素子を含み、
前記別の交流電圧を生成するために前記第1スイッチング素子がオンしているとき、前記第2スイッチング素子がオンする期間が設けられていることを特徴とする請求項1から3のいずれかに記載のAC-ACコンバータ回路。 - 前記降圧回路と前記インバータ回路とを制御する制御回路を含み、
前記降圧回路は、降圧回路用スイッチング素子を含み、
前記インバータ回路は、インバータ回路用スイッチング素子を含み、
前記制御回路は、
前記降圧回路用スイッチング素子がオンであり、前記インバータ回路用スイッチング素子がオフである第1の動作モードと、
前記降圧回路用スイッチング素子がオフであり、前記インバータ回路用スイッチング素子がオフである第2の動作モードと、
前記インバータ回路用スイッチング素子がオンである第3の動作モードと、を使用して制御を行うことを特徴とする、請求項2に記載のAC-ACコンバータ回路。 - 前記制御回路は、
入力電圧をvG、キャパシタ電圧をvc、平均出力電圧をvPN、変調率をm=|vG|/vPN、としたとき、
昇降圧動作時の第1の動作モードのデューティDA、BB、第1のパラメータM、第2のパラメータcosφが以下の式を満足するように制御を行うことを特徴とする、請求項5に記載のAC-ACコンバータ回路。
M<2/√3、
cosφ<1、
DA、BB≧6M・cosφ/(4-3M・cosφ)・(vc/VG)2・m - 前記制御回路は、
前記昇降圧動作時の第1の動作モードのデューティDA、BBが以下の式を満足するように制御を行うことを特徴とする、請求項6に記載のAC-ACコンバータ回路。
DA、BB=6M・cosφ/(4-3M・cosφ)・(vc/VG)2・m - スッチング信号のPWMキャリア波形は時間軸に対して非対称である、請求項6または7に記載のAC-ACコンバータ回路。
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EP18866692.9A EP3696966B1 (en) | 2017-10-13 | 2018-10-04 | Ac-ac converter circuit |
KR1020207013239A KR102387744B1 (ko) | 2017-10-13 | 2018-10-04 | Ac-ac 컨버터 회로 |
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US11451181B2 (en) * | 2020-09-29 | 2022-09-20 | GM Global Technology Operations LLC | Inverter circuit for an electric machine |
CN113300614A (zh) * | 2021-05-29 | 2021-08-24 | 湖南工业大学 | 一种含γ源电路的新型超稀疏矩阵变换器拓扑结构 |
Citations (5)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
JP2006186950A (ja) * | 2004-12-28 | 2006-07-13 | Tdk Corp | ノイズ抑制回路 |
US7130205B2 (en) | 2002-06-12 | 2006-10-31 | Michigan State University | Impedance source power converter |
JP2010119174A (ja) | 2008-11-11 | 2010-05-27 | Toyota Central R&D Labs Inc | 電力変換回路 |
JP2013048516A (ja) * | 2011-08-29 | 2013-03-07 | Sharp Corp | 力率改善回路 |
JP2016052167A (ja) * | 2014-08-29 | 2016-04-11 | 東洋電機製造株式会社 | 電力変換装置 |
Family Cites Families (15)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
US1998325A (en) * | 1933-08-23 | 1935-04-16 | Gen Electric | Uniform impedance filter |
JP2784783B2 (ja) * | 1989-01-31 | 1998-08-06 | ソニー株式会社 | フイルタ回路 |
CN1040272C (zh) * | 1995-03-15 | 1998-10-14 | 松下电工株式会社 | 逆变装置 |
JP3627303B2 (ja) * | 1995-08-11 | 2005-03-09 | 日立工機株式会社 | 遠心機 |
JP2004349734A (ja) * | 2003-04-24 | 2004-12-09 | Tdk Corp | ノーマルモードノイズ抑制回路 |
CN100367646C (zh) * | 2004-09-17 | 2008-02-06 | 浙江大学 | 单/三相阻抗源升/降电压交/交变换器 |
US8026691B2 (en) * | 2007-07-30 | 2011-09-27 | GM Global Technology Operations LLC | Double ended inverter system with a cross-linked ultracapacitor network |
US8334616B2 (en) * | 2008-09-19 | 2012-12-18 | Electric Power Research Institute, Inc. | Photovoltaic integrated variable frequency drive |
US8754625B2 (en) * | 2010-09-30 | 2014-06-17 | Intersil Americas Inc. | System and method for converting an AC input voltage to regulated output current |
CN103534916A (zh) * | 2011-03-10 | 2014-01-22 | 三菱电机株式会社 | 功率转换装置 |
JP2014143892A (ja) * | 2012-12-25 | 2014-08-07 | Toyo Electric Mfg Co Ltd | Zソースインバータ回路 |
JP5804167B2 (ja) * | 2013-09-19 | 2015-11-04 | ダイキン工業株式会社 | 電力変換装置 |
CN103595265A (zh) * | 2013-11-15 | 2014-02-19 | 山东航宇船业集团有限公司 | 内河船舶用小型风力发电变换器 |
US9431819B2 (en) * | 2014-01-31 | 2016-08-30 | Drs Power & Control Technologies, Inc. | Methods and systems of impedance source semiconductor device protection |
CN104201717A (zh) * | 2014-09-01 | 2014-12-10 | 黄守道 | 一种永磁直驱风电系统 |
-
2018
- 2018-10-04 JP JP2019548167A patent/JP6831924B2/ja active Active
- 2018-10-04 WO PCT/JP2018/037260 patent/WO2019073904A1/ja unknown
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- 2018-10-04 CN CN201880066813.7A patent/CN111213311B/zh active Active
- 2018-10-04 EP EP18866692.9A patent/EP3696966B1/en active Active
-
2020
- 2020-04-13 US US16/846,866 patent/US11177741B2/en active Active
Patent Citations (5)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
US7130205B2 (en) | 2002-06-12 | 2006-10-31 | Michigan State University | Impedance source power converter |
JP2006186950A (ja) * | 2004-12-28 | 2006-07-13 | Tdk Corp | ノイズ抑制回路 |
JP2010119174A (ja) | 2008-11-11 | 2010-05-27 | Toyota Central R&D Labs Inc | 電力変換回路 |
JP2013048516A (ja) * | 2011-08-29 | 2013-03-07 | Sharp Corp | 力率改善回路 |
JP2016052167A (ja) * | 2014-08-29 | 2016-04-11 | 東洋電機製造株式会社 | 電力変換装置 |
Non-Patent Citations (1)
Title |
---|
See also references of EP3696966A4 |
Cited By (2)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
WO2021117098A1 (ja) * | 2019-12-09 | 2021-06-17 | 三菱電機株式会社 | 電力変換装置 |
JPWO2021117098A1 (ja) * | 2019-12-09 | 2021-06-17 |
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