WO2015001924A1 - Convertisseur de fréquence - Google Patents

Convertisseur de fréquence Download PDF

Info

Publication number
WO2015001924A1
WO2015001924A1 PCT/JP2014/065364 JP2014065364W WO2015001924A1 WO 2015001924 A1 WO2015001924 A1 WO 2015001924A1 JP 2014065364 W JP2014065364 W JP 2014065364W WO 2015001924 A1 WO2015001924 A1 WO 2015001924A1
Authority
WO
WIPO (PCT)
Prior art keywords
frequency
signal
input
terminal
local oscillation
Prior art date
Application number
PCT/JP2014/065364
Other languages
English (en)
Japanese (ja)
Inventor
満仲　健
Original Assignee
シャープ株式会社
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by シャープ株式会社 filed Critical シャープ株式会社
Publication of WO2015001924A1 publication Critical patent/WO2015001924A1/fr

Links

Images

Classifications

    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03D—DEMODULATION OR TRANSFERENCE OF MODULATION FROM ONE CARRIER TO ANOTHER
    • H03D7/00—Transference of modulation from one carrier to another, e.g. frequency-changing
    • H03D7/14—Balanced arrangements
    • H03D7/1425—Balanced arrangements with transistors
    • H03D7/1466—Passive mixer arrangements
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03D—DEMODULATION OR TRANSFERENCE OF MODULATION FROM ONE CARRIER TO ANOTHER
    • H03D7/00—Transference of modulation from one carrier to another, e.g. frequency-changing
    • H03D7/14—Balanced arrangements
    • H03D7/1425—Balanced arrangements with transistors
    • H03D7/1441—Balanced arrangements with transistors using field-effect transistors

Definitions

  • the present invention relates to a frequency converter that mixes a millimeter-wave band or higher frequency input signal using a local oscillation signal and converts it to a baseband signal or an intermediate frequency.
  • the direct conversion method has often been used because the size of the device can be reduced.
  • the high-frequency signal is converted into baseband.
  • the self-mixing generated by the local oscillation signal wrapping around the high-frequency signal input occurs and the reception performance of the receiver deteriorates.
  • the even harmonic mixer performs an odd symmetric nonlinear operation on positive and negative signals of an input signal, and a local oscillator for an input signal that is a part of a signal generated by a third-order term included in the nonlinear operation This is a method of extracting a signal component whose frequency is shifted by twice the frequency of the output signal.
  • FIG. 6 is a circuit diagram showing an example of a conventional even harmonic mixer disclosed in Patent Document 1.
  • FIG. 6 is a circuit diagram showing an example of a conventional even harmonic mixer disclosed in Patent Document 1.
  • the even harmonic mixer receives an input signal input from IN1 and IN2 and a local oscillation signal (L01 / L02 / L03 / L04).
  • the input signal is converted into a complementary current input on which a direct current is superimposed by a differential amplifier composed of field effect transistors Q9 and Q10, and then the frequency is applied from terminals P1 and P2.
  • the output signals OUT1 and OUT2 are output from the first output terminal P3 and the second output terminal P4 as differential current outputs on which DC components are superimposed, and the local oscillation signal is the first local oscillation signal.
  • L01 a second local oscillation signal L02 that is an inverted signal of the first local oscillation signal L01, a third local oscillation signal L03 whose phase is delayed by 90 degrees from the first local oscillation signal L01, It consists of a fourth local oscillation signal L04 which is an inverted signal of the local oscillation signal L03.
  • a signal including a signal having a frequency obtained by modulating the input signal with a frequency twice the frequency of the local oscillation signal is output.
  • Japanese Patent Publication Japanese Patent Laid-Open No. 2005-1559587 (published on June 16, 2005)
  • even harmonic mixers generally have high intermodulation distortion, so if the increase in power consumption of even harmonic mixers is allowed, cross modulation distortion can be suppressed, but receivers are required to have low power consumption. In many cases, even even harmonic mixers require low power consumption, and the magnitude of intermodulation distortion of even harmonic mixers is a problem.
  • the even harmonic mixer by using the third-order distortion term, it is necessary to considerably increase the amplitude of the output signal of the local oscillator as compared with the case where the conventional second-order distortion term is used. was there. In a receiver handling a millimeter wave band or higher, it is difficult to considerably increase the amplitude of the local oscillation signal.
  • the double conversion system that performs frequency conversion a plurality of times has a problem that the gain in all circuits that perform frequency conversion decreases because a plurality of switch transistors that perform frequency conversion are connected in series.
  • the conventional even harmonic mixer shown in FIG. 6 when used as a frequency converter that handles millimeter wave or higher frequency input signals, the input signal is converted into a current signal, so that the gain is reduced in the high frequency characteristics. Problems arise.
  • An object of the present invention is to receive an unnecessary signal (an input signal having a frequency similar to that of a local oscillation signal), to reduce power consumption and to efficiently perform frequency conversion, and to reduce an input signal to 1 Not only the frequency of / 2, but also the local oscillation signal with a frequency of 1 / N can be converted into a baseband signal, and even if the local oscillation signal is a low frequency, an input signal with a millimeter wave or higher frequency can be To provide a frequency converter capable of performing frequency conversion to a baseband signal.
  • the frequency converter of the present invention has an input signal and a local oscillation signal as inputs, and outputs an output signal whose frequency is shifted with respect to the input signal.
  • the output signal is output from an output terminal, and the local oscillation signal is composed of N signals having different phases, and N switch transistors having first, second, and third terminals
  • the current flowing between the third terminal and the second terminal is a function of the voltage between the first terminal and the second terminal, each of the second terminals being And each of the third terminals is connected to the output terminal, and each of the local oscillation signals is supplied to each of the first terminals in an alternating manner, and
  • the frequency is the local oscillation signal.
  • Respect is characterized in that it is a frequency close to N times or N times.
  • an unnecessary signal (input signal having the same frequency as that of the local oscillation signal) is not received, power consumption can be reduced, and efficient frequency conversion can be performed.
  • the local oscillation signal with a frequency of 1 / N can be converted into a baseband signal, and even if the local oscillation signal is a low frequency, an input signal with a millimeter wave or higher frequency can be A frequency converter that can convert the frequency into a baseband signal can be realized.
  • an unnecessary signal (an input signal having a frequency similar to that of a local oscillation signal) is not received, power consumption can be reduced and efficient frequency conversion can be performed.
  • a local oscillation signal having a frequency of 1 / N as well as a frequency of 1/2 can be converted into a baseband signal, and even if the local oscillation signal has a low frequency, the frequency is a millimeter wave or higher.
  • a frequency converter that can convert the frequency of an input signal into a baseband signal can be realized.
  • FIG. 3 is a circuit diagram of the frequency converter according to the first embodiment.
  • 4 is a circuit diagram of a buffer amplifier provided in the frequency converter according to the first embodiment.
  • FIG. FIG. 2 is a circuit diagram of a frequency converter that converts an output signal output from a terminal A into a voltage signal with a configuration different from the configuration illustrated in FIG. 1 and outputs the voltage signal from an output terminal.
  • 6 is a circuit diagram of a frequency converter according to Embodiment 2.
  • FIG. 6 is a circuit diagram of a frequency converter according to Embodiment 3.
  • FIG. It is a circuit diagram of the conventional even harmonic mixer currently disclosed by patent document 1.
  • FIG. 1 is a circuit diagram of the conventional even harmonic mixer currently disclosed by patent document 1.
  • FIGS. 1 to 5 Embodiments of the present invention will be described with reference to FIGS. 1 to 5 as follows.
  • FIG. 1 is a circuit diagram of the frequency converter 1.
  • the input signal input from the input terminal IN of the frequency converter 1 is a high-frequency signal having a millimeter wave band or a higher frequency carrier wave, while the switch transistors M1, M2... MN (N is an integer of 2 or more)
  • the local oscillation frequency of the local oscillation signal supplied to the gate terminal G serving as the first terminal of 1) is configured around 1 / N times the frequency of the input signal (including 1 / N times). .
  • the source terminals S (second terminals) on the input sides of the switch transistors M1, M2,... MN are connected to the input terminal IN, while the switch transistors M1, M2,.
  • Each drain terminal D (third terminal) on the output side of M2... MN is connected to the terminal A.
  • the output signal output from the terminal A is converted into a voltage signal by the illustrated resistance element R1 and output from the output terminal OUT1.
  • the current flowing between the drain terminal D (third terminal) and the source terminal S (second terminal) of each switch transistor M1, M2,... MN is the gate terminal G (first terminal). And a source terminal S (second terminal).
  • a signal having a phase of 0 degree of the local oscillation signal is supplied to the gate terminal G that is the first terminal of the switch transistor M1, and the gate terminal G that is the first terminal of the switch transistor M2 is supplied to the gate terminal G.
  • a signal of phase 360 / N degrees of the local oscillation signal is supplied to the gate terminal G which is the first terminal of the switch transistor MN.
  • the local oscillation signal is supplied from a voltage controlled oscillator (not shown) formed on the same semiconductor substrate as the frequency converter 1.
  • Each of the first to Nth local oscillation signals is supplied to each of the first terminals of the switch transistors M1, M2,.
  • the voltage is supplied in an alternating manner means that the voltage is not supplied only with a direct-current voltage (DC voltage).
  • DC voltage direct-current voltage
  • the frequency is as low as 1 / N times, but the local oscillation. This means that the signal is supplied as a relatively high frequency signal that is inverted every predetermined period.
  • the buffer amplifier 11 has a phase 0 Is supplied to the gate terminal G which is the first terminal of the switch transistor M1, and the buffer amplifier 12 supplies the local oscillation signal having a phase of 360 / N degrees to the gate terminal which is the first terminal of the switch transistor M2. Further, the buffer amplifier 1N supplies a local oscillation signal having a phase of 360 ⁇ (N ⁇ 1) / N degrees to the gate terminal G serving as the first terminal of the switch transistor MN.
  • the Nth order harmonics of the local oscillation signals having different phases from the Nth order are K ⁇ cosN ( ⁇ t + 2 ⁇ (N ⁇ 1) / N) (K is a calculated coefficient).
  • the input signal can be k 1 ⁇ cos ( ⁇ 1 t) ( k 1 is a coefficient).
  • the frequency conversion of the fundamental wave performed by the N switch transistors M1, M2,... MN is Bcos ( ⁇ 1 t) ⁇ cos ( ⁇ t), Bcos ( ⁇ 1 t) ⁇ cos ( ⁇ t + 2 ⁇ / N) ⁇ Bcos ( ⁇ 1 t) ⁇ cos ( ⁇ t + 2 ⁇ (N ⁇ 1) / N) (B is a calculated coefficient), but when added at point A (terminal A), it becomes 0.
  • the frequency conversion with the Mth order (2 ⁇ M ⁇ N, M is an integer) harmonic component is similarly Ccos ( ⁇ 1 t) ⁇ cosM ( ⁇ t), Ccos ( ⁇ 1 t) ⁇ cosM ( ⁇ t + 2 ⁇ / N ) ... Ccos ( ⁇ 1 t) ⁇ cosM ( ⁇ t + 2 ⁇ (N ⁇ 1) / N) (C is a calculated coefficient), but when added at point A (terminal A), it becomes zero.
  • the frequency conversion with the Nth order (M ⁇ N, N is an integer) harmonic component is Dcos ( ⁇ 1 t) ⁇ cosN ( ⁇ t), Dcos ( ⁇ 1 t) ⁇ cosN ( ⁇ t + 2 ⁇ / N). Since Dcos ( ⁇ 1 t) ⁇ cosN ( ⁇ t + 2 ⁇ (N ⁇ 1) / N) (D is a calculated coefficient), at point A (terminal A), Dcos ( ⁇ 1 t) ⁇ cosN ( ⁇ t). .
  • FIG. 2 is a circuit diagram of the buffer amplifiers 11, 12... 1N provided in the frequency converter 1.
  • the gate voltages of the switch transistors M1, M2,... MN are the same as the power supply voltages of the buffer amplifiers 11, 12,.
  • the capacity for cutting the DC voltage in the buffer amplifiers 11, 12,..., 1N is deleted, and the circuit is simplified.
  • a buffer circuit including a transistor 21 and an inductor 22 as a load is used.
  • N local oscillation signals whose phases are shifted from each other by 360 / N degrees input from a voltage controlled oscillator (not shown) or the like are supplied to the transistors 21 provided in the respective buffer amplifiers 11, 12. Input to the gate terminal G.
  • each buffer amplifier 11, 12,... 1N an inductor 22 is connected to the drain terminal D of the transistor 21, and each buffer amplifier 11, 12,. Since the outputs are directly connected to the gate terminals G of the switch transistors M1, M2,... MN, it is necessary to provide N buffer amplifiers corresponding to the number of switch transistors.
  • the gate voltages of the switch transistors M1, M2,... MN are made the same as the power supply voltages of the buffer amplifiers 11, 12,.
  • the circuit for cutting the DC voltage at 1N is deleted to simplify the circuit, the present invention is not limited to this, and a configuration using a buffer amplifier having a capacity for cutting the DC voltage is used. It is good.
  • FIG. 3 is a circuit diagram of the frequency converter 1a that converts the output signal output from the terminal A into a voltage signal by the transimpedance amplifier 10 and the impedance element Z1 such as a resistor and outputs the voltage signal from the output terminal OUT2.
  • the output signal output from the terminal A shown in FIG. 1 is converted into a voltage signal by the resistance element R1 and output from the output terminal OUT1, instead of the configuration shown in FIG.
  • the output signal output from the terminal A is input to the transimpedance amplifier 10 connected in the subsequent stage, and after forming a closed loop with the impedance element Z1 such as a resistor, the voltage signal is output from the output terminal OUT2.
  • a configuration can also be used.
  • FIG. 4 is a circuit diagram of the frequency converter 1b.
  • the DC terminal (DC component) at the A terminal (point A) connected to each drain terminal D on the output side of the MN has the same potential, and has a low power consumption performance in which no DC current flows, A bias state in which the nonlinearity of the switch transistors M1, M2,.
  • the input terminals IN connected to the source terminals S on the input sides of the switch transistors M1, M2,... MN, and the output sides of the switch transistors M1, M2,.
  • the input side is connected via an impedance element 31 formed of, for example, a stub.
  • the bias voltage Vb is applied.
  • the output side is configured to supply the reference voltage of the transimpedance amplifier.
  • the present invention is not limited to this.
  • the frequency converter 1c includes a plurality of input terminals IN1, IN2,... IN (N / 2) (N is an integer of 2 or more), and these input terminals IN1, IN2,. ... The same input signal is input to each of IN (N / 2).
  • the source terminals S on the input sides of the switch transistors M1 and M2 are connected to the input terminal IN1, and the source terminals S on the input sides of the switch transistors M3 and M4 are connected to the input terminal IN2.
  • the source terminals S on the input side of the switch transistor MN-1 and the switch transistor MN are connected to the input terminal IN (N / 2), and an input signal input from one input terminal is applied to the corresponding input terminal.
  • the difference from Embodiments 1 and 2 described above is that the signals are input from the source terminals S of two adjacent switch transistors.
  • Other configurations are as described in the first and second embodiments. For convenience of explanation, members having the same functions as those shown in the drawings of Embodiments 1 and 2 are given the same reference numerals, and explanation thereof is omitted.
  • FIG. 5 is a circuit diagram of the frequency converter 1c.
  • the frequency converter 1c includes a plurality of input terminals IN1, IN2,... IN (N / 2), and these input terminals IN1, IN2,.
  • the same input signal is input to each of 2).
  • an antenna is connected to each of the input terminals IN1, IN2,... IN (N / 2).
  • the source terminals S on the input sides of the switch transistors M1 and M2 are connected to the input terminal IN1, and the source terminals S on the input sides of the switch transistors M3 and M4 are connected to the input terminal IN2.
  • the source terminals S on the input side of the switch transistor MN-1 and the switch transistor MN are connected to the input terminal IN (N / 2), and an input signal input from one input terminal is applied to the corresponding input terminal. Input is made from source terminals S of two adjacent switch transistors.
  • each drain terminal D (third terminal) on the output side of the switch transistors M1, M2,... MN is connected to the terminal A as in the first and second embodiments.
  • the gate terminals G serving as the first terminals of the respective switch transistors M1, M2,... MN have N local portions whose phases are different from each other by 360 / N, as in the first and second embodiments.
  • the oscillation signals may be input respectively, in the present embodiment, the gate terminals G serving as the first terminals of the two switch transistors connected to the same input terminal have phases opposite to each other.
  • a differential signal is input as a local oscillation signal.
  • the local oscillation signals are composed of N pieces having different phases from each other, and the gates serving as the first terminals of the switch transistors MN-1 and MN connected to the input terminal IN (N / 2).
  • the two local oscillation signals input to each of the terminals G are local oscillation signals having opposite phases.
  • the case where two switch transistors are connected to one input terminal has been described as an example.
  • the number of switch transistors connected to one input terminal is not particularly limited.
  • two switch transistors may be connected to the input terminal IN1, and three switch transistors may be connected to the input terminal IN2.
  • a configuration may be adopted in which one switch transistor is connected to one input terminal.
  • the frequency converter according to the first aspect of the present invention is a frequency converter that receives an input signal and a local oscillation signal as an input, and outputs an output signal whose frequency is shifted with respect to the input signal.
  • the output signal is output from an output terminal, and the local oscillation signal includes N signals having different phases, and includes N, first, second, and third terminals.
  • a plurality of switch transistors, and a current flowing between the third terminal and the second terminal is a function of a voltage between the first terminal and the second terminal, and the second
  • Each of the terminals is connected to the input terminal, each of the third terminals is connected to the output terminal, each of the local oscillation signals is supplied to each of the first terminals in an alternating manner,
  • the frequency of the input signal is against parts oscillation signal, a frequency close to N times or N times.
  • an unnecessary signal (input signal having the same frequency as that of the local oscillation signal) is not received, power consumption can be reduced, and efficient frequency conversion can be performed.
  • the local oscillation signal with a frequency of 1 / N can be converted into a baseband signal, and even if the local oscillation signal is a low frequency, an input signal with a millimeter wave or higher frequency can be A frequency converter that can convert the frequency into a baseband signal can be realized.
  • the local oscillation signals may be different in phase from each other by 360 / N degrees.
  • a local oscillation signal having a frequency of 1 / N as well as a 1/2 frequency with respect to the input signal can be converted into a baseband signal, and even if the local oscillation signal has a low frequency, A frequency converter that can convert an input signal having a frequency of millimeter wave or higher into a baseband signal can be realized.
  • bias voltages having the same potential are applied to the second and third terminals.
  • the voltage superimposed on the local oscillation signal has the same potential as the power supply voltage of the buffer circuit that supplies the local oscillation signal.
  • the buffer circuit does not need a capacity for cutting off the DC voltage, which can contribute to a reduction in area.
  • each of the input terminals is connected to a second terminal of one or more of the switch transistors. Is preferred.
  • the input signal may be a high-frequency signal and the output signal may be a baseband signal.
  • a direct conversion receiver or a low IF receiver can be configured.
  • a configuration may be such that local oscillation signals having opposite phases are supplied to the first terminals of the two switch transistors connected to each other.
  • the frequency converter of the present invention can be used as a frequency converter in a direct conversion system using a millimeter wave and a higher frequency as a carrier wave or a low IF output receiver. Furthermore, since the local oscillation signal can be used as a receiving device even if only a low frequency can be prepared for the input signal, a receiver capable of receiving a higher frequency signal can be provided on the semiconductor substrate.

Landscapes

  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Superheterodyne Receivers (AREA)

Abstract

Des bornes de source (S) de transistors de commutation (M1∙M2∙∙∙MN) sont connectées à une borne d'entrée (IN). Chaque signal d'un nombre N de signaux d'oscillation locale présentant différentes phases est envoyé respectivement par courant alternatif vers des bornes de grille (G) des transistors de commutation (M1∙M2∙∙∙MN). Des bornes de drain (D) des transistors de commutation (M1∙M2∙∙∙MN) sont connectées à une borne de sortie (OUT1). Les fréquences des signaux d'entrée représentent N fois, ou près de N fois, les fréquences des signaux d'oscillation locale. En conséquence, un convertisseur de fréquence peut être produit, avec lequel : la consommation de puissance peut être réduite et une conversion de fréquence efficace peut être réalisée sans recevoir de signaux indésirables ; non seulement les signaux d'oscillation locale dont la fréquence est la moitié de celle du signal d'entrée, mais en outre ceux dont la fréquence est 1/N de celle du signal d'entrée, peuvent être utilisés pour réaliser une conversion de fréquence dans un signal dans la bande de base ; et des signaux d'entrée à onde millimétrique ou de fréquences supérieures peuvent avoir leur fréquence convertie dans le signal dans la bande de base, même si les fréquences des signaux d'oscillation locale sont basses.
PCT/JP2014/065364 2013-07-03 2014-06-10 Convertisseur de fréquence WO2015001924A1 (fr)

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
JP2013139968 2013-07-03
JP2013-139968 2013-07-03

Publications (1)

Publication Number Publication Date
WO2015001924A1 true WO2015001924A1 (fr) 2015-01-08

Family

ID=52143508

Family Applications (1)

Application Number Title Priority Date Filing Date
PCT/JP2014/065364 WO2015001924A1 (fr) 2013-07-03 2014-06-10 Convertisseur de fréquence

Country Status (1)

Country Link
WO (1) WO2015001924A1 (fr)

Cited By (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
WO2022264185A1 (fr) * 2021-06-14 2022-12-22 三菱電機株式会社 Mélangeur d'harmoniques et dispositif de commande

Citations (6)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JP2005244397A (ja) * 2004-02-25 2005-09-08 Sony Corp 周波数変換回路、ｉｃおよび受信機
JP2007150663A (ja) * 2005-11-28 2007-06-14 Renesas Technology Corp ミキサ回路、局所発振信号発生回路、通信用半導体素子
WO2008084760A1 (fr) * 2007-01-12 2008-07-17 Rohm Co., Ltd. Circuit mélangeur et dispositif électronique l'utilisant
JP2009218637A (ja) * 2008-03-06 2009-09-24 Nagoya Industrial Science Research Inst ミキサ
JP2012049899A (ja) * 2010-08-27 2012-03-08 Toshiba Corp 周波数変換装置、受信装置およびテレビジョン装置
JP2012129636A (ja) * 2010-12-13 2012-07-05 Steady Design Ltd 周波数変換回路、送信機、及び受信機

Patent Citations (6)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JP2005244397A (ja) * 2004-02-25 2005-09-08 Sony Corp 周波数変換回路、ｉｃおよび受信機
JP2007150663A (ja) * 2005-11-28 2007-06-14 Renesas Technology Corp ミキサ回路、局所発振信号発生回路、通信用半導体素子
WO2008084760A1 (fr) * 2007-01-12 2008-07-17 Rohm Co., Ltd. Circuit mélangeur et dispositif électronique l'utilisant
JP2009218637A (ja) * 2008-03-06 2009-09-24 Nagoya Industrial Science Research Inst ミキサ
JP2012049899A (ja) * 2010-08-27 2012-03-08 Toshiba Corp 周波数変換装置、受信装置およびテレビジョン装置
JP2012129636A (ja) * 2010-12-13 2012-07-05 Steady Design Ltd 周波数変換回路、送信機、及び受信機

Cited By (2)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
WO2022264185A1 (fr) * 2021-06-14 2022-12-22 三菱電機株式会社 Mélangeur d'harmoniques et dispositif de commande
JP7199578B1 (ja) * 2021-06-14 2023-01-05 三菱電機株式会社 Ｎ次高調波ミクサ及び制御装置

Similar Documents

Publication Publication Date Title
KR101066054B1 (ko) 주파수 변환을 위한 시스템, 방법 및 장치
US5995819A (en) Frequency converter and radio receiver using same
US9071197B2 (en) Harmonic rejective passive up converter
Shrestha et al. A polyphase multipath technique for software-defined radio transmitters
US10326432B2 (en) Harmonic multiplier architecture
WO2009030938A3 (fr) Multiplicateur, mélangeur, modulateur, récepteur et émetteur
KR102640588B1 (ko) 믹서 출력에서 고조파를 제거하여 송신기를 선형화하는 시스템 및 방법
KR101085698B1 (ko) 주파수 혼합 장치
TW201001900A (en) Quadrature mixer circuit
Rieß et al. Analysis and design of a 60 GHz fully-differential frequency doubler in 130 nm SiGe BiCMOS
JP5016506B2 (ja) 電力増幅装置および通信装置
WO2015001924A1 (fr) Convertisseur de fréquence
US8217715B2 (en) Active polyphase filter producing two difference outputs having phase difference of π/2 radians
US8526536B2 (en) Quad LINC transmitter with switchable Chireix amplifiers
JP4393544B2 (ja) ミキサ回路及びこれを用いた無線通信装置
JP6705376B2 (ja) 可変ｒｆフィルタおよび無線装置
WO2016041575A1 (fr) Multiplicateur de fréquence à faible consommation d'énergie
JPH09205382A (ja) 周波数変換器およびこれを用いた無線受信機
JP2005236600A (ja) 高周波２逓倍回路
JP2008311863A (ja) 多入力多出力増幅器とこれを用いたアクティブインダクタ、フィルタ及び無線通信装置
US8432218B1 (en) Harmonic-rejection power amplifier
US8543078B2 (en) Harmonic mixer circuit
KR100679125B1 (ko) 직접 변환 방식 주파수 혼합기
JP2016036080A (ja) 周波数変換器
Saeed et al. Exploiting graphene quantum capacitance in subharmonic parametric downconversion

Legal Events

Date Code Title Description
121 Ep: the epo has been informed by wipo that ep was designated in this application

Ref document number: 14820334

Country of ref document: EP

Kind code of ref document: A1

NENP Non-entry into the national phase

Ref country code: DE

122 Ep: pct application non-entry in european phase

Ref document number: 14820334

Country of ref document: EP

Kind code of ref document: A1

NENP Non-entry into the national phase

Ref country code: JP