WO2013042437A1 - 電力変換装置、電動機駆動装置および空調機 - Google Patents

電力変換装置、電動機駆動装置および空調機 Download PDF

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Publication number
WO2013042437A1
WO2013042437A1 PCT/JP2012/067611 JP2012067611W WO2013042437A1 WO 2013042437 A1 WO2013042437 A1 WO 2013042437A1 JP 2012067611 W JP2012067611 W JP 2012067611W WO 2013042437 A1 WO2013042437 A1 WO 2013042437A1
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Prior art keywords
pulse
phase
stop
power conversion
current
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PCT/JP2012/067611
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English (en)
French (fr)
Japanese (ja)
Inventor
渉 初瀬
能登原　保夫
田村　建司
奥山　敦
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日立アプライアンス株式会社
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Priority to CN201280036040.0A priority Critical patent/CN103703669B/zh
Priority to KR1020137034744A priority patent/KR20140018407A/ko
Priority to JP2013534627A priority patent/JP5718474B2/ja
Publication of WO2013042437A1 publication Critical patent/WO2013042437A1/ja

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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P27/00—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage
    • H02P27/04—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage
    • H02P27/06—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage using dc to ac converters or inverters
    • H02P27/08—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage using dc to ac converters or inverters with pulse width modulation
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P6/00—Arrangements for controlling synchronous motors or other dynamo-electric motors using electronic commutation dependent on the rotor position; Electronic commutators therefor
    • H02P6/14—Electronic commutators
    • H02P6/16—Circuit arrangements for detecting position
    • H02P6/18—Circuit arrangements for detecting position without separate position detecting elements
    • H02P6/185—Circuit arrangements for detecting position without separate position detecting elements using inductance sensing, e.g. pulse excitation

Definitions

  • the present invention relates to a control technology for a power converter using a PWM (Pulse Width Modulation) control method.
  • PWM Pulse Width Modulation
  • the energization angle at the time of 120 degrees energization is expanded to 150 degrees energization by a torque command, so that the current flowing through the motor is sinusoidal.
  • a 120-degree / 150-degree energization switching technique that reduces pulsation of torque close to a wave is disclosed. It is described that, by using this method, the motor can be driven with high performance at the time of starting the motor and from a heavy load to a light load with a rotational force with less noise and vibration (see Patent Document 2). .
  • the 120-degree energization method and the 150-degree energization method described in Patent Document 1 and Patent Document 2 have a narrower switching operation region in one cycle than the 180-degree energization method, and thus reduce the switching loss of the power conversion device. It is possible.
  • an induced voltage detection circuit is provided to acquire phase information of the induced voltage during the stop period of the switching operation. It is necessary to switch the phase for performing the switching operation based on the phase information.
  • the magnet position sensorless 120-degree energization method and 150-degree energization method must always provide a period for stopping the switching operation near the zero cross of the induced voltage of the motor. Therefore, it is difficult to extend the switching operation period to an electrical angle of 150 degrees or more. Further, the switching operation stop period must be performed in synchronization with the induced voltage phase. However, there is a difference between the induced voltage phase and the current phase of the electric motor depending on the load condition and driving condition. Therefore, even if the 150-degree energization method is used, the effect of reducing torque pulsation is not always obtained. Further, if it is attempted to prevent a deviation between the phase of the induced voltage and the current phase of the electric motor, the operation of energization at 150 degrees may be impossible.
  • the 120-degree energization method and the 150-degree energization method determine the energization section and the open phase section (section in which both the upper and lower arm switching elements of the inverter are stopped) based on the phase of the induced voltage.
  • the open phase section section in which both the upper and lower arm switching elements of the inverter are stopped
  • the zero cross point of the induced voltage may not be included in the open phase section.
  • position detection may not be performed accurately when vector control is performed based on the phase of the induced voltage without a magnet position sensor.
  • the switching loss can be reduced by stopping the switching operation in a predetermined section, vector control based on accurate position detection cannot be performed.
  • the current flowing through the motor can be controlled in a sine wave without using an induced voltage detection circuit or the like, but the switching operation is always performed during one cycle of voltage and current. Therefore, switching loss increases and the efficiency of the power conversion circuit decreases.
  • Patent Document 3 when performing vector control using a three-phase power converter that performs PWM control, only the phase whose current value is close to zero is paused to perform two-phase modulation. Is going. However, since there is no current rest period, the copper loss of the motor occurs. That is, even if the two-phase modulation method described in Patent Document 3 is used, the switching loss of PWM control cannot be reduced and the efficiency of the power converter cannot be improved.
  • This invention is made
  • a power converter is a power converter that performs power conversion by PWM control using a vector control method, and outputs a pulse signal for performing the PWM control.
  • a control unit a power conversion circuit that converts DC power into AC power using a pulse signal output from the pulse control unit, a current detection unit that detects a current of the power conversion circuit, and the current detection unit
  • a vector control unit that performs vector control based on the detected current and generates a command voltage to the pulse control unit, and the pulse signal in a section determined based on a current phase of the power conversion circuit is defined.
  • a pulse stop control unit for generating a pulse stop control signal for stopping over a certain section and outputting the pulse stop control signal to the pulse control unit. That.
  • a switching loss during PWM control can be reduced, and a high-efficiency power conversion device can be provided.
  • it is a wave form chart showing the relation of the alternating voltage which flows into an electric motor, an alternating current, and a pulse signal, (a) expresses a PWM carrier signal and an applied voltage command, (b) expresses a U phase alternating current, (C) represents a pulse signal.
  • the power conversion device includes a power conversion circuit (inverter) that converts DC power into AC power using a PWM control pulse signal, detects a current flowing through the power conversion circuit, and vectorizes the power conversion circuit. And a vector control unit for controlling. Further, an open phase section is provided in which the pulse signal in the section determined with reference to the zero cross point of the current phase flowing through the power conversion circuit is stopped, and the switch elements of the upper and lower arms of the same phase are stopped. As a result, the number of switching operations during PWM control can be reduced to reduce switching loss, and accurate position information of the magnet position of the motor can be obtained from the zero cross point of the current phase by providing an open phase section. Can do. As a result, it is possible to perform stable vector control and improve the efficiency of the power conversion circuit (inverter) and the electric motor.
  • FIG. 1 shows a circuit configuration of a PWM control power converter 1a according to the first embodiment.
  • the AC motor 3 that is a permanent magnet synchronous motor is driven by vector control by the power conversion circuit 4 that is constituted by a three-phase inverter driven by PWM control.
  • the control method when a phase pulse stop section (that is, an open phase section) is provided in the pulse signal of the power conversion circuit 4 will be described.
  • the power conversion device 1 a includes a power conversion circuit 4 including a three-phase inverter that converts DC power into AC power, and a motor current that flows through an AC motor (motor) 3 connected to the power conversion circuit 4. And a control device 5a that performs vector control using a pulse signal that performs PWM control based on phase current information (current) 6A detected by the phase current detection unit 6. Is done.
  • the power conversion circuit 4 includes a power conversion main circuit 41 including three-phase semiconductor switching elements Sup, Sun, Svp, Svn, Swp, and Swn in which IGBTs (Insulated Gate Bipolar Transistors) and diodes are antiparallel.
  • a gate driver 42 that generates a gate signal supplied to the IGBT of the power conversion main circuit 41 based on the pulse signal 7A from the pulse control unit 7.
  • the control device 5a also includes a pulse control unit 7 that supplies a pulse signal 7A controlled based on an applied voltage command (command voltage) V * to the gate driver 42, and a phase current detected by the phase current detection unit 6.
  • a vector control unit 8 that performs vector control using the information 6A and calculates the applied voltage command V * , and a phase pulse stop section near the current zero cross based on the current phase information (current phase) 8A calculated by the vector control (Open phase section) It is constituted by a pulse stop control unit 9 that outputs a phase pulse stop control signal (pulse stop control signal) 9A for stopping the pulse signal 7A of ⁇ to the pulse control unit 7.
  • the vector control unit 8 is, for example, Non-Patent Document 1 (Sakamoto et al., “Simple Vector Control of a Position Sensorless Permanent Magnet Synchronous Motor for Home Appliances”, D. Vol. 124, No. 11 (2004) pp. 1133-1140) and Non-Patent Document 2 (Tohari et al., "Study of New Vector Control Method for Permanent Magnet Synchronous Motor for High Speed", Electron Theory D, Vol. 129, No. 1 (2009), pp. 36-45) Inverter output current is detected, three-phase to two-phase conversion (dq conversion; direct-quadrature conversion) is performed and fed back to the control system, and then the inverter is driven by two-phase to three-phase conversion again. This can be realized by using general vector control, and the control method is not specified. Therefore, since the operation of the vector control unit 8 is a well-known technique, a detailed description thereof is omitted.
  • FIG. 2 is a waveform diagram showing the relationship between an AC voltage, an AC current, and a pulse signal flowing through the AC motor 3 in a comparative example, where the horizontal axis indicates the voltage phase, and the vertical axis indicates the levels of the voltage, current, and pulse signal.
  • FIG. 6 shows a circuit configuration of a power conversion device 1b of the PWM control method of the comparative example.
  • elements having the same reference numerals as those in FIG. 1 have the same functions.
  • the vector control performed by the vector control unit 8 is the same control method as in FIG.
  • the control device 5b shown in FIG. 6 generates a PWM pulse signal by comparing the PWM carrier signal and the applied voltage command V * as shown in FIG. Further, the command value of the applied voltage command V * is obtained by performing calculation by the vector control unit 8 based on the phase current information 6A detected by the phase current detection unit 6.
  • the acquisition of the phase current information 6A by the phase current detection unit 6 is performed by directly detecting the AC output current by CT (Current Transformer) as disclosed in FIG. 1 of JP-A-2004-48886, for example.
  • CT Current Transformer
  • the current information of the DC bus may be acquired by a shunt resistor, and the phase current may be reproduced based on this current information.
  • FIG. 2A shows the PWM carrier signal and the applied voltage command V *, and the U-phase applied voltage command Vu * is representatively shown.
  • ⁇ v represents a voltage phase based on the U phase.
  • the pulse control unit 7 performs the pulse shown in FIG. 2C based on the U-phase applied voltage command Vu * and the triangular wave carrier signal (PWM carrier signal).
  • PWM carrier signal the triangular wave carrier signal
  • the U-phase AC current Iu as shown in FIG. 2B flows in the AC motor 3 by the PWM conversion control performed by the power conversion main circuit 41 using this pulse signal (GPU + / GPU ⁇ pulse signal).
  • ⁇ represents the phase difference between voltage and current.
  • the vector control unit 8 controls the amplitude of the voltage and the phase difference ⁇ between the voltage and the current by performing vector control based on the phase current information 6A including the U-phase alternating current Iu.
  • the switching operation is always performed during one period of the voltage / current, and the current is supplied by 180 degrees. More switching times than current energization. Therefore, with 180 degree energization, the switching loss resulting from this increases.
  • FIG. 3 is a waveform diagram showing the relationship between the AC voltage, AC current and pulse signal flowing through the AC motor 3 and the phase pulse stop control signal in the first embodiment, with the horizontal axis representing the voltage phase and the vertical axis representing the voltage. , Current, pulse signal, and open phase control signal (phase pulse stop control signal) levels. That is, FIG. 3 is a waveform diagram of this embodiment shown in contrast to the waveform diagram of FIG.
  • the pulse stop control unit 9 uses the zero cross point ⁇ of the current phase controlled by the vector control as a reference, and the phase ⁇ and the phase ⁇ + ⁇ are as shown in the following formula (1).
  • the pulse signals GPU + and GPU ⁇ both output a phase pulse stop control signal (open phase control signal) 9A for stopping switching to the pulse controller 7.
  • the phase pulse stop control signal 9A outputs “0” when switching is stopped for both the pulse signals GPU + and GPU ⁇ , and “1” when switching in the PWM control method of the comparative example is performed without stopping switching.
  • Equation (1) when ⁇ is the phase difference between voltage and current and ⁇ is the phase pulse stop period (open phase period), the voltage phase ⁇ v with respect to the U phase is ⁇ / When 2 ⁇ v ⁇ + ⁇ / 2 and ⁇ + ⁇ / 2 ⁇ v ⁇ + ⁇ + ⁇ / 2, switching by the pulse signals GPU + and GPU ⁇ is stopped. In other cases, switching is performed using pulse signals GPU + and GPU ⁇ .
  • both the pulse signals GPU + and GPU ⁇ are turned off in the phase pulse stop section ⁇ of the phase pulse stop control signal 9A. Therefore, as shown in FIG. 3C, the pulse controller 7 outputs a signal train of pulse signals paused in the phase pulse stop period ⁇ .
  • the phase pulse stop section (open phase section) ⁇ is set twice during one period of voltage and current.
  • the sinusoidal PWM control method not only the sinusoidal PWM control method but also the two-phase modulation type PWM control method and the third harmonic addition type PWM control method are the target PWM control modulation methods. It is possible to provide a pulse stop interval ⁇ .
  • the pulse signals GPU + and GPU ⁇ provided with the period for stopping the switching operation by the pulse stop control unit 9 according to the first embodiment are applied to the applied voltage phase and the AC motor 3 in the switching stop period and the switching operation period.
  • the shape is not provided based on the induced voltage phase. That is, the switching stop period and the switching operation period of the pulse signals GPU + and GPU ⁇ are set with reference to the zero cross point of the current phase.
  • the pulse signal sequence since the pulse signal is based on the voltage phase of the induced voltage, as shown in FIG. 2 (c), the pulse signal sequence has symmetrical ON / OFF duty before and after the zero cross point of the voltage. It becomes the shape to become.
  • the phase pulse stop section ⁇ is provided based on the current phase (that is, not a pulse signal based on the voltage phase), as shown in FIG.
  • the ON / OFF duty of the pulse signal train is not symmetrical before and after the voltage zero-cross point. That is, in the first embodiment, the ON / OFF duty of the pulse signal train is asymmetric before and after the current zero-cross point.
  • the phase pulse stop section ⁇ is provided in the section including the zero cross point of the current, as shown in FIG. 3C, before and after the phase pulse stop section ⁇ as the center.
  • the pulse signal trains A and B have an asymmetric shape. From this, when the phase pulse stop section ⁇ is provided in the section including the zero cross point of the current as in the first embodiment, it is observed whether the pulse signals before and after the phase pulse stop section ⁇ are asymmetric. Thus, it can be easily determined whether or not the first embodiment is applied.
  • FIG. 4 is a waveform diagram showing the relationship between the U-phase voltage, the U-phase current, and the pulse signal when the real machine including the power conversion device 1a according to the first embodiment is driven.
  • Fig. 4 shows voltage, current, and pulse signal levels. That is, FIG. 4 is a method in which a phase pulse stop period is provided in the vicinity including the zero cross point of the current according to the first embodiment, and the actual machine is driven by setting the phase pulse stop period in the two-phase modulation type PWM control method. Shows the voltage, current and pulse signal.
  • FIG. 4A shows the U-phase terminal voltage Vun of the power conversion main circuit 41
  • FIG. 4B shows the U-phase current Iu flowing through the AC motor 3
  • FIG. 4C shows the pulse signals GPU + and GPU ⁇ . .
  • the switching signals of the pulse signals GPU + and GPU ⁇ are both turned off in the section (indicated by ⁇ ) sandwiched by the alternate long and short dash line, and the phase pulse stop section ⁇ is set. I can confirm that. Further, since the phase pulse stop section ⁇ is set, it can be confirmed that the U-phase current Iu becomes zero in the section sandwiched by the alternate long and short dash line.
  • FIG. 5 is a characteristic diagram showing a relationship between the power conversion circuit loss, the motor loss, and the total loss obtained by adding them to the phase pulse stop period (open phase period) ⁇ by the power conversion device 1a of the first embodiment.
  • the horizontal axis represents the phase pulse stop interval (open phase interval) ⁇
  • the vertical axis represents the loss. That is, FIG. 5 shows the characteristics of the total pulse loss including the phase pulse stop interval ⁇ set by the pulse stop control unit 9 and the loss of the power conversion circuit 4, the loss of the AC motor 3, and these two losses.
  • the loss (power conversion circuit loss) of the power conversion circuit 4 of the first embodiment is caused by the fact that the number of switching times decreases as the phase pulse stop interval ⁇ increases. To reduce. Further, the loss of the AC motor 3 (motor loss) increases due to the increase in the harmonic component of the current by providing the phase pulse stop section ⁇ . Furthermore, since the increase of the harmonic component of the current becomes significant due to the increase of the phase pulse stop section ⁇ , the increase in loss (motor loss) of the AC motor 3 due to this increases. For this reason, as shown in FIG. 5, there is a phase pulse stop section ⁇ opt in which the total loss obtained by adding these two losses (power conversion circuit loss and motor loss) is minimum, and the phase pulse stop section ⁇ is represented by this phase pulse. By setting the stop section ⁇ opt, it is possible to reduce the loss of the entire power conversion device 1a.
  • the pulse stop control unit 9 it is possible to reduce the number of switching of the pulse signal for performing the PWM control with the configuration of the power conversion circuit 4 similar to the PWM control method of the comparative example. Become. In other words, when the pulse stop control unit 9 that is controlled by the microcomputer is configured by software, the configuration of the power conversion circuit 4 of the comparative example is not changed, and the power converter 1a is not added without adding new hardware. High efficiency can be achieved. Moreover, since the switching operation is stopped near the zero cross of the current of the AC motor 3, an increase in torque pulsation can be suppressed compared to the 150-degree energization method.
  • FIG. 7 is a waveform diagram showing a relationship between an AC voltage, an AC current and a pulse signal flowing through the motor, and a phase pulse stop control signal in the power conversion device according to the modified example of the first embodiment, and the horizontal axis indicates the voltage.
  • the phase ⁇ v, and the vertical axis represents the levels of voltage, current, pulse signal, and open phase control signal.
  • control device 5a shown in FIG. 1 is realized by an integrated circuit such as a microcomputer, it is preferable to reduce the calculation load of the microcomputer. Therefore, as shown in FIG. 7D, if the pulse stop control unit 9 sets the phase pulse stop section ⁇ only once per current cycle, it is possible to reduce the calculation load of the microcomputer.
  • the pulse stop control unit 9 performed by the control of the microcomputer uses the zero cross point ⁇ of the current phase controlled by the vector control as a reference at the phase ⁇ + ⁇ (see FIG. 7D), As shown in the equation (2), the phase pulse stop control signal 9A for stopping both the switching signals of the pulse signals GPU + and GPU ⁇ during the phase pulse stop period ⁇ is output to the pulse controller 7.
  • phase pulse stop section ⁇ may be set only once per current cycle in the phase difference ⁇ between the voltage and current.
  • phase pulse stop section ⁇ By setting the phase pulse stop section ⁇ to be set once per current cycle, it is possible to halve the calculation load of the pulse stop control unit 9 by the microcomputer. Further, by measuring the phase difference ⁇ between the voltage and the current under the load condition to be driven in advance, and setting the phase difference ⁇ between the voltage and the current in the phase pulse stop control signal 9A of the pulse stop control unit 9 as a fixed value. This further reduces the computational load on the microcomputer.
  • the power conversion circuit 4 of the first embodiment performs PWM control by the switching operation using the pulse signal 7A output from the pulse control unit 7 and outputs AC power to the AC motor 3.
  • the vector control unit 8 outputs the phase information 8A of the current calculated based on the phase current information 6A from the phase current detection unit 6 to the pulse stop control unit 9.
  • the pulse stop control unit 9 outputs a phase pulse stop control signal 9A generated based on the current phase information 8A to the pulse control unit 7. Therefore, the pulse control unit 7 stops the pulse signal 7A in a predetermined section with reference to the zero cross of the current phase of a predetermined phase (for example, U phase) of the power conversion circuit 4. Therefore, the power conversion circuit 4 stops switching near the current zero crossing, so that the switching loss is reduced.
  • the efficiency of the power conversion device 1a can be improved and distortion of the output current can be reduced.
  • Second Embodiment switching between the PWM control method in which the phase pulse stop interval ⁇ is provided as in the first embodiment and the normal PWM control method in which the phase pulse stop interval ⁇ is not provided will be described. That is, in 2nd Embodiment, the power converter device which can switch phase pulse stop area (delta) with driving
  • running conditions for example, rotation speed of AC motor
  • FIG. 8 shows a circuit configuration of the PWM control type power converter 11 according to the second embodiment.
  • the power converter 11 instead of the phase current detection unit 6 of the power converting apparatus 1a of the first embodiment shown in FIG. 1, the DC bus current detector for detecting a DC bus current I DC ( A current detection unit) 10. That is, the power converter 11 of the second embodiment is configured such that the DC bus current detection unit 10 outputs DC bus current information (current) 10 ⁇ / b> A to the vector control unit 8.
  • the vector control unit 8 is configured to output current phase information 8 ⁇ / b> A calculated by vector control and rotation speed information 8 ⁇ / b> B that is the rotation speed of the AC motor 3 to the pulse stop control unit 91. .
  • the pulse stop control part 91 of 2nd Embodiment can switch the phase pulse stop area (delta) with an operating condition (namely, rotational speed of AC motor 3).
  • the other configuration contents are the same as those of the power conversion device 1a of the first embodiment shown in FIG.
  • FIG. 9 is a characteristic diagram showing a setting example of a phase pulse stop section (open phase section) in the power converter 11 of the second embodiment, where the horizontal axis represents the rotation speed and the vertical axis represents the open phase section ⁇ . . That is, in the power conversion device 11 of the second embodiment, the pulse stop control unit 91 determines the magnitude of the current rotation speed N of the AC motor 3 and a preset rotation speed N1 as shown in FIG. When the current rotational speed N is less than the rotational speed N1, the phase pulse stop control signal 91A in which the phase pulse stop section ⁇ is set is output to the pulse controller 7. When the current rotational speed N is equal to or higher than the rotational speed N1, the phase pulse stop section ⁇ is set to 0, and a phase pulse stop control signal 91A that does not set the phase pulse stop section ⁇ is output to the pulse controller 7.
  • the pulse control unit 7 when the current rotational speed N of the AC motor 3 is less than the rotational speed N1, the pulse control unit 7 outputs a pulse signal having a phase pulse stop section ⁇ , and when the rotational speed is equal to or higher than the rotational speed N1, the pulse control unit. 7 outputs a pulse signal without a phase pulse stop section ⁇ .
  • the phase pulse stop section ⁇ is set to the rotational speed as shown in FIG.
  • a method of changing from N2 to the rotational speed N3 at a constant change rate may be used.
  • the phase pulse is stopped at a non-linear change rate along a predetermined curve.
  • a method of changing the section ⁇ may be used.
  • phase A configuration may be employed in which the pulse stop interval ⁇ is switched.
  • the horizontal axis in the characteristic diagrams of FIGS. 9A, 9 ⁇ / b> B, and 9 ⁇ / b> C is read as the DC bus current average value I DCave instead of the rotational speed N.
  • phase pulse stop section ⁇ may be switched based on the torque ⁇ output from the AC motor 3 instead of switching the phase pulse stop section ⁇ based on the rotational speed of the AC motor 3.
  • the horizontal axis in the characteristic diagrams of FIGS. 9A, 9 ⁇ / b> B, and 9 ⁇ / b> C is read as output torque ⁇ instead of the rotational speed N.
  • the AC motor 3 When in the low-speed rotation range, setting the phase pulse stop interval ⁇ enables the power converter to be driven more efficiently than the PWM control method of the comparative example. Further, when the AC motor 3 is in the high speed rotation range, the phase pulse stop section ⁇ is set to 0, and it is possible to smoothly shift to 180-degree energization without setting the phase pulse stop section.
  • phase pulse stop area (delta) when changing to the direction which narrows phase pulse stop area (delta) according to the driving
  • the phase pulse stop section ⁇ when changing the phase pulse stop section ⁇ in the direction of widening according to the operating conditions of the AC motor 3, the phase is stopped immediately from the stop section zero state to the predetermined stop section. It can be performed by either changing at a change rate or changing at a non-linear change rate from a stop zone zero state to a predetermined stop zone.
  • FIG. 10 illustrates an overall configuration diagram of an air conditioner 100 according to the third embodiment.
  • the air conditioner 100 includes an outdoor unit 101 that exchanges heat with the outside air, an indoor unit 102 that exchanges heat with the indoor atmosphere, and the outdoor unit 101 and the indoor unit 102. And a pipe 103 to be connected.
  • the outdoor unit 101 includes a compressor 104 that compresses refrigerant, a compressor drive motor 105 that drives the compressor 104, an electric motor drive device 106 that drives and controls the compressor drive motor 105, and outside air and heat using the compressed refrigerant. It is comprised with the heat exchanger 107 which performs exchange.
  • the electric power drive device 106 uses the power conversion device 1a of the first embodiment or the power conversion device 11 of the second embodiment.
  • the indoor unit 102 includes a heat exchanger 108 that exchanges heat with the room and a blower 109 that blows air into the room.
  • FIG. 11 is a characteristic diagram showing the relationship of efficiency with respect to the rotational speed of the compressor drive motor 105 in the air conditioner 100 shown in FIG. 10, the horizontal axis shows the rotational speed of the compressor drive motor 105, and the vertical axis shows the compressor. The efficiency of the drive motor 105 is shown.
  • the power conversion device 1a of the first embodiment is applied to the air conditioner 100, and the pulse signal 7A in which the phase pulse stop section ⁇ is provided from the pulse control unit 7 to the pulse stop control unit 9 is provided. Is output to control the power conversion circuit 4.
  • the number of times of switching of the power conversion circuit 4 can be reduced by providing the phase pulse stop section ⁇ , the loss of the motor driving device 106 can be reduced as a result.
  • the pulse stop controller 9 in FIG. 1 outputs a pulse signal with the phase pulse stop interval ⁇ set to 0, and switches to the 180-degree energization PWM control method to weaken it. It is possible to drive the field control region.
  • the number of switching operations of the power conversion circuit 4 can be reduced with the configuration of the power conversion circuit 4 similar to that of the PWM control method of the comparative example.
  • the control unit 9 is configured by software, it is possible to realize high efficiency of the air conditioner 100 without adding hardware.
  • the power converters 1a, 11 according to the present invention, the motor drive device 106 using the power converters 1a, 11 and the air conditioner 100 using the motor drive device 106 have been specifically described. Needless to say, the present invention is not limited to the contents of the above-described embodiments, and various modifications can be made without departing from the scope of the invention.
  • the present invention is not limited to the contents of the first to third embodiments, and various modifications are possible.
  • the above-described embodiments are illustrated in detail in order to easily understand the contents of the present invention, and are not necessarily limited to those having all the configurations described above.
  • a part of the configuration of an embodiment can be replaced with the configuration of another embodiment, and the configuration of another embodiment can be added to the configuration of an embodiment.
  • each of the above-described configurations, functions, processing units, processing means, and the like may be realized by hardware by designing a part or all of them with, for example, an integrated circuit.
  • Each of the above-described configurations, functions, and the like may be realized by software by having a processor interpret and execute a program that realizes each function.
  • Information such as programs, tables, and files that realize each function is stored in a recording device such as a memory, hard disk, SSD (Solid State Drive), or IC (integrated circuit) card, SD card, DVD (Digital Versatile Disc). Etc. can be placed on a recording medium.
  • the control lines and information lines indicate what is considered necessary for the explanation, and not all the control lines and information lines on the product are necessarily shown. Actually, it may be considered that almost all the components are connected to each other.
  • a power conversion device that drives an electric motor used in an air conditioner but also an electric power conversion device that drives an electric motor used in household appliances such as a refrigerator, a washing machine, and a vacuum cleaner, etc. are effectively used. can do.

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  • Power Engineering (AREA)
  • Control Of Ac Motors In General (AREA)
  • Control Of Motors That Do Not Use Commutators (AREA)
PCT/JP2012/067611 2011-09-21 2012-07-10 電力変換装置、電動機駆動装置および空調機 WO2013042437A1 (ja)

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JP6364573B1 (ja) * 2017-10-17 2018-07-25 日立ジョンソンコントロールズ空調株式会社 空気調和機
JP2019004617A (ja) * 2017-06-15 2019-01-10 三菱重工サーマルシステムズ株式会社 インバータ装置、空気調和機、インバータ装置の制御方法及びプログラム
JP2019004616A (ja) * 2017-06-15 2019-01-10 三菱重工サーマルシステムズ株式会社 インバータ装置、空気調和機、インバータ装置の制御方法及びプログラム
JPWO2018047274A1 (ja) * 2016-09-08 2019-03-14 三菱電機株式会社 モータ駆動装置、電動送風機、および電気掃除機
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CN105099285A (zh) * 2014-05-08 2015-11-25 株式会社大亨 电动机驱动装置及电动机驱动装置的控制方法
CN105099285B (zh) * 2014-05-08 2019-03-01 株式会社大亨 电动机驱动装置及电动机驱动装置的控制方法
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WO2016002745A1 (ja) * 2014-06-30 2016-01-07 マイクロスペース株式会社 モータ駆動制御装置
JP2016019448A (ja) * 2014-07-11 2016-02-01 株式会社東芝 モータ駆動装置及びモータ駆動方法
JPWO2018047274A1 (ja) * 2016-09-08 2019-03-14 三菱電機株式会社 モータ駆動装置、電動送風機、および電気掃除機
JP2019004617A (ja) * 2017-06-15 2019-01-10 三菱重工サーマルシステムズ株式会社 インバータ装置、空気調和機、インバータ装置の制御方法及びプログラム
JP2019004616A (ja) * 2017-06-15 2019-01-10 三菱重工サーマルシステムズ株式会社 インバータ装置、空気調和機、インバータ装置の制御方法及びプログラム
JP6364573B1 (ja) * 2017-10-17 2018-07-25 日立ジョンソンコントロールズ空調株式会社 空気調和機
WO2019077689A1 (ja) * 2017-10-17 2019-04-25 日立ジョンソンコントロールズ空調株式会社 空気調和機
US10608570B2 (en) 2017-10-18 2020-03-31 Hitachi-Johnson Controls Air Conditioning, Inc. Power converter and refrigeration air conditioner
EP3703248A4 (en) * 2017-10-18 2021-07-21 Hitachi-Johnson Controls Air Conditioning, Inc. CURRENT CONVERSION DEVICE AND REFRIGERATION AIR CONDITIONER
CN111756307A (zh) * 2019-03-28 2020-10-09 南京德朔实业有限公司 电动工具
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CN111835249B (zh) * 2019-03-28 2023-08-04 南京泉峰科技有限公司 电动工具

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