WO2013042437A1 - Electric power conversion device, motor drive device and air conditioner - Google Patents

Electric power conversion device, motor drive device and air conditioner Download PDF

Info

Publication number
WO2013042437A1
WO2013042437A1 PCT/JP2012/067611 JP2012067611W WO2013042437A1 WO 2013042437 A1 WO2013042437 A1 WO 2013042437A1 JP 2012067611 W JP2012067611 W JP 2012067611W WO 2013042437 A1 WO2013042437 A1 WO 2013042437A1
Authority
WO
WIPO (PCT)
Prior art keywords
pulse
phase
stop
power conversion
current
Prior art date
Application number
PCT/JP2012/067611
Other languages
French (fr)
Japanese (ja)
Inventor
渉 初瀬
能登原　保夫
田村　建司
奥山　敦
Original Assignee
日立アプライアンス株式会社
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by 日立アプライアンス株式会社 filed Critical 日立アプライアンス株式会社
Priority to JP2013534627A priority Critical patent/JP5718474B2/en
Priority to KR1020137034744A priority patent/KR20140018407A/en
Priority to CN201280036040.0A priority patent/CN103703669B/en
Publication of WO2013042437A1 publication Critical patent/WO2013042437A1/en

Links

Images

Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P27/00—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage
    • H02P27/04—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage
    • H02P27/06—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage using dc to ac converters or inverters
    • H02P27/08—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage using dc to ac converters or inverters with pulse width modulation
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P6/00—Arrangements for controlling synchronous motors or other dynamo-electric motors using electronic commutation dependent on the rotor position; Electronic commutators therefor
    • H02P6/14—Electronic commutators
    • H02P6/16—Circuit arrangements for detecting position
    • H02P6/18—Circuit arrangements for detecting position without separate position detecting elements
    • H02P6/185—Circuit arrangements for detecting position without separate position detecting elements using inductance sensing, e.g. pulse excitation

Definitions

  • the present invention relates to a control technology for a power converter using a PWM (Pulse Width Modulation) control method.
  • PWM Pulse Width Modulation
  • the energization angle at the time of 120 degrees energization is expanded to 150 degrees energization by a torque command, so that the current flowing through the motor is sinusoidal.
  • a 120-degree / 150-degree energization switching technique that reduces pulsation of torque close to a wave is disclosed. It is described that, by using this method, the motor can be driven with high performance at the time of starting the motor and from a heavy load to a light load with a rotational force with less noise and vibration (see Patent Document 2). .
  • the 120-degree energization method and the 150-degree energization method described in Patent Document 1 and Patent Document 2 have a narrower switching operation region in one cycle than the 180-degree energization method, and thus reduce the switching loss of the power conversion device. It is possible.
  • an induced voltage detection circuit is provided to acquire phase information of the induced voltage during the stop period of the switching operation. It is necessary to switch the phase for performing the switching operation based on the phase information.
  • the magnet position sensorless 120-degree energization method and 150-degree energization method must always provide a period for stopping the switching operation near the zero cross of the induced voltage of the motor. Therefore, it is difficult to extend the switching operation period to an electrical angle of 150 degrees or more. Further, the switching operation stop period must be performed in synchronization with the induced voltage phase. However, there is a difference between the induced voltage phase and the current phase of the electric motor depending on the load condition and driving condition. Therefore, even if the 150-degree energization method is used, the effect of reducing torque pulsation is not always obtained. Further, if it is attempted to prevent a deviation between the phase of the induced voltage and the current phase of the electric motor, the operation of energization at 150 degrees may be impossible.
  • the 120-degree energization method and the 150-degree energization method determine the energization section and the open phase section (section in which both the upper and lower arm switching elements of the inverter are stopped) based on the phase of the induced voltage.
  • the open phase section section in which both the upper and lower arm switching elements of the inverter are stopped
  • the zero cross point of the induced voltage may not be included in the open phase section.
  • position detection may not be performed accurately when vector control is performed based on the phase of the induced voltage without a magnet position sensor.
  • the switching loss can be reduced by stopping the switching operation in a predetermined section, vector control based on accurate position detection cannot be performed.
  • the current flowing through the motor can be controlled in a sine wave without using an induced voltage detection circuit or the like, but the switching operation is always performed during one cycle of voltage and current. Therefore, switching loss increases and the efficiency of the power conversion circuit decreases.
  • Patent Document 3 when performing vector control using a three-phase power converter that performs PWM control, only the phase whose current value is close to zero is paused to perform two-phase modulation. Is going. However, since there is no current rest period, the copper loss of the motor occurs. That is, even if the two-phase modulation method described in Patent Document 3 is used, the switching loss of PWM control cannot be reduced and the efficiency of the power converter cannot be improved.
  • This invention is made
  • a power converter is a power converter that performs power conversion by PWM control using a vector control method, and outputs a pulse signal for performing the PWM control.
  • a control unit a power conversion circuit that converts DC power into AC power using a pulse signal output from the pulse control unit, a current detection unit that detects a current of the power conversion circuit, and the current detection unit
  • a vector control unit that performs vector control based on the detected current and generates a command voltage to the pulse control unit, and the pulse signal in a section determined based on a current phase of the power conversion circuit is defined.
  • a pulse stop control unit for generating a pulse stop control signal for stopping over a certain section and outputting the pulse stop control signal to the pulse control unit. That.
  • a switching loss during PWM control can be reduced, and a high-efficiency power conversion device can be provided.
  • it is a wave form chart showing the relation of the alternating voltage which flows into an electric motor, an alternating current, and a pulse signal, (a) expresses a PWM carrier signal and an applied voltage command, (b) expresses a U phase alternating current, (C) represents a pulse signal.
  • the power conversion device includes a power conversion circuit (inverter) that converts DC power into AC power using a PWM control pulse signal, detects a current flowing through the power conversion circuit, and vectorizes the power conversion circuit. And a vector control unit for controlling. Further, an open phase section is provided in which the pulse signal in the section determined with reference to the zero cross point of the current phase flowing through the power conversion circuit is stopped, and the switch elements of the upper and lower arms of the same phase are stopped. As a result, the number of switching operations during PWM control can be reduced to reduce switching loss, and accurate position information of the magnet position of the motor can be obtained from the zero cross point of the current phase by providing an open phase section. Can do. As a result, it is possible to perform stable vector control and improve the efficiency of the power conversion circuit (inverter) and the electric motor.
  • FIG. 1 shows a circuit configuration of a PWM control power converter 1a according to the first embodiment.
  • the AC motor 3 that is a permanent magnet synchronous motor is driven by vector control by the power conversion circuit 4 that is constituted by a three-phase inverter driven by PWM control.
  • the control method when a phase pulse stop section (that is, an open phase section) is provided in the pulse signal of the power conversion circuit 4 will be described.
  • the power conversion device 1 a includes a power conversion circuit 4 including a three-phase inverter that converts DC power into AC power, and a motor current that flows through an AC motor (motor) 3 connected to the power conversion circuit 4. And a control device 5a that performs vector control using a pulse signal that performs PWM control based on phase current information (current) 6A detected by the phase current detection unit 6. Is done.
  • the power conversion circuit 4 includes a power conversion main circuit 41 including three-phase semiconductor switching elements Sup, Sun, Svp, Svn, Swp, and Swn in which IGBTs (Insulated Gate Bipolar Transistors) and diodes are antiparallel.
  • a gate driver 42 that generates a gate signal supplied to the IGBT of the power conversion main circuit 41 based on the pulse signal 7A from the pulse control unit 7.
  • the control device 5a also includes a pulse control unit 7 that supplies a pulse signal 7A controlled based on an applied voltage command (command voltage) V * to the gate driver 42, and a phase current detected by the phase current detection unit 6.
  • a vector control unit 8 that performs vector control using the information 6A and calculates the applied voltage command V * , and a phase pulse stop section near the current zero cross based on the current phase information (current phase) 8A calculated by the vector control (Open phase section) It is constituted by a pulse stop control unit 9 that outputs a phase pulse stop control signal (pulse stop control signal) 9A for stopping the pulse signal 7A of ⁇ to the pulse control unit 7.
  • the vector control unit 8 is, for example, Non-Patent Document 1 (Sakamoto et al., “Simple Vector Control of a Position Sensorless Permanent Magnet Synchronous Motor for Home Appliances”, D. Vol. 124, No. 11 (2004) pp. 1133-1140) and Non-Patent Document 2 (Tohari et al., "Study of New Vector Control Method for Permanent Magnet Synchronous Motor for High Speed", Electron Theory D, Vol. 129, No. 1 (2009), pp. 36-45) Inverter output current is detected, three-phase to two-phase conversion (dq conversion; direct-quadrature conversion) is performed and fed back to the control system, and then the inverter is driven by two-phase to three-phase conversion again. This can be realized by using general vector control, and the control method is not specified. Therefore, since the operation of the vector control unit 8 is a well-known technique, a detailed description thereof is omitted.
  • FIG. 2 is a waveform diagram showing the relationship between an AC voltage, an AC current, and a pulse signal flowing through the AC motor 3 in a comparative example, where the horizontal axis indicates the voltage phase, and the vertical axis indicates the levels of the voltage, current, and pulse signal.
  • FIG. 6 shows a circuit configuration of a power conversion device 1b of the PWM control method of the comparative example.
  • elements having the same reference numerals as those in FIG. 1 have the same functions.
  • the vector control performed by the vector control unit 8 is the same control method as in FIG.
  • the control device 5b shown in FIG. 6 generates a PWM pulse signal by comparing the PWM carrier signal and the applied voltage command V * as shown in FIG. Further, the command value of the applied voltage command V * is obtained by performing calculation by the vector control unit 8 based on the phase current information 6A detected by the phase current detection unit 6.
  • the acquisition of the phase current information 6A by the phase current detection unit 6 is performed by directly detecting the AC output current by CT (Current Transformer) as disclosed in FIG. 1 of JP-A-2004-48886, for example.
  • CT Current Transformer
  • the current information of the DC bus may be acquired by a shunt resistor, and the phase current may be reproduced based on this current information.
  • FIG. 2A shows the PWM carrier signal and the applied voltage command V *, and the U-phase applied voltage command Vu * is representatively shown.
  • ⁇ v represents a voltage phase based on the U phase.
  • the pulse control unit 7 performs the pulse shown in FIG. 2C based on the U-phase applied voltage command Vu * and the triangular wave carrier signal (PWM carrier signal).
  • PWM carrier signal the triangular wave carrier signal
  • the U-phase AC current Iu as shown in FIG. 2B flows in the AC motor 3 by the PWM conversion control performed by the power conversion main circuit 41 using this pulse signal (GPU + / GPU ⁇ pulse signal).
  • ⁇ represents the phase difference between voltage and current.
  • the vector control unit 8 controls the amplitude of the voltage and the phase difference ⁇ between the voltage and the current by performing vector control based on the phase current information 6A including the U-phase alternating current Iu.
  • the switching operation is always performed during one period of the voltage / current, and the current is supplied by 180 degrees. More switching times than current energization. Therefore, with 180 degree energization, the switching loss resulting from this increases.
  • FIG. 3 is a waveform diagram showing the relationship between the AC voltage, AC current and pulse signal flowing through the AC motor 3 and the phase pulse stop control signal in the first embodiment, with the horizontal axis representing the voltage phase and the vertical axis representing the voltage. , Current, pulse signal, and open phase control signal (phase pulse stop control signal) levels. That is, FIG. 3 is a waveform diagram of this embodiment shown in contrast to the waveform diagram of FIG.
  • the pulse stop control unit 9 uses the zero cross point ⁇ of the current phase controlled by the vector control as a reference, and the phase ⁇ and the phase ⁇ + ⁇ are as shown in the following formula (1).
  • the pulse signals GPU + and GPU ⁇ both output a phase pulse stop control signal (open phase control signal) 9A for stopping switching to the pulse controller 7.
  • the phase pulse stop control signal 9A outputs “0” when switching is stopped for both the pulse signals GPU + and GPU ⁇ , and “1” when switching in the PWM control method of the comparative example is performed without stopping switching.
  • Equation (1) when ⁇ is the phase difference between voltage and current and ⁇ is the phase pulse stop period (open phase period), the voltage phase ⁇ v with respect to the U phase is ⁇ / When 2 ⁇ v ⁇ + ⁇ / 2 and ⁇ + ⁇ / 2 ⁇ v ⁇ + ⁇ + ⁇ / 2, switching by the pulse signals GPU + and GPU ⁇ is stopped. In other cases, switching is performed using pulse signals GPU + and GPU ⁇ .
  • both the pulse signals GPU + and GPU ⁇ are turned off in the phase pulse stop section ⁇ of the phase pulse stop control signal 9A. Therefore, as shown in FIG. 3C, the pulse controller 7 outputs a signal train of pulse signals paused in the phase pulse stop period ⁇ .
  • the phase pulse stop section (open phase section) ⁇ is set twice during one period of voltage and current.
  • the sinusoidal PWM control method not only the sinusoidal PWM control method but also the two-phase modulation type PWM control method and the third harmonic addition type PWM control method are the target PWM control modulation methods. It is possible to provide a pulse stop interval ⁇ .
  • the pulse signals GPU + and GPU ⁇ provided with the period for stopping the switching operation by the pulse stop control unit 9 according to the first embodiment are applied to the applied voltage phase and the AC motor 3 in the switching stop period and the switching operation period.
  • the shape is not provided based on the induced voltage phase. That is, the switching stop period and the switching operation period of the pulse signals GPU + and GPU ⁇ are set with reference to the zero cross point of the current phase.
  • the pulse signal sequence since the pulse signal is based on the voltage phase of the induced voltage, as shown in FIG. 2 (c), the pulse signal sequence has symmetrical ON / OFF duty before and after the zero cross point of the voltage. It becomes the shape to become.
  • the phase pulse stop section ⁇ is provided based on the current phase (that is, not a pulse signal based on the voltage phase), as shown in FIG.
  • the ON / OFF duty of the pulse signal train is not symmetrical before and after the voltage zero-cross point. That is, in the first embodiment, the ON / OFF duty of the pulse signal train is asymmetric before and after the current zero-cross point.
  • the phase pulse stop section ⁇ is provided in the section including the zero cross point of the current, as shown in FIG. 3C, before and after the phase pulse stop section ⁇ as the center.
  • the pulse signal trains A and B have an asymmetric shape. From this, when the phase pulse stop section ⁇ is provided in the section including the zero cross point of the current as in the first embodiment, it is observed whether the pulse signals before and after the phase pulse stop section ⁇ are asymmetric. Thus, it can be easily determined whether or not the first embodiment is applied.
  • FIG. 4 is a waveform diagram showing the relationship between the U-phase voltage, the U-phase current, and the pulse signal when the real machine including the power conversion device 1a according to the first embodiment is driven.
  • Fig. 4 shows voltage, current, and pulse signal levels. That is, FIG. 4 is a method in which a phase pulse stop period is provided in the vicinity including the zero cross point of the current according to the first embodiment, and the actual machine is driven by setting the phase pulse stop period in the two-phase modulation type PWM control method. Shows the voltage, current and pulse signal.
  • FIG. 4A shows the U-phase terminal voltage Vun of the power conversion main circuit 41
  • FIG. 4B shows the U-phase current Iu flowing through the AC motor 3
  • FIG. 4C shows the pulse signals GPU + and GPU ⁇ . .
  • the switching signals of the pulse signals GPU + and GPU ⁇ are both turned off in the section (indicated by ⁇ ) sandwiched by the alternate long and short dash line, and the phase pulse stop section ⁇ is set. I can confirm that. Further, since the phase pulse stop section ⁇ is set, it can be confirmed that the U-phase current Iu becomes zero in the section sandwiched by the alternate long and short dash line.
  • FIG. 5 is a characteristic diagram showing a relationship between the power conversion circuit loss, the motor loss, and the total loss obtained by adding them to the phase pulse stop period (open phase period) ⁇ by the power conversion device 1a of the first embodiment.
  • the horizontal axis represents the phase pulse stop interval (open phase interval) ⁇
  • the vertical axis represents the loss. That is, FIG. 5 shows the characteristics of the total pulse loss including the phase pulse stop interval ⁇ set by the pulse stop control unit 9 and the loss of the power conversion circuit 4, the loss of the AC motor 3, and these two losses.
  • the loss (power conversion circuit loss) of the power conversion circuit 4 of the first embodiment is caused by the fact that the number of switching times decreases as the phase pulse stop interval ⁇ increases. To reduce. Further, the loss of the AC motor 3 (motor loss) increases due to the increase in the harmonic component of the current by providing the phase pulse stop section ⁇ . Furthermore, since the increase of the harmonic component of the current becomes significant due to the increase of the phase pulse stop section ⁇ , the increase in loss (motor loss) of the AC motor 3 due to this increases. For this reason, as shown in FIG. 5, there is a phase pulse stop section ⁇ opt in which the total loss obtained by adding these two losses (power conversion circuit loss and motor loss) is minimum, and the phase pulse stop section ⁇ is represented by this phase pulse. By setting the stop section ⁇ opt, it is possible to reduce the loss of the entire power conversion device 1a.
  • the pulse stop control unit 9 it is possible to reduce the number of switching of the pulse signal for performing the PWM control with the configuration of the power conversion circuit 4 similar to the PWM control method of the comparative example. Become. In other words, when the pulse stop control unit 9 that is controlled by the microcomputer is configured by software, the configuration of the power conversion circuit 4 of the comparative example is not changed, and the power converter 1a is not added without adding new hardware. High efficiency can be achieved. Moreover, since the switching operation is stopped near the zero cross of the current of the AC motor 3, an increase in torque pulsation can be suppressed compared to the 150-degree energization method.
  • FIG. 7 is a waveform diagram showing a relationship between an AC voltage, an AC current and a pulse signal flowing through the motor, and a phase pulse stop control signal in the power conversion device according to the modified example of the first embodiment, and the horizontal axis indicates the voltage.
  • the phase ⁇ v, and the vertical axis represents the levels of voltage, current, pulse signal, and open phase control signal.
  • control device 5a shown in FIG. 1 is realized by an integrated circuit such as a microcomputer, it is preferable to reduce the calculation load of the microcomputer. Therefore, as shown in FIG. 7D, if the pulse stop control unit 9 sets the phase pulse stop section ⁇ only once per current cycle, it is possible to reduce the calculation load of the microcomputer.
  • the pulse stop control unit 9 performed by the control of the microcomputer uses the zero cross point ⁇ of the current phase controlled by the vector control as a reference at the phase ⁇ + ⁇ (see FIG. 7D), As shown in the equation (2), the phase pulse stop control signal 9A for stopping both the switching signals of the pulse signals GPU + and GPU ⁇ during the phase pulse stop period ⁇ is output to the pulse controller 7.
  • phase pulse stop section ⁇ may be set only once per current cycle in the phase difference ⁇ between the voltage and current.
  • phase pulse stop section ⁇ By setting the phase pulse stop section ⁇ to be set once per current cycle, it is possible to halve the calculation load of the pulse stop control unit 9 by the microcomputer. Further, by measuring the phase difference ⁇ between the voltage and the current under the load condition to be driven in advance, and setting the phase difference ⁇ between the voltage and the current in the phase pulse stop control signal 9A of the pulse stop control unit 9 as a fixed value. This further reduces the computational load on the microcomputer.
  • the power conversion circuit 4 of the first embodiment performs PWM control by the switching operation using the pulse signal 7A output from the pulse control unit 7 and outputs AC power to the AC motor 3.
  • the vector control unit 8 outputs the phase information 8A of the current calculated based on the phase current information 6A from the phase current detection unit 6 to the pulse stop control unit 9.
  • the pulse stop control unit 9 outputs a phase pulse stop control signal 9A generated based on the current phase information 8A to the pulse control unit 7. Therefore, the pulse control unit 7 stops the pulse signal 7A in a predetermined section with reference to the zero cross of the current phase of a predetermined phase (for example, U phase) of the power conversion circuit 4. Therefore, the power conversion circuit 4 stops switching near the current zero crossing, so that the switching loss is reduced.
  • the efficiency of the power conversion device 1a can be improved and distortion of the output current can be reduced.
  • Second Embodiment switching between the PWM control method in which the phase pulse stop interval ⁇ is provided as in the first embodiment and the normal PWM control method in which the phase pulse stop interval ⁇ is not provided will be described. That is, in 2nd Embodiment, the power converter device which can switch phase pulse stop area (delta) with driving
  • running conditions for example, rotation speed of AC motor
  • FIG. 8 shows a circuit configuration of the PWM control type power converter 11 according to the second embodiment.
  • the power converter 11 instead of the phase current detection unit 6 of the power converting apparatus 1a of the first embodiment shown in FIG. 1, the DC bus current detector for detecting a DC bus current I DC ( A current detection unit) 10. That is, the power converter 11 of the second embodiment is configured such that the DC bus current detection unit 10 outputs DC bus current information (current) 10 ⁇ / b> A to the vector control unit 8.
  • the vector control unit 8 is configured to output current phase information 8 ⁇ / b> A calculated by vector control and rotation speed information 8 ⁇ / b> B that is the rotation speed of the AC motor 3 to the pulse stop control unit 91. .
  • the pulse stop control part 91 of 2nd Embodiment can switch the phase pulse stop area (delta) with an operating condition (namely, rotational speed of AC motor 3).
  • the other configuration contents are the same as those of the power conversion device 1a of the first embodiment shown in FIG.
  • FIG. 9 is a characteristic diagram showing a setting example of a phase pulse stop section (open phase section) in the power converter 11 of the second embodiment, where the horizontal axis represents the rotation speed and the vertical axis represents the open phase section ⁇ . . That is, in the power conversion device 11 of the second embodiment, the pulse stop control unit 91 determines the magnitude of the current rotation speed N of the AC motor 3 and a preset rotation speed N1 as shown in FIG. When the current rotational speed N is less than the rotational speed N1, the phase pulse stop control signal 91A in which the phase pulse stop section ⁇ is set is output to the pulse controller 7. When the current rotational speed N is equal to or higher than the rotational speed N1, the phase pulse stop section ⁇ is set to 0, and a phase pulse stop control signal 91A that does not set the phase pulse stop section ⁇ is output to the pulse controller 7.
  • the pulse control unit 7 when the current rotational speed N of the AC motor 3 is less than the rotational speed N1, the pulse control unit 7 outputs a pulse signal having a phase pulse stop section ⁇ , and when the rotational speed is equal to or higher than the rotational speed N1, the pulse control unit. 7 outputs a pulse signal without a phase pulse stop section ⁇ .
  • the phase pulse stop section ⁇ is set to the rotational speed as shown in FIG.
  • a method of changing from N2 to the rotational speed N3 at a constant change rate may be used.
  • the phase pulse is stopped at a non-linear change rate along a predetermined curve.
  • a method of changing the section ⁇ may be used.
  • phase A configuration may be employed in which the pulse stop interval ⁇ is switched.
  • the horizontal axis in the characteristic diagrams of FIGS. 9A, 9 ⁇ / b> B, and 9 ⁇ / b> C is read as the DC bus current average value I DCave instead of the rotational speed N.
  • phase pulse stop section ⁇ may be switched based on the torque ⁇ output from the AC motor 3 instead of switching the phase pulse stop section ⁇ based on the rotational speed of the AC motor 3.
  • the horizontal axis in the characteristic diagrams of FIGS. 9A, 9 ⁇ / b> B, and 9 ⁇ / b> C is read as output torque ⁇ instead of the rotational speed N.
  • the AC motor 3 When in the low-speed rotation range, setting the phase pulse stop interval ⁇ enables the power converter to be driven more efficiently than the PWM control method of the comparative example. Further, when the AC motor 3 is in the high speed rotation range, the phase pulse stop section ⁇ is set to 0, and it is possible to smoothly shift to 180-degree energization without setting the phase pulse stop section.
  • phase pulse stop area (delta) when changing to the direction which narrows phase pulse stop area (delta) according to the driving
  • the phase pulse stop section ⁇ when changing the phase pulse stop section ⁇ in the direction of widening according to the operating conditions of the AC motor 3, the phase is stopped immediately from the stop section zero state to the predetermined stop section. It can be performed by either changing at a change rate or changing at a non-linear change rate from a stop zone zero state to a predetermined stop zone.
  • FIG. 10 illustrates an overall configuration diagram of an air conditioner 100 according to the third embodiment.
  • the air conditioner 100 includes an outdoor unit 101 that exchanges heat with the outside air, an indoor unit 102 that exchanges heat with the indoor atmosphere, and the outdoor unit 101 and the indoor unit 102. And a pipe 103 to be connected.
  • the outdoor unit 101 includes a compressor 104 that compresses refrigerant, a compressor drive motor 105 that drives the compressor 104, an electric motor drive device 106 that drives and controls the compressor drive motor 105, and outside air and heat using the compressed refrigerant. It is comprised with the heat exchanger 107 which performs exchange.
  • the electric power drive device 106 uses the power conversion device 1a of the first embodiment or the power conversion device 11 of the second embodiment.
  • the indoor unit 102 includes a heat exchanger 108 that exchanges heat with the room and a blower 109 that blows air into the room.
  • FIG. 11 is a characteristic diagram showing the relationship of efficiency with respect to the rotational speed of the compressor drive motor 105 in the air conditioner 100 shown in FIG. 10, the horizontal axis shows the rotational speed of the compressor drive motor 105, and the vertical axis shows the compressor. The efficiency of the drive motor 105 is shown.
  • the power conversion device 1a of the first embodiment is applied to the air conditioner 100, and the pulse signal 7A in which the phase pulse stop section ⁇ is provided from the pulse control unit 7 to the pulse stop control unit 9 is provided. Is output to control the power conversion circuit 4.
  • the number of times of switching of the power conversion circuit 4 can be reduced by providing the phase pulse stop section ⁇ , the loss of the motor driving device 106 can be reduced as a result.
  • the pulse stop controller 9 in FIG. 1 outputs a pulse signal with the phase pulse stop interval ⁇ set to 0, and switches to the 180-degree energization PWM control method to weaken it. It is possible to drive the field control region.
  • the number of switching operations of the power conversion circuit 4 can be reduced with the configuration of the power conversion circuit 4 similar to that of the PWM control method of the comparative example.
  • the control unit 9 is configured by software, it is possible to realize high efficiency of the air conditioner 100 without adding hardware.
  • the power converters 1a, 11 according to the present invention, the motor drive device 106 using the power converters 1a, 11 and the air conditioner 100 using the motor drive device 106 have been specifically described. Needless to say, the present invention is not limited to the contents of the above-described embodiments, and various modifications can be made without departing from the scope of the invention.
  • the present invention is not limited to the contents of the first to third embodiments, and various modifications are possible.
  • the above-described embodiments are illustrated in detail in order to easily understand the contents of the present invention, and are not necessarily limited to those having all the configurations described above.
  • a part of the configuration of an embodiment can be replaced with the configuration of another embodiment, and the configuration of another embodiment can be added to the configuration of an embodiment.
  • each of the above-described configurations, functions, processing units, processing means, and the like may be realized by hardware by designing a part or all of them with, for example, an integrated circuit.
  • Each of the above-described configurations, functions, and the like may be realized by software by having a processor interpret and execute a program that realizes each function.
  • Information such as programs, tables, and files that realize each function is stored in a recording device such as a memory, hard disk, SSD (Solid State Drive), or IC (integrated circuit) card, SD card, DVD (Digital Versatile Disc). Etc. can be placed on a recording medium.
  • the control lines and information lines indicate what is considered necessary for the explanation, and not all the control lines and information lines on the product are necessarily shown. Actually, it may be considered that almost all the components are connected to each other.
  • a power conversion device that drives an electric motor used in an air conditioner but also an electric power conversion device that drives an electric motor used in household appliances such as a refrigerator, a washing machine, and a vacuum cleaner, etc. are effectively used. can do.

Landscapes

  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Control Of Ac Motors In General (AREA)
  • Control Of Motors That Do Not Use Commutators (AREA)

Abstract

An electric power conversion circuit (4) performs PWM control by switching operation using a pulse signal (7A) output from a pulse control unit (7) and outputs AC power to an AC motor (3). At this time, a vector control unit (8) outputs to a pulse stop control unit (9) the phase information (8A) of current calculated on the basis of phase current information (6A) from a phase current detection unit (6). The pulse stop control unit (9) outputs to the pulse control unit (7) a phase pulse stop control signal (9A) generated on the basis of the phase information (8A) of the current. Thereby, the pulse control unit (7) stops the pulse signal (7A) in a prescribed interval with the zero crossing of the current phase for a prescribed phase in the power conversion circuit (4) as the reference point.

Description

電力変換装置、電動機駆動装置および空調機Power conversion device, electric motor drive device, and air conditioner
　本発明は、ＰＷＭ（Pulse Width Modulation）制御方式を用いた電力変換装置の制御技術に関する。 The present invention relates to a control technology for a power converter using a PWM (Pulse Width Modulation) control method.
　空調機等に使用される電動機駆動装置は、部品点数の削減による小型化や高効率・高出力化への要求が強く、これらの要求を実現させるための技術が種々開発されている。このような電動機駆動装置に使用される電力変換装置、およびその負荷となる電動機を高効率に駆動させる手法の一つとして、電力変換装置から電動機へ流れる電流を正弦波状にＰＷＭ制御する１８０度通電方式と、誘起電圧の位相を基準として１２０度ごとにＰＷＭ制御してスイッチング動作を行う１２０度通電方式とを、電動機の負荷条件や駆動条件によって切り替える１８０度／１２０度通電切替方式の技術が開示されている。この方式を用いることにより、電動機の負荷条件や駆動条件に応じて高効率な駆動が可能になると共に、広範囲な回転速度において電動機の駆動を安定化できることが記載されている（特許文献１参照）。 Motor drive devices used in air conditioners and the like have strong demands for miniaturization, high efficiency, and high output by reducing the number of parts, and various technologies have been developed to realize these demands. As one of the methods for driving the electric power converter used in such an electric motor drive device and the electric motor serving as a load thereof with high efficiency, 180 degree energization is performed in which the current flowing from the electric power converter to the electric motor is PWM-controlled in a sine wave form. Disclosed is a 180 degree / 120 degree energization switching technique that switches between a method and a 120 degree energization method that performs a PWM control every 120 degrees with reference to the phase of the induced voltage depending on the load conditions and drive conditions of the motor. Has been. It is described that by using this method, high-efficiency driving can be performed according to the load condition and driving condition of the motor, and the driving of the motor can be stabilized over a wide range of rotation speeds (see Patent Document 1). .
　また、ＰＷＭ制御を行う電力変換装置の１２０度通電時における電動機の損失を低減させる手法として、１２０度通電時の通電角をトルク指令によって１５０度通電へ拡張させることにより、電動機に流れる電流を正弦波に近づけてトルクの脈動を低減させる１２０度／１５０度通電切替方式の技術が開示されている。この方式を用いることにより、電動機の起動時、および重負荷から軽負荷に至るまで、騒音や振動の少ない回転力で高性能に電動機の駆動を行えることが記載されている（特許文献２参照）。 Further, as a method of reducing the loss of the motor when the power conversion device that performs PWM control is energized at 120 degrees, the energization angle at the time of 120 degrees energization is expanded to 150 degrees energization by a torque command, so that the current flowing through the motor is sinusoidal. A 120-degree / 150-degree energization switching technique that reduces pulsation of torque close to a wave is disclosed. It is described that, by using this method, the motor can be driven with high performance at the time of starting the motor and from a heavy load to a light load with a rotational force with less noise and vibration (see Patent Document 2). .
　また、ＰＷＭ制御を行う三相の電力変換装置を用いて電動機を運転するときに、電力変換装置をベクトル制御する場合において、電流値がゼロに近くなった相のみスイッチングを行わないで２アーム変調（２相変調）を行う２相変調方式の技術も開示されている。この技術によれば、位置センサレスでベクトル制御を行う場合において、一定の電気角ごとのタイミングで２相変調を行うことにより、電動機の固定子電流がゼロクランプするゼロクランプ現象を回避することができる。その結果、全負荷範囲におけるベクトル制御において制御系の安定性を向上させることができる（特許文献３参照）。 In addition, when operating a motor using a three-phase power converter that performs PWM control, in the case of vector control of the power converter, two-arm modulation is performed without switching only the phase where the current value is close to zero. A technique of a two-phase modulation system that performs (two-phase modulation) is also disclosed. According to this technique, in the case of performing vector control without a position sensor, the zero clamp phenomenon in which the stator current of the motor is zero clamped can be avoided by performing the two-phase modulation at the timing of each constant electrical angle. . As a result, it is possible to improve the stability of the control system in vector control over the entire load range (see Patent Document 3).
特開２００８－１７２９４８号公報JP 2008-172948 A 特開２００３－１６９４９１号公報JP 2003-169491 A 特開平１１－１６４５９７号公報Japanese Patent Laid-Open No. 11-164597
　前記の特許文献１および特許文献２に記載された１２０度通電方式および１５０度通電方式は、１８０度通電方式に比べて１周期におけるスイッチング動作領域が狭いため、電力変換装置のスイッチング損失を低減させることが可能である。しかし、磁石位置センサを用いないで電動機の磁石位置を検出（つまり、位置検出）するためには、誘起電圧検出回路を設けて、スイッチング動作の停止期間に誘起電圧の位相情報を取得し、これらの位相情報に基づいてスイッチング動作を行う相を切り替える必要がある。 The 120-degree energization method and the 150-degree energization method described in Patent Document 1 and Patent Document 2 have a narrower switching operation region in one cycle than the 180-degree energization method, and thus reduce the switching loss of the power conversion device. It is possible. However, in order to detect the magnet position of the motor without using the magnet position sensor (that is, position detection), an induced voltage detection circuit is provided to acquire phase information of the induced voltage during the stop period of the switching operation. It is necessary to switch the phase for performing the switching operation based on the phase information.
　言い換えると、磁石位置センサレス方式の１２０度通電方式および１５０度通電方式は、必ず、電動機の誘起電圧のゼロクロス付近でスイッチング動作を停止する期間を設ける必要がある。よって、スイッチング動作期間を電気角１５０度以上に広げることは困難である。また、スイッチング動作の停止期間は誘起電圧位相に必ず同期して行う必要がある。ところが、負荷条件や駆動条件によっては誘起電圧位相と電動機の電流位相にズレが発生するため、１５０度通電方式を用いても、必ずしもトルク脈動の低減効果が得られるとは限らない。さらに、上記誘起電圧の位相と電動機の電流位相とのズレを防止しようとすると、１５０度通電の動作自体が不可能になることもあり得る。 In other words, the magnet position sensorless 120-degree energization method and 150-degree energization method must always provide a period for stopping the switching operation near the zero cross of the induced voltage of the motor. Therefore, it is difficult to extend the switching operation period to an electrical angle of 150 degrees or more. Further, the switching operation stop period must be performed in synchronization with the induced voltage phase. However, there is a difference between the induced voltage phase and the current phase of the electric motor depending on the load condition and driving condition. Therefore, even if the 150-degree energization method is used, the effect of reducing torque pulsation is not always obtained. Further, if it is attempted to prevent a deviation between the phase of the induced voltage and the current phase of the electric motor, the operation of energization at 150 degrees may be impossible.
　すなわち、１２０度通電方式や１５０度通電方式は、誘起電圧の位相を基準にして通電区間と開放相区間（インバータの同相の上下アームのスイッチ素子を両方とも停止させる区間）を決めているので、磁石位置センサレス方式において位置信号を取得するためには、開放相区間に誘起電圧のゼロクロス点を含ませる必要がある。ところが、負荷条件や駆動条件によっては誘起電圧の位相と電動機の電流位相にズレが発生するため、開放相区間に誘起電圧のゼロクロス点が含まれないこともある。その結果、磁石位置センサレスで誘起電圧の位相に基づいてベクトル制御を行う場合の位置検出が正確に行われないことがある。言い換えると、所定区間のスイッチング動作の停止によってスイッチング損失を低減させることはできても、正確な位置検出によるベクトル制御を行うことができない。 That is, the 120-degree energization method and the 150-degree energization method determine the energization section and the open phase section (section in which both the upper and lower arm switching elements of the inverter are stopped) based on the phase of the induced voltage. In order to acquire a position signal in the magnet position sensorless system, it is necessary to include the zero cross point of the induced voltage in the open phase section. However, since a phase difference between the induced voltage and the motor current phase occurs depending on the load condition and driving condition, the zero cross point of the induced voltage may not be included in the open phase section. As a result, position detection may not be performed accurately when vector control is performed based on the phase of the induced voltage without a magnet position sensor. In other words, although the switching loss can be reduced by stopping the switching operation in a predetermined section, vector control based on accurate position detection cannot be performed.
　このように、特許文献１および特許文献２の方式では、１２０度通電方式および１５０度通電方式の駆動時にスイッチングを停止させる区間を設けることで電力変換回路のスイッチング回数を低減させることは可能である。しかし、誘起電圧検出回路等を用いて誘起電圧の位相情報を取得し、この誘起電圧の位相情報に基づいてスイッチングを行う相の切替えを行っているので、電圧と電流の位相が異なる場合は正確な位置検出を行うことができない。その結果、電流歪が大きくなって電動機のトルク脈動が増加する虞がある。また、特許文献１による１８０度通電方式の駆動においては、誘起電圧検出回路等を用いないで電動機に流れる電流を正弦波状に制御することはできるが、電圧・電流一周期の間に常にスイッチング動作を行わなければならないので、スイッチング損失が増加して電力変換回路の効率が低下してしまう。 As described above, in the methods of Patent Document 1 and Patent Document 2, it is possible to reduce the number of times of switching of the power conversion circuit by providing a section in which switching is stopped when driving the 120-degree energization method and the 150-degree energization method. . However, the phase information of the induced voltage is obtained using an induced voltage detection circuit and the like, and the phase to be switched is switched based on the phase information of the induced voltage. Position detection cannot be performed. As a result, current distortion may increase and torque pulsation of the motor may increase. In addition, in the 180-degree energization drive according to Patent Document 1, the current flowing through the motor can be controlled in a sine wave without using an induced voltage detection circuit or the like, but the switching operation is always performed during one cycle of voltage and current. Therefore, switching loss increases and the efficiency of the power conversion circuit decreases.
　なお、特許文献３に開示された技術は、ＰＷＭ制御を行う三相の電力変換装置を用いてベクトル制御する場合に、電流値がゼロに近くなった相のみスイッチングを休止して２相変調を行っている。しかし、電流の休止期間が生じないために電動機の銅損が発生する。つまり、特許文献３に記載の２相変調方式を用いても、ＰＷＭ制御のスイッチング損失を低減させて電力変換装置の効率を向上させることはできない。 In the technique disclosed in Patent Document 3, when performing vector control using a three-phase power converter that performs PWM control, only the phase whose current value is close to zero is paused to perform two-phase modulation. Is going. However, since there is no current rest period, the copper loss of the motor occurs. That is, even if the two-phase modulation method described in Patent Document 3 is used, the switching loss of PWM control cannot be reduced and the efficiency of the power converter cannot be improved.
　本発明は、このような事情に鑑みてなされたものであり、ＰＷＭ制御時のスイッチング損失を低減させ、高効率な電力変換装置を提供することを課題とする。 This invention is made | formed in view of such a situation, and makes it a subject to reduce the switching loss at the time of PWM control, and to provide a highly efficient power converter device.
　前記課題を解決するために、本発明の電力変換装置は、ベクトル制御方式を用いて、ＰＷＭ制御によって電力変換を行う電力変換装置であって、前記ＰＷＭ制御を行うためのパルス信号を出力するパルス制御部と、前記パルス制御部から出力されたパルス信号を用いて、直流電力を交流電力に変換する電力変換回路と、前記電力変換回路の電流を検出する電流検出部と、前記電流検出部で検出された電流に基づいてベクトル制御を行い、前記パルス制御部への指令電圧を生成するベクトル制御部と、前記電力変換回路の電流位相を基準として定められた区間の前記パルス信号を前記定められた区間に亘って停止させるための、パルス停止制御信号を生成し、このパルス停止制御信号を前記パルス制御部へ出力するパルス停止制御部とを具備する。 In order to solve the above problems, a power converter according to the present invention is a power converter that performs power conversion by PWM control using a vector control method, and outputs a pulse signal for performing the PWM control. A control unit, a power conversion circuit that converts DC power into AC power using a pulse signal output from the pulse control unit, a current detection unit that detects a current of the power conversion circuit, and the current detection unit A vector control unit that performs vector control based on the detected current and generates a command voltage to the pulse control unit, and the pulse signal in a section determined based on a current phase of the power conversion circuit is defined. A pulse stop control unit for generating a pulse stop control signal for stopping over a certain section and outputting the pulse stop control signal to the pulse control unit. That.
　本発明によれば、ＰＷＭ制御時のスイッチング損失を低減させ、高効率電力変換装置を提供することができる。 According to the present invention, a switching loss during PWM control can be reduced, and a high-efficiency power conversion device can be provided.
第１実施形態に係るＰＷＭ制御方式の電力変換装置の回路構成を示すブロック図である。It is a block diagram which shows the circuit structure of the power converter device of the PWM control system which concerns on 1st Embodiment. 比較例における、電動機に流れる交流電圧、交流電流およびパルス信号の関係を示す波形図であり、（ａ）はＰＷＭキャリア信号と印加電圧指令とを表し、（ｂ）はＵ相交流電流を表し、（ｃ）はパルス信号を表す。In a comparative example, it is a wave form chart showing the relation of the alternating voltage which flows into an electric motor, an alternating current, and a pulse signal, (a) expresses a PWM carrier signal and an applied voltage command, (b) expresses a U phase alternating current, (C) represents a pulse signal. 第１実施形態における、電動機に流れる交流電圧、交流電流およびパルス信号と、相パルス停止制御信号との関係を示す波形図であり、（ａ）はＰＷＭキャリア信号と印加電圧指令とを表し、（ｂ）はＵ相交流電流を表し、（ｃ）はパルス信号を表し、（ｄ）は開放相制御信号を表す。It is a wave form diagram which shows the relationship between the alternating voltage which flows into an electric motor in 1st Embodiment, an alternating current, and a pulse signal, and a phase pulse stop control signal, (a) represents a PWM carrier signal and an applied voltage command, ( b) represents a U-phase alternating current, (c) represents a pulse signal, and (d) represents an open phase control signal. 第１実施形態の電力変換装置を備える実機を駆動した場合の、Ｕ相電圧、Ｕ相電流およびパルス信号の関係を示す波形図であり、（ａ）はＵ相端子電圧を表し、（ｂ）はＵ相電流を表し、（ｃ）はパルス信号を表す。It is a wave form chart showing the relation of U phase voltage, U phase current, and a pulse signal at the time of driving a real machine provided with a power converter of a 1st embodiment, (a) expresses U phase terminal voltage, (b) Represents a U-phase current, and (c) represents a pulse signal. 第１実施形態の電力変換装置による、相パルス停止区間（開放相区間）に対する電力変換回路損失、電動機損失およびそれらを足し合わせた総合損失の関係を示す特性図である。It is a characteristic view which shows the relationship of the power conversion circuit loss with respect to a phase pulse stop area (open phase area), the motor loss, and the total loss which added them with the power converter device of 1st Embodiment. 比較例のＰＷＭ制御方式の電力変換装置の回路構成を示すブロック図である。It is a block diagram which shows the circuit structure of the power converter device of the PWM control system of a comparative example. 第１実施形態に係る電力変換装置の変形例における、電動機に流れる交流電圧、交流電流およびパルス信号と、相パルス停止制御信号との関係を示す波形図であり、（ａ）はＰＷＭキャリア信号と印加電圧指令とを表し、（ｂ）はＵ相交流電流を表し、（ｃ）はパルス信号を表し、（ｄ）は開放相制御信号を表す。It is a wave form diagram which shows the relationship between the alternating voltage which flows into an electric motor, an alternating current, and a pulse signal, and a phase pulse stop control signal in the modification of the power converter device which concerns on 1st Embodiment, (a) is a PWM carrier signal and (B) represents a U-phase alternating current, (c) represents a pulse signal, and (d) represents an open phase control signal. 第２実施形態に係るＰＷＭ制御方式の電力変換装置の回路構成を示すブロック図である。It is a block diagram which shows the circuit structure of the power converter device of the PWM control system which concerns on 2nd Embodiment. 第２実施形態の電力変換装置における相パルス停止区間（開放相区間）の設定例を示す特性図であり、（ａ）は理想的に回転速度Ｎ１に設定された場合を表し、（ｂ）は回転速度Ｎ２から回転速度Ｎ３まで一定の変化率で変化させた場合を表し、（ｃ）は回転速度Ｎ２から回転速度Ｎ３まで所定の曲線で変化させた場合を表す。It is a characteristic view which shows the example of a setting of the phase pulse stop area (open phase area) in the power converter device of 2nd Embodiment, (a) represents the case where it sets to the rotational speed N1 ideally, (b) is A case where the rotation speed N2 is changed at a constant change rate from the rotation speed N3 is represented, and (c) represents a case where the rotation speed N2 is changed from the rotation speed N2 to the rotation speed N3 by a predetermined curve. 第３実施形態に係る、電力変換装置を用いた空調機の全体構成図である。It is a whole block diagram of the air conditioner using the power converter device which concerns on 3rd Embodiment. 図１０に示す空調機における圧縮機駆動電動機の回転速度に対する効率の関係を示す特性図である。It is a characteristic view which shows the relationship of the efficiency with respect to the rotational speed of the compressor drive motor in the air conditioner shown in FIG.
　次に、発明を実施するための形態（以降、「実施形態」と称す。）について、適宜図面を参照しながら詳細に説明する。 Next, modes for carrying out the invention (hereinafter referred to as “embodiments”) will be described in detail with reference to the drawings as appropriate.
《概要》
　本実施形態に係る電力変換装置は、ＰＷＭ制御のパルス信号を用いて直流電力を交流電力に変換する電力変換回路（インバータ）と、電力変換回路に流れる電流を検出してその電力変換回路をベクトル制御するベクトル制御部とを備えている。さらに、電力変換回路に流れる電流位相のゼロクロス点を基準として定められた区間のパルス信号を停止させて、同相の上下アームのスイッチ素子を停止させる開放相区間を設けている。これにより、ＰＷＭ制御時のスイッチング回数を低減させてスイッチング損失を低下させることができると共に、開放相区間を設けることで電流位相のゼロクロス点によって、電動機の磁石位置の正確な位置情報を取得することができる。その結果、安定したベクトル制御を行って、電力変換回路（インバータ）および電動機の効率を向上させることが可能となる。 "Overview"
The power conversion device according to the present embodiment includes a power conversion circuit (inverter) that converts DC power into AC power using a PWM control pulse signal, detects a current flowing through the power conversion circuit, and vectorizes the power conversion circuit. And a vector control unit for controlling. Further, an open phase section is provided in which the pulse signal in the section determined with reference to the zero cross point of the current phase flowing through the power conversion circuit is stopped, and the switch elements of the upper and lower arms of the same phase are stopped. As a result, the number of switching operations during PWM control can be reduced to reduce switching loss, and accurate position information of the magnet position of the motor can be obtained from the zero cross point of the current phase by providing an open phase section. Can do. As a result, it is possible to perform stable vector control and improve the efficiency of the power conversion circuit (inverter) and the electric motor.
　以下、本発明に係る電力変換装置の実施形態について図面を参照しながら詳細に説明する。なお、各実施形態を説明するための全図において、同一の構成要素は原則として同一の符号を付し、その繰り返しの説明は省略する。また、以下に述べる実施形態においては、理解を容易にするために、従来方式を用いた比較例と対比しながら本実施形態の内容について説明する。 Hereinafter, embodiments of a power conversion device according to the present invention will be described in detail with reference to the drawings. Note that components having the same function are denoted by the same reference symbols throughout the drawings for describing the embodiments, and the repetitive description thereof will be omitted. In the embodiment described below, the contents of this embodiment will be described in comparison with a comparative example using a conventional method in order to facilitate understanding.
《第１実施形態》
　図１は、第１実施形態に係るＰＷＭ制御方式の電力変換装置１ａの回路構成を示している。第１実施形態の電力変換装置１ａでは、図１に示すように、ＰＷＭ制御で駆動する三相インバータからなる電力変換回路４によって、永久磁石同期電動機である交流電動機３をベクトル制御で駆動する場合において、電力変換回路４のパルス信号に相パルス停止区間（すなわち、開放相区間）を設けたときの制御方法について説明する。 << First Embodiment >>
FIG. 1 shows a circuit configuration of a PWM control power converter 1a according to the first embodiment. In the power conversion device 1a of the first embodiment, as shown in FIG. 1, the AC motor 3 that is a permanent magnet synchronous motor is driven by vector control by the power conversion circuit 4 that is constituted by a three-phase inverter driven by PWM control. The control method when a phase pulse stop section (that is, an open phase section) is provided in the pulse signal of the power conversion circuit 4 will be described.
〈電力変換装置の回路構成〉
　図１に示すように、電力変換装置１ａは、直流電力を交流電力に変換する３相インバータからなる電力変換回路４と、電力変換回路４に接続された交流電動機（電動機）３に流れる電動機電流を検出する相電流検出部６と、相電流検出部６で検出された相電流情報（電流）６Ａに基づいてＰＷＭ制御を行うパルス信号を用いてベクトル制御を行う制御装置５ａとを備えて構成される。また、電力変換回路４は、ＩＧＢＴ（Insulated Gate Bipolar Transistor）とダイオードとが逆並列された三相構成の半導体スイッチング素子Ｓｕｐ、Ｓｕｎ、Ｓｖｐ、Ｓｖｎ、Ｓｗｐ、Ｓｗｎから構成された電力変換主回路４１と、パルス制御部７からのパルス信号７Ａに基づいて電力変換主回路４１のＩＧＢＴへ供給されるゲート信号を発生するゲート・ドライバ４２とを備えて構成される。 <Circuit configuration of power converter>
As shown in FIG. 1, the power conversion device 1 a includes a power conversion circuit 4 including a three-phase inverter that converts DC power into AC power, and a motor current that flows through an AC motor (motor) 3 connected to the power conversion circuit 4. And a control device 5a that performs vector control using a pulse signal that performs PWM control based on phase current information (current) 6A detected by the phase current detection unit 6. Is done. The power conversion circuit 4 includes a power conversion main circuit 41 including three-phase semiconductor switching elements Sup, Sun, Svp, Svn, Swp, and Swn in which IGBTs (Insulated Gate Bipolar Transistors) and diodes are antiparallel. And a gate driver 42 that generates a gate signal supplied to the IGBT of the power conversion main circuit 41 based on the pulse signal 7A from the pulse control unit 7.
　また、制御装置５ａは、印加電圧指令（指令電圧）Ｖ＊に基づいて制御されたパルス信号７Ａをゲート・ドライバ４２へ供給するパルス制御部７と、相電流検出部６で検出された相電流情報６Ａを用いてベクトル制御を行い、印加電圧指令Ｖ＊を算出するベクトル制御部８と、ベクトル制御により算出された電流の位相情報（電流位相）８Ａに基づいて電流ゼロクロス付近で相パルス停止区間（開放相区間）δのパルス信号７Ａを停止させる相パルス停止制御信号（パルス停止制御信号）９Ａをパルス制御部７へ出力するパルス停止制御部９と、によって構成される。 The control device 5a also includes a pulse control unit 7 that supplies a pulse signal 7A controlled based on an applied voltage command (command voltage) V * to the gate driver 42, and a phase current detected by the phase current detection unit 6. A vector control unit 8 that performs vector control using the information 6A and calculates the applied voltage command V * , and a phase pulse stop section near the current zero cross based on the current phase information (current phase) 8A calculated by the vector control (Open phase section) It is constituted by a pulse stop control unit 9 that outputs a phase pulse stop control signal (pulse stop control signal) 9A for stopping the pulse signal 7A of δ to the pulse control unit 7.
　ここで、ベクトル制御部８は、例えば、非特許文献１（坂本他、「家電機器向け位置センサレス永久磁石同期モータの簡易ベクトル制御」電学論Ｄ、Ｖｏｌ．１２４巻１１号（２００４年）ｐｐ．１１３３－１１４０）や非特許文献２（戸張他、「高速用永久磁石同期モータの新ベクトル制御方式の検討」電学論Ｄ、Ｖｏｌ．１２９巻１号（２００９年）ｐｐ．３６－４５）に記載されているように、インバータ出力電流を検出して３相－２相変換（ｄｑ変換；direct-quadrature変換）して制御系にフィードバックし、再び２相－３相変換してインバータを駆動する一般的なベクトル制御を用いることで実現可能であり、制御方式については特定するものではない。したがって、ベクトル制御部８の動作は周知の技術であるので詳細な説明は省略する。 Here, the vector control unit 8 is, for example, Non-Patent Document 1 (Sakamoto et al., “Simple Vector Control of a Position Sensorless Permanent Magnet Synchronous Motor for Home Appliances”, D. Vol. 124, No. 11 (2004) pp. 1133-1140) and Non-Patent Document 2 (Tohari et al., "Study of New Vector Control Method for Permanent Magnet Synchronous Motor for High Speed", Electron Theory D, Vol. 129, No. 1 (2009), pp. 36-45) Inverter output current is detected, three-phase to two-phase conversion (dq conversion; direct-quadrature conversion) is performed and fed back to the control system, and then the inverter is driven by two-phase to three-phase conversion again. This can be realized by using general vector control, and the control method is not specified. Therefore, since the operation of the vector control unit 8 is a well-known technique, a detailed description thereof is omitted.
〈比較例〉
　ここで、第１実施形態の電力変換装置１ａにおけるＰＷＭ制御時のスイッチング動作を明確化するため、従来方式を用いた比較例の電力変換装置１ｂ（図６参照）におけるＰＷＭ制御について、図２および図６を用いて説明する。図２は、比較例における、交流電動機３に流れる交流電圧、交流電流およびパルス信号の関係を示す波形図であり、横軸に電圧位相、縦軸に電圧、電流およびパルス信号の各レベルを示している。また、図６は、比較例のＰＷＭ制御方式の電力変換装置１ｂの回路構成を示している。なお、図６において、図１と同じ符号の要素は同じ機能を有している。また、ベクトル制御部８が行うベクトル制御は図１の場合と同様の制御方法である。 <Comparative example>
Here, in order to clarify the switching operation at the time of PWM control in the power conversion device 1a of the first embodiment, the PWM control in the power conversion device 1b (see FIG. 6) of the comparative example using the conventional method is illustrated in FIG. This will be described with reference to FIG. FIG. 2 is a waveform diagram showing the relationship between an AC voltage, an AC current, and a pulse signal flowing through the AC motor 3 in a comparative example, where the horizontal axis indicates the voltage phase, and the vertical axis indicates the levels of the voltage, current, and pulse signal. ing. FIG. 6 shows a circuit configuration of a power conversion device 1b of the PWM control method of the comparative example. In FIG. 6, elements having the same reference numerals as those in FIG. 1 have the same functions. The vector control performed by the vector control unit 8 is the same control method as in FIG.
　図６に示す制御装置５ｂは、パルス制御部７において、図２（ａ）に示すように、ＰＷＭキャリア信号と印加電圧指令Ｖ＊とを比較してＰＷＭパルス信号を生成する。また、この印加電圧指令Ｖ＊の指令値は、相電流検出部６で検出された相電流情報６Ａを基にベクトル制御部８で演算を行って得られたものである。ここで、相電流検出部６による相電流情報６Ａの取得は、例えば、特開２００４－４８８８６号公報の図１に開示されているように、ＣＴ（Current Transformer）によって交流出力電流を直接検出しても良いし、同
公報の図１２に開示されているように、シャント抵抗によって直流母線の電流情報を取得し、この電流情報に基づいて相電流を再現させる方式でも良い。 As shown in FIG. 2A, the control device 5b shown in FIG. 6 generates a PWM pulse signal by comparing the PWM carrier signal and the applied voltage command V * as shown in FIG. Further, the command value of the applied voltage command V * is obtained by performing calculation by the vector control unit 8 based on the phase current information 6A detected by the phase current detection unit 6. Here, the acquisition of the phase current information 6A by the phase current detection unit 6 is performed by directly detecting the AC output current by CT (Current Transformer) as disclosed in FIG. 1 of JP-A-2004-48886, for example. Alternatively, as disclosed in FIG. 12 of the same publication, the current information of the DC bus may be acquired by a shunt resistor, and the phase current may be reproduced based on this current information.
　次に、図２を用いて、電力変換装置１ｂ（図６参照）から交流電動機３へ供給される交流電圧および交流電流とパルス信号との関係について詳細に説明する。図２（ａ）はＰＷＭキャリア信号と印加電圧指令Ｖ＊とを示しており、代表としてＵ相印加電圧指令Ｖｕ＊を示している。ここで、θｖはＵ相を基準とする電圧位相を示している。 Next, the relationship between the AC voltage and AC current supplied from the power converter 1b (see FIG. 6) to the AC motor 3 and the pulse signal will be described in detail with reference to FIG. FIG. 2A shows the PWM carrier signal and the applied voltage command V *, and the U-phase applied voltage command Vu * is representatively shown. Here, θv represents a voltage phase based on the U phase.
　ＰＷＭ制御方式では、パルス制御部７は、図２（ａ）に示す通り、Ｕ相印加電圧指令Ｖｕ＊と三角波キャリア信号（ＰＷＭキャリア信号）とを基にして、図２（ｃ）に示すパルス信号「ＧＰＵ＋：Ｕ相上側素子（Ｓup）のパルス信号」、「ＧＰＵ－：Ｕ相下側素子（Ｓun）のパルス信号」を生成し、このパルス信号を、電力変換主回路４１を駆動するためにゲート・ドライバ４２へ出力する。すなわち、ＧＰＵ＋のパルス信号とＧＰＵ－のパルス信号は正負（１，０）が逆の信号となっている。 In the PWM control method, as shown in FIG. 2A, the pulse control unit 7 performs the pulse shown in FIG. 2C based on the U-phase applied voltage command Vu * and the triangular wave carrier signal (PWM carrier signal). To generate the signals “GPU +: U-phase upper element (Sup) pulse signal” and “GPU−: U-phase lower element (Sun) pulse signal”, and drive the power conversion main circuit 41 with this pulse signal. To the gate driver 42. That is, the GPU + pulse signal and the GPU− pulse signal are signals with opposite positive and negative (1, 0).
　このパルス信号（ＧＰＵ＋／ＧＰＵ－のパルス信号）によって電力変換主回路４１がＰＷＭ制御を行うことにより、交流電動機３には図２（ｂ）に示すようなＵ相交流電流Ｉｕが流れる。ここで、φは電圧と電流の位相差を示している。 The U-phase AC current Iu as shown in FIG. 2B flows in the AC motor 3 by the PWM conversion control performed by the power conversion main circuit 41 using this pulse signal (GPU + / GPU− pulse signal). Here, φ represents the phase difference between voltage and current.
　また、ベクトル制御部８では、Ｕ相交流電流Ｉｕを含む相電流情報６Ａを基に、ベクトル制御を行うことで、電圧の振幅および電圧と電流の位相差φの制御を行っている。 Further, the vector control unit 8 controls the amplitude of the voltage and the phase difference φ between the voltage and the current by performing vector control based on the phase current information 6A including the U-phase alternating current Iu.
　図２に示す通り、比較例によるＰＷＭ制御では、電圧・電流の一周期の間は常にスイッチング動作を行って１８０度通電しており、スイッチング動作が停止する期間が存在する１２０度通電方式や１５０度通電方式よりスイッチング回数が多い。したがって、１８０度通電では、これに起因するスイッチング損失が多くなる。 As shown in FIG. 2, in the PWM control according to the comparative example, the switching operation is always performed during one period of the voltage / current, and the current is supplied by 180 degrees. More switching times than current energization. Therefore, with 180 degree energization, the switching loss resulting from this increases.
〈第１実施形態におけるパルス停止制御部の動作〉
　以下の説明においては、ＰＷＭ制御を行うパルス信号のスイッチング動作を一時停止させるパルス停止制御部９（図１参照）の動作について、図１と図３を用いて説明する。したがって、比較例で述べたＰＷＭ制御の基本的な動作については、重複を避けるために説明を省略する。 <Operation of Pulse Stop Control Unit in First Embodiment>
In the following description, the operation of the pulse stop control unit 9 (see FIG. 1) for temporarily stopping the switching operation of the pulse signal for performing the PWM control will be described with reference to FIGS. Therefore, the description of the basic operation of the PWM control described in the comparative example is omitted to avoid duplication.
　図３は、第１実施形態における、交流電動機３に流れる交流電圧、交流電流およびパルス信号と、相パルス停止制御信号との関係を示す波形図であり、横軸に電圧位相、縦軸に電圧、電流、パルス信号および開放相制御信号（相パルス停止制御信号）の各レベルを示している。すなわち、図３は、図２の波形図と対比して示した本実施形態の波形図である。 FIG. 3 is a waveform diagram showing the relationship between the AC voltage, AC current and pulse signal flowing through the AC motor 3 and the phase pulse stop control signal in the first embodiment, with the horizontal axis representing the voltage phase and the vertical axis representing the voltage. , Current, pulse signal, and open phase control signal (phase pulse stop control signal) levels. That is, FIG. 3 is a waveform diagram of this embodiment shown in contrast to the waveform diagram of FIG.
　パルス停止制御部９は、図３（ｄ）に示すように、ベクトル制御により制御された電流位相のゼロクロス点φを基準として、位相φと位相φ＋πにおいて、下記の式（１）に示すように、相パルス停止区間（開放相区間）δの間、パルス信号ＧＰＵ＋、ＧＰＵ－共にスイッチングを停止する相パルス停止制御信号（開放相制御信号）９Ａをパルス制御部７へ出力する。この相パルス停止制御信号９Ａは、パルス信号ＧＰＵ＋、ＧＰＵ－共にスイッチングを停止する場合は“０”、スイッチングを停止せず比較例のＰＷＭ制御方式のスイッチングを行う場合は“１”を出力する。 As shown in FIG. 3D, the pulse stop control unit 9 uses the zero cross point φ of the current phase controlled by the vector control as a reference, and the phase φ and the phase φ + π are as shown in the following formula (1). During the phase pulse stop period (open phase period) δ, the pulse signals GPU + and GPU− both output a phase pulse stop control signal (open phase control signal) 9A for stopping switching to the pulse controller 7. The phase pulse stop control signal 9A outputs “0” when switching is stopped for both the pulse signals GPU + and GPU−, and “1” when switching in the PWM control method of the comparative example is performed without stopping switching.
Figure JPOXMLDOC01-appb-M000001
Figure JPOXMLDOC01-appb-M000001
　すなわち、式（１）からわかるように、φを電圧と電流の位相差、δを相パルス停止区間（開放相区間）としたとき、Ｕ相を基準とする電圧位相θｖが、φ－δ/２＜θｖ＜φ＋δ/２のときおよびφ＋π－δ/２＜θｖ＜φ＋π＋δ/２のときは、パルス信号ＧＰＵ＋およびＧＰＵ－によるスイッチングを停止する。そして、それ以外のときはパルス信号ＧＰＵ＋およびＧＰＵ－によるスイッチングを行う。 That is, as can be seen from Equation (1), when φ is the phase difference between voltage and current and δ is the phase pulse stop period (open phase period), the voltage phase θv with respect to the U phase is φ−δ / When 2 <θv <φ + δ / 2 and φ + π−δ / 2 <θv <φ + π + δ / 2, switching by the pulse signals GPU + and GPU− is stopped. In other cases, switching is performed using pulse signals GPU + and GPU−.
　このため、パルス制御部７からの出力状態は、相パルス停止制御信号９Ａの相パルス停止区間δでは、パルス信号ＧＰＵ＋、ＧＰＵ－が共にオフとなる。したがって、パルス制御部７からは、図３（ｃ）に示すように、相パルス停止区間δで休止したパルス信号の信号列が出力される。言い換えると、電圧および電流の一周期の間に２回に亘って相パルス停止区間（開放相区間）δを設定することとなる。なお、第１実施形態の構成の場合、対象となるＰＷＭ制御の変調方式は正弦波ＰＷＭ制御方式のみではなく、二相変調型ＰＷＭ制御方式や三次調波加算型ＰＷＭ制御方式でも、同様の相パルス停止区間δを設けることが可能となる。 For this reason, both the pulse signals GPU + and GPU− are turned off in the phase pulse stop section δ of the phase pulse stop control signal 9A. Therefore, as shown in FIG. 3C, the pulse controller 7 outputs a signal train of pulse signals paused in the phase pulse stop period δ. In other words, the phase pulse stop section (open phase section) δ is set twice during one period of voltage and current. In the case of the configuration of the first embodiment, not only the sinusoidal PWM control method but also the two-phase modulation type PWM control method and the third harmonic addition type PWM control method are the target PWM control modulation methods. It is possible to provide a pulse stop interval δ.
　このように、第１実施形態のパルス停止制御部９によりスイッチング動作を停止する期間が設けられたパルス信号ＧＰＵ＋、ＧＰＵ－は、スイッチング停止区間とスイッチング動作区間では、印加電圧位相および交流電動機３の誘起電圧位相を基準として設けられていない形状となる。すなわち、パルス信号ＧＰＵ＋、ＧＰＵ－のスイッチング停止区間とスイッチング動作区間は、電流位相のゼロクロス点を基準として設定される。 As described above, the pulse signals GPU + and GPU− provided with the period for stopping the switching operation by the pulse stop control unit 9 according to the first embodiment are applied to the applied voltage phase and the AC motor 3 in the switching stop period and the switching operation period. The shape is not provided based on the induced voltage phase. That is, the switching stop period and the switching operation period of the pulse signals GPU + and GPU− are set with reference to the zero cross point of the current phase.
　言い換えると、比較例では、誘起電圧の電圧位相を基準にしたパルス信号であるため、図２（ｃ）に示すように、パルス信号列は、電圧のゼロクロス点の前後においてＯＮ／ＯＦＦデューティが対称となる形状になっている。ところが、第１実施形態では、電流位相を基準として相パルス停止区間δが設けられているため（つまり、電圧位相を基準にしたパルス信号ではないため）、図３(ｃ)に示すように、電圧のゼロクロス点の前後において、パルス信号列のＯＮ／ＯＦＦデューティは対称にはならない。すなわち、第１実施形態では、電流のゼロクロス点の前後において、パルス信号列のＯＮ／ＯＦＦデューティは非対称となっている。 In other words, in the comparative example, since the pulse signal is based on the voltage phase of the induced voltage, as shown in FIG. 2 (c), the pulse signal sequence has symmetrical ON / OFF duty before and after the zero cross point of the voltage. It becomes the shape to become. However, in the first embodiment, since the phase pulse stop section δ is provided based on the current phase (that is, not a pulse signal based on the voltage phase), as shown in FIG. The ON / OFF duty of the pulse signal train is not symmetrical before and after the voltage zero-cross point. That is, in the first embodiment, the ON / OFF duty of the pulse signal train is asymmetric before and after the current zero-cross point.
　このように、第１実施形態では、電流のゼロクロス点を含んだ区間に相パルス停止区間δを設けているので、図３(ｃ)に示すように、相パルス停止区間δを中心とした前後のパルス信号列ＡおよびＢが非対称な形状となる。このことから、第１実施形態のように電流のゼロクロス点を含んだ区間に相パルス停止区間δを設けた場合は、相パルス停止区間δの前後のパルス信号が非対称であるか否かを観測するにより、第１実施形態が適用されたか否かを容易に判別することができる。 Thus, in the first embodiment, since the phase pulse stop section δ is provided in the section including the zero cross point of the current, as shown in FIG. 3C, before and after the phase pulse stop section δ as the center. The pulse signal trains A and B have an asymmetric shape. From this, when the phase pulse stop section δ is provided in the section including the zero cross point of the current as in the first embodiment, it is observed whether the pulse signals before and after the phase pulse stop section δ are asymmetric. Thus, it can be easily determined whether or not the first embodiment is applied.
〈実機による駆動時の波形〉
　図４は、第１実施形態の電力変換装置１ａを備える実機を駆動した場合の、Ｕ相電圧、Ｕ相電流、およびパルス信号の関係を示す波形図であり、横軸に電圧位相、縦軸に電圧、電流、およびパルス信号の各レベルを示している。すなわち、図４は、第１実施形態による電流のゼロクロス点を含んだ近傍に相パルス停止区間を設けた手法で、二相変調型ＰＷＭ制御方式において相パルス停止区間を設定して実機を駆動した場合の電圧、電流およびパルス信号を示している。 <Waveforms when driving with actual machine>
FIG. 4 is a waveform diagram showing the relationship between the U-phase voltage, the U-phase current, and the pulse signal when the real machine including the power conversion device 1a according to the first embodiment is driven. Fig. 4 shows voltage, current, and pulse signal levels. That is, FIG. 4 is a method in which a phase pulse stop period is provided in the vicinity including the zero cross point of the current according to the first embodiment, and the actual machine is driven by setting the phase pulse stop period in the two-phase modulation type PWM control method. Shows the voltage, current and pulse signal.
　図４（ａ）は電力変換主回路４１のＵ相端子電圧Ｖｕｎ、同図（ｂ）は交流電動機３に流れるＵ相電流Ｉｕ、同図（ｃ）にパルス信号ＧＰＵ＋、ＧＰＵ－を示している。 4A shows the U-phase terminal voltage Vun of the power conversion main circuit 41, FIG. 4B shows the U-phase current Iu flowing through the AC motor 3, and FIG. 4C shows the pulse signals GPU + and GPU−. .
　図４（ｃ）に示すように、一点鎖線で挟まれた区間（δで表示）においてパルス信号ＧＰＵ＋、ＧＰＵ－のスイッチング信号が共にオフとなっており、相パルス停止区間δが設定されていることが確認できる。また、相パルス停止区間δが設定されているため、一点鎖線で挟まれた区間ではＵ相電流Ｉｕがゼロとなることも併せて確認することができる。 As shown in FIG. 4 (c), the switching signals of the pulse signals GPU + and GPU− are both turned off in the section (indicated by δ) sandwiched by the alternate long and short dash line, and the phase pulse stop section δ is set. I can confirm that. Further, since the phase pulse stop section δ is set, it can be confirmed that the U-phase current Iu becomes zero in the section sandwiched by the alternate long and short dash line.
〈第１実施形態の効果〉
　図５は、第１実施形態の電力変換装置１ａによる、相パルス停止区間（開放相区間）δに対する電力変換回路損失、電動機損失およびそれらを足し合わせた総合損失の関係を示す特性図であり、横軸に相パルス停止区間（開放相区間）δ、縦軸に損失を表わしている。すなわち、図５は、パルス停止制御部９で設定する相パルス停止区間δと電力変換回路４の損失、交流電動機３の損失およびこれらの二つの損失を合わせた総合損失の特性を示している。 <Effects of First Embodiment>
FIG. 5 is a characteristic diagram showing a relationship between the power conversion circuit loss, the motor loss, and the total loss obtained by adding them to the phase pulse stop period (open phase period) δ by the power conversion device 1a of the first embodiment. The horizontal axis represents the phase pulse stop interval (open phase interval) δ, and the vertical axis represents the loss. That is, FIG. 5 shows the characteristics of the total pulse loss including the phase pulse stop interval δ set by the pulse stop control unit 9 and the loss of the power conversion circuit 4, the loss of the AC motor 3, and these two losses.
　図５に示すように、第１実施形態の電力変換回路４の損失（電力変換回路損失）は、相パルス停止区間δを大きくしていくにしたがってスイッチング回数が低減するため、これに起因して低減する。また、交流電動機３の損失（電動機損失）は、相パルス停止区間δを設けることで電流の高調波成分が増加するため、これに起因して大きくなる。さらに、相パルス停止区間δが大きくなることにより、電流の高調波成分の増加が顕著となるため、これに起因する交流電動機３の損失（電動機損失）の増加も顕著となる。このため、図５に示すように、これら二つの損失（電力変換回路損失と電動機損失）を加算した総合損失が最少となる相パルス停止区間δｏｐｔが存在し、相パルス停止区間δをこの相パルス停止区間δｏｐｔに設定することで、電力変換装置１ａ全体の損失を低減させることが可能となる。 As shown in FIG. 5, the loss (power conversion circuit loss) of the power conversion circuit 4 of the first embodiment is caused by the fact that the number of switching times decreases as the phase pulse stop interval δ increases. To reduce. Further, the loss of the AC motor 3 (motor loss) increases due to the increase in the harmonic component of the current by providing the phase pulse stop section δ. Furthermore, since the increase of the harmonic component of the current becomes significant due to the increase of the phase pulse stop section δ, the increase in loss (motor loss) of the AC motor 3 due to this increases. For this reason, as shown in FIG. 5, there is a phase pulse stop section δopt in which the total loss obtained by adding these two losses (power conversion circuit loss and motor loss) is minimum, and the phase pulse stop section δ is represented by this phase pulse. By setting the stop section δopt, it is possible to reduce the loss of the entire power conversion device 1a.
　以上、説明したように、パルス停止制御部９を用いることで、比較例のＰＷＭ制御方式と同様の電力変換回路４の構成で、ＰＷＭ制御を行うパルス信号のスイッチング回数を低減させることが可能となる。言い換えると、マイコンの制御で行われるパルス停止制御部９をソフトウェアで構成した場合は、比較例の電力変換回路４の構成は変えずに、新規のハードウェアを追加することなく電力変換装置１ａの高効率化を達成することが可能となる。また、交流電動機３の電流のゼロクロス付近でスイッチング動作を停止させるため、１５０度通電方式に対してトルク脈動の増加を抑制することができる。 As described above, by using the pulse stop control unit 9, it is possible to reduce the number of switching of the pulse signal for performing the PWM control with the configuration of the power conversion circuit 4 similar to the PWM control method of the comparative example. Become. In other words, when the pulse stop control unit 9 that is controlled by the microcomputer is configured by software, the configuration of the power conversion circuit 4 of the comparative example is not changed, and the power converter 1a is not added without adding new hardware. High efficiency can be achieved. Moreover, since the switching operation is stopped near the zero cross of the current of the AC motor 3, an increase in torque pulsation can be suppressed compared to the 150-degree energization method.
〈第１実施形態の変形例〉
　ここで、第１実施形態の変形例として、相パルス停止区間δを１サイクル区間の片方のみとする場合と、相パルス停止区間の位相を固定の状態にする場合とについて説明する。図７は、第１実施形態の変形例に係る電力変換装置における、電動機に流れる交流電圧、交流電流およびパルス信号と、相パルス停止制御信号との関係を示す波形図であり、横軸に電圧位相θｖ、縦軸に電圧、電流、パルス信号および開放相制御信号の各レベルを表している。 <Modification of First Embodiment>
Here, as a modification of the first embodiment, a case where the phase pulse stop section δ is only one of the one cycle sections and a case where the phase of the phase pulse stop section is in a fixed state will be described. FIG. 7 is a waveform diagram showing a relationship between an AC voltage, an AC current and a pulse signal flowing through the motor, and a phase pulse stop control signal in the power conversion device according to the modified example of the first embodiment, and the horizontal axis indicates the voltage. The phase θv, and the vertical axis represents the levels of voltage, current, pulse signal, and open phase control signal.
　この変形例では、図１に示すパルス停止制御部９の相パルス停止区間δを電流一周期（１サイクル）に対して１回のみ設定する方式について述べる。なお、上述した第１実施形態の電力変換装置１ａと共通する内容については説明を省略する。 In this modification, a method of setting the phase pulse stop section δ of the pulse stop control unit 9 shown in FIG. 1 only once for one cycle of current (one cycle) will be described. In addition, description is abbreviate | omitted about the content which is common in the power converter device 1a of 1st Embodiment mentioned above.
　図１に示す制御装置５ａをマイコン等の集積回路で実現させる場合は、そのマイコンの演算負荷を低減させることが好適である。そこで、図７（ｄ）に示すように、パルス停止制御部９が、相パルス停止区間δを電流一周期につき１回のみ設定するようすれば、マイコンの演算負荷を低減させることができる。 When the control device 5a shown in FIG. 1 is realized by an integrated circuit such as a microcomputer, it is preferable to reduce the calculation load of the microcomputer. Therefore, as shown in FIG. 7D, if the pulse stop control unit 9 sets the phase pulse stop section δ only once per current cycle, it is possible to reduce the calculation load of the microcomputer.
　すなわち、この変形例では、マイコンの制御で行われるパルス停止制御部９が、ベクトル制御により制御された電流位相のゼロクロス点φを基準として、位相φ＋πにおいて（図７（ｄ）参照）、下記の式（２）に示すように、相パルス停止区間δの間パルス信号ＧＰＵ＋とＧＰＵ－のスイッチング信号を共に停止させる相パルス停止制御信号９Ａをパルス制御部７へ出力する。 That is, in this modified example, the pulse stop control unit 9 performed by the control of the microcomputer uses the zero cross point φ of the current phase controlled by the vector control as a reference at the phase φ + π (see FIG. 7D), As shown in the equation (2), the phase pulse stop control signal 9A for stopping both the switching signals of the pulse signals GPU + and GPU− during the phase pulse stop period δ is output to the pulse controller 7.
Figure JPOXMLDOC01-appb-M000002
Figure JPOXMLDOC01-appb-M000002
　すなわち、式（２）からわかるように、φを電圧と電流との位相差、δを相パルス停止区間（開放相区間）としたとき、Ｕ相を基準とする電圧位相θｖが、φ＋π－δ/２＜θｖ＜φ＋π＋δ/２のときのみ、１回だけパルス信号ＧＰＵ＋およびＧＰＵ－によるスイッチングを停止する。そして、それ以外のときはパルス信号ＧＰＵ＋およびＧＰＵ－によるスイッチングを行う。なお、電圧と電流との位相差φにおいて電流一周期につき１回のみ相パルス停止区間δを設定する構成としても良い。 That is, as can be seen from equation (2), when φ is the phase difference between voltage and current and δ is the phase pulse stop period (open phase period), the voltage phase θv with respect to the U phase is φ + π−δ Only when / 2 <θv <φ + π + δ / 2, switching by the pulse signals GPU + and GPU− is stopped only once. In other cases, switching is performed using pulse signals GPU + and GPU−. Note that the phase pulse stop section δ may be set only once per current cycle in the phase difference φ between the voltage and current.
　このように、相パルス停止区間δを電流一周期につき１回だけ設定する構成とすることで、マイコンによるパルス停止制御部９の演算負荷を半減することが可能となる。また、あらかじめ駆動する負荷条件における電圧と電流との位相差φを測定しておき、パルス停止制御部９の相パルス停止制御信号９Ａにおける電圧と電流との位相差φを固定値とすることで、マイコンの演算負荷のさらなる低減が可能となる。 Thus, by setting the phase pulse stop section δ to be set once per current cycle, it is possible to halve the calculation load of the pulse stop control unit 9 by the microcomputer. Further, by measuring the phase difference φ between the voltage and the current under the load condition to be driven in advance, and setting the phase difference φ between the voltage and the current in the phase pulse stop control signal 9A of the pulse stop control unit 9 as a fixed value. This further reduces the computational load on the microcomputer.
　以上説明したように、第１実施形態の電力変換回路４は、パルス制御部７から出力されたパルス信号７Ａによるスイッチング動作によってＰＷＭ制御を行い、交流電動機３へ交流電力を出力している。このとき、ベクトル制御部８が、相電流検出部６からの相電流情報６Ａに基づいて算出した電流の位相情報８Ａをパルス停止制御部９ヘ出力している。これによって、パルス停止制御部９は、電流の位相情報８Ａに基づいて生成した相パルス停止制御信号９Ａをパルス制御部７へ出力する。したがって、パルス制御部７は、電力変換回路４の所定の相（例えば、Ｕ相）の電流位相のゼロクロスを基準として所定の区間のパルス信号７Ａを停止する。よって、電力変換回路４は、電流のゼロクロス付近でスイッチングを停止するのでスイッチング損失が低減される。その結果、電力変換装置１ａの効率を向上させることができると共に、出力電流の歪を低減させることができる。 As described above, the power conversion circuit 4 of the first embodiment performs PWM control by the switching operation using the pulse signal 7A output from the pulse control unit 7 and outputs AC power to the AC motor 3. At this time, the vector control unit 8 outputs the phase information 8A of the current calculated based on the phase current information 6A from the phase current detection unit 6 to the pulse stop control unit 9. Accordingly, the pulse stop control unit 9 outputs a phase pulse stop control signal 9A generated based on the current phase information 8A to the pulse control unit 7. Therefore, the pulse control unit 7 stops the pulse signal 7A in a predetermined section with reference to the zero cross of the current phase of a predetermined phase (for example, U phase) of the power conversion circuit 4. Therefore, the power conversion circuit 4 stops switching near the current zero crossing, so that the switching loss is reduced. As a result, the efficiency of the power conversion device 1a can be improved and distortion of the output current can be reduced.
《第２実施形態》
　第２実施形態では、第１実施形態のように相パルス停止区間δを設けたＰＷＭ制御方式と、相パルス停止区間δを設けない通常のＰＷＭ制御方式との切替えについて説明する。すなわち、第２実施形態では、運転条件（例えば、交流電動機の回転速度）によって相パルス停止区間δを切り替えることができる電力変換装置について説明する。 << Second Embodiment >>
In the second embodiment, switching between the PWM control method in which the phase pulse stop interval δ is provided as in the first embodiment and the normal PWM control method in which the phase pulse stop interval δ is not provided will be described. That is, in 2nd Embodiment, the power converter device which can switch phase pulse stop area (delta) with driving | running conditions (for example, rotation speed of AC motor) is demonstrated.
　図８は、第２実施形態に係るＰＷＭ制御方式の電力変換装置１１の回路構成を表す。図８に示すように、電力変換装置１１は、図１に示す第１実施形態の電力変換装置１ａの相電流検出部６の代わりに、直流母線電流ＩＤＣを検出する直流母線電流検出部（電流検出部）１０を備えている。すなわち、第２実施形態の電力変換装置１１は、直流母線電流検出部１０がベクトル制御部８へ直流母線電流情報（電流）１０Ａを出力するように構成される。 FIG. 8 shows a circuit configuration of the PWM control type power converter 11 according to the second embodiment. As shown in FIG. 8, the power converter 11, instead of the phase current detection unit 6 of the power converting apparatus 1a of the first embodiment shown in FIG. 1, the DC bus current detector for detecting a DC bus current I DC ( A current detection unit) 10. That is, the power converter 11 of the second embodiment is configured such that the DC bus current detection unit 10 outputs DC bus current information (current) 10 </ b> A to the vector control unit 8.
　図８において、ベクトル制御部８は、ベクトル制御によって算出された電流の位相情報８Ａと、交流電動機３の回転速度である回転速度情報８Ｂとをパルス停止制御部９１へ出力するように構成される。これによって、第２実施形態のパルス停止制御部９１は、相パルス停止区間δを運転条件（つまり、交流電動機３の回転速度）によって切り替えることができる。その他の構成内容は、図１で示した第１実施形態の電力変換装置１ａと同じであるため、説明は省略する。 In FIG. 8, the vector control unit 8 is configured to output current phase information 8 </ b> A calculated by vector control and rotation speed information 8 </ b> B that is the rotation speed of the AC motor 3 to the pulse stop control unit 91. . Thereby, the pulse stop control part 91 of 2nd Embodiment can switch the phase pulse stop area (delta) with an operating condition (namely, rotational speed of AC motor 3). The other configuration contents are the same as those of the power conversion device 1a of the first embodiment shown in FIG.
　図９は、第２実施形態の電力変換装置１１における相パルス停止区間（開放相区間）の設定例を示す特性図であり、横軸に回転速度、縦軸に開放相区間δを表わしている。すなわち、第２実施形態の電力変換装置１１においては、パルス停止制御部９１は、図９（ａ）に示すように、交流電動機３の現在の回転速度Ｎとあらかじめ設定した回転速度Ｎ１との大小関係を判定し、現在の回転速度Ｎが回転速度Ｎ１未満の場合は、相パルス停止区間δを設定した相パルス停止制御信号９１Ａをパルス制御部７へ出力する。また、現在の回転速度Ｎが回転速度Ｎ１以上の場合は、相パルス停止区間δを０とし、相パルス停止区間δを設定しない相パルス停止制御信号９１Ａをパルス制御部７へ出力する。 FIG. 9 is a characteristic diagram showing a setting example of a phase pulse stop section (open phase section) in the power converter 11 of the second embodiment, where the horizontal axis represents the rotation speed and the vertical axis represents the open phase section δ. . That is, in the power conversion device 11 of the second embodiment, the pulse stop control unit 91 determines the magnitude of the current rotation speed N of the AC motor 3 and a preset rotation speed N1 as shown in FIG. When the current rotational speed N is less than the rotational speed N1, the phase pulse stop control signal 91A in which the phase pulse stop section δ is set is output to the pulse controller 7. When the current rotational speed N is equal to or higher than the rotational speed N1, the phase pulse stop section δ is set to 0, and a phase pulse stop control signal 91A that does not set the phase pulse stop section δ is output to the pulse controller 7.
　言い換えると、交流電動機３の現在の回転速度Ｎが回転速度Ｎ１未満の場合は、パルス制御部７は相パルス停止区間δのあるパルス信号を出力し、回転速度Ｎ１以上の場合は、パルス制御部７は相パルス停止区間δのないパルス信号を出力する。 In other words, when the current rotational speed N of the AC motor 3 is less than the rotational speed N1, the pulse control unit 7 outputs a pulse signal having a phase pulse stop section δ, and when the rotational speed is equal to or higher than the rotational speed N1, the pulse control unit. 7 outputs a pulse signal without a phase pulse stop section δ.
　なお、運転条件によって相パルス停止区間δを切り替えるときの交流電動機３の回転速度・トルクの過度的な変動を抑制するため、図９（ｂ）に示すように、相パルス停止区間δを回転速度Ｎ２から回転速度Ｎ３まで一定の変化率で変化させる方式としても良い。また、相パルス停止区間δの切り替えをさらにスムーズにするため、図９（ｃ）に示すように、回転速度Ｎ２から回転速度Ｎ３までは、所定の曲線に沿って非線形な変化率で相パルス停止区間δを変えるような方式としても良い。 In order to suppress excessive fluctuations in the rotational speed and torque of the AC motor 3 when switching the phase pulse stop section δ depending on the operating conditions, the phase pulse stop section δ is set to the rotational speed as shown in FIG. A method of changing from N2 to the rotational speed N3 at a constant change rate may be used. Further, in order to make the switching of the phase pulse stop section δ even smoother, as shown in FIG. 9C, from the rotational speed N2 to the rotational speed N3, the phase pulse is stopped at a non-linear change rate along a predetermined curve. A method of changing the section δ may be used.
　また、交流電動機３の回転速度に基づいて相パルス停止区間δを切り替えるのではなく、図８の直流母線電流検出部１０で検出される直流母線電流ＩＤＣの平均値ＩＤＣａｖｅに基づいて、相パルス停止区間δを切り替える構成としても良い。この場合は、図９（ａ）、（ｂ）、（ｃ）の特性図における横軸は、回転速度Ｎではなく、直流母線電流平均値ＩＤＣａｖｅに読み替える。 Further, instead of switching the phase pulse stop intervals δ based on the rotational speed of the AC motor 3, based on the average value I DCave the DC-bus current I DC detected by the DC bus current detection unit 10 in FIG. 8, a phase A configuration may be employed in which the pulse stop interval δ is switched. In this case, the horizontal axis in the characteristic diagrams of FIGS. 9A, 9 </ b> B, and 9 </ b> C is read as the DC bus current average value I DCave instead of the rotational speed N.
　また、交流電動機３の回転速度に基づいて相パルス停止区間δを切り替えるのではなく、交流電動機３が出力するトルクτに基づいて相パルス停止区間δを切り替える構成としても良い。この場合は、図９（ａ）、（ｂ）、（ｃ）の特性図における横軸は、回転速度Ｎではなく、出力トルクτに読み替える。 Further, the phase pulse stop section δ may be switched based on the torque τ output from the AC motor 3 instead of switching the phase pulse stop section δ based on the rotational speed of the AC motor 3. In this case, the horizontal axis in the characteristic diagrams of FIGS. 9A, 9 </ b> B, and 9 </ b> C is read as output torque τ instead of the rotational speed N.
　以上、説明したように、相パルス停止区間δを交流電動機３の運転条件（交流電動機３の回転速度Ｎ、出力トルクτまたは直流母線電流平均値ＩＤＣａｖｅ等）によって切り替えることにより、交流電動機３が低速回転域にある場合は、相パルス停止区間δを設定することで、比較例のＰＷＭ制御方式よりも電力変換装置を高効率に駆動することが可能となる。また、交流電動機３が高速回転域の場合は、相パルス停止区間δを０とし、相パルス停止区間を設定しない１８０度通電にスムーズに移行することが可能となる。 As described above, by switching the phase pulse stop section δ according to the operating conditions of the AC motor 3 (the rotational speed N of the AC motor 3, the output torque τ, the DC bus current average value I DCave, etc.), the AC motor 3 When in the low-speed rotation range, setting the phase pulse stop interval δ enables the power converter to be driven more efficiently than the PWM control method of the comparative example. Further, when the AC motor 3 is in the high speed rotation range, the phase pulse stop section δ is set to 0, and it is possible to smoothly shift to 180-degree energization without setting the phase pulse stop section.
　なお、交流電動機３の運転条件によって相パルス停止区間δを狭める方向へ変更させる場合は、所定の停止区間から停止区間ゼロの状態へ直ちに切り替える、所定の停止区間から停止区間ゼロの状態へ一定の変化率で変化させる、または、所定の停止区間から停止区間ゼロの状態へ非線形な変化率で変化させる、のいずれかによって行うことができる。 In addition, when changing to the direction which narrows phase pulse stop area (delta) according to the driving | running condition of AC motor 3, it switches from a predetermined stop area to the state of zero stop area immediately, and it is constant from the predetermined stop area to the state of zero stop area. It can be performed by changing at a rate of change or changing at a non-linear rate of change from a predetermined stop interval to a stop interval zero state.
　また、交流電動機３の運転条件によって相パルス停止区間δを広げる方向へ変更させる場合は、停止区間ゼロの状態から所定の停止区間へ直ちに切り替える、停止区間ゼロの状態から所定の停止区間へ一定の変化率で変化させる、停止区間ゼロの状態から所定の停止区間へ非線形な変化率で変化させる、のいずれかによって行うことができる。 In addition, when changing the phase pulse stop section δ in the direction of widening according to the operating conditions of the AC motor 3, the phase is stopped immediately from the stop section zero state to the predetermined stop section. It can be performed by either changing at a change rate or changing at a non-linear change rate from a stop zone zero state to a predetermined stop zone.
《第３実施形態》
　第３実施形態では、第１実施形態の電力変換装置１ａまたは第２実施形態の電力変換装置１１を空調機の圧縮機駆動に適用した場合について、説明する。
　図１０は、第３実施形態に係る空調機１００の全体構成図を表している。 << Third Embodiment >>
3rd Embodiment demonstrates the case where the power converter device 1a of 1st Embodiment or the power converter device 11 of 2nd Embodiment is applied to the compressor drive of an air conditioner.
FIG. 10 illustrates an overall configuration diagram of an air conditioner 100 according to the third embodiment.
　図１０に示すように、第３実施形態の空調機１００は、外気と熱交換を行う室外機１０１と、室内の雰囲気と熱交換を行う室内機１０２と、室外機１０１と室内機１０２とをつなぐ配管１０３とによって構成される。 As shown in FIG. 10, the air conditioner 100 according to the third embodiment includes an outdoor unit 101 that exchanges heat with the outside air, an indoor unit 102 that exchanges heat with the indoor atmosphere, and the outdoor unit 101 and the indoor unit 102. And a pipe 103 to be connected.
　室外機１０１は、冷媒を圧縮する圧縮機１０４と、圧縮機１０４を駆動する圧縮機駆動電動機１０５と、圧縮機駆動電動機１０５を駆動制御する電動機駆動装置１０６と、圧縮冷媒を用いて外気と熱交換を行う熱交換機１０７とによって構成される。ここで、電動機駆動装置１０６には、第１実施形態の電力変換装置１ａまたは第２実施形態の電力変換装置１１が用いられる。また、室内機１０２は、室内と熱交換を行う熱交換機１０８と、室内に送風する送風機１０９とによって構成される。 The outdoor unit 101 includes a compressor 104 that compresses refrigerant, a compressor drive motor 105 that drives the compressor 104, an electric motor drive device 106 that drives and controls the compressor drive motor 105, and outside air and heat using the compressed refrigerant. It is comprised with the heat exchanger 107 which performs exchange. Here, the electric power drive device 106 uses the power conversion device 1a of the first embodiment or the power conversion device 11 of the second embodiment. The indoor unit 102 includes a heat exchanger 108 that exchanges heat with the room and a blower 109 that blows air into the room.
　ここで、圧縮機駆動電動機１０５の効率について、図１１を用いて説明する。図１１は、図１０に示す空調機１００における圧縮機駆動電動機１０５の回転速度に対する効率の関係を示す特性図であり、横軸は圧縮機駆動電動機１０５の回転速度を示し、縦軸は圧縮機駆動電動機１０５の効率を表している。 Here, the efficiency of the compressor drive motor 105 will be described with reference to FIG. FIG. 11 is a characteristic diagram showing the relationship of efficiency with respect to the rotational speed of the compressor drive motor 105 in the air conditioner 100 shown in FIG. 10, the horizontal axis shows the rotational speed of the compressor drive motor 105, and the vertical axis shows the compressor. The efficiency of the drive motor 105 is shown.
　電動機駆動装置１０６にＰＷＭ制御を適用するとき、圧縮機駆動電動機１０５の回転速度がＮ４以上の場合は、電力変換回路４の正弦波変調方式で出力可能な電圧を上回る電圧飽和領域では、弱め界磁制御により無効電流を流すことによって界磁コイルの電流を減らすことで、圧縮機駆動電動機１０５の高速回転域における安定駆動を実現することができる。ところが、このような弱め界磁制御を行うため、図１１の実線に示すように、圧縮機駆動電動機１０５の高速回転域（回転速度Ｎ４以上）においては効率の低下が発生する。 When applying PWM control to the motor drive device 106, if the rotational speed of the compressor drive motor 105 is N4 or higher, field weakening control is performed in a voltage saturation region exceeding the voltage that can be output by the sine wave modulation method of the power conversion circuit 4. By reducing the current of the field coil by causing the reactive current to flow, stable driving in the high speed rotation region of the compressor drive motor 105 can be realized. However, since such field weakening control is performed, the efficiency is reduced in the high speed rotation region (rotation speed N4 or more) of the compressor drive motor 105 as shown by the solid line in FIG.
　そこで、第３実施形態では、例えば、第１実施形態の電力変換装置１ａを空調機１００に適用し、パルス制御部７からパルス停止制御部９により相パルス停止区間δが設けられたパルス信号７Ａを出力することにより電力変換回路４を制御する。言い換えると、相パルス停止区間δを設けたことによって、電力変換回路４のスイッチング回数を低減させることができるので、結果的に電動機駆動装置１０６の損失を低減させることができる。 Therefore, in the third embodiment, for example, the power conversion device 1a of the first embodiment is applied to the air conditioner 100, and the pulse signal 7A in which the phase pulse stop section δ is provided from the pulse control unit 7 to the pulse stop control unit 9 is provided. Is output to control the power conversion circuit 4. In other words, since the number of times of switching of the power conversion circuit 4 can be reduced by providing the phase pulse stop section δ, the loss of the motor driving device 106 can be reduced as a result.
　このようにして、電力変換回路４のスイッチング損失を低減させることで、図１１の一点鎖線の特性に示すように、圧縮機駆動電動機１０５を駆動させる電動機駆動装置１０６の効率がピークとなる回転速度Ｎ４より低速回転の領域において、効率の向上を図ることが可能となる。また、回転速度Ｎ４以上の電圧飽和領域においては、図１のパルス停止制御部９により相パルス停止区間δを０としたパルス信号を出力して、１８０度通電のＰＷＭ制御方式へ切り替えて、弱め界磁制御領域の駆動を行うことが可能である。 In this way, by reducing the switching loss of the power conversion circuit 4, the rotational speed at which the efficiency of the motor driving device 106 for driving the compressor driving motor 105 reaches its peak as shown by the one-dot chain line characteristic in FIG. It is possible to improve the efficiency in a region where the rotation speed is lower than N4. In the voltage saturation region where the rotational speed is N4 or higher, the pulse stop controller 9 in FIG. 1 outputs a pulse signal with the phase pulse stop interval δ set to 0, and switches to the 180-degree energization PWM control method to weaken it. It is possible to drive the field control region.
　以上説明したように、第３実施形態により、比較例のＰＷＭ制御方式と同様の電力変換回路４の構成で電力変換回路４のスイッチング回数を減らすことができるため、マイコンの制御で行われるパルス停止制御部９をソフトウェアにより構成した場合は、ハードウェアの追加を行うことなく、空調機１００の高効率化を実現することが可能となる。 As described above, according to the third embodiment, the number of switching operations of the power conversion circuit 4 can be reduced with the configuration of the power conversion circuit 4 similar to that of the PWM control method of the comparative example. When the control unit 9 is configured by software, it is possible to realize high efficiency of the air conditioner 100 without adding hardware.
　なお、本発明に係る電力変換装置１ａ，１１およびこの電力変換装置１ａ，１１を用いた電動機駆動装置１０６、並びにこの電動機駆動装置１０６を用いた空調機１００の実施形態について具体的に説明したが、本発明は前記した各実施形態の内容に限定されるものではなく、その要旨を逸脱しない範囲で種々の変更が可能であることは言うまでもない。 The power converters 1a, 11 according to the present invention, the motor drive device 106 using the power converters 1a, 11 and the air conditioner 100 using the motor drive device 106 have been specifically described. Needless to say, the present invention is not limited to the contents of the above-described embodiments, and various modifications can be made without departing from the scope of the invention.
　すなわち、本発明は、第１実施形態ないし第３実施形態の内容に限定されるものではなく、様々な変形が可能である。言い換えると、前記した各実施形態は、本発明の内容を分かりやすく説明するために詳細に例示したものであり、必ずしも前記で説明した全ての構成を備えるものに限定されるものではない。また、ある実施形態の構成の一部を他の実施形態の構成に置き換えることも可能であり、さらに、ある実施形態の構成に他の実施形態の構成を加えることも可能である。 That is, the present invention is not limited to the contents of the first to third embodiments, and various modifications are possible. In other words, the above-described embodiments are illustrated in detail in order to easily understand the contents of the present invention, and are not necessarily limited to those having all the configurations described above. Further, a part of the configuration of an embodiment can be replaced with the configuration of another embodiment, and the configuration of another embodiment can be added to the configuration of an embodiment.
　また、各実施形態の構成の一部について、他の実施形態の構成を追加、削除、置換をすることも可能である。さらに、前記の各構成、機能、処理部、処理手段等は、それらの一部または全部を、例えば集積回路で設計する等によりハードウェアで実現しても良い。また、上記の各構成、機能等は、プロセッサがそれぞれの機能を実現するプログラムを解釈して実行することにより、ソフトウェアで実現しても良い。なお、各機能を実現するプログラム、テーブル、ファイル等の情報は、メモリ、ハードディスク、ＳＳＤ(Solid State Drive)等の記録装置、または、ＩＣ（integrated circuit）カード、ＳＤカード、ＤＶＤ（Digital Versatile Disc）等の記録媒体に置くことができる。また、制御線や情報線は説明上必要と考えられるものを示しており、製品上必ずしも全ての制御線や情報線を示しているとは限らない。実際には殆ど全ての構成が相互に接続されていると考えても良い。 Moreover, it is also possible to add, delete, and replace the configuration of the other embodiments with respect to a part of the configuration of each embodiment. Furthermore, each of the above-described configurations, functions, processing units, processing means, and the like may be realized by hardware by designing a part or all of them with, for example, an integrated circuit. Each of the above-described configurations, functions, and the like may be realized by software by having a processor interpret and execute a program that realizes each function. Information such as programs, tables, and files that realize each function is stored in a recording device such as a memory, hard disk, SSD (Solid State Drive), or IC (integrated circuit) card, SD card, DVD (Digital Versatile Disc). Etc. can be placed on a recording medium. Further, the control lines and information lines indicate what is considered necessary for the explanation, and not all the control lines and information lines on the product are necessarily shown. Actually, it may be considered that almost all the components are connected to each other.
　本発明によれば、空調機に用いられる電動機を駆動する電力変換装置に限らず、冷蔵庫、洗濯機、電気掃除機等の家電機器に用いられる電動機を駆動する電力変換装置等にも有効に利用することができる。 According to the present invention, not only a power conversion device that drives an electric motor used in an air conditioner but also an electric power conversion device that drives an electric motor used in household appliances such as a refrigerator, a washing machine, and a vacuum cleaner, etc. are effectively used. can do.
　１ａ、１１　電力変換装置
　２　直流電源
　３　交流電動機（電動機）
　４　電力変換回路
　４１　電力変換主回路
　４２　ゲート・ドライバ
　５ａ　制御装置
　６　相電流検出部（電流検出部）
　７　パルス制御部
　８　ベクトル制御部
　９、９１　パルス停止制御部
　１０　直流母線電流検出部（電流検出部）
　６Ａ　相電流情報（電流）
　７Ａ　パルス信号
　８Ａ　位相情報（電流位相）
　８Ｂ　回転速度情報
　９Ａ、９１Ａ　相パルス停止制御信号（パルス停止制御信号）
　１０Ａ　直流母線電流情報（電流）
　Ｖ＊　印加電圧指令（指令電圧）
　δ　相パルス停止区間
　１００　空調機
　１０１　室外機
　１０２　室内機
　１０３　配管
　１０４　圧縮機
　１０５　圧縮機駆動電動機
　１０６　電動機駆動装置
　１０７、１０８　熱交換器
　１０９　送風機 1a, 11 Power converter 2 DC power source 3 AC motor (motor)
4 Power Conversion Circuit 41 Power Conversion Main Circuit 42 Gate Driver 5a Control Device 6 Phase Current Detection Unit (Current Detection Unit)
7 Pulse control unit 8 Vector control unit 9, 91 Pulse stop control unit 10 DC bus current detection unit (current detection unit)
6A Phase current information (current)
7A Pulse signal 8A Phase information (current phase)
8B Rotational speed information 9A, 91A Phase pulse stop control signal (pulse stop control signal)
10A DC bus current information (current)
V * Applied voltage command (command voltage)
δ phase pulse stop section 100 Air conditioner 101 Outdoor unit 102 Indoor unit 103 Piping 104 Compressor 105 Compressor drive motor 106 Motor drive unit 107, 108 Heat exchanger 109 Blower

Claims (13)

  1. 　ベクトル制御方式を用いて、ＰＷＭ制御によって電力変換を行う電力変換装置であって、
    　前記ＰＷＭ制御を行うためのパルス信号を出力するパルス制御部と、
    　前記パルス制御部から出力されたパルス信号を用いて、直流電力を交流電力に変換する電力変換回路と、
    　前記電力変換回路の電流を検出する電流検出部と、
    　前記電流検出部で検出された電流に基づいてベクトル制御を行い、前記パルス制御部への指令電圧を生成するベクトル制御部と、
    　前記電力変換回路の電流位相を基準として定められた区間の前記パルス信号を前記定められた区間に亘って停止させるための、パルス停止制御信号を生成し、このパルス停止制御信号を前記パルス制御部へ出力するパルス停止制御部と
    を具備することを特徴とする電力変換装置。     A power conversion device that performs power conversion by PWM control using a vector control method,
    A pulse control unit for outputting a pulse signal for performing the PWM control;
    Using the pulse signal output from the pulse control unit, a power conversion circuit that converts DC power into AC power;
    A current detection unit for detecting a current of the power conversion circuit;
    A vector control unit that performs vector control based on the current detected by the current detection unit and generates a command voltage to the pulse control unit;
    A pulse stop control signal is generated for stopping the pulse signal in a section determined with reference to the current phase of the power conversion circuit over the predetermined section, and the pulse stop control signal is generated as the pulse control unit. And a pulse stop control unit for outputting to the power converter.
  2. 　前記パルス停止制御部は、
    　所定の相ごとに、前記定められた区間の前記パルス信号を前記定められた区間に亘って停止させるための、パルス停止制御信号を生成し、このパルス停止制御信号を前記パルス制御部へ出力する
    ことを特徴とする請求の範囲第１項に記載の電力変換装置。     The pulse stop control unit
    For each predetermined phase, a pulse stop control signal is generated to stop the pulse signal in the predetermined section over the predetermined section, and the pulse stop control signal is output to the pulse control unit. The power conversion device according to claim 1, wherein
  3. 　前記定められた区間の前記パルス信号は、前記電力変換回路に流れる電流のゼロクロス点を含む区間にあるパルス信号であることを特徴とする請求の範囲第２項に記載の電力変換装置。 3. The power conversion device according to claim 2, wherein the pulse signal in the predetermined section is a pulse signal in a section including a zero cross point of a current flowing in the power conversion circuit.
  4. 　前記パルス停止制御部は、
    　前記電力変換回路に流れる電流の１サイクル区間に１回または２回、前記パルス停止制御信号を生成することを特徴とするは請求の範囲第２項に記載の電力変換装置。     The pulse stop control unit
    The power conversion device according to claim 2, wherein the pulse stop control signal is generated once or twice in one cycle section of the current flowing through the power conversion circuit.
  5. 　前記パルス停止制御部は、
    　前記電力変換回路における、直流母線電流情報、交流出力電流情報、または交流出力周波数情報、の少なくとも１つの情報に基づいて、前記パルス信号の停止区間を所定の変化率で変化させることができる前記パルス停止制御信号を生成することを特徴とする請求の範囲第２項に記載の電力変換装置。     The pulse stop control unit
    The pulse capable of changing the stop period of the pulse signal at a predetermined rate of change based on at least one information of DC bus current information, AC output current information, or AC output frequency information in the power conversion circuit. The power converter according to claim 2, wherein a stop control signal is generated.
  6. 　前記パルス停止制御部は、
    　前記電力変換回路における、直流母線電流情報、交流出力電流情報、または交流出力周波数情報、の少なくとも１つの情報に基づいて、前記パルス信号の停止区間をゼロと所定の区間との間で切り替えることができる前記パルス停止制御信号を生成することを特徴とする請求の範囲第２項に記載の電力変換装置。     The pulse stop control unit
    Switching the stop section of the pulse signal between zero and a predetermined section based on at least one of DC bus current information, AC output current information, or AC output frequency information in the power conversion circuit. The power converter according to claim 2, wherein the pulse stop control signal that can be generated is generated.
  7. 　ベクトル制御方式を用いてＰＷＭ制御により電力変換を行う電力変換装置によって駆動する電動機駆動装置であって、
    　前記電力変換装置は、
    　前記ＰＷＭ制御を行うためのパルス信号を出力するパルス制御部と、
    　前記パルス制御部から出力されたパルス信号を用いて、直流電力を交流電力に変換する電力変換回路と、
    　前記電力変換回路の電流を検出する電流検出部と、
    　前記電流検出部で検出された電流に基づいてベクトル制御を行い、前記パルス制御部への指令電圧を生成するベクトル制御部と、
    　前記電力変換回路の電流位相を基準として定められた区間の前記パルス信号を前記定められた区間に亘って停止させるための、パルス停止制御信号を生成し、このパルス停止制御信号を前記パルス制御部へ出力するパルス停止制御部と
    を具備し、
    　前記電力変換回路から出力された交流電力によって電動機を駆動させることを特徴とする電動機駆動装置。     An electric motor drive device driven by a power conversion device that performs power conversion by PWM control using a vector control method,
    The power converter is
    A pulse control unit for outputting a pulse signal for performing the PWM control;
    Using the pulse signal output from the pulse control unit, a power conversion circuit that converts DC power into AC power;
    A current detection unit for detecting a current of the power conversion circuit;
    A vector control unit that performs vector control based on the current detected by the current detection unit and generates a command voltage to the pulse control unit;
    A pulse stop control signal is generated for stopping the pulse signal in a section determined with reference to the current phase of the power conversion circuit over the predetermined section, and the pulse stop control signal is generated as the pulse control unit. A pulse stop controller that outputs to
    An electric motor driving apparatus for driving an electric motor with AC power output from the power conversion circuit.
  8. 　前記パルス停止制御部は、
    　前記電動機の運転条件に応じて、所定の相ごとに、前記電力変換回路に流れる電流のゼロクロス点を含む区間にある前記パルス信号の停止区間を変更するための前記パルス停止制御信号を生成することを特徴とする請求の範囲第７項に記載の電動機駆動装置。     The pulse stop control unit
    Generating the pulse stop control signal for changing a stop section of the pulse signal in a section including a zero cross point of a current flowing through the power conversion circuit for each predetermined phase according to an operating condition of the motor. The electric motor drive device according to claim 7, wherein:
  9. 　前記電動機の運転条件は、該電動機の回転速度、該電動機の出力トルク、前記電力変換回路の直流母線電流、交流出力電流、または交流出力周波数、の少なくとも１つの動作状態であることを特徴とする請求の範囲第８項に記載の電動機駆動装置。 The operating condition of the electric motor is at least one operation state of a rotational speed of the electric motor, an output torque of the electric motor, a DC bus current, an AC output current, or an AC output frequency of the power conversion circuit. The electric motor drive device according to claim 8.
  10. 　前記パルス停止制御部は、
    　前記パルス信号の停止区間の変更を、
    　所定の停止区間から停止区間ゼロの状態へ直ちに切り替える、
    　所定の停止区間から停止区間ゼロの状態へ一定の変化率で変化させる、
    　所定の停止区間から停止区間ゼロの状態へ非線形な変化率で変化させる、
    のいずれかによって行うことを特徴とする請求の範囲第８項に記載の電動機駆動装置。     The pulse stop control unit
    Changing the stop period of the pulse signal,
    Immediately switch from a predetermined stop section to a stop section zero state,
    Change from a predetermined stop section to a stop section zero state at a constant rate of change,
    Change from a predetermined stop section to a stop section zero state at a non-linear change rate,
    The electric motor drive device according to claim 8, wherein the electric motor drive device is performed by any one of the following.
  11. 　前記パルス停止制御部は、
    　前記パルス信号の停止区間の変更を、
    　停止区間ゼロの状態から所定の停止区間へ直ちに切り替える、
    　停止区間ゼロの状態から所定の停止区間へ一定の変化率で変化させる、
    　停止区間ゼロの状態から所定の停止区間へ非線形な変化率で変化させる、
    のいずれかによって行うことを特徴とする請求の範囲第８項に記載の電動機駆動装置。     The pulse stop control unit
    Changing the stop period of the pulse signal,
    Immediately switch from the stop zone zero state to the predetermined stop zone,
    Change from a stop zone zero state to a predetermined stop zone at a constant rate of change,
    Change from a stop zone zero state to a predetermined stop zone at a non-linear rate of change,
    The electric motor drive device according to claim 8, wherein the electric motor drive device is performed by any one of the following.
  12. 　前記パルス信号の停止区間の前後においては、該パルス信号のパルス列は、ＯＮ／ＯＦＦデューティ波形が非対称であることを特徴とする請求の範囲第８項に記載の電動機駆動装置。 The electric motor drive device according to claim 8, wherein the pulse train of the pulse signal has an asymmetric ON / OFF duty waveform before and after the stop period of the pulse signal.
  13. 　請求の範囲第７項ないし請求の範囲第１２項のいずれか一項に記載の電動機駆動装置によって、外気と熱交換を行うための冷媒を圧縮する圧縮機を駆動する圧縮機駆動電動機を駆動制御することを特徴とする空調機。 Drive control of the compressor drive motor which drives the compressor which compresses the refrigerant | coolant for heat-exchanging with outside air by the electric motor drive device as described in any one of Claim 7 thru | or Claim 12 An air conditioner characterized by
PCT/JP2012/067611 2011-09-21 2012-07-10 Electric power conversion device, motor drive device and air conditioner WO2013042437A1 (en)

Priority Applications (3)

Application Number Priority Date Filing Date Title
JP2013534627A JP5718474B2 (en) 2011-09-21 2012-07-10 Power conversion device, electric motor drive device, and air conditioner
KR1020137034744A KR20140018407A (en) 2011-09-21 2012-07-10 Electric power conversion device, motor drive device and air conditioner
CN201280036040.0A CN103703669B (en) 2011-09-21 2012-07-10 Power-converting device, motor drive and air conditioner

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
JP2011-205421 2011-09-21
JP2011205421 2011-09-21

Publications (1)

Publication Number Publication Date
WO2013042437A1 true WO2013042437A1 (en) 2013-03-28

Family

ID=47914218

Family Applications (1)

Application Number Title Priority Date Filing Date
PCT/JP2012/067611 WO2013042437A1 (en) 2011-09-21 2012-07-10 Electric power conversion device, motor drive device and air conditioner

Country Status (4)

Country Link
JP (1) JP5718474B2 (en)
KR (1) KR20140018407A (en)
CN (1) CN103703669B (en)
WO (1) WO2013042437A1 (en)

Cited By (11)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JP2014166044A (en) * 2013-02-26 2014-09-08 Hitachi Appliances Inc Refrigerator
CN105099285A (en) * 2014-05-08 2015-11-25 株式会社大亨 Motor driving device and control method for same
WO2016002745A1 (en) * 2014-06-30 2016-01-07 マイクロスペース株式会社 Motor-driving control device
JP2016019448A (en) * 2014-07-11 2016-02-01 株式会社東芝 Motor driving device and motor driving method
JP6364573B1 (en) * 2017-10-17 2018-07-25 日立ジョンソンコントロールズ空調株式会社 Air conditioner
JP2019004617A (en) * 2017-06-15 2019-01-10 三菱重工サーマルシステムズ株式会社 Inverter device, air conditioner, control method for inverter device, and program
JP2019004616A (en) * 2017-06-15 2019-01-10 三菱重工サーマルシステムズ株式会社 Inverter device, air conditioner, control method for inverter device, and program
JPWO2018047274A1 (en) * 2016-09-08 2019-03-14 三菱電機株式会社 Motor drive device, electric blower, and vacuum cleaner
US10432115B2 (en) 2014-06-30 2019-10-01 Microspace Corporation Motor driving control apparatus
US10608570B2 (en) 2017-10-18 2020-03-31 Hitachi-Johnson Controls Air Conditioning, Inc. Power converter and refrigeration air conditioner
CN111756285A (en) * 2019-03-28 2020-10-09 南京德朔实业有限公司 Electric tool

Families Citing this family (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN105656370A (en) * 2016-03-09 2016-06-08 广东美的制冷设备有限公司 Air conditioner and shutdown control method and device for compressor of air conditioner
CN106067744A (en) * 2016-05-18 2016-11-02 陕西科技大学 A kind of novel intelligent motor controller
CN111869096B (en) * 2018-03-28 2023-12-22 新电元工业株式会社 Driving device, electric vehicle, and control method for driving device
JP7358059B2 (en) * 2019-03-22 2023-10-10 ミネベアミツミ株式会社 Motor drive control device

Citations (5)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JPH0746855A (en) * 1993-08-02 1995-02-14 Toyota Motor Corp Two phase pwm controller for inverter
JP2000188876A (en) * 1998-12-22 2000-07-04 Matsushita Electric Ind Co Ltd Converter
JP2001327172A (en) * 2000-05-15 2001-11-22 Matsushita Electric Ind Co Ltd Inverter controller and air conditioiner using the inverter controller
JP2003092888A (en) * 2001-09-20 2003-03-28 Denso Corp Power converter and driving control method for multi- phase load
JP2011067023A (en) * 2009-09-17 2011-03-31 Hitachi Appliances Inc Current detection method, inverter device and converter device utilizing current detection method, motor drive equipped with such device, and refrigeration and air-conditioning equipment

Family Cites Families (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JPH11164597A (en) * 1997-11-28 1999-06-18 Meidensha Corp Vector controller for induction motor

Patent Citations (5)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JPH0746855A (en) * 1993-08-02 1995-02-14 Toyota Motor Corp Two phase pwm controller for inverter
JP2000188876A (en) * 1998-12-22 2000-07-04 Matsushita Electric Ind Co Ltd Converter
JP2001327172A (en) * 2000-05-15 2001-11-22 Matsushita Electric Ind Co Ltd Inverter controller and air conditioiner using the inverter controller
JP2003092888A (en) * 2001-09-20 2003-03-28 Denso Corp Power converter and driving control method for multi- phase load
JP2011067023A (en) * 2009-09-17 2011-03-31 Hitachi Appliances Inc Current detection method, inverter device and converter device utilizing current detection method, motor drive equipped with such device, and refrigeration and air-conditioning equipment

Cited By (18)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JP2014166044A (en) * 2013-02-26 2014-09-08 Hitachi Appliances Inc Refrigerator
CN105099285A (en) * 2014-05-08 2015-11-25 株式会社大亨 Motor driving device and control method for same
CN105099285B (en) * 2014-05-08 2019-03-01 株式会社大亨 The control method of motor drive and motor drive
US10432115B2 (en) 2014-06-30 2019-10-01 Microspace Corporation Motor driving control apparatus
WO2016002745A1 (en) * 2014-06-30 2016-01-07 マイクロスペース株式会社 Motor-driving control device
JP2016019448A (en) * 2014-07-11 2016-02-01 株式会社東芝 Motor driving device and motor driving method
JPWO2018047274A1 (en) * 2016-09-08 2019-03-14 三菱電機株式会社 Motor drive device, electric blower, and vacuum cleaner
JP2019004617A (en) * 2017-06-15 2019-01-10 三菱重工サーマルシステムズ株式会社 Inverter device, air conditioner, control method for inverter device, and program
JP2019004616A (en) * 2017-06-15 2019-01-10 三菱重工サーマルシステムズ株式会社 Inverter device, air conditioner, control method for inverter device, and program
JP6364573B1 (en) * 2017-10-17 2018-07-25 日立ジョンソンコントロールズ空調株式会社 Air conditioner
WO2019077689A1 (en) * 2017-10-17 2019-04-25 日立ジョンソンコントロールズ空調株式会社 Air conditioner
US10608570B2 (en) 2017-10-18 2020-03-31 Hitachi-Johnson Controls Air Conditioning, Inc. Power converter and refrigeration air conditioner
EP3703248A4 (en) * 2017-10-18 2021-07-21 Hitachi-Johnson Controls Air Conditioning, Inc. Power conversion device and refrigeration air conditioner
CN111756285A (en) * 2019-03-28 2020-10-09 南京德朔实业有限公司 Electric tool
CN111756307A (en) * 2019-03-28 2020-10-09 南京德朔实业有限公司 Electric tool
CN111835248A (en) * 2019-03-28 2020-10-27 南京德朔实业有限公司 Electric tool
CN111835249A (en) * 2019-03-28 2020-10-27 南京德朔实业有限公司 Electric tool
CN111835249B (en) * 2019-03-28 2023-08-04 南京泉峰科技有限公司 Electric tool

Also Published As

Publication number Publication date
KR20140018407A (en) 2014-02-12
CN103703669B (en) 2017-08-08
CN103703669A (en) 2014-04-02
JPWO2013042437A1 (en) 2015-03-26
JP5718474B2 (en) 2015-05-13

Similar Documents

Publication Publication Date Title
JP5718474B2 (en) Power conversion device, electric motor drive device, and air conditioner
JP5675567B2 (en) Power conversion device, electric motor drive device, and air conditioner
US9998049B2 (en) Inverter control device and air conditioner
TWI664802B (en) Power conversion device and refrigerating and air-conditioning equipment
JP5047582B2 (en) Inverter device
JP2004101151A (en) Air-conditioner
JP6046446B2 (en) Vector control device, motor control device using the same, and air conditioner
JP5813934B2 (en) Power converter
JP6000801B2 (en) Motor control device and air conditioner using the same
JP6826928B2 (en) Inverter device, air conditioner, control method and program of inverter device
JP6847775B2 (en) Inverter device, air conditioner, control method and program of inverter device
JP6480859B2 (en) Heat pump device, air conditioner and refrigerator
JP6087167B2 (en) refrigerator
JP6591081B2 (en) Inverter device, compressor drive device and air conditioner
JP6364573B1 (en) Air conditioner
JPWO2020213045A1 (en) Inverter device, compressor drive device and air conditioner
JP2024047610A (en) Method for controlling inverter for driving motor
JP2011019352A (en) Power converter and air conditioner including the same

Legal Events

Date Code Title Description
121 Ep: the epo has been informed by wipo that ep was designated in this application

Ref document number: 12833013

Country of ref document: EP

Kind code of ref document: A1

ENP Entry into the national phase

Ref document number: 2013534627

Country of ref document: JP

Kind code of ref document: A

ENP Entry into the national phase

Ref document number: 20137034744

Country of ref document: KR

Kind code of ref document: A

NENP Non-entry into the national phase

Ref country code: DE

122 Ep: pct application non-entry in european phase

Ref document number: 12833013

Country of ref document: EP

Kind code of ref document: A1