WO2013014798A1 - Dispositif de commande de moteur - Google Patents

Dispositif de commande de moteur Download PDF

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Publication number
WO2013014798A1
WO2013014798A1 PCT/JP2011/067341 JP2011067341W WO2013014798A1 WO 2013014798 A1 WO2013014798 A1 WO 2013014798A1 JP 2011067341 W JP2011067341 W JP 2011067341W WO 2013014798 A1 WO2013014798 A1 WO 2013014798A1
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WO
WIPO (PCT)
Prior art keywords
loss
turn
switching
inverter
motor control
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PCT/JP2011/067341
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English (en)
Japanese (ja)
Inventor
雅哉 原川
今中　晶
Original Assignee
三菱電機株式会社
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Priority to JP2013525525A priority Critical patent/JP5546687B2/ja
Priority to PCT/JP2011/067341 priority patent/WO2013014798A1/fr
Publication of WO2013014798A1 publication Critical patent/WO2013014798A1/fr

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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P27/00—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage
    • H02P27/04—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage
    • H02P27/06—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage using dc to ac converters or inverters
    • H02P27/08—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage using dc to ac converters or inverters with pulse width modulation
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0048—Circuits or arrangements for reducing losses
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/32—Means for protecting converters other than automatic disconnection
    • H02M1/327—Means for protecting converters other than automatic disconnection against abnormal temperatures
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes

Definitions

  • the present invention relates to a motor control device and a switching element loss calculation method.
  • the switching element In a main circuit inverter using a switching element which is a semiconductor element, the switching element generates heat due to a loss in a semiconductor junction portion inside the element due to a flowing current and an applied voltage. This heat is conducted from the semiconductor junction to a cooling body such as a semiconductor case or fin, and is dissipated to the surrounding gas or cooling water.
  • a cooling body such as a semiconductor case or fin
  • Switching elements have an allowable maximum temperature, and exceeding this will cause deterioration and destruction of the switching elements.
  • the main circuit inverter is composed of many electrical components (for example, resistors, capacitors, reactors, etc.), generally the maximum allowable temperature of the switching element is lower than other electrical components. Therefore, in the main circuit inverter, thermal design is made with an emphasis on switching elements.
  • Patent Document 1 discloses a voltage detection unit for detecting a voltage at both ends of a filter capacitor inserted between a DC power supply and an inverter device, and a current flowing through a high-power semiconductor element.
  • An example is disclosed in which information detected by a temperature detection unit is used as a current detection unit to detect and a cooling means for cooling the high-power semiconductor element.
  • information on the voltage detection unit, the current detection unit, and the temperature detection unit is input to the junction temperature calculation unit, and the calculation result in the junction temperature calculation unit is compared with the allowable temperature. Controls the output power of the inverter device.
  • Patent Document 2 discloses a voltage detector for detecting a DC voltage input to an inverter, a current detector for detecting a current from the inverter to the synchronous motor, and an arithmetic unit for calculating a loss generated in the switching element of the inverter. And an element temperature calculation circuit for calculating the temperature of the switching element, and an example of calculating the switching loss using a predetermined calculation formula is shown.
  • the present invention has been made in view of the above, and an object of the present invention is to obtain a motor control device that can determine the loss of the switching element more accurately than the conventional method.
  • the present invention provides a motor control device that includes a main circuit inverter and calculates a loss of the switching element in the main circuit inverter, the gate voltage of the switching element.
  • a gate voltage detector for detecting the gate voltage, and holding characteristic information indicating a relationship between the gate voltage and the turn-on loss, the turn-off loss, and the recovery loss of the switching element, and the gate voltage measured by the gate voltage detector and the characteristic information
  • an element loss calculating unit that obtains the turn-on loss, the turn-off loss, and the recovery loss of the switching element as the loss based on the above.
  • the motor control device has an effect that the loss of the switching element can be obtained with higher accuracy than the conventional method.
  • FIG. 1 is a diagram illustrating a configuration example of the motor control device according to the first embodiment.
  • FIG. 2 is a diagram showing an example of the collector-emitter voltage, collector current, and loss of the IGBT.
  • FIG. 3 is a diagram illustrating an example of the forward voltage, forward current, and loss of the FWD.
  • FIG. 4 is a diagram illustrating an example of table data indicating a relationship between an input variable and a turn-on loss.
  • FIG. 5 is a diagram illustrating an example of table data indicating a relationship between an input variable and a turn-off loss.
  • FIG. 6 is a diagram illustrating an example of table data of the collector-emitter voltage.
  • FIG. 7 is a diagram illustrating an example of table data indicating the recovery loss according to the input variable.
  • FIG. 8 is a diagram illustrating an example of forward voltage table data according to input variables.
  • FIG. 9 is a diagram illustrating a configuration example of the motor control device according to the third embodiment.
  • FIG. 1 is a diagram illustrating a configuration example of a first embodiment of a motor control device according to the present invention.
  • the main circuit inverter 20 of the motor control device according to the present embodiment converts the voltage of the inverter power supply 21 into alternating current and gives it to the motor 22.
  • the inverter power supply 21 is a DC power supply.
  • the inverter power supply 21 may be, for example, a rectified AC power supply or a battery.
  • the motor 22 is a driving power source used in, for example, industrial applications and electric vehicles.
  • the main circuit inverter 20 includes 12 switching elements.
  • FIG. 1 shows an example in which twelve switching elements are composed of IGBTs (gate insulation type bipolar transistors) 7a to 7f and FWDs (freewheeling diodes) 8a to 8f.
  • the IGBTs 7a to 7f are switching-controlled by gate drive circuits 25a to 25f.
  • the gate power supplies 24a to 24f are power supplies for operating the gate drive circuits 25a to 25f, respectively.
  • the motor control unit 23 calculates the AC voltage to be output from the main circuit inverter 20 by, for example, a method called vector control or V / f control, and modulates the calculated voltage by PWM (Pulse Width Modulation) to IGBTs 7a to 7f. Output as a gate signal.
  • PWM Pulse Width Modulation
  • the current detectors 1a to 1c detect the inverter output current output from the main circuit inverter 20, the voltage detector 2 detects the power supply voltage of the inverter power supply 21, and the gate voltage detectors 4a to 4f include the gate power supplies 24a to 24f. Each of the gate voltages is detected. Moreover, the temperature detector 9 detects the temperature of arbitrary fins among the fins (not shown) provided for cooling the switching elements and the like.
  • Real switching detectors 3a to 3f detect actual switching voltages and output the number of rises and falls per unit time, on / off ratio, and the like.
  • the actual switching detector 3a can detect the actual switching voltage of the U-phase upper element (IGBT 7a, FWD 8a) by detecting the potential difference between the P terminal of the inverter power supply 21 and the U terminal of the motor 22. is there.
  • the actual switching detector 3b can detect the actual switching voltage of the U-phase lower element (IGBT 7b, FWD 8b) by detecting the potential difference between the N terminal of the inverter power supply 21 and the U terminal of the motor 22. Is possible.
  • the actual switching detectors 3c (IGBT7c, FWD8c), 3d (IGBT7d, FWD8d), 3e (IGBT7e, FWD8e), 3f (IGBT7f, FWD8f) are the V-phase upper element, V-phase lower element, and W-phase, respectively. It is possible to detect the switching voltage of the upper element and the W-phase lower element.
  • the element loss calculation units 5a to 5f use these detected information to calculate the loss of all the switching elements, and the element temperature calculation unit (temperature calculation unit) 6 calculates the switching element based on the calculated loss. Calculate the temperature.
  • the operations of the element loss calculation units 5a to 5f and the element temperature calculation unit 6 will be described in detail below.
  • the loss of all switching elements (IGBTs 7a to 7f, FWDs 8a to 8f) is calculated by the element loss calculation units 5a to 5f.
  • the element loss calculation unit 5a of the U-phase upper element (IGBT 7a, FWD 8a) will be described.
  • FIG. 2 is a diagram illustrating an example of the collector-emitter voltage Vce [UP], the collector current Ic [UP], and the loss of the IGBT 7a when the IGBT 7a performs a switching operation.
  • the upper diagram in FIG. 2 shows the collector-emitter voltage Vce [UP] and the collector current Ic [UP] .
  • the lower diagram in FIG. 2 shows the multiplication of the U-phase upper IGBT (IGBT 7a) by multiplying the two. It shows that the element loss P (IGBT) [UP] is required.
  • the loss that occurs when the IGBT 7a is turned on is the turn-on loss Pon [UP]
  • the loss that occurs when the IGBT 7a is turned off is the turn-off loss Poff [UP]
  • the loss that occurs when the IGBT 7a is conductive is the conduction loss.
  • FIG. 3 is a diagram illustrating an example of the forward voltage Vf [UP], the forward current If [UP], and the loss of the FWD 8a when the FWD 8a performs a switching operation.
  • the upper diagram of FIG. 3 shows the forward voltage Vf [UP] and the forward current If [UP] of the FWD 8a
  • the lower diagram of FIG. 3 shows the elements of the U-phase upper FWD (FWD 8a) by multiplying them. It shows that the loss P (FWD) [UP] is required. Of these, the loss that occurs when the FWD 8a is turned off is called the recovery loss Prec [UP] , and the loss that occurs when the FWD 8a is conductive is called the conduction loss Psat (FWD) [UP] .
  • the element loss calculation unit 5a includes the inverter output current Iu from the current detector 1a, the inverter power supply voltage Vdc from the voltage detector 2, the number of rises per unit time fup [UP] from the actual switching detector 3a, and unit time. Number of falling times per element fdown [UP] , ON / OFF ratio D [UP] per unit time, gate voltage Vg [UP] from the gate voltage detector 4a, element temperature Tj (IGBT) from the element temperature calculator 6 [UP] and Tj (FWD) [UP] are input.
  • the element loss calculation part 5a calculates each loss mentioned above as follows using such information.
  • FIG. 4 is a diagram illustrating an example of table data indicating the relationship between the input variable and the turn-on loss.
  • the horizontal axis represents the inverter output current Iu and the inverter power supply voltage Vdc, and a line corresponding to the element temperature Tj (IGBT) [UP] is drawn.
  • IGBT element temperature
  • FIG. 4 shows the relationship between the inverter output current Iu, the inverter power supply voltage Vdc, the element temperature, and the loss.
  • the loss also depends on the gate voltage. Therefore, actually, as table data, data as shown in FIG. 4 exists for each gate voltage.
  • this table data may be held in the form of a function, and the turn-on loss may be derived by calculation.
  • the turn-on loss Pon [UP] per unit time can be obtained by multiplying the turn-on loss per turn thus obtained by the carrier frequency in PWM modulation.
  • the turn-on loss Pon [UP] per unit time can be obtained with higher accuracy.
  • FIG. 5 is a diagram showing an example of table data indicating the relationship between the input variable and the turn-off loss.
  • the horizontal axis represents the inverter output current Iu and the inverter power supply voltage Vdc, and the lines corresponding to the element temperature Tj (IGBT) [UP] (three lines indicated by circles, squares, and triangles are different element temperatures). Corresponding to).
  • the points indicated by circles, squares, and triangles in FIG. 5 are held as numerical values as table data, and interpolation or the like is performed as necessary, whereby the turn-off loss on the vertical axis can be obtained.
  • FIG. 4 actually, as shown in FIG. 5, data as shown in FIG. 5 exists for each gate voltage.
  • this table data may be held in the form of a function, and the turn-off loss may be derived by calculation.
  • the turn-off loss Poff [UP] per unit time can be obtained by multiplying the turn-off loss obtained in this way by the carrier frequency in PWM modulation.
  • the turn-off loss Poff [UP] per unit time can be obtained with higher accuracy.
  • the conduction loss of IGBT 7a can be obtained by multiplying the collector-emitter voltage Vce [UP] and the collector current Ic [UP] as described in FIG. .
  • the collector-emitter voltage varies depending on the collector current Ic [UP] and the element temperature Tj (IGBT) [UP] . Therefore, the collector-emitter voltage corresponding to the input variable is obtained in advance by changing the value of the input variable and conducting an experiment, and stored in the form of table data in a memory or the like. That is, characteristic information indicating the relationship between the input variable and the conduction loss is held as table data.
  • FIG. 6 is a diagram showing an example of table data of the collector-emitter voltage.
  • the horizontal axis represents the collector current Ic [UP] , and lines corresponding to the element temperature Tj (IGBT) [UP] (three lines indicated by circles, squares, and triangles correspond to different element temperatures, respectively. ) Is drawn.
  • the points indicated by circles, squares, and triangles in FIG. 5 are stored as numerical values as table data, and the collector-emitter voltage Vce [UP] on the vertical axis is obtained by performing interpolation or the like as necessary .
  • this table data may be held in the form of a function, and the collector-emitter voltage may be derived by calculation.
  • the collector current used here can be derived from the inverter output current (equivalent).
  • the energization ratio of the IGBT 7a is obtained by multiplying the collector-emitter voltage Vce [UP] and the collector current Ic [UP] described above. Need to hang. Although it is possible to simply obtain the energization ratio of the IGBT 7a using the voltage command obtained from the motor control unit 23, the on / off ratio D [UP] per unit time calculated by the actual switching detector 3a is used. When the energization ratio of the IGBT 7a is obtained, it is possible to obtain the IGBT conduction loss Psat (IGBT) [UP] per unit time with higher accuracy.
  • the recovery loss varies depending on the inverter output current Iu, the inverter power supply voltage Vdc, the gate voltage Vg [UP] , and the element temperature Tj (FWD) [UP] . Therefore, the recovery loss corresponding to the input variable is obtained in advance by experimenting by changing the value of the input variable, and stored in the form of table data in a memory or the like. That is, characteristic information indicating the relationship between the input variable and the recovery loss is held as table data. Although it is possible to improve the accuracy most when all input variables are used, one or more of these input variables may be used, and it is not always necessary to use all the input variables shown here.
  • FIG. 7 is a diagram illustrating an example of table data indicating recovery loss according to the input variable.
  • the horizontal axis indicates the inverter output current Iu and the inverter power supply voltage Vdc, and the lines corresponding to the element temperature Tj (FWD) [UP] (three lines indicated by circles, squares, and triangles are different element temperatures). Corresponding to).
  • the points indicated by circles, squares, and triangles in FIG. 7 are held as numerical values as table data, and interpolation loss or the like is performed as necessary to obtain the recovery loss on the vertical axis.
  • the table data actually includes data as shown in FIG. 7 for each gate voltage.
  • this table data may be held in the form of a function, and recovery loss may be derived by calculation.
  • the recovery loss Prec [UP] per unit time can be obtained by multiplying the recovery loss per time thus obtained by the carrier frequency in PWM modulation.
  • the number of rises fup [UP] per unit time calculated by the actual switching detector 3a is used (because the FWD recovery loss occurs when the IGBT is turned on), and It becomes possible to obtain the recovery loss Prec [UP] per unit time with high accuracy.
  • the FWD conduction loss is obtained by multiplying the forward voltage Vf [UP] and the forward current If [UP] as described in FIG.
  • the forward voltage Vf [UP] varies depending on the forward current If [UP] and the element temperature Tj (FWD) [UP] . Therefore, a forward voltage corresponding to the input variable is obtained in advance by changing the value of the input variable and conducting an experiment, and stored in the form of table data in a memory or the like.
  • FIG. 8 is a diagram showing an example of the forward voltage table data corresponding to the input variable.
  • the horizontal axis represents the forward current If [UP] , and lines corresponding to the element temperature Tj (FWD) [UP] are drawn (the three lines indicated by circles, squares, and triangles correspond to different element temperatures). It has been.
  • the points indicated by circles, squares, and triangles in FIG. 8 are held as numerical values as table data, and the forward voltage Vf [UP] taken on the vertical axis by performing interpolation or the like as necessary . Can be obtained.
  • this table data may be held in the form of a function, and the forward voltage may be derived by calculation. Note that the forward current used here can be derived from the inverter output current (equivalent).
  • the conduction loss Psat (FWD) [UP] of the FWD 8a per unit time In order to obtain the conduction loss Psat (FWD) [UP] of the FWD 8a per unit time, the result of multiplication of the forward voltage Vf [UP] and the forward current If [UP] is multiplied by the energization ratio of the FWD 8a. There is a need. Although it is possible to easily obtain the energization ratio of the FWD by using the voltage command obtained from the motor control unit 23, if the on / off ratio D [UP] per unit time calculated by the actual switching detector 3a is used. In addition, the conduction loss Psat (FWD) [UP] of the FWD per unit time can be obtained with higher accuracy.
  • the element loss calculation unit 5a can obtain the turn-on loss Pon [UP] , the turn-off loss Poff [UP] , and the conduction loss Psat (IGBT) [UP] of the IGBT 7a.
  • the element loss P (IGBT) [UP] of the upper-side IGBT can be obtained.
  • the recovery loss Prec [UP] and conduction loss Psat (FWD) [UP] of the FWD 8a can be obtained, and by adding them, the element loss P (FWD) [UP] of the U-phase upper FWD is obtained.
  • the element loss calculation units 5b to 5f can also calculate the element loss based on the same concept and obtain all the element losses. These element loss calculations can be performed by a microprocessor or the like. That is, a microprocessor or the like can be used as the element loss calculation units 5a to 5f.
  • the element temperature calculation unit 6 receives all element losses as inputs and calculates their temperatures. An example of the calculation method is shown below.
  • ⁇ Tj (IGBT) [UP] P (IGBT) [UP] x Rth (IGBT) [UP] (1)
  • P (IGBT) [UP] in the equation is the element loss of the U-phase upper IGBT obtained earlier.
  • Rth (IGBT) [UP] is called a thermal resistance and is a characteristic value unique to the element.
  • the thermal resistance is obtained in advance through experiments or the like, and is stored in the form of table data in a memory or the like. It is also possible to obtain a more accurate temperature difference by using the thermal resistance as a variable of the thermal capacity and obtaining the thermal resistance using the time constant and the thermal capacity. Specifically, if the temperature difference from the element of the U-phase upper IGBT to the fin is ⁇ Tj (IGBT) [UP] , this temperature difference can be obtained as follows.
  • ⁇ Tj (IGBT) [UP] P (IGBT) [UP] * [Rth (IGBT) [UP] * ⁇ 1-exp (-t / (Rth (IGBT) [UP] * Cth (IGBT) [UP] )) ⁇ ] (2) Cth (IGBT) [UP] is called a heat capacity, and is a characteristic value unique to the element.
  • All element temperatures can be obtained with the same concept. These element temperature calculations can be performed by a microprocessor or the like. That is, a microprocessor or the like can be used as the element temperature calculation unit 6.
  • the element loss calculation units 5a to 5f and the element temperature calculation unit 6 may be implemented by the same microprocessor.
  • the element temperature obtained as described above is input to the element loss calculation units 5a to 5f and used for more accurate element loss calculation. Further, these element temperatures are input to the motor control unit 23, and when the element temperature exceeds a certain threshold value, the current value is decreased, the number of times of switching is reduced, and the motor operation is performed so that the switching element temperature does not thermally break. It is also used to prevent the switching element from being destroyed by overheating protection such as stopping.
  • gate voltage detectors 4a to 4f are used and gate voltages individually detected by the respective switching elements are used. However, for reasons such as cost reduction, Only one of the gate voltages may be detected and the same value may be used for all element loss calculations.
  • the element loss calculation units 5a to 5f include the inverter output current Iu, the inverter power supply voltage Vdc, the number of rises per unit time fup [UP] , and the number of fall times per unit time fdown [ UP] , on / off ratio D [UP] per unit time, gate voltage Vg [UP] , element temperature Tj (IGBT) [UP] and Tj (FWD) [UP]
  • the element loss of each switching element was obtained.
  • the element temperature calculation unit 6 calculates the element temperature based on the fin temperature Tfin and the element loss of the switching element, and inputs the calculated element temperature to the element loss calculation units 5a to 5f. For this reason, it becomes possible to calculate the loss of the switching element with higher accuracy than the conventional method.
  • the switching element when calculating the conduction loss of the element using the on / off ratio of the actual switching voltage per unit time using the carrier frequency in PWM modulation, the switching element is energized using the voltage command obtained from the motor control unit 23.
  • the loss of the switching element can be obtained with higher accuracy than the method of obtaining the ratio.
  • Embodiment 2 the loss calculation method according to the second embodiment of the present invention will be described.
  • the configuration of the motor control device of the present embodiment is the same as that of the first embodiment. Components having the same functions as those in the first embodiment are denoted by the same reference numerals as those in the first embodiment, and redundant description is omitted.
  • the inverter output currents from the current detectors 1a to 1c are input to the element loss calculation units 5a to 5f.
  • the element loss is calculated sequentially, for example, at a predetermined calculation timing (calculation timing for each predetermined time interval), and therefore, an instantaneous value of the inverter output current is used.
  • the element loss calculation units 5a to 5f obtain the effective value of the input inverter output current. Then, the motor control unit 23 passes the inverter operating frequency to the element loss calculating units 5a to 5f, and the element loss calculating units 5a to 5f receive the inverter operating frequency when the inverter operating frequency becomes high (for example, when the inverter operating frequency exceeds a predetermined threshold value). The inverter output current used for the loss calculation is switched from the instantaneous value to the effective value.
  • the operations of the present embodiment other than those described above are the same as those of the first embodiment.
  • the inverter output current used for the loss calculation is switched between the instantaneous value and the effective value. For this reason, the same effect as in the first embodiment can be obtained, and the accuracy of element loss can be maintained even when the inverter operating frequency is increased.
  • FIG. 9 is a diagram illustrating a configuration example of a third embodiment of the motor control device according to the present invention.
  • the configuration of the motor control device of the present embodiment is the same as that of the motor control device of the first embodiment except that an electrical component loss calculation unit 10 is added and a temperature calculation unit 11 is provided instead of the element temperature calculation unit 6. is there.
  • Components having the same functions as those in the first embodiment are denoted by the same reference numerals as those in the first embodiment, and redundant description is omitted.
  • the element temperature calculation unit 6 calculates the temperatures of all element losses as inputs. Many electric parts (resistors, capacitors, reactors, etc.) are used for the main circuit inverter 20, but generally the allowable maximum temperature of the switching element is lower than other electric parts, so only the temperature calculation of the switching element is performed. If the element is protected so as not to be thermally destroyed, there is no problem as the main circuit inverter 20.
  • the switching element of the main circuit inverter 20 may be formed of a wide band gap semiconductor.
  • the wide band gap semiconductor include silicon carbide, a gallium nitride-based material, and diamond.
  • SiC silicon carbide
  • the switching element can operate at a higher temperature than a conventional semiconductor element using Si (silicon), and the allowable maximum temperature can be increased.
  • Switching elements and diode elements formed of wide bandgap semiconductors as described above have high voltage resistance and high allowable current density, so that switching elements can be miniaturized, and these miniaturized switching elements should be used. Thus, it is possible to reduce the size of a semiconductor module incorporating these elements.
  • the heat resistance is high, it is possible to reduce the size of the heat sink fins and the air cooling of the water cooling part, thereby further reducing the size of the semiconductor module.
  • the allowable maximum temperature of other electrical components used in the main circuit inverter 20 may be lower than that of the switching element. For this reason, a problem arises as the main circuit inverter 20 unless protection is provided so that the electrical components are not thermally destroyed.
  • the electrical component loss calculation unit 10 calculates the loss of electrical components (not shown) that have a low allowable maximum temperature and may cause thermal destruction.
  • the loss P can be obtained by the following equation (4).
  • I is a current flowing through the electrical component
  • R is a resistance value of the electrical component. Since the resistance value changes depending on the temperature, it can be changed according to the temperature of the electrical component derived later, and more accurate loss calculation can be performed.
  • the temperature calculation unit 11 receives the losses of all the switching elements and electrical components as input and calculates their temperatures.
  • the temperature calculation method of the switching element is the same as the method described in the first embodiment. Although the temperature calculation method of the switching element has been described in the first embodiment, the temperature of the electrical component can be calculated in the same manner.
  • the thermal resistance is obtained by conducting an experiment in advance and stored in the form of table data in a memory or the like.
  • the influence can be taken into consideration by extending Equation (5) to an equation that considers thermal interference. And a more accurate temperature difference can be obtained.
  • the temperature T of the electrical component can be obtained by the following equation (6).
  • T ⁇ T + Tfin (6)
  • the electrical component temperature obtained as described above is returned to the electrical component loss calculation unit 10 and used for more accurate loss calculation. Further, the electrical component temperature is input to the motor control unit 23, and when the electrical component temperature exceeds a certain threshold value, the current value is decreased or the motor operation is stopped so that the electrical component is not thermally destroyed. It is also used to protect and prevent destruction of electrical components.
  • the operations of the present embodiment other than those described above are the same as those of the first embodiment.
  • the main circuit inverter has been described as a general two-level inverter having 12 switching elements.
  • the present invention can also be applied to a single-phase inverter or a multi-level inverter.
  • the loss and temperature of electrical parts other than the switching element are obtained in the same manner as the switching element. For this reason, the same effects as those of the first embodiment can be obtained, and the temperature of the electrical component can be detected without attaching a temperature detector. Moreover, since the temperature of the electrical component of the main circuit inverter 20 is obtained and overheat protection is performed based on this, it is possible to prevent thermal destruction of the electrical component. In particular, when applied to a main circuit inverter using a switching element capable of high temperature operation such as SiC, it is possible to further enhance the effect of overheat protection as a motor control device.

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  • Control Of Ac Motors In General (AREA)

Abstract

L'invention concerne un dispositif de commande de moteur comprenant un inverseur principal de circuit (20), destiné à calculer la perte d'éléments commutateurs (IGBT 7a à 7f et FWD 8a à 8f) dans l'inverseur principal de circuit (20), le dispositif de commande de moteur étant doté de détecteurs de tension de grille (4a à 4f) destinés à détecter les tensions de grille des éléments commutateurs, et d'unités de calcul de perte d'élément (5a à 5f) destinées à stocker des données en tableau qui indiquent la relation entre les tensions de grille et les pertes de fermeture, d'ouverture et de rétablissement des éléments commutateurs et à retrouver les pertes de fermeture, d'ouverture et de rétablissement des éléments commutateurs sur la base des données en tableau et des tensions de grille mesurées par les détecteurs de tension de grille (4a à 4f).
PCT/JP2011/067341 2011-07-28 2011-07-28 Dispositif de commande de moteur WO2013014798A1 (fr)

Priority Applications (2)

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JP2013525525A JP5546687B2 (ja) 2011-07-28 2011-07-28 モータ制御装置
PCT/JP2011/067341 WO2013014798A1 (fr) 2011-07-28 2011-07-28 Dispositif de commande de moteur

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Cited By (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
WO2014155622A1 (fr) * 2013-03-28 2014-10-02 三菱電機株式会社 Dispositif de pompe à chaleur, climatiseur et congélateur
WO2016031715A1 (fr) * 2014-08-28 2016-03-03 日立工機株式会社 Circuit d'attaque de moteur et outil électrique
CN112019007A (zh) * 2019-05-31 2020-12-01 三菱电机株式会社 功率转换装置
WO2023188502A1 (fr) * 2022-03-29 2023-10-05 三菱電機株式会社 Dispositif de conversion de puissance

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JP2003018861A (ja) * 2001-06-27 2003-01-17 Nissan Motor Co Ltd インバータの冷却制御装置
JP2005027379A (ja) * 2003-06-30 2005-01-27 Honda Motor Co Ltd モータ駆動装置
WO2007034544A1 (fr) * 2005-09-21 2007-03-29 Mitsubishi Denki Kabushiki Kaisha Système de détection de température excessive de contrôleur de moteur
JP2011024377A (ja) * 2009-07-17 2011-02-03 Toshiba Carrier Corp 圧縮機駆動装置および冷凍サイクル装置
WO2011052623A1 (fr) * 2009-11-02 2011-05-05 株式会社 東芝 Dispositif onduleur

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Publication number Priority date Publication date Assignee Title
JP2003018861A (ja) * 2001-06-27 2003-01-17 Nissan Motor Co Ltd インバータの冷却制御装置
JP2005027379A (ja) * 2003-06-30 2005-01-27 Honda Motor Co Ltd モータ駆動装置
WO2007034544A1 (fr) * 2005-09-21 2007-03-29 Mitsubishi Denki Kabushiki Kaisha Système de détection de température excessive de contrôleur de moteur
JP2011024377A (ja) * 2009-07-17 2011-02-03 Toshiba Carrier Corp 圧縮機駆動装置および冷凍サイクル装置
WO2011052623A1 (fr) * 2009-11-02 2011-05-05 株式会社 東芝 Dispositif onduleur

Cited By (7)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
WO2014155622A1 (fr) * 2013-03-28 2014-10-02 三菱電機株式会社 Dispositif de pompe à chaleur, climatiseur et congélateur
WO2016031715A1 (fr) * 2014-08-28 2016-03-03 日立工機株式会社 Circuit d'attaque de moteur et outil électrique
CN112019007A (zh) * 2019-05-31 2020-12-01 三菱电机株式会社 功率转换装置
JP2020198662A (ja) * 2019-05-31 2020-12-10 三菱電機株式会社 電力変換装置
US11201538B2 (en) 2019-05-31 2021-12-14 Mitsubishi Electric Corporation Power conversion device with temperature protection
CN112019007B (zh) * 2019-05-31 2024-03-05 三菱电机株式会社 功率转换装置
WO2023188502A1 (fr) * 2022-03-29 2023-10-05 三菱電機株式会社 Dispositif de conversion de puissance

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