WO2011016199A1 - Dc/dc電力変換装置 - Google Patents
Dc/dc電力変換装置 Download PDFInfo
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- WO2011016199A1 WO2011016199A1 PCT/JP2010/004746 JP2010004746W WO2011016199A1 WO 2011016199 A1 WO2011016199 A1 WO 2011016199A1 JP 2010004746 W JP2010004746 W JP 2010004746W WO 2011016199 A1 WO2011016199 A1 WO 2011016199A1
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
- H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
- H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
- H02M3/158—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
- H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
- H02M3/06—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using resistors or capacitors, e.g. potential divider
- H02M3/07—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using resistors or capacitors, e.g. potential divider using capacitors charged and discharged alternately by semiconductor devices with control electrode, e.g. charge pumps
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
- H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
- H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M7/483—Converters with outputs that each can have more than two voltages levels
- H02M7/4837—Flying capacitor converters
Definitions
- the present invention relates to a DC / DC power converter that converts a DC voltage into a DC voltage that is stepped up or stepped down.
- a conventional DC / DC power converter performs a voltage conversion from direct current to direct current by controlling the amount of energy stored in and discharged from a reactor by using an on / off operation of a switch element.
- this reactor since this reactor has a problem that it is large and heavy, the voltage applied to the reactor is reduced using charging and discharging of the capacitor, and the reactor is reduced in size by reducing the inductance value necessary for the reactor.
- a technique for reducing the weight is shown (for example, see Patent Documents 1 and 2).
- the switching element is turned on and off at a certain switching frequency to control the accumulation and release of energy to the reactor, and the voltage is boosted or lowered to a predetermined voltage. Supply voltage.
- the switching element generates a switching loss due to the on / off operation of the switching element, and the loss increases as the switching frequency increases. Also, if the switching frequency is lowered to suppress switching loss, the current ripple of the reactor will increase, and the radiated noise and conduction noise will increase due to the magnitude of the current and voltage change, causing malfunctions of surrounding devices and equipment. There is a problem that the loss of reactors and wiring increases due to the occurrence of problems and the increase in the effective current value.
- the DC / DC power conversion apparatus may be configured in combination with an inverter that converts direct current into alternating current.
- an inverter that converts direct current into alternating current.
- the DC / DC power converters used in these systems have a power supply state (for example, the amount of irradiation of light from a solar battery of a solar power generation system) and a load state (for example, the rotational speed of a motor in an electric drive system of a hybrid vehicle ), The output voltage is controlled, and thus the voltage ratio related to the voltage conversion is controlled.
- the switching frequency of the switching element is set in consideration of the fluctuation of the reactor current ripple due to the change in the voltage ratio. This is in conflict with the problems associated with the reactor current, and its setting was not easy. Accordingly, there has been a problem that it is not possible to sufficiently meet the recent demand for advanced energy saving that aims to reduce the average power consumption in a wide operating range.
- the present invention has been made to solve the above-described problems, and an object of the present invention is to provide a DC / DC power converter capable of reducing average power consumption in a wide range of DC voltage ratio. To do.
- a DC / DC power conversion device is connected between a high voltage terminal, a low voltage terminal, and a high voltage terminal, and is an element series body in which a plurality of rectifier elements are connected in series with each other.
- a switch element connected in parallel to all or part of each, a capacitor connected in parallel with a plurality of rectifier elements and holding a voltage obtained by dividing the voltage between the high voltage terminals, and one end connected to one of the low voltage terminals The other end is connected to the series connection point of the rectifying element and energized according to the switching operation of the switch element to store and release energy, and the voltage between the high voltage terminals is controlled by controlling the on / off operation of the switch element.
- the control circuit includes a current flowing through the reactor. To pull the size is equal to or lower than a predetermined limit value regardless of the voltage ratio of the DC voltage converter, in which so as to vary the switching frequency for turning on and off the switching element in accordance with the voltage ratio.
- the control circuit of the DC / DC power conversion device adjusts the voltage ratio so that the magnitude of the current ripple flowing through the reactor is not more than a predetermined limit value regardless of the voltage ratio of DC voltage conversion. Since the switching frequency for switching on and off the switching element is changed accordingly, the current ripple of the reactor is suppressed to a limit value or less, and therefore the voltage ratio is reduced while suppressing the loss and malfunction associated with this current ripple to a level below a certain level. The average value of the switching frequency over a wide range can be reduced, and the average power consumption can be reduced as compared with the conventional case where the switching frequency is constant regardless of the voltage ratio.
- FIG. 5 is a diagram showing a relationship between a switching frequency and an output voltage at which the magnitude of the current ripple of reactor Lc is the same in the boosting operation according to the first embodiment of the present invention.
- FIG. 10 is a diagram for explaining the boosting operation of the DC / DC power conversion device according to Embodiment 3 of the present invention, and shows the relationship between the output voltage and the current ripple when switching two types of switching frequencies in the entire range of the voltage ratio. It is.
- FIG. 1 shows a circuit configuration of a DC / DC power conversion apparatus according to Embodiment 1 of the present invention.
- the DC / DC power converter converts a voltage V1 input between the low voltage terminal VL and Vcom into a voltage V2 boosted to V1 or higher and converts the voltage V1 between the high voltage terminal VH and Vcom.
- the voltage V2 input between the high voltage terminal VH and Vcom is converted to a voltage V1 stepped down to V2 or lower and output between the low voltage terminal VL and Vcom (step down operation) DC.
- DC power conversion function As shown in FIG. 1, the DC / DC power converter converts a voltage V1 input between the low voltage terminal VL and Vcom into a voltage V2 boosted to V1 or higher and converts the voltage V1 between the high voltage terminal VH and Vcom.
- the voltage V2 input between the high voltage terminal VH and Vcom is converted to a voltage V1 stepped down to V2 or lower and output between the low voltage terminal VL and Vcom (
- the DC / DC power conversion apparatus includes a main circuit 110 and a control circuit 120.
- the main circuit 110 includes smoothing capacitors CL and CH that smooth the input / output voltages V1 and V2, four IGBTs (Insulated Gate Bipolar Transistors) S1 to S4 (hereinafter abbreviated as S1 etc. as appropriate), and each of the switching elements.
- IGBTs Insulated Gate Bipolar Transistors
- Both terminals of the smoothing capacitor CL are connected to the low voltage terminals VL and Vcom, respectively, and the low voltage terminal Vcom is grounded.
- the low voltage side terminal of the smoothing capacitor CH is connected to the high voltage terminal Vcom, and the high voltage terminal is connected to the high voltage terminal VH.
- the emitter terminal of S1 is connected to the low voltage terminal Vcom, the collector terminal is connected to the emitter terminal of S2, and the collector terminal of S2 is connected to the emitter terminal of S3.
- the collector terminal of S3 is connected to the emitter terminal of S4, and the collector terminal of S4 is connected to the high voltage terminal VH.
- the anode terminal of D1 is connected to the emitter terminal of S1, the cathode terminal is connected to the collector terminal, the anode terminal of D2 is connected to the emitter terminal of S2, and the cathode terminal is connected to the collector terminal.
- the anode terminal of D3 is connected to the emitter terminal of S3, the cathode terminal is connected to the collector terminal, the anode terminal of D4 is connected to the emitter terminal of S4, and the cathode terminal is connected to the collector terminal.
- Reactor Lc is connected between a series connection point of a parallel body of S2 and D2 and a parallel body of S3 and D3 and low voltage terminal VL.
- the capacitor Cp is connected in parallel with a parallel body of S2 and D2 and a parallel body of S3 and D3 connected in series with each other.
- the gate terminals of S1, S2, S3, and S4 and the voltage terminals VH, VL, and Vcom are connected to the control circuit 120. Gate signals based on the voltage at the emitter terminal of each IGBT are input to the gate terminals of S1, S2, S3, and S4.
- the operation will be described.
- the boosting operation will be described.
- the operation of this DC / DC power converter differs depending on the input / output voltage, depending on whether V2 is 1 ⁇ V1 or more and less than 2 ⁇ V1 or greater than 2 ⁇ V1.
- V2 is 1 ⁇ V1 or more and less than 2 ⁇ V1 or greater than 2 ⁇ V1.
- an operation of boosting and outputting the voltage V2 between the high voltage terminals VH and Vcom to 1 ⁇ V1 ⁇ V2 ⁇ 2 ⁇ V1 will be described.
- a DC power source of voltage V1 (smoothing capacitor CL may be regarded as a DC power source in operation within a predetermined time since the capacity is large) is connected between low voltage terminal VL-Vcom and high voltage terminal VH- A DC load is connected between Vcom, and energy is consumed by a route of VL-Vcom ⁇ VH-Vcom.
- FIG. 2 shows the waveform of the gate signal voltage of the IGBTs 1 and S2 and the waveform of the current IL of the reactor Lc.
- the IGBT is turned on when the gate signal is at a high voltage.
- a voltage of 0.5 ⁇ V2 is accumulated in the capacitor Cp.
- S3 and S4 are in an off state, and S1 and S2 perform an on / off operation.
- the operation consists of the following four modes.
- the input voltage V1 is boosted and adjusted as voltage V2 in the range of 1 ⁇ V1 ⁇ V2 ⁇ 2 ⁇ V1.
- FIG. 3 shows the waveform of the gate signal voltage of the IGBTs 1 and S2 and the waveform of the current IL of the reactor Lc.
- a voltage of 0.5 ⁇ V2 is accumulated in the capacitor Cp in a steady state.
- S3 and S4 are in an off state, and S1 and S2 perform an on / off operation.
- the operation consists of the following four modes.
- the input voltage V1 is boosted and adjusted as V2 in the range of V2> 2 ⁇ V1.
- step-down operation will be described. Even in the step-down operation, the operation differs depending on the relationship between the input and output voltages when V2 is 1 ⁇ V1 or more and less than 2 ⁇ V1 and when it is greater than 2 ⁇ V1.
- V2 is 1 ⁇ V1 or more and less than 2 ⁇ V1 and when it is greater than 2 ⁇ V1.
- the operation of stepping down and outputting the voltage V1 as 1 ⁇ V2 ⁇ V1> 0.5 ⁇ V2 between the low voltage terminals VL-Vcom will be described.
- a DC power source of voltage V2 (smoothing capacitor CH may be regarded as a DC power source in operation within a predetermined time assuming that the capacity is large) is connected between high voltage terminal VH-Vcom and low voltage terminal VL- A DC load is connected between Vcom, and energy is consumed by a route of VH ⁇ Vcom ⁇ VL ⁇ Vcom.
- FIG. 4 shows the waveform of the gate signal voltage of the IGBTs 3 and S4 and the waveform of the current IL of the reactor Lc. Since the current during the boosting operation is expressed as a positive direction, IL is expressed as a negative current here. In the steady state, a voltage of 0.5 ⁇ V2 is also stored in the capacitor Cp here. In the step-down operation, S1 and S2 are in an off state, and S3 and S4 perform an on / off operation. The operation consists of the following four modes.
- the input voltage V2 is stepped down in the range of 1 ⁇ V2 ⁇ V1> 0.5 ⁇ V2 and output as the voltage V1.
- V1 V2 corresponds to maintaining both S3 and S4 in the on state.
- FIG. 5 shows the waveform of the gate signal voltage of the IGBTs 3 and S4 and the waveform of the current IL of the reactor Lc.
- the current IL is represented as a negative current.
- a voltage of 0.5 ⁇ V2 is accumulated in the capacitor Cp in a steady state.
- S1 and S2 are in an off state, and S3 and S4 perform an on / off operation.
- the operation consists of the following four modes.
- the input voltage V2 is stepped down in the range of V1 ⁇ 0.5 ⁇ V2 and output as the voltage V1.
- This DC / DC power conversion device can perform the step-up / step-down operation by operating as described above.
- the current ripple of the reactor increases, the loss of the magnetic material constituting the reactor increases, and when the reactor generates heat, the temperature rises, the inductance value decreases, and the function of the reactor cannot be performed. Or damaged by heat.
- the current ripple is increased, electromagnetic noise and noise radiated from the reactor are increased, and the surroundings are adversely affected. For this reason, the reactor current ripple must be below a certain magnitude.
- the switching frequency for turning on and off the switching element and the inductance value of the reactor have been selected so that the current ripple can be allowed under any voltage ratio condition.
- the DC / DC power conversion device of the present invention further changes the magnitude of the reactor current ripple by changing the switching frequency for turning on / off the switching element according to the input / output voltage ratio.
- the switching loss of the switch element is reduced, and the power consumption is reduced in a wide operation range of the DC / DC power converter.
- V1-V2 / 2 L x ⁇ I / Ton (1)
- equation (2) holds.
- V2-V1 L ⁇ ⁇ I / Toff (2)
- the switching frequency f is represented by the equation (4).
- V1 L ⁇ ⁇ I / Ton (5)
- V2-V2 / 2-V1 L ⁇ ⁇ I / Toff (6)
- the switching frequency f is expressed by the equation (7).
- V2 ⁇ V1 L ⁇ ⁇ I / Ton (8)
- V1 ⁇ V2 / 2 L ⁇ ⁇ I / Toff (9)
- V2-V2 / 2-V1 L ⁇ ⁇ I / Ton (11)
- V1 L ⁇ ⁇ I / Toff (12)
- the switching frequency f is expressed by the equation (13).
- the switching frequency f is expressed by the following equations (14) and (15) based on the range of the voltage ratio k.
- the control circuit 120 inputs an allowable value as the reactor current ripple ⁇ I, and changes the switching frequency f to a value calculated by the equation (14) or (15) according to the voltage ratio k.
- the switching loss of the switch element can be reduced without changing the magnitude of the reactor current ripple, and the power consumption can be reduced in the wide operating range of the DC / DC power converter.
- the burden of cooling the device is reduced, the device is reduced in size and weight, and the durability of the device is improved.
- the relationship between the output voltage V2 and the switching frequency at which the current ripple is the same is as shown in FIG.
- the switching frequency can be reduced in the vicinity of the output of 500 V, and as a result, the switching loss of the IGBT is reduced, so that an operation with a small loss is possible.
- the output increases from 250V to 350V as the voltage increases, the frequency increases from 350V to 500V as the voltage increases, and above 500V, the frequency increases as the voltage increases. I am letting.
- an operating region with a small loss can be formed in the operating region, so that the power consumption can be greatly reduced compared to the case where the device is operated at a constant frequency.
- the power consumption can be greatly reduced by operating at the switching frequency determined according to the voltage ratio of the input and output from the above formula.
- S3 and S4 are unnecessary when only the step-up operation is performed, and S1 and S2 are not necessary when only the step-down operation is performed. Therefore, when only a one-way function is required, a configuration in which unnecessary switch elements are omitted may be used.
- FIG. A DC / DC power converter according to Embodiment 2 of the present invention will be described below.
- the circuit configuration is partially different from that of the DC / DC power conversion device of the first embodiment, the control operation related to the step-up / step-down is not basically different.
- FIG. 7 shows a circuit configuration of a DC / DC power converter according to Embodiment 2 of the present invention.
- the DC / DC power converter converts a voltage V1 input between the low voltage terminal VL and VcomL into a voltage V2 boosted to V1 or higher and converts the voltage V1 between the high voltage terminal VH and VcomH.
- the voltage V2 input between the high voltage terminals VH and VcomH is converted into a voltage V1 stepped down to V2 or lower and output between the low voltage terminals VL and VcomL (step-down operation) DC / DC power conversion function.
- the DC / DC power conversion apparatus includes a main circuit 210 and a control circuit 220.
- the main circuit 210 includes smoothing capacitors CL, CH1, and CH2 that smooth the input and output voltages V1 and V2, four IGBTs 1 to S4 (hereinafter, abbreviated as S1 as appropriate) as switching elements, and IGBTs in parallel with the IGBTs.
- S1 four IGBTs 1 to S4
- IGBTs in parallel with the IGBTs.
- Four first to fourth rectifier elements D1 to D4 (hereinafter abbreviated as D1 etc. as appropriate) connected so as to conduct in the direction opposite to the conduction direction, low voltage terminal VL, IGBT and rectifier element.
- a reactor Lc connected between the switch element groups to be configured.
- the smoothing capacitors CH1 and CH2 also function as capacitors that hold a voltage obtained by dividing the voltage V2 between the high voltage terminal VH and VcomH.
- Both terminals of the smoothing capacitor CL are connected to the low voltage terminals VL and VcomL, respectively.
- the high voltage side terminal of the smoothing capacitor CH1 is connected to the high voltage terminal VH
- the low voltage side terminal is connected to the high voltage side terminal of the smoothing capacitor CH2
- the low voltage side terminal of the smoothing capacitor CH2 is connected to the high voltage terminal VcomH.
- VcomH is grounded.
- the emitter terminal of S1 is connected to the high voltage terminal VcomH, the collector terminal is connected to the emitter terminal of S2, and the low voltage terminal VcomL.
- the collector terminal of S2 is connected to the emitter terminal of S3.
- the collector terminal of S3 is connected to the emitter terminal of S4, and the collector terminal of S4 is connected to the high voltage terminal VH.
- the anode terminal of D1 is connected to the emitter terminal of S1, the cathode terminal is connected to the collector terminal, the anode terminal of D2 is connected to the emitter terminal of S2, and the cathode terminal is connected to the collector terminal.
- the anode terminal of D3 is connected to the emitter terminal of S3, the cathode terminal is connected to the collector terminal, the anode terminal of D4 is connected to the emitter terminal of S4, and the cathode terminal is connected to the collector terminal.
- Reactor Lc is connected between a series connection point of a parallel body of S3 and D3 and a parallel body of S4 and D4 and low voltage terminal VL.
- Smoothing capacitor CH1 is connected in parallel with a parallel body of S3 and D3 connected in series and a parallel body of S4 and D4, and smoothing capacitor CH2 is a parallel body of S1 and D1 connected in series with each other. And connected in parallel with a parallel body of S2 and D2.
- the gate terminals of S1, S2, S3, and S4 and the voltage terminals VH, VL, VcomL, and VcomH are connected to the control circuit 220. Gate signals based on the voltage at the emitter terminal of each IGBT are input to the gate terminals of S1, S2, S3, and S4.
- the operation will be described.
- the boosting operation will be described.
- the operation of this DC / DC power converter differs depending on the input / output voltage, depending on whether V2 is 1 ⁇ V1 or more and less than 2 ⁇ V1 or greater than 2 ⁇ V1.
- V2 is 1 ⁇ V1 or more and less than 2 ⁇ V1 or greater than 2 ⁇ V1.
- an operation for boosting and outputting the voltage V2 to 1 ⁇ V1 ⁇ V2 ⁇ 2 ⁇ V1 between the high voltage terminals VH and VcomH will be described.
- a DC power source of voltage V1 (smoothing capacitor CL may be regarded as a DC power source in operation within a predetermined time assuming that the capacity is large) is connected between low voltage terminal VL-VcomL and high voltage terminal VH- A DC load is connected between VcomH, and energy is consumed by a route of VL-VcomL ⁇ VH-VcomH.
- FIG. 8 shows the waveform of the gate signal voltage of the IGBTs 2 and S3 and the waveform of the current IL of the reactor Lc.
- the IGBT is turned on when the gate signal is at a high voltage.
- a voltage of 0.5 ⁇ V2 is accumulated in the smoothing capacitors CH1 and CH2.
- S1 and S4 are in an off state, and S2 and S3 perform an on / off operation.
- the operation consists of the following four modes.
- the input voltage V1 is boosted and adjusted as voltage V2 in the range of 1 ⁇ V1 ⁇ V2 ⁇ 2 ⁇ V1.
- V1 V2 corresponds to turning off both S2 and S3.
- FIG. 9 shows the waveform of the gate signal voltage of the IGBTs 2 and S3 and the waveform of the current IL of the reactor Lc. Also in this case, in a steady state, a voltage of 0.5 ⁇ V2 is accumulated in the smoothing capacitors CH1 and CH2. Similarly, in the step-up operation, S1 and S4 are in an off state, and S2 and S3 perform an on / off operation. The operation consists of the following four modes.
- the input voltage V1 is boosted and adjusted as V2 in the range of V2> 2 ⁇ V1.
- step-down operation will be described. Even in the step-down operation, the operation differs depending on the relationship between the input and output voltages when V2 is 1 ⁇ V1 or more and less than 2 ⁇ V1 and when it is greater than 2 ⁇ V1.
- V2 is 1 ⁇ V1 or more and less than 2 ⁇ V1 and when it is greater than 2 ⁇ V1.
- the operation of stepping down and outputting 1 ⁇ V2 ⁇ V1> 0.5 ⁇ V2 as the voltage V1 between the low voltage terminals VL-VcomL will be described.
- a DC power source of voltage V2 (smoothing capacitors CH1 and CH2 may be regarded as a DC power source in an operation within a predetermined time assuming that the capacity is large) is connected between the high voltage terminals VH and VcomH, and the low voltage terminal VL A DC load is connected between ⁇ VcomL, and energy is consumed by a route of VH ⁇ VcomH ⁇ VL ⁇ VcomL.
- FIG. 10 shows the waveform of the gate signal voltage of the IGBTs 1 and S4 and the waveform of the current IL of the reactor Lc. Since the current during the boosting operation is expressed as a positive direction, IL is expressed as a negative current here.
- the voltage of 0.5 ⁇ V2 is also stored in the smoothing capacitors CH1 and CH2 here.
- S2 and S3 are in an off state, and S1 and S4 perform an on / off operation.
- the operation consists of the following four modes.
- the input voltage V2 is stepped down in the range of 1 ⁇ V2 ⁇ V1> 0.5 ⁇ V2 and output as the voltage V1.
- V1 V2 corresponds to maintaining both S1 and S4 in the on state.
- FIG. 11 shows the waveform of the gate signal voltage of the IGBTs 1 and S4 and the waveform of the current IL of the reactor Lc.
- the current IL is represented as a negative current.
- a voltage of 0.5 ⁇ V2 is accumulated in the smoothing capacitors CH1 and CH2.
- S2 and S3 are in an off state, and S1 and S4 perform an on / off operation.
- the operation consists of the following four modes.
- the input voltage V2 is stepped down in the range of V1 ⁇ 0.5 ⁇ V2 and output as the voltage V1.
- the DC / DC power conversion apparatus can perform the step-up / step-down operation by operating as described above, similarly to the first embodiment. Further, on the basis of the same principle as described in the first embodiment, the switching frequency f, the peak-peak value ⁇ I of the current ripple, the inductance L of the reactor, the voltages V1 and V2 related to the step-up / step-down operation, and the voltage ratio k The above equations (14) and (15) are established.
- control circuit 220 inputs an allowable value as the reactor current ripple ⁇ I, and calculates the switching frequency f according to the equation (14) or (15) according to the voltage ratio k.
- the switching loss of the switch element can be reduced without changing the magnitude of the reactor current ripple, and the power consumption can be reduced in the wide operating range of the DC / DC power converter. .
- S1 and S4 are unnecessary when only the step-up operation is performed, and S2 and S3 are not necessary when only the step-down operation is performed. Therefore, when only a one-way function is required, a configuration in which unnecessary switch elements are omitted may be used.
- Embodiment 3 FIG.
- the switching frequency f it is necessary to continuously change the switching frequency f so that the magnitude of the current ripple is constant based on the equations (14) and (15). There is an aspect that becomes complicated.
- the third embodiment of the present invention has been made in consideration of the above points.
- the switching frequency f is changed by several fixed types,
- the reactor inductance value L is not so large (the reactor size is not so large), the current ripple is suppressed to a certain value or less, and the power consumption can be reduced in the operation region where the switching frequency is low. .
- the circuit configuration is the same as that shown in FIG. Similarly, as the DC / DC power converter, the voltage V1 input between the low voltage terminals VL and Vcom is converted into the voltage V2 boosted to V1 or higher and output between the high voltage terminals VH and Vcom. (Boosting operation) Voltage V2 input between high voltage terminals VH and Vcom is converted to voltage V1 stepped down to V2 or less and output between low voltage terminals VL and Vcom (stepping down operation) DC / DC power Has a conversion function.
- Boosting operation Voltage V2 input between high voltage terminals VH and Vcom is converted to voltage V1 stepped down to V2 or less and output between low voltage terminals VL and Vcom
- the step-up operation and the step-down operation are the same as described in the first embodiment, and a description thereof will be omitted.
- the range of the voltage ratio k is divided into a plurality of operation regions, two different types of switching frequencies are set in each operation region, and the switching frequency f is switched according to the operation region and accordingly according to the voltage ratio k. The method and its effect will be described.
- FIG. 12 shows the relationship between the output voltage and the current ripple ⁇ I (difference between the maximum value and the minimum value) when the switching frequency f is constant at 10 kHz in the boosting operation.
- V1 250 V
- the reactor L 100 ⁇ H.
- the current ripple has a maximum value at 375V (1.5 times 250V), the minimum value at 500V (2 times 250V), and the voltage value above 500V.
- the maximum value is 30.3A at 660V.
- f 5 kHz in the operating region 260 V to 280 V
- f 10 kHz for 280 V to 440 V
- f 5 kHz for 440 V to 560 V
- output voltage and current ripple ⁇ I when operated at f 10 kHz for 560 V to 660 V.
- the frequency switching point there are three frequency switching points in the entire operating voltage range. However, under the condition where the operating voltage range is 440V to 660V, the frequency switching point is two times. In the above example, two types of frequencies are set, but by increasing to three types and four types, current ripple can be further suppressed and power consumption can be reduced.
- the step-up operation has been described.
- the same operation is possible in the step-down operation, and the same effect can be obtained.
- the DC / DC power conversion apparatus shown in the second embodiment can perform the same operation and can obtain the same effect.
- an unnecessary switch element may be omitted.
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Abstract
Description
そして、このスイッチ素子のオンオフ動作により、スイッチ素子にはスイッチング損失が発生し、この損失はスイッチング周波数が高いほど大きくなる。また、スイッチング損失を抑制するためにスイッチング周波数を低くすると、リアクトルの電流リプルが大きくなり、その電流、電圧変化の大きさが原因となり放射ノイズや伝導ノイズが大きくなり周囲の装置、機器の誤動作といった問題の発生や、電流実効値が大きくなることからリアクトルや配線の損失が増大するという不具合がある。
このため、従来のDC/DC電力変換装置では、これら電圧比の変化に伴うリアクトルの電流リプルの変動を加味してスイッチ素子のスイッチング周波数を設定することになるが、上述した通り、スイッチング損失とリアクトル電流に伴う不具合とは相反する関係にあり、その設定は容易ではなかった。
従って、昨今の、広い動作範囲における平均的な電力消費量の低減を図るという高度な省エネ化要請に十分応えることができないという課題があった。
以下、この発明の実施の形態1によるDC/DC電力変換装置について説明する。
図1は、この発明の実施の形態1によるDC/DC電力変換装置の回路構成を示す。図1に示すように、DC/DC電力変換装置は、低圧電圧端子VLとVcom間に入力された電圧V1を、V1以上に昇圧された電圧V2に変換して高圧電圧端子VHとVcom間に出力したり(昇圧動作)、高圧電圧端子VHとVcom間に入力された電圧V2を、V2以下に降圧された電圧V1に変換して低圧電圧端子VLとVcom間に出力する(降圧動作)DC/DC電力変換機能を有する。
S1のエミッタ端子は低圧電圧端子Vcomに、コレクタ端子はS2のエミッタ端子に接続され、S2のコレクタ端子はS3のエミッタ端子に接続されている。S3のコレクタ端子はS4のエミッタ端子に接続され、S4のコレクタ端子は高圧電圧端子VHに接続されている。D1のアノード端子はS1のエミッタ端子に、カソード端子はコレクタ端子に接続され、D2のアノード端子はS2のエミッタ端子に、カソード端子はコレクタ端子に接続されている。D3のアノード端子はS3のエミッタ端子に、カソード端子はコレクタ端子に接続され、D4のアノード端子はS4のエミッタ端子に、カソード端子はコレクタ端子に接続されている。
S1、S2、S3、S4のゲート端子と、電圧端子VH、VL、Vcomは、制御回路120に接続されている。S1、S2、S3、S4のゲート端子には、各IGBTのエミッタ端子の電圧を基準としたゲート信号が入力されている。
この場合は、電圧V1の直流電源(平滑コンデンサCLは容量が大きいとして所定の時間内の動作では直流電源とみなしてもよい)が低圧電圧端子VL-Vcom間に接続され、高圧電圧端子VH-Vcom間には直流負荷が接続され、エネルギをVL-Vcom→VH-Vcomの経路で消費している状態である。
CL→Lc→D3→Cp→S1→CL
即ち、リアクトルLcによるエネルギの蓄勢動作が、平滑コンデンサCL、従って低圧電圧端子VL、Vcom間にコンデンサCpを介して接続されるリアクトルLcへの通電により行われる。
CL→Lc→D3→D4→CH→CL
CL→Lc→S2→Cp→D4→CH→CL
即ち、ここでも、リアクトルLcによるエネルギの蓄勢動作が、低圧電圧端子VL、Vcom間にコンデンサCpを介して接続されるリアクトルLcへの通電により行われる。
CL→Lc→D3→D4→CH→CL
CL→Lc→S2→S1→CL
即ち、リアクトルLcによるエネルギの蓄勢動作が、低圧電圧端子VL、Vcom間にコンデンサCpを介さず直接接続されるリアクトルLcへの通電により行われる。
CL→Lc→D3→Cp→S1→CL
CL→Lc→S2→S1→CL
即ち、ここでも、リアクトルLcによるエネルギの蓄勢動作が、低圧電圧端子VL、Vcom間にコンデンサCpを介さず直接接続されるリアクトルLcへの通電により行われる。
CL→Lc→S2→Cp→D4→CH→CL
この場合は、電圧V2の直流電源(平滑コンデンサCHは容量が大きいとして所定の時間内の動作では直流電源とみなしてもよい)が高圧電圧端子VH-Vcom間に接続され、低圧電圧端子VL-Vcom間には直流負荷が接続され、エネルギをVH-Vcom→VL-Vcomの経路で消費している状態である。
CH→S4→S3→Lc→CL→CH
即ち、リアクトルLcによるエネルギの蓄勢動作が、高圧電圧端子VH、Vcom間にコンデンサCpを介さず直接接続されるリアクトルLcへの通電により行われる。
Cp→S3→Lc→CL→D1→Cp
CH→S4→S3→Lc→CL→CH
即ち、ここでも、リアクトルLcによるエネルギの蓄勢動作が、高圧電圧端子VH、Vcom間にコンデンサCpを介さず直接接続されるリアクトルLcへの通電により行われる。
CH→S4→Cp→D2→Lc→CL→CH
Cp→S3→Lc→CL→D1→Cp
コンデンサCpは、高圧電圧端子VH-Vcom間の電圧V2を分圧した電圧(0.5×V2)を蓄積しているものであることから、上記した経路により、リアクトルLcによるエネルギの蓄勢動作は、高圧電圧端子VH、Vcom間にコンデンサCpを介して接続されるリアクトルLcへの通電により行われる、と言える。
Lc→CL→D1→D2→Lc
CH→S4→Cp→D2→Lc→CL→CH
即ち、ここでも、リアクトルLcによるエネルギの蓄勢動作は、高圧電圧端子VH、Vcom間にコンデンサCpを介して接続されるリアクトルLcへの通電により行われる。
Lc→CL→D1→D2→Lc
ところで、既述したように、リアクトルの電流リプルが大きくなると、リアクトルを構成する磁性体の損失が大きくなり、リアクトルが発熱することにより温度が上昇しインダクタンス値が低下しリアクトルの機能を果たさなくなったり、熱で破損したりする。また、電流リプルが大きくなると、リアクトルから放射される電磁ノイズや騒音が大きくなり、その周辺に悪影響を及ぼしたりする。このようなことから、リアクトルの電流リプルは、ある大きさ以下にしなければならない。この為、従来はどんな電圧比の条件においても電流リプルが許容できる値になるように、スイッチ素子をオンオフするスイッチング周波数とリアクトルのインダクタンス値が選ばれていた。
この関係式は、先の図2~図5で説明した、昇圧動作または降圧動作、およびそれらの電圧変換範囲により異なるので、以下、これら各ケース毎に求める。
S1、S2のいずれかのゲート電圧がハイの期間(図2の時間帯(1)、(3)の期間)をTon、S1がオフしてS2がオンするまでの期間(図2の時間帯(2)の期間)、S2がオフしてS1がオンするまでの期間(図2の時間帯(4)の期間)をToffとすると、コンデンサCpの電圧が0.5×V2であることから、Tonの期間では、(1)式が成り立つ。
S1、S2のゲート電圧が同時にハイの期間(両方ともオンしている期間)で、S1がオンしてからS2がオフするまでの期間(図3の時間帯(5)の期間)、S2がオンしてからS1がオフするまでの期間(図3の時間帯(7)の期間)をTon、S1、S2のいずれかがオフしている期間(図3の時間帯(6)、(8)の期間)をToffとすると、Tonの期間では、(5)式が成り立つ。
S3、S4のゲート電圧が同時にハイの期間(両方ともオンしている期間)で、S3がオンしてからS4がオフするまでの期間(図4の時間帯(9)の期間)、S4がオンしてからS3がオフするまでの期間(図4の時間帯(11)の期間)をTon、S3、S4のいずれかがオフしている期間(図4の時間帯(10)、(12)の期間)をToffとすると、Tonの期間では、(8)式が成り立ち、Toffの期間では、(9)式が成り立つ。
V1-V2/2=L×ΔI/Toff ・・・ (9)
S3、S4のいずれかのゲート電圧がハイの期間(図5の時間帯(13)、(15)の期間)をTon、S3がオフしてS4がオンするまでの期間(図5の時間帯(14)の期間)、S4がオフしてS3がオンするまでの期間(図5の時間帯(16)の期間)をToffとすると、Tonの期間では、(11)式が成り立ち、Toffの期間では(12)式が成り立つ。
V1=L×ΔI/Toff ・・・ (12)
f=(V1/(2×L×ΔI))×(k-1)×(2-k)/k ・・・ (14)
k>2の場合:
f=(V1/(2×L×ΔI))×(k-2)/k ・・・ (15)
電力消費量が低減することで、装置を冷却する負担が軽減して装置の小形軽量化も実現し、装置の耐久性も向上する。
よって、出力500V付近ではスイッチング周波数を小さくすることができ、その結果、IGBTのスイッチング損失が小さくなることから、損失の小さい動作が可能となる。
同様に、降圧動作においても上記式から、入出力の電圧比に応じて決まるスイッチング周波数で動作することにより、電力消費量を大幅に削減することができる。
以下、この発明の実施の形態2によるDC/DC電力変換装置について説明する。先の実施の形態1のDC/DC電力変換装置に対して回路構成は一部異なるが昇降圧に係る制御動作は基本的に異なるものではない。
なお、平滑コンデンサCH1、CH2は、高圧電圧端子VHとVcomH間の電圧V2を分圧した電圧を保持するコンデンサとしても機能する。
S1、S2、S3、S4のゲート端子と、電圧端子VH、VL、VcomL、VcomHは、制御回路220に接続されている。S1、S2、S3、S4のゲート端子には、各IGBTのエミッタ端子の電圧を基準としたゲート信号が入力されている。
CL→Lc→D4→CH1→S2→CL
即ち、リアクトルLcによるエネルギの蓄勢動作が、平滑コンデンサCL、従って低圧電圧端子VL、VcomL間に分圧コンデンサとして機能する平滑コンデンサCH1を介して接続されるリアクトルLcへの通電により行われる。
CL→Lc→D4→CH1→CH2→D1→CL
CL→Lc→S3→CH2→D1→CL
即ち、ここでも、リアクトルLcによるエネルギの蓄勢動作が、低圧電圧端子VL、VcomL間に分圧コンデンサとして機能する平滑コンデンサCH2を介して接続されるリアクトルLcへの通電により行われる。
CL→Lc→D4→CH1→CH2→D1→CL
CL→Lc→S3→S2→CL
即ち、リアクトルLcによるエネルギの蓄勢動作が、低圧電圧端子VL、VcomL間に平滑コンデンサCH1、CH2を介さず直接接続されるリアクトルLcへの通電により行われる。
CL→Lc→D4→CH1→S2→CL
CL→Lc→S3→S2→CL
即ち、ここでも、リアクトルLcによるエネルギの蓄勢動作が、低圧電圧端子VL、VcomL間に平滑コンデンサCH1、CH2を介さず直接接続されるリアクトルLcへの通電により行われる。
CL→Lc→S3→CH2→D1→CL
この場合は、電圧V2の直流電源(平滑コンデンサCH1、CH2は容量が大きいとして所定の時間内の動作では直流電源とみなしてよい)が高圧電圧端子VH-VcomH間に接続され、低圧電圧端子VL-VcomL間には直流負荷が接続され、エネルギをVH-VcomH→VL-VcomLの経路で消費している状態である。
(CH2→CH1)→S4→Lc→CL→S1→(CH2→CH1)
平滑コンデンサCH1とCH2との直列体は、高圧電圧端子VH-VcomH間に接続される直流電源でもあるので、この経路により、リアクトルLcによるエネルギの蓄勢動作が、高圧電圧端子VH、VcomH間に(分圧コンデンサとして機能する平滑コンデンサCH1、CH2を介さず)直接接続されるリアクトルLcへの通電により行われる、と言える。
CH2→D3→Lc→CL→S1→CH2
(CH2→CH1)→S4→Lc→CL→S1→(CH2→CH1)
即ち、ここでも、リアクトルLcによるエネルギの蓄勢動作が、高圧電圧端子VH、VcomH間に(分圧コンデンサとして機能する平滑コンデンサCH1、CH2を介さず)直接接続されるリアクトルLcへの通電により行われる。
CH1→S4→Lc→CL→D2→CH1
CH2→D3→Lc→CL→S1→CH2
平滑コンデンサCH2は、高圧電圧端子VH-VcomH間の電圧V2を分圧した電圧(0.5×V2)を蓄積しているものであることから、上記した経路により、リアクトルLcによるエネルギの蓄勢動作は、高圧電圧端子VH、VcomH間に分圧コンデンサとして機能する平滑コンデンサCH2を介して接続されるリアクトルLcへの通電により行われる、と言える。
Lc→CL→D2→D3→Lc
CH1→S4→Lc→CL→D2→CH1
即ち、ここでも、リアクトルLcによるエネルギの蓄勢動作は、高圧電圧端子VH、VcomH間に分圧コンデンサとして機能する平滑コンデンサCH1を介して接続されるリアクトルLcへの通電により行われる。
Lc→CL→D2→D3→Lc
先の実施の形態1では、記述したように、(14)式、(15)式に基づき、電流リプルの大きさが一定になるようスイッチング周波数fを連続的に変化させる必要があり、制御が複雑になるという側面がある。また、電圧比k=2では、両式からは有効なスイッチング周波数fが得られないので、これも記述したとおり、電圧比k=2の付近で動作させたい場合は、スイッチング周波数fとして極小さい値に設定するという制御上の特別の配慮が必要となる。
図からわかるように、出力電圧260V~660Vの範囲において、電流リプルは375V(250Vの1.5倍)で極大値をもち、500V(250Vの2倍)で最小値、500V以上では電圧の大きさに依存して大きくなり、660Vでは最大値の30.3Aをとる。
そして、このf=5kHzの動作領域で消費電力を低減できることから、動作電圧範囲の全体として見て電力消費量を低減でき、装置を冷却する負担が軽減して装置の小形軽量化も実現し、装置の耐久性も向上し、制御も全体として簡便となる。
Claims (17)
- 高圧電圧端子、低圧電圧端子、前記高圧電圧端子間に接続され、整流素子を複数個互いに直列に接続してなる素子直列体、前記複数個の整流素子の全部または一部のそれぞれに並列に接続されたスイッチ素子、複数の前記整流素子と並列に接続され前記高圧電圧端子間の電圧を分圧した電圧を保持するコンデンサ、一端が前記低圧電圧端子の一方に接続され他端が前記整流素子の直列接続点に接続され前記スイッチ素子のスイッチング動作に応じて通電しエネルギの蓄勢放勢を行うリアクトル、および前記スイッチ素子のオンオフ動作を制御することにより前記高圧電圧端子間の電圧と前記低圧電圧端子間の電圧との間の直流電圧変換の制御を行う制御回路を備えたDC/DC電力変換装置において、
前記制御回路は、前記リアクトルに流れる電流リプルの大きさが前記直流電圧変換の電圧比に拘わらず所定の制限値以下となるよう、前記電圧比に応じて前記スイッチ素子をオンオフするスイッチング周波数を変化させるようにしたDC/DC電力変換装置。 - 前記素子直列体は、低電位側から高電位側に順次互いに直列に接続された第1~第4の整流素子からなり、前記低圧電圧端子は、前記リアクトルを介して前記第1の整流素子と前記第2の整流素子との直列体と並列に接続され、前記コンデンサは、前記第2の整流素子と前記第3の整流素子との直列体と並列に接続されており、
前記第1~第4の整流素子のそれぞれに並列に前記スイッチ素子を接続することにより、前記低圧電圧端子間の電圧を前記高圧電圧端子間の電圧に昇圧する昇圧動作と前記高圧電圧端子間の電圧を前記低圧電圧端子間の電圧に降圧する降圧動作の双方を実行するようにした請求項1記載のDC/DC電力変換装置。 - 前記素子直列体は、低電位側から高電位側に順次互いに直列に接続された第1~第4の整流素子からなり、前記低圧電圧端子は、前記リアクトルを介して前記第1の整流素子と前記第2の整流素子との直列体と並列に接続され、前記コンデンサは、前記第2の整流素子と前記第3の整流素子との直列体と並列に接続されており、
前記第1の整流素子と前記第2の整流素子とのそれぞれに並列に前記スイッチ素子を接続することにより、前記低圧電圧端子間の電圧を前記高圧電圧端子間の電圧に昇圧する昇圧動作を実行するようにした請求項1記載のDC/DC電力変換装置。 - 前記素子直列体は、低電位側から高電位側に順次互いに直列に接続された第1~第4の整流素子からなり、前記低圧電圧端子は、前記リアクトルを介して前記第1の整流素子と前記第2の整流素子との直列体と並列に接続され、前記コンデンサは、前記第2の整流素子と前記第3の整流素子との直列体と並列に接続されており、
前記第3の整流素子と前記第4の整流素子とのそれぞれに並列に前記スイッチ素子を接続することにより、前記高圧電圧端子間の電圧を前記低圧電圧端子間の電圧に降圧する降圧動作を実行するようにした請求項1記載のDC/DC電力変換装置。 - 前記素子直列体は、低電位側から高電位側に順次互いに直列に接続された第1~第4の整流素子からなり、前記低圧電圧端子は、前記リアクトルを介して前記第2の整流素子と前記第3の整流素子との直列体と並列に接続され、前記コンデンサは、前記第1の整流素子と前記第2の整流素子との直列体および前記第3の整流素子と前記第4の整流素子との直列体のそれぞれと並列に接続されており、
前記第1~第4の整流素子のそれぞれに並列に前記スイッチ素子を接続することにより、前記低圧電圧端子間の電圧を前記高圧電圧端子間の電圧に昇圧する昇圧動作と前記高圧電圧端子間の電圧を前記低圧電圧端子間の電圧に降圧する降圧動作の双方を実行するようにした請求項1記載のDC/DC電力変換装置。 - 前記素子直列体は、低電位側から高電位側に順次互いに直列に接続された第1~第4の整流素子からなり、前記低圧電圧端子は、前記リアクトルを介して前記第2の整流素子と前記第3の整流素子との直列体と並列に接続され、前記コンデンサは、前記第1の整流素子と前記第2の整流素子との直列体および前記第3の整流素子と前記第4の整流素子との直列体のそれぞれと並列に接続されており、
前記第2の整流素子と前記第3の整流素子とのそれぞれに並列に前記スイッチ素子を接続することにより、前記低圧電圧端子間の電圧を前記高圧電圧端子間の電圧に昇圧する昇圧動作を実行するようにした請求項1記載のDC/DC電力変換装置。 - 前記素子直列体は、低電位側から高電位側に順次互いに直列に接続された第1~第4の整流素子からなり、前記低圧電圧端子は、前記リアクトルを介して前記第2の整流素子と前記第3の整流素子との直列体と並列に接続され、前記コンデンサは、前記第1の整流素子と前記第2の整流素子との直列体および前記第3の整流素子と前記第4の整流素子との直列体のそれぞれと並列に接続されており、
前記第1の整流素子と前記第4の整流素子とのそれぞれに並列に前記スイッチ素子を接続することにより、前記高圧電圧端子間の電圧を前記低圧電圧端子間の電圧に降圧する降圧動作を実行するようにした請求項1記載のDC/DC電力変換装置。 - 前記低圧電圧端子間に直流電源が接続され前記高圧電圧端子間に直流負荷が接続され、
前記制御回路は、前記リアクトルによる前記エネルギの蓄勢動作が、前記低圧電圧端子間に前記コンデンサを介して接続される前記リアクトルへの通電により行われるよう前記各スイッチ素子をオンオフ制御することにより、(前記高圧電圧端子間の電圧/前記低圧電圧端子間の電圧)を電圧比kとしたとき、1≦k<2の範囲で昇圧動作の直流電圧変換の制御をする請求項1~3、5、6のいずれか1項に記載のDC/DC電力変換装置。 - 前記低圧電圧端子間に直流電源が接続され前記高圧電圧端子間に直流負荷が接続され、
前記制御回路は、前記リアクトルによる前記エネルギの蓄勢動作が、前記低圧電圧端子間に前記コンデンサを介さず接続される前記リアクトルへの通電により行われるよう前記各スイッチ素子をオンオフ制御することにより、(前記高圧電圧端子間の電圧/前記低圧電圧端子間の電圧)を電圧比kとしたとき、k>2の範囲で昇圧動作の直流電圧変換の制御をする請求項1~3、5、6のいずれか1項に記載のDC/DC電力変換装置。 - 前記高圧電圧端子間に直流電源が接続され前記低圧電圧端子間に直流負荷が接続され、
前記制御回路は、前記リアクトルによる前記エネルギの蓄勢動作が、前記高圧電圧端子間に前記コンデンサを介さず接続される前記リアクトルへの通電により行われるよう前記各スイッチ素子をオンオフ制御することにより、(前記高圧電圧端子間の電圧/前記低圧電圧端子間の電圧)を電圧比kとしたとき、1≦k<2の範囲で降圧動作の直流電圧変換の制御をする請求項1、2、4、5、7のいずれか1項に記載のDC/DC電力変換装置。 - 前記高圧電圧端子間に直流電源が接続され前記低圧電圧端子間に直流負荷が接続され、
前記制御回路は、前記リアクトルによる前記エネルギの蓄勢動作が、前記高圧電圧端子間に前記コンデンサを介して接続される前記リアクトルへの通電により行われるよう前記各スイッチ素子をオンオフ制御することにより、(前記高圧電圧端子間の電圧/前記低圧電圧端子間の電圧)を電圧比kとしたとき、k>2の範囲で降圧動作の直流電圧変換の制御をする請求項1、2、4、5、7のいずれか1項に記載のDC/DC電力変換装置。 - 前記低圧電圧端子間の電圧をV1、前記スイッチング周波数をf、前記リアクトルのインダクタンスをL、前記リアクトルに流れる電流リプルの前記制限値をΔIとしたとき、
前記制御回路は、下式に基づき、前記電圧比kに応じて前記スイッチング周波数fを変化させるようにした請求項8記載のDC/DC電力変換装置。
f=(V1/(2×L×ΔI))×(k-1)×(2-k)/k - 前記低圧電圧端子間の電圧をV1、前記スイッチング周波数をf、前記リアクトルのインダクタンスをL、前記リアクトルに流れる電流リプルの前記制限値をΔIとしたとき、
前記制御回路は、下式に基づき、前記電圧比kに応じて前記スイッチング周波数fを変化させるようにした請求項10記載のDC/DC電力変換装置。
f=(V1/(2×L×ΔI))×(k-1)×(2-k)/k - 前記低圧電圧端子間の電圧をV1、前記スイッチング周波数をf、前記リアクトルのインダクタンスをL、前記リアクトルに流れる電流リプルの前記制限値をΔIとしたとき、
前記制御回路は、下式に基づき、前記電圧比kに応じて前記スイッチング周波数fを変化させるようにした請求項9記載のDC/DC電力変換装置。
f=(V1/(2×L×ΔI))×(k-2)/k - 前記低圧電圧端子間の電圧をV1、前記スイッチング周波数をf、前記リアクトルのインダクタンスをL、前記リアクトルに流れる電流リプルの前記制限値をΔIとしたとき、
前記制御回路は、下式に基づき、前記電圧比kに応じて前記スイッチング周波数fを変化させるようにした請求項11記載のDC/DC電力変換装置。
f=(V1/(2×L×ΔI))×(k-2)/k - 前記昇圧動作または前記降圧動作を実行する場合の前記電圧比kの範囲を複数の動作領域に分割し、
前記制御回路は、前記リアクトルに流れる前記電流リプルの大きさが前記動作領域に拘わらず前記制限値以下となるよう、前記動作領域毎に前記スイッチ素子をオンオフするスイッチング周波数を設定するようにした請求項1ないし7のいずれか1項に記載のDC/DC電力変換装置。 - 前記動作領域として前記電圧比k=2を含む動作領域を設け、当該動作領域で設定する前記スイッチング周波数を他の動作領域で設定する前記スイッチング周波数以下とした請求項16記載のDC/DC電力変換装置。
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DE112010003189T DE112010003189T5 (de) | 2009-08-05 | 2010-07-26 | DC/DC-Leistungsumwandlungsvorrichtung |
EP10806199A EP2485376A1 (en) | 2009-08-05 | 2010-07-26 | Dc/dc power converter |
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US10003264B2 (en) | 2015-01-08 | 2018-06-19 | Mitsubishi Electric Corporation | DC/DC converter |
CN107112897B (zh) * | 2015-01-08 | 2019-05-10 | 三菱电机株式会社 | Dc/dc转换器 |
US10027234B2 (en) | 2015-07-24 | 2018-07-17 | Mitsubishi Electric Corporation | Power conversion device for performing power conversion between DC and DC by controlling switching of a semiconductor switching element |
JP2017050977A (ja) * | 2015-09-02 | 2017-03-09 | 三菱電機株式会社 | 電力変換装置 |
JP2016041012A (ja) * | 2015-12-22 | 2016-03-24 | 三菱電機株式会社 | 電力変換装置 |
JP2020501488A (ja) * | 2016-12-01 | 2020-01-16 | インテグレーテッド・デバイス・テクノロジー・インコーポレーテッド | バッテリ充電システム |
Also Published As
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EP2485376A1 (en) | 2012-08-08 |
US8773082B2 (en) | 2014-07-08 |
DE112010003189T5 (de) | 2012-09-20 |
US20120126764A1 (en) | 2012-05-24 |
JP5325983B2 (ja) | 2013-10-23 |
CN102474180A (zh) | 2012-05-23 |
JPWO2011016199A1 (ja) | 2013-01-10 |
CN102474180B (zh) | 2014-09-24 |
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