WO2005093979A1 - 無線システムおよび無線通信装置 - Google Patents
無線システムおよび無線通信装置 Download PDFInfo
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- WO2005093979A1 WO2005093979A1 PCT/JP2005/005237 JP2005005237W WO2005093979A1 WO 2005093979 A1 WO2005093979 A1 WO 2005093979A1 JP 2005005237 W JP2005005237 W JP 2005005237W WO 2005093979 A1 WO2005093979 A1 WO 2005093979A1
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- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04B—TRANSMISSION
- H04B1/00—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission
- H04B1/06—Receivers
- H04B1/10—Means associated with receiver for limiting or suppressing noise or interference
- H04B1/12—Neutralising, balancing, or compensation arrangements
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- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
- H04L27/00—Modulated-carrier systems
- H04L27/26—Systems using multi-frequency codes
- H04L27/2601—Multicarrier modulation systems
- H04L27/2647—Arrangements specific to the receiver only
- H04L27/2655—Synchronisation arrangements
- H04L27/2657—Carrier synchronisation
-
- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
- H04L27/00—Modulated-carrier systems
- H04L27/26—Systems using multi-frequency codes
- H04L27/2601—Multicarrier modulation systems
- H04L27/2602—Signal structure
-
- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
- H04L27/00—Modulated-carrier systems
- H04L27/26—Systems using multi-frequency codes
- H04L27/2601—Multicarrier modulation systems
- H04L27/2647—Arrangements specific to the receiver only
- H04L27/2655—Synchronisation arrangements
- H04L27/2668—Details of algorithms
- H04L27/2673—Details of algorithms characterised by synchronisation parameters
- H04L27/2675—Pilot or known symbols
-
- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
- H04L5/00—Arrangements affording multiple use of the transmission path
- H04L5/02—Channels characterised by the type of signal
- H04L5/023—Multiplexing of multicarrier modulation signals
Definitions
- the present invention relates to a wireless system and a wireless communication device, and particularly to a wireless system and a wireless communication device having excellent phase noise characteristics.
- FIG. 11 is a characteristic diagram showing frequency characteristics of each component of the local noise 'canceller shown in FIG.
- the input signal is a signal obtained by multiplexing a modulated IF signal (BST-OFDM) and a pilot carrier (PILOT). It shall be superimposed.
- BST-OFDM modulated IF signal
- PILOT pilot carrier
- phase noise is ⁇ (t)
- the input phase noise ⁇ (t) is superimposed on f and f.
- the input signal A is distributed by the distributor 50, and one is output to a pilot branch and the other is output to a signal branch.
- the pilot branch one of the signals distributed by the distributor 50 is band-limited by the band-pass filter 51, only the pilot's carrier component is passed and extracted, and the signal is further amplified by the limiter amplifier 52.
- the input pilot 'carrier frequency f, input phase noise has been delayed by ⁇ 0 (t- ⁇
- a local oscillation signal D is output from the local oscillator 60.
- the frequency characteristic of the local oscillation signal D output from the local oscillator 60 is, as shown in FIG. 11D, a signal of a local oscillation frequency (LO) and a local oscillation phase noise superimposed on the signal. .
- LO local oscillation frequency
- f is the local oscillation signal frequency in the system
- ⁇ is the local oscillation signal phase noise in the system.
- the local oscillation signal frequency f in the system includes the local oscillation signal phase noise ⁇ in the system.
- the signal output from distributor 50 is frequency-converted in frequency converter 61 by local oscillation signal D from local oscillator 60, and signal E is output.
- the frequency characteristic of the signal E output from the frequency change includes a sum component and a difference component of the input signal A and the local oscillation signal D. Therefore, the relationship between each signal component included in the signal E and the superposed phase noise is as follows.
- the frequency-converted signal E is band-limited by the band-pass filter 62 so that only the difference component passes, it is output as a signal F from the band-pass filter 62, and the frequency of the signal F
- the characteristic is that, as shown in FIG. 11F, the sum component in E is removed and only the difference component exists.
- the signal F is delayed by the delay corrector 63 so as to be equivalent to the delay time of the pilot branch band-pass filter 51, and is output as a signal G.
- the delay time ⁇ of the band-pass filter 51 is compared with the delay time ⁇ of the band-pass filter 62.
- the delay corrector 63 adds the delay At to the signal F, and equalizes the delay time difference from the pilot branch.
- the signal G of the signal branch and the signal C of the neurot branch output from the limiter amplifier 52 are frequency-converted by the frequency converter 70 and output as a signal H.
- the frequency characteristics of signal H output from frequency converter 70 include a sum component and a difference component of signal G and signal C. Therefore, the relationship between each signal component included in the signal H and the superposed phase noise is as follows.
- the delay corrector 63 the delay corrector 63
- BPFl BPF2 The delay ⁇ t is adjusted so that the delay time difference between the signal branch and the pilot branch is equalized.
- the frequency of the output signal component is determined by the frequency (f) of the local oscillation signal in the system related to the frequency of the input signal.
- the sideband of the signal when focusing on the pilot carrier is inverted between input and output.
- phase noise of the output signal is such that the input phase noise ⁇ (X) is canceled, and instead, the phase noise becomes the phase noise ⁇ (X) of the local oscillation signal in the system. That is, if the phase noise ⁇ (X) of the local oscillation signal in the system is sufficiently small, the phase noise of the input signal is sufficiently reduced and output.
- the signal H which has been frequency-converted by the frequency conversion, is band-limited by the band-pass filter 71 so that only the difference component and only the signal component pass, and the signal I is output.
- the phase component superimposed on the signal component included in the signal I where the pilot component and the carrier component in the difference component in ⁇ are removed and only the signal component of the difference component exists.
- the local oscillator 60 According to the principle of frequency synchronization and noise elimination of the local noise canceller, for example, even if a frequency deviation occurs in the input signal, the local oscillator 60 generates a local oscillator having high frequency accuracy and high stability. Since an output signal having a frequency according to the frequency is obtained, the frequency deviation of the input signal can be eliminated.
- phase noise of the output signal is superimposed on the input signal, and the phase noise ⁇ ) is cancelled. Instead, only the phase noise ⁇ (X) of the local oscillation signal in the system is obtained. If the phase noise ⁇ (X) of the local oscillation signal in the system is sufficiently small, the phase noise of the input signal is sufficiently reduced and output.
- Patent Document 1 JP-A-2002-152158 Disclosure of the invention
- An object of the present invention is to provide a wireless system and a wireless communication device that removes phase noise superimposed on a received signal and also removes phase noise generated in a system of a receiving wireless unit.
- a wireless system includes a wireless transmission device that includes a transmitting unit that transmits a wireless signal in which a modulated signal having no signal at the center frequency and a pilot signal having the same center frequency as the center frequency are multiplexed.
- An antenna for receiving the radio signal, first distribution means for distributing the received signal received by the antenna in two directions, and one of the received signal powers distributed by the first distribution means.
- Extracting means for extracting a signal component corresponding to a pilot signal, second distributing means for distributing a local oscillation signal from a local oscillation signal generating means in two directions, and a signal component corresponding to the extracted pilot signal, A first frequency multiplying means for performing frequency conversion using one of the local oscillation signals distributed by the second distributing means, and a delay to the other received signal distributed by the first distributing means; And a signal component corresponding to the pilot signal that has been frequency-converted by the first frequency multiplying means and the other one of the other delay-added means.
- Second frequency multiplying means for multiplying the received signal by frequency, second delay adding means for delaying the other local oscillation signal distributed by the second distribution means, and second frequency multiplying means And a quadrature demodulation means for frequency-multiplying the reception signal after frequency multiplication by the second local oscillation signal delayed by the second delay addition means and performing quadrature demodulation.
- a configuration including a wireless receiving device is adopted.
- the radio receiving apparatus is characterized in that the modulated signal having no signal at the center frequency and the center signal
- An antenna for receiving a radio signal in which a pilot signal having the same center frequency as the wave number is multiplexed; a first distribution unit for distributing a reception signal received by the antenna in two directions; and the first distribution unit Extracting means for extracting a signal component corresponding to the pilot signal; second distributing means for distributing a local oscillation signal from a local oscillation signal generating means in two directions; and First frequency multiplication means for frequency-converting a signal component corresponding to a pilot signal using one of the local oscillation signals distributed by the second distribution means, and the other frequency division means distributed by the first distribution means First delay adding means for delaying the received signal, a signal component corresponding to the pilot signal frequency-converted by the first frequency multiplying means, and the first delay adding means.
- Second frequency multiplying means for multiplying the frequency of the other received signal to which a delay has been added by a stage, and a second means for delaying the other local oscillation signal distributed by the second distribution means.
- Delay multiplying means frequency multiplying the received signal multiplied by the frequency by the second frequency multiplying means and the other local oscillation signal delayed by the second delay multiplying means,
- quadrature demodulation means for performing quadrature demodulation is employed.
- a radio system and a radio communication which improve phase noise characteristics by removing phase noise superimposed on a received signal and also removing phase noise generated in a system of a reception radio section An apparatus can be provided.
- FIG. 1 is a block diagram showing a configuration of a wireless system according to Embodiment 1.
- FIG. 3 is a block diagram showing a configuration of a wireless system according to a second embodiment.
- FIG. 4 is a block diagram showing a configuration of a wireless system according to Embodiment 3.
- FIG. 5 is a block diagram showing a configuration of a wireless system according to a fourth embodiment.
- FIG. 6 is a block diagram showing a configuration of a wireless system according to a fifth embodiment.
- FIG. 7 is a block diagram showing a configuration of a wireless system according to Embodiment 6.
- FIG. 8 is a block diagram showing a configuration of a wireless system according to a seventh embodiment.
- FIG. 9 is a block diagram showing a configuration of a wireless system according to Embodiment 8.
- FIG. 10 A block diagram showing a configuration of a local 'noise' canceller provided in a conventional wireless system.
- FIG. 11 is a characteristic diagram showing frequency characteristics of each component of the local noise canceller in FIG. 10
- FIG. 1 is a block diagram showing a configuration of the wireless system according to the present embodiment.
- the wireless system 100 includes a wireless transmitting device 101 and a wireless receiving device 151.
- the radio transmission apparatus 101 includes a transmission baseband section 110 that generates a baseband signal, and a transmission radio section 120 that performs predetermined processing on the baseband signal and transmits the baseband signal as an RF signal.
- modulation signal generation section 111 In transmission baseband section 110, modulation signal generation section 111 generates a modulation signal and supplies it to pilot signal synthesis section 112.
- the modulation signal may be any modulation signal as long as no signal is placed on the center frequency portion on the frequency axis.
- an OFDM signal or a multicarrier CDMA may be used! / ⁇ .
- the pilot signal synthesizing section 112 synthesizes the modulated signal received from the modulated signal generating section 111 and the pilot signal received from the pilot signal generating section 113, and supplies the synthesized radio signal to the transmitting radio section 120.
- local oscillation section 121 generates a local oscillation signal and supplies it to quadrature modulator 122.
- Quadrature modulator 122 uses the local oscillation signal from local oscillation section 121 to quadrature the synthesized signal of the modulated signal and pilot signal output from pilot signal synthesis section 112 of transmission baseband section 110. The signal is modulated and given to the frequency multiplier 123.
- Frequency multiplier 123 uses the local oscillation signal received from local oscillation section 124 to convert the signal orthogonally modulated in quadrature modulator 122 into a radio signal. This radio signal is transmitted via antenna 125.
- radio receiving apparatus 151 has radio reception section 165 and reception baseband section 170 for processing a signal from radio reception section 165.
- antenna 152 receives the radio signal transmitted from radio transmitting apparatus 101. This received radio signal is amplified by an amplifier 153,
- Divider 154 distributes the signal received from amplifier 153 into two routes, a modulated signal branch and a pilot branch.
- band-pass filter 155 extracts only a pilot signal component from the signal distributed by distributor 154.
- the extracted pilot signal component is amplified by an amplifier 156 and then supplied to a frequency multiplier 157.
- the frequency multiplier 157 multiplies the frequency of the signal amplified by the amplifier 156 by using the signal obtained by distributing the local oscillation signal of the local oscillation unit 159 by the distributor 158, and supplies the signal to the bandpass filter 160. .
- the band-pass filter 160 also extracts only the signal output from the frequency multiplier 157 in the desired frequency band.
- the signal extracted by the band pass filter 160 is provided to the frequency multiplier 161.
- the delay compensator 162 delays the signal received from the divider 154 so as to synchronize with the signal reaching the frequency multiplier 161 through the pilot branch, and transmits the delayed signal to the frequency multiplier 161. give.
- Frequency multiplier 161 multiplies the output signal from delay corrector 162 by the signal extracted by band-pass filter 160, and outputs the result to quadrature demodulator 163.
- the delay corrector 164 applies a predetermined delay to the signal obtained by distributing the local oscillation signal of the local oscillator 159 by the distributor 158, and outputs the resultant signal to the quadrature demodulator 163.
- Quadrature demodulator 163 performs quadrature demodulation on the output signal from frequency multiplier 161 using the output signal from delay corrector 164, and outputs it to reception baseband section 170.
- FIG. 2 is a characteristic diagram showing frequency characteristics of each signal in wireless system 100. Note that
- Figure 2A-H shows the signal circumference of the part with the corresponding alphabet added in Figure 1. It shows a wave number characteristic.
- Composite signal A of the modulated signal and the pilot signal output from transmission baseband section 110 has the frequency characteristic shown in FIG. 2A. As described above, here, the pilot signal is located at the center on the frequency axis of the modulated signal.
- the composite signal A is frequency-converted into a radio signal by the transmission radio section 120 to become a transmission signal, and is output from the antenna 125.
- the transmission signal has phase noise included in the local oscillation signal of local oscillation section 121 ⁇
- ⁇ be the phase noise included in the local oscillation signal of the IFTx oscillator 124, and let the frequency of the transmission signal be f
- the received signal B received by the radio receiving apparatus 151 has phase noise and a frequency error in the propagation path in addition to the phase noise added by the transmitting radio section 120, so that the frequency characteristic shown in FIG. And the frequency at the time of reception is f
- Radio signal B received by antenna 152 is amplified by amplifier 153, and is distributed by distributor 154 in two directions: a modulated signal branch and a pilot branch.
- pilot signal component C is extracted and has the frequency characteristics shown in FIG. 2C.
- the extracted pilot signal component C is amplified by an amplifier 156, and is then provided to a frequency multiplier 157.
- the frequency multiplier 157 multiplies the frequency of the signal amplified by the amplifier 156 by using the signal obtained by distributing the local oscillation signal of the local oscillator 159 by the distributor 158, and supplies the multiplied signal to the bandpass filter 160. .
- the band-pass filter 160 extracts a signal E output from the frequency multiplier 157, which is a signal having only a difference component.
- the signal E extracted by the band-pass filter 160 has frequency characteristics shown in FIG. 2E and is provided to the frequency multiplier 161.
- the frequency of the local oscillation signal of local oscillation section 159 is f
- the phase error is ⁇
- the amount of delay generated from the divider 158 to the frequency multiplier 161 after passing through the frequency multiplier 157 and the band-pass filter 160 is denoted by ⁇ ′, and the delay
- ⁇ be the amount of delay that occurs until the signal passes through the filter 155, the amplifier 156, the frequency multiplier 157, and the bandpass filter 160 and is input to the frequency multiplier 161.
- the signal distributed by the distributor 154 is subjected to the delay amount ⁇ by the delay corrector 162, and is output to the frequency multiplier 161 as a signal D.
- the delay corrector 162 adds a delay amount so that ⁇ is equal to ⁇ .
- This signal D has frequency characteristics shown in FIG. 2D, and the frequency and phase noise are given by the following equations.
- the frequency multiplier 161 multiplies the frequency of the signal D by using the output signal E from the bandpass filter 160 and outputs the result to the quadrature demodulator 163 as the signal F.
- This signal F has frequency characteristics shown in FIG. 2F, and the frequency and phase are as follows.
- the quadrature demodulator 163 quadrature demodulates the signal F by using the signal G to which the delay compensator 164 ⁇ delay amount ⁇ has been applied after the signal F is distributed by the distributor 158, and Band
- the delay compensator 164 passes through the frequency multiplier 157, the bandpass filter 160, and the frequency multiplier 161 from the distributor 158 and is input to the quadrature demodulator 163.
- ⁇ the amount of delay that occurs before the delay
- a delay is added so that ⁇ and
- the output signal G of the delay corrector 164 has the frequency characteristic shown in FIG. 2G, and is represented by the following equation.
- the signal H has the frequency error and the phase noise completely removed, and has a frequency characteristic shown in FIG. 2H.
- This signal H indicates a baseband signal after quadrature demodulation.
- radio transmitting apparatus 101 multiplexes and transmits the pilot signal so that the pilot signal is placed on the center frequency of the transmission signal, and radio receiving apparatus 151 generates the same frequency error and phase noise as the received signal.
- Frequency multiplication is performed with the pilot signal and quadrature demodulation is also performed on the phase noise generated in the system using the signal with the same phase noise. Therefore, the frequency error and the phase error included in the received signal can be removed, and the phase error generated in the system can be completely removed.
- phase noise outside the band of the non-pass filter 155 is not extracted, so that it is necessary to suppress the phase noise in the transmission radio unit 120.
- local oscillation section 121 and local oscillation section 124 allow suppression.
- local oscillation section 121 and local oscillation section 124 can be configured as a PLL frequency synthesizer.
- the loop bandwidth of the PLL frequency synthesizer to be equal to or less than the bandwidth of the bandpass filter 155, the phase noise of the local oscillator 121 and the local oscillator 124 existing outside the pass band of the bandpass filter 155 is suppressed. This makes it possible to remove the phase noise generated in the local oscillator 121 and the local oscillator 124.
- a radio signal in which a modulated signal having no signal at the center frequency and a pilot signal having the same center frequency as the center frequency are multiplexed in radio receiving apparatus 151 A receiving antenna 152, a distributor 154 for distributing the received signal received by the antenna 152 in two directions, and a band for extracting a signal component corresponding to the pilot signal from one of the received signals distributed by the distributor 154 A frequency component is determined by using a pass filter 155 and one local oscillation signal, which is a local oscillation signal generated by a local oscillation unit 159 and distributed in two directions by a distributor 158, using a signal component corresponding to the extracted pilot signal.
- the frequency multiplication is performed with the pilot signal having the same frequency error and phase noise as the received signal, and the phase noise generated in the system is orthogonalized using a signal having the same phase noise. Since demodulation is performed, the frequency error and the phase error included in the received signal can be removed, and the phase error generated in the system can be completely removed.
- FIG. 3 is a block diagram showing a configuration of the wireless system according to the second embodiment.
- the wireless receiver 351 of the wireless system 300 shown in FIG. 3 is different from the wireless receiver 151 of the wireless system 100 of the first embodiment in that an amplifier 353 is added between the distributor 154 and the bandpass filter 155. Only the differences are described, and other configurations are the same. Therefore, in the following, description of the same configuration will be omitted, and only different points will be described.
- the pilot signal branch when comparing the modulated signal branch with the pilot signal branch, the pilot signal branch has a band-pass filter 155 and a band-pass filter 160. Therefore, paying attention to the fact that the NF characteristic and the CZN characteristic at the time of a weak electric field are degraded from the modulation signal branch, the reception radio section 352 of the radio reception apparatus 351 has a section between the distributor 154 and the band-pass filter 155. Then, I added the amplifier 353.
- amplifier 353 In reception radio section 352, in the pilot branch, amplifier 353 amplifies the signal distributed by distributor 154 and provides the amplified signal to bandpass filter 155.
- the bandpass filter 155 extracts only the pilot signal component from the signal power amplified by the amplifier 353.
- a radio signal in which a modulated signal having no signal at the center frequency and a pilot signal having the same center frequency as the center frequency are multiplexed in radio receiving apparatus 351 A receiving antenna 152, a distributor 154 for distributing the received signal received by the antenna 152 in two directions, and a band for extracting a signal component corresponding to the pilot signal from one of the received signals distributed by the distributor 154 A frequency component is determined by using a pass filter 155 and one local oscillation signal, which is a local oscillation signal generated by a local oscillation unit 159 and distributed in two directions by a distributor 158, using a signal component corresponding to the extracted pilot signal.
- radio receiving apparatus 351 includes an amplifier 353 that amplifies the one signal distributed by distributor 154 and outputs the amplified signal to bandpass filter 155.
- FIG. 4 is a block diagram showing a configuration of the wireless system according to the third embodiment.
- the radio receiver 451 of the radio system 400 shown in FIG. 4 is different from the radio receiver 151 of the radio system 100 of the first embodiment in that a variable gain amplifier 453 is added instead of the amplifier 156, and a frequency multiplier 161 is provided. And a quadrature demodulator 163, a variable gain amplifier 454 is added, and a reception baseband unit 470 including a reception power calculation unit 471 is provided instead of the reception baseband unit 170. Is similar. Therefore, hereinafter, description of the same configuration will be omitted, and only different points will be described.
- Received power calculation section 471 calculates the power of the signal H output from quadrature demodulator 163 and the power of the received signal. Then, reception baseband section 470 gives a control signal according to the calculation result to variable gain amplifier 453 and variable gain amplifier 454 to control the gain.
- variable gain amplifier 453 receiving the control signal makes the input level to frequency multiplier 157 constant, and variable gain amplifier 454 makes the input level to quadrature demodulator 163 constant.
- the input level to the reception baseband section 470 can be kept constant.
- the input level to the reception baseband unit can be kept constant even when the reception level changes, a wireless system that operates over a wide reception level can be realized.
- radio reception apparatus 451 transmits a radio signal in which a modulated signal having no signal at the center frequency and a pilot signal having the same center frequency as the center frequency are multiplexed.
- a frequency component is determined by using a pass filter 155 and one local oscillation signal, which is a local oscillation signal generated by a local oscillation unit 159 and distributed in two directions by a distributor 158, using a signal component corresponding to the extracted pilot signal.
- radio receiving apparatus 451 is arranged at a preceding stage of reception power calculation section 471 for calculating the reception power value of the reception signal based on the amplitude of the output signal of quadrature demodulator 163, and frequency multiplier 157.
- a variable gain amplifier 453 for amplifying a signal component corresponding to the pilot signal extracted by the band-pass filter 155 in accordance with the received power value, and a variable gain amplifier 453 provided before the quadrature demodulator 163.
- a variable gain amplifier 454 for amplifying the multiplied signal according to the received power value.
- FIG. 5 is a block diagram showing a configuration of the wireless system according to the fourth embodiment.
- the wireless receiver 551 of the wireless system 500 shown in FIG. 5 is different from the wireless receiver 451 of the wireless system 400 of the third embodiment in that the delay corrector 162 is replaced with a variable delay corrector 553, A variable delay compensator 554 is used instead of the device 164, and a reception baseband unit 570 including a reception power calculation unit 471 and a delay amount calculation unit 571 is used instead of the reception baseband unit 470.
- a variable delay compensator 554 is used instead of the device 164
- a reception baseband unit 570 including a reception power calculation unit 471 and a delay amount calculation unit 571 is used instead of the reception baseband unit 470.
- variable gain amplifier 453 and the variable gain amplifier 454 that change the gain according to the reception level, a change in the amount of delay occurs simultaneously with a change in the gain.
- the delay amount calculating section 571 includes the variable gain amplifier 453 and the variable gain amplifier 454. Using the control signal from the received power calculation section 471 for controlling the gain, the delay amounts of the variable delay corrector 553 and the variable delay corrector 554 are determined, and the control signals are output to the respective delay amounts.
- variable delay corrector 553 corrects the change in the amount of delay in variable gain amplifier 453
- variable delay corrector 554 corrects the change in the amount of delay in variable gain amplifier 454. I do.
- the input level to reception baseband section 570 can be kept constant, and the delay amount in the system caused by the change in reception level can be reduced. Since a change can be corrected, a wireless system that operates stably with respect to the reception level can be realized.
- radio reception apparatus 551 transmits a radio signal in which a modulated signal having no signal at the center frequency and a pilot signal having the same center frequency as the center frequency are multiplexed.
- a frequency component is determined by using a pass filter 155 and one local oscillation signal, which is a local oscillation signal generated by a local oscillation unit 159 and distributed in two directions by a distributor 158, using a signal component corresponding to the extracted pilot signal.
- a variable delay compensator 554 for delaying the signal, the received signal after frequency multiplication by the frequency multiplier 161 and the other local oscillation signal to which the delay is added by the variable delay compensator 554 are frequency-converted.
- a quadrature demodulator 163 for multiplying and performing quadrature demodulation.
- radio reception apparatus 551 includes a reception power calculation section 471 for calculating the reception power value of the reception signal based on the amplitude of the output signal of quadrature demodulator 163, and a reception power value based on the reception power value.
- the variable delay corrector 553 and the variable delay corrector 554 are provided with a delay amount calculator 571 for calculating the delay amount, and change the delay to be added based on the delay amount. [0099] By doing so, it is possible to correct even for a change in the amount of delay in the system caused by a change in the reception level. Since they can be matched, the phase noise characteristics can be improved.
- FIG. 6 is a block diagram showing a configuration of a wireless system according to Embodiment 5 of the present invention.
- the radio receiver 651 of the radio system 600 shown in FIG. 6 is different from the radio receiver 151 of the radio system 100 of the first embodiment in that a frequency multiplier 653 is used instead of the quadrature demodulator 163,
- a receiving baseband section 670 is used instead of section 170, and the other configuration is the same. Therefore, in the following, description of the same configuration will be omitted, and only different points will be described.
- Frequency multiplier 653 multiplies signal F output from frequency multiplier 161 by signal G delayed by delay corrector 164, and outputs the result to reception baseband section 670.
- Reception baseband section 670 receives and processes this signal.
- FIG. 7 is a block diagram showing a configuration of a wireless system according to Embodiment 6 of the present invention.
- the wireless receiver 751 of the wireless system 700 shown in FIG. 7 differs from the wireless receiver 151 of the wireless system 100 of the first embodiment in that a variable gain amplifier 753 is provided between the amplifier 153 and the distributor 154.
- the only difference is that a reception baseband unit 770 including a reception power calculation unit 771 is provided instead of the reception baseband unit 170, and the other configuration is the same. Therefore, in the following, description of the same configuration will be omitted, and only different points will be described.
- Received power calculation section 771 calculates the power of the received signal H output from quadrature demodulator 163. Then, reception baseband section 770 gives a control signal according to the calculation result to variable gain amplifier 753 to control the gain.
- variable gain amplifier 753 converts the signal output from the amplifier 153 into the reception baseband unit 7
- the signal is amplified based on the control signal received from 70, and the input signal to the distributor 154 is set to a constant level.
- the reception power calculation section 771 and the reception power calculation section 471 of the third and fourth embodiments calculate the power of the received signal from the power of the signal H, and output the calculation result.
- This embodiment can be applied to the third embodiment and the fourth embodiment as well, since only the place to be performed is different.
- radio reception apparatus 751 transmits a radio signal in which a modulated signal having no signal at the center frequency and a pilot signal having the same center frequency as the center frequency are multiplexed.
- a frequency component is determined by using a pass filter 155 and one local oscillation signal, which is a local oscillation signal generated by a local oscillation unit 159 and distributed in two directions by a distributor 158, using a signal component corresponding to the extracted pilot signal.
- radio reception section 751 is provided in front of reception power calculation section 771 for calculating the reception power value of the reception signal based on the amplitude of the output signal of quadrature demodulator 163, and distributor 154, A variable gain amplifier 753 for amplifying the received signal in accordance with the received power value.
- quadrature demodulation can be performed with a simple configuration that does not require separate power adjustment for the received signal and the pilot signal.
- the input level to the container 163 can be kept constant.
- FIG. 8 is a block diagram showing a configuration of the wireless system according to the seventh embodiment.
- the radio receiver 851 of the radio system 800 shown in FIG. 7 differs from the radio receiver 151 of the radio system 100 of the first embodiment in that a variable gain amplifier 853 and a variable gain amplifier 854 are provided after the quadrature demodulator 163.
- the only difference is that a reception baseband section 870 having a reception power calculation section 871 is added instead of the reception baseband section 170, and other configurations are the same. Therefore, in the following, description of the same configuration will be omitted, and only different points will be described.
- Reception baseband section 870 receives signal H from quadrature demodulator 163, and reception power calculation section 871 calculates the power of signal H. Then, reception baseband section 870 gives a control signal according to the calculation result to variable gain amplifier 853 and variable gain amplifier 854 to control their gains. This makes it possible to cope with a wide range of reception level fluctuations.
- radio receiving apparatus 851 transmits a radio signal in which a modulation signal having no signal at the center frequency and a pilot signal having the same center frequency as the center frequency are multiplexed.
- a frequency component is determined by using a pass filter 155 and one local oscillation signal, which is a local oscillation signal generated by a local oscillation unit 159 and distributed in two directions by a distributor 158, using a signal component corresponding to the extracted pilot signal.
- Multiplier 161 for frequency-multiplying the signal component corresponding to the G signal and the other received signal delayed by the delay compensator 162, and the other local oscillation signal distributed in two directions by the distributor 158.
- Compensator 164 that delays the signal and frequency multiplier 161 And a quadrature demodulator 163 for frequency multiplying the other local oscillation signal delayed by the delay compensator 164 with the received signal after the frequency multiplication at, and for performing quadrature demodulation.
- radio receiving apparatus 851 is orthogonally demodulated by orthogonal power demodulating section 163 and receiving power calculating section 871 for calculating the power level of the received signal based on the amplitude of the output signal of orthogonal demodulator 163.
- a variable gain amplifier 853 and a variable gain amplifier 854 for amplifying the received signal in accordance with the received power value.
- FIG. 9 is a block diagram showing a configuration of a wireless system according to Embodiment 8.
- Radio receiving apparatus 951 of radio system 900 shown in FIG. 9 differs from radio receiving apparatus 151 of Embodiment 1 in that a band limiting filter 953 is provided downstream of distributor 154, and other configurations are the same. is there. Therefore, in the following, description of the same configuration will be omitted, and only different points will be described.
- band limiting filter 953 is set to remove only the pilot signal component from the signal received from distributor 154. Therefore, signal D, which is an output signal from delay corrector 162 in the present embodiment, has no peak corresponding to a pilot signal component in the center frequency region.
- frequency multiplier 161 signal D from which the peak corresponding to the pilot signal component in the center frequency region has been removed is multiplied by signal E, and given to quadrature demodulator 163.
- the peak corresponding to the pilot signal component in the center frequency region of the signal input to the frequency multiplier 161 is removed by the band-limiting filter 953 of the modulated signal branch.
- the effect of DC offset on the input signal can be eliminated. Therefore, it is possible to prevent distortion from occurring in the signal input from the frequency multiplier 161 to the quadrature demodulator 163. Therefore, reception characteristics can be improved. That is, the reception characteristics can be improved by preventing the occurrence of distortion caused by the DC offset.
- radio reception apparatus 951 transmits a radio signal in which a modulated signal having no signal at the center frequency and a pilot signal having the same center frequency as the center frequency are multiplexed.
- a frequency component is determined by using a pass filter 155 and one local oscillation signal, which is a local oscillation signal generated by a local oscillation unit 159 and distributed in two directions by a distributor 158, using a signal component corresponding to the extracted pilot signal.
- radio receiving apparatus 951 is provided before delay adder 162, and has a signal corresponding to a pilot signal having the same center frequency as the center frequency of the other received signal power distributed by divider 154.
- a bandpass filter 953 for removing components is provided.
- the band limiting filter 953 removes the peak corresponding to the pilot signal component in the center frequency region of the signal input to the frequency multiplier 161.
- the effect of the DC offset on the signal to be removed can be eliminated. Therefore, it is possible to prevent distortion from occurring in the signal input to the quadrature demodulator 163, and it is possible to improve reception characteristics.
- the power provided with the band limiting filter 953 between the divider 154 and the delay adder 162 is not limited to this, and is provided between the delay adder 162 and the frequency multiplier 161. The same effect can be obtained.
- the present specification is based on Japanese Patent Application No. 2004-089726 filed on March 25, 2004. All of this content is included here.
- the wireless system and the wireless communication device of the present invention remove phase noise superimposed on a received signal, and also remove phase noise generated in a system of a wireless reception unit, thereby improving phase noise characteristics. Useful.
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- Engineering & Computer Science (AREA)
- Signal Processing (AREA)
- Computer Networks & Wireless Communication (AREA)
- Noise Elimination (AREA)
- Superheterodyne Receivers (AREA)
Abstract
Description
Claims
Priority Applications (3)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
EP05727178A EP1724956A1 (en) | 2004-03-25 | 2005-03-23 | Radio system and radio communication device |
US10/593,698 US20080233878A1 (en) | 2004-03-25 | 2005-03-23 | Radio System and Radio Communication Device |
JP2006519439A JPWO2005093979A1 (ja) | 2004-03-25 | 2005-03-23 | 無線システムおよび無線通信装置 |
Applications Claiming Priority (2)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
JP2004089726 | 2004-03-25 | ||
JP2004-089726 | 2004-03-25 |
Publications (1)
Publication Number | Publication Date |
---|---|
WO2005093979A1 true WO2005093979A1 (ja) | 2005-10-06 |
Family
ID=35056536
Family Applications (1)
Application Number | Title | Priority Date | Filing Date |
---|---|---|---|
PCT/JP2005/005237 WO2005093979A1 (ja) | 2004-03-25 | 2005-03-23 | 無線システムおよび無線通信装置 |
Country Status (6)
Country | Link |
---|---|
US (1) | US20080233878A1 (ja) |
EP (1) | EP1724956A1 (ja) |
JP (1) | JPWO2005093979A1 (ja) |
KR (1) | KR20070006784A (ja) |
CN (1) | CN1934813A (ja) |
WO (1) | WO2005093979A1 (ja) |
Cited By (2)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
WO2007007729A1 (ja) * | 2005-07-11 | 2007-01-18 | Matsushita Electric Industrial Co., Ltd. | 無線受信装置 |
JP2013187663A (ja) * | 2012-03-07 | 2013-09-19 | Kddi Corp | 光ファイバ伝送装置および伝送方法 |
Families Citing this family (5)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
JP4102375B2 (ja) * | 2004-03-25 | 2008-06-18 | 松下電器産業株式会社 | 無線送信装置および無線受信装置 |
CN101136731B (zh) * | 2007-08-09 | 2011-08-31 | 复旦大学 | 一种利用连续传输参数信令消除相位噪声的方法 |
CN102342056A (zh) * | 2009-03-05 | 2012-02-01 | 三菱电机株式会社 | 无线通信系统、发送装置以及接收装置 |
JP5075189B2 (ja) * | 2009-12-03 | 2012-11-14 | 株式会社エヌ・ティ・ティ・ドコモ | 無線通信端末 |
EP3051762B1 (en) * | 2013-10-29 | 2019-07-10 | Huawei Technologies Co., Ltd. | Phase noise correction method, device and system |
Citations (7)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
JPH09270765A (ja) * | 1996-01-31 | 1997-10-14 | Victor Co Of Japan Ltd | Ofdm変復調装置及びofdm変調方法 |
JPH1065644A (ja) * | 1996-08-20 | 1998-03-06 | Nippon Hoso Kyokai <Nhk> | Ofdm信号伝送方法およびofdm信号受信装置 |
JPH10303852A (ja) * | 1997-04-28 | 1998-11-13 | Nippon Hoso Kyokai <Nhk> | 直交周波数分割多重変調の基準搬送周波数再生方式 |
JPH11355242A (ja) * | 1998-06-11 | 1999-12-24 | Victor Co Of Japan Ltd | マルチキャリア変調装置及び復調装置 |
JP2000092142A (ja) * | 1998-09-11 | 2000-03-31 | Hitachi Denshi Ltd | データ伝送方式 |
JP2001203663A (ja) * | 2000-01-18 | 2001-07-27 | Victor Co Of Japan Ltd | 直交周波数分割多重伝送システム |
JP2002152158A (ja) * | 2000-11-15 | 2002-05-24 | Hitachi Kokusai Electric Inc | 地上デジタルtv放送伝送方法及び地上デジタルtv放送システム |
-
2005
- 2005-03-23 WO PCT/JP2005/005237 patent/WO2005093979A1/ja not_active Application Discontinuation
- 2005-03-23 JP JP2006519439A patent/JPWO2005093979A1/ja active Pending
- 2005-03-23 US US10/593,698 patent/US20080233878A1/en not_active Abandoned
- 2005-03-23 EP EP05727178A patent/EP1724956A1/en not_active Withdrawn
- 2005-03-23 CN CNA2005800090331A patent/CN1934813A/zh active Pending
- 2005-03-23 KR KR1020067019260A patent/KR20070006784A/ko not_active Application Discontinuation
Patent Citations (7)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
JPH09270765A (ja) * | 1996-01-31 | 1997-10-14 | Victor Co Of Japan Ltd | Ofdm変復調装置及びofdm変調方法 |
JPH1065644A (ja) * | 1996-08-20 | 1998-03-06 | Nippon Hoso Kyokai <Nhk> | Ofdm信号伝送方法およびofdm信号受信装置 |
JPH10303852A (ja) * | 1997-04-28 | 1998-11-13 | Nippon Hoso Kyokai <Nhk> | 直交周波数分割多重変調の基準搬送周波数再生方式 |
JPH11355242A (ja) * | 1998-06-11 | 1999-12-24 | Victor Co Of Japan Ltd | マルチキャリア変調装置及び復調装置 |
JP2000092142A (ja) * | 1998-09-11 | 2000-03-31 | Hitachi Denshi Ltd | データ伝送方式 |
JP2001203663A (ja) * | 2000-01-18 | 2001-07-27 | Victor Co Of Japan Ltd | 直交周波数分割多重伝送システム |
JP2002152158A (ja) * | 2000-11-15 | 2002-05-24 | Hitachi Kokusai Electric Inc | 地上デジタルtv放送伝送方法及び地上デジタルtv放送システム |
Cited By (4)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
WO2007007729A1 (ja) * | 2005-07-11 | 2007-01-18 | Matsushita Electric Industrial Co., Ltd. | 無線受信装置 |
US8027411B2 (en) | 2005-07-11 | 2011-09-27 | Panasonic Corporation | Wireless receiver |
JP4791468B2 (ja) * | 2005-07-11 | 2011-10-12 | パナソニック株式会社 | 無線受信装置 |
JP2013187663A (ja) * | 2012-03-07 | 2013-09-19 | Kddi Corp | 光ファイバ伝送装置および伝送方法 |
Also Published As
Publication number | Publication date |
---|---|
EP1724956A1 (en) | 2006-11-22 |
CN1934813A (zh) | 2007-03-21 |
US20080233878A1 (en) | 2008-09-25 |
JPWO2005093979A1 (ja) | 2008-02-14 |
KR20070006784A (ko) | 2007-01-11 |
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