WO2004042943A1 - Procede et ensemble circuit permettant d'injecter un signal d'entree dans plusieurs recepteurs - Google Patents

Procede et ensemble circuit permettant d'injecter un signal d'entree dans plusieurs recepteurs Download PDF

Info

Publication number
WO2004042943A1
WO2004042943A1 PCT/EP2003/011904 EP0311904W WO2004042943A1 WO 2004042943 A1 WO2004042943 A1 WO 2004042943A1 EP 0311904 W EP0311904 W EP 0311904W WO 2004042943 A1 WO2004042943 A1 WO 2004042943A1
Authority
WO
WIPO (PCT)
Prior art keywords
resistor
capacitance
transformer
diodes
connection
Prior art date
Application number
PCT/EP2003/011904
Other languages
German (de)
English (en)
Inventor
Stefan Brinkhaus
Original Assignee
Harman Becker Automotive Systems Gmbh
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Harman Becker Automotive Systems Gmbh filed Critical Harman Becker Automotive Systems Gmbh
Publication of WO2004042943A1 publication Critical patent/WO2004042943A1/fr

Links

Classifications

    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03J—TUNING RESONANT CIRCUITS; SELECTING RESONANT CIRCUITS
    • H03J1/00—Details of adjusting, driving, indicating, or mechanical control arrangements for resonant circuits in general
    • H03J1/0008—Details of adjusting, driving, indicating, or mechanical control arrangements for resonant circuits in general using a central processing unit, e.g. a microprocessor
    • H03J1/0058—Details of adjusting, driving, indicating, or mechanical control arrangements for resonant circuits in general using a central processing unit, e.g. a microprocessor provided with channel identification means
    • H03J1/0083—Details of adjusting, driving, indicating, or mechanical control arrangements for resonant circuits in general using a central processing unit, e.g. a microprocessor provided with channel identification means using two or more tuners
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03H—IMPEDANCE NETWORKS, e.g. RESONANT CIRCUITS; RESONATORS
    • H03H7/00—Multiple-port networks comprising only passive electrical elements as network components
    • H03H7/46—Networks for connecting several sources or loads, working on different frequencies or frequency bands, to a common load or source
    • H03H7/461—Networks for connecting several sources or loads, working on different frequencies or frequency bands, to a common load or source particularly adapted for use in common antenna systems
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03H—IMPEDANCE NETWORKS, e.g. RESONANT CIRCUITS; RESONATORS
    • H03H7/00—Multiple-port networks comprising only passive electrical elements as network components
    • H03H7/48—Networks for connecting several sources or loads, working on the same frequency or frequency band, to a common load or source
    • H03H7/482—Networks for connecting several sources or loads, working on the same frequency or frequency band, to a common load or source particularly adapted for use in common antenna systems
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B1/00—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission
    • H04B1/06—Receivers
    • H04B1/16—Circuits
    • H04B1/18—Input circuits, e.g. for coupling to an antenna or a transmission line

Definitions

  • the invention relates to a method for feeding an input signal into n receivers by means of n transmitters, each with a primary and a secondary winding.
  • the invention further relates to a circuit arrangement for feeding an input signal into n receivers by means of n transmitters, each with a primary and a secondary winding.
  • Such methods and circuit arrangements are e.g. used when the energy received by a common antenna is to be distributed to several receivers. If the receivers are tuned to different frequency bands, the antenna energy can be frequency-selectively distributed to the individual receivers via reception switches. Because the receivers are almost completely decoupled from each other, none of the receivers draws energy not intended for them from another receiver.
  • the energy received by the antenna must be distributed among the individual receivers so that each receiver only receives a fraction of the antenna energy determined by the number of all receivers.
  • the energy supplied by the antenna is initially amplified in a preamplifier before it is distributed to the individual receivers via a decoupling network, for example from attenuators or so-called power splitters, largely without feedback and without loss of sensitivity becomes.
  • a decoupling network for example from attenuators or so-called power splitters
  • State-of-the-art car radios are equipped with two receivers as antenna diversity or frequency diversity reception systems.
  • One receiver which is referred to as an operating, playback or foreground receiver, is used for playback, while the other receiver, which is referred to as a search, test or background receiver, searches for alternative reception frequencies and checks their reception quality. If the search receiver finds an alternative reception frequency that offers a better reception quality than the reception frequency that has been set for a longer time at the operating temperature, then either the operation receiver is tuned to the new reception frequency of better quality found or the search and operation receiver swap roles. The search receiver then remains tuned to the currently optimal reception frequency found and takes over the task of the previous company receiver, who is now looking for alternative reception frequencies as a search receiver and checks their reception quality.
  • a preamplifier for a mobile car radio must be dimensioned much stronger than for a stationary receiving system.
  • Such a preamplifier required for a mobile receiving system would be technically very complex, because both its dimensions and its power consumption was also significantly higher than that of a preamplifier sufficient for a stationary reception system.
  • the smallest possible dimensions and low power consumption are sought for car radios.
  • a capacitive coupling of the two receivers is usually used instead of a preamplifier to amplify the antenna signals the car antenna provided.
  • the playback receiver In a receiving system with a playback and with a search receiver, the playback receiver is strongly coupled to the antenna, while a loose coupling to the antenna is chosen for the search receiver.
  • This measure 5 has the advantage that the search receiver sucks little energy from the playback receiver, even if both receivers are tuned to the same reception frequency. In this case, however, the noise is audibly increased.
  • a disadvantage of this arrangement is that the search or background receiver receives significantly less energy from the antenna than the playback or foreground receiver.
  • the search receiver can therefore no longer detect weakly receivable transmitters, which can, however, still be received and reproduced by the playback receiver.
  • Radio data system signals - abbreviated to RDS - broadcast in such a weakly received transmitter are therefore no longer possible, although the detection of the RDS data does not pose any difficulties for the playback receiver. Therefore, the search receiver can broadcast radio stations that are poorly receivable, but which can still be reproduced by the playback receiver in good listening quality
  • both receivers are coupled to the car antenna to the same extent. As long as both receivers are tuned to receive frequencies whose frequency spacing is large enough, neither of the two receivers draws energy from the other.
  • the search receiver is tuned to reception frequencies that are close to the reception frequency of the playback receiver, suction effects of up to 10 dB can occur. A clear noise can be heard when the search receiver sweeps over the reception area of the playback receiver. The evaluation of the RDS data is significantly impaired. If the search receiver quickly jumps over the reception area of the playback receiver, its pre-circuit is phase-modulated, with a loud click pulse being heard.
  • a termination with the characteristic impedance of the connecting line to the receiver is important.
  • the selective coupling just described ensures an adaptation to the characteristic impedance but only on the receiving frequency.
  • the standing waves that form on the connecting line due to mismatch adversely affect the control behavior and the amplification and thus also the large signal behavior.
  • this object is achieved with the features specified in claim 1 in that one of the n receivers is connected to each secondary winding of the n transmitters is connected that the current of a controllable current source is impressed on the series-connected primary windings of the transformers and that the current source and thus the current supplied by it is controlled by the input signal.
  • this object is achieved with the features specified in claim 15 in that one of the n receivers is connected to each secondary winding of the n transmitters, that a current source is connected to the series connection of the primary windings of the n transmitters and that the input signal at the control input of the current source lies.
  • the invention provides for the input signal to be transmitted to the receiver by means of a transmitter.
  • a transmitter is assigned to each recipient.
  • a receiver is connected to each secondary winding of the transformer.
  • the primary windings of the transformers are connected in series.
  • the current from a controllable current source which is connected to the series circuit from the primary windings of the transformers, is impressed on the series circuit from the transformers.
  • the input signal e.g. an antenna signal is at the control input of the controllable current source.
  • An embodiment of the invention provides for the input signal to be passed through a filter, e.g. a bandpass to feed the control input of the controllable power source.
  • a filter e.g. a bandpass to feed the control input of the controllable power source.
  • a transistor in base circuit is preferably provided as the current source, the emitter of which the input signal is supplied and the collector current of which is impressed on the primary windings of the transformers.
  • the input signal is preferably fed to the emitter of the transistor via a series resonant circuit comprising an inductance and a capacitance and an ohmic resistor connected in series with it.
  • the series resonant circuit serves as a bandpass filter, while the ohmic resistance together with the input resistance of the transistor den Termination forms.
  • the collector of the transistor represents a current source for the collector current generated by the emitter control, which flows through the primary windings of the transformers.
  • the amplification factors of the individual transformers can be set independently of one another through the transmission ratio of the coupling effects. Except for inevitable minor repercussions, the collector current of the transistor provided as the current source and operated in the base circuit is independent of the frequency and thus also the impedance of the transformers and their coupling windings. For this reason, the energy coupled into one transmitter is almost independent of the tuning frequency of the other transmitters.
  • 5 shows the pass curve of an input filter
  • 6 shows the independent selection curves of two receivers
  • Fig. 7 shows an antenna distribution system with a preamplifier according to the prior art
  • Fig. 8 is a car radio with two receivers and capacitive coupling of the
  • FIG. 7 shows an antenna distribution system with a preamplifier and two receivers according to the prior art.
  • An antenna A is connected to the input of a preamplifier V, to the output of which a first receiver FM1 and a second receiver FM2 are connected via an attenuator made up of ohmic resistors R35 to R39.
  • An antenna A is connected via a capacitance C1 to a first parallel circuit comprising a resistor R40, an inductor L10 and a series circuit comprising two oppositely polarized diodes D1 and D2 and via a capacitance C3 to a second parallel circuit comprising a resistor R41, an inductor L20 and connected in series from two oppositely polarized diodes D3 and D4.
  • the common connection point of the two diodes D1 and D2 is connected via a capacitance C16 to the input of a first receiver FM1.
  • the common connection point of the two diodes D3 and D4 is connected via a capacitance C17 to the input of a second receiver FM2.
  • the antenna A is capacitively coupled to the two receivers FM1 and FM2. 1 shows a first exemplary embodiment of the invention.
  • An antenna A is connected to the control input of a controlled current source S, which is connected to the series windings PW of n transformers Kl-Kn.
  • One of the receivers FM1-FMn is connected to each secondary winding SW of the transformer Kl-Kn.
  • the current of the current source S controlled by the antenna signal AS is impressed on the series connection from the primary windings PW of the n transformers Kl-Kn.
  • the antenna signal AS is coupled into the n receivers FM1-FMn irrespective of the frequency. Because the current source S impresses its current on the primary windings PW of the transformers Kl-Kn, no preamplifier is required which would have a greater current requirement than the current source provided according to the invention.
  • FIG. 2 shows a second exemplary embodiment of the invention, in which a transistor operating in the basic circuit is provided as the current source.
  • An antenna A is connected via a series circuit comprising an inductor L1, a capacitor C3 and a resistor R33 to the emitter of a transistor Ql, the collector of which is connected to the one terminal of a series circuit comprising a resistor R28, the primary winding L3 of a transformer Kl and the primary winding L6 a transformer K2 is connected.
  • the other connection of this series circuit is connected to the first pole of a supply voltage source U1 and via a capacitance C18 to the one connection of the secondary winding L7 of the transformer K2 and to reference potential.
  • Parallel to the secondary winding L7 of the transformer K2 is a resistor R18, to which there is a series connection of two diodes D2 and D4 with opposite polarity.
  • the common connection point of the two diodes D2 and D4 is via a capacitance C17 with the input one FM2 receiver connected.
  • a voltage Uabs2 representing the reception field strength is tapped off at the connection point of the two diodes D2 and D4 by means of a resistor R21.
  • the two diodes D2 and D4 are tuning diodes which, together with the associated secondary winding L7 of the transformer K2, form an oscillating circuit for tuning.
  • a resistor R12 and a series circuit comprising two oppositely polarized diodes D1 and D3 are connected in parallel with the secondary winding L4 of the transmission Kl.
  • One connection of the parallel circuit from the secondary winding L4, the resistor R12 and the series circuit from the two diodes D1 and D3 is at reference potential.
  • the common node of the two diodes D1 and D3 is connected via a capacitance C16 to the input of a receiver FM1.
  • a voltage Uabsl representing the received field strength is tapped off at the common node of the two diodes D1 and D3 via a resistor R20.
  • the two diodes D1 and D3 are also tuning diodes which, together with the associated secondary winding L4 of the transformer Kl, form an oscillating circuit for tuning.
  • the first pole of the supply voltage source U1 is connected to the reference potential via a series circuit comprising a resistor R3 and R4.
  • a capacitor C1 is connected in parallel with the resistor R4.
  • the base of the transistor Ql is connected to the common connection point of the two resistors R3 and R4 and the capacitance C1.
  • the emitter of transistor Ql is connected to reference potential via a series circuit comprising a resistor R1 and an inductor L12.
  • the antenna signal supplied by the antenna A is fed to the emitter of the transistor Q1 via the series circuit comprising the inductance L1, the capacitance C3 and the resistor R33.
  • the inductance L1 and the capacitance C3 form a bandpass for the intended wave range. Instead of a band pass, other selection means are also possible.
  • the resistor R33 together with the Input resistance of the transistor Ql the termination resistance of the bandpass from the inductance Ll and the capacitance C3. By adjusting resistor R33, the input resistance can be adjusted to achieve an optimal noise figure, an optimal resistance match, or any compromise of both.
  • the collector of transistor Ql represents a current source for the collector current generated by the emitter driver, which flows through the primary winding L3 of the transformer K1 and through the primary winding L6 of the transformer K2.
  • the amplification factors of the two transmitters K 1 and K 2 can be set independently of one another by the transmission ratio of the coupling windings.
  • the voltage on the secondary winding L4 of the transformer K1 is coupled out to the receiver FM1 via the capacitance C16, while the voltage on the secondary winding L7 of the transformer K2 is coupled out to the receiver FM2 via the capacitance C17.
  • the collector current of the transistor Q1 is independent of the frequency and thus also of the impedance of the transformers K1 and K2 and their coupling windings. Therefore, the energy coupled into one transmitter is almost independent of the tuning frequency of the other transmitter.
  • the remaining resistors, capacitors and inductors are used to set the operating point.
  • the embodiment of the invention shown in FIG. 2 is characterized by a defined input resistance.
  • the two transmitters and thus also the two selection circles can be tuned independently of one another. No power is consumed as in the prior art in power splitters or attenuators.
  • the transistor provided as a current source serves as a distribution and coupling amplifier with only a low power consumption.
  • the invention is not limited to two receivers. Rather, any number of primary windings can be connected to the collector of the transistor, as indicated in Fig. 1.
  • the reception frequencies can be anywhere, in the same reception band or in different reception bands. It is only necessary to design the input selection in the emitter circuit of transistor Q1 accordingly.
  • FIG. 3 shows a second exemplary embodiment of the invention, which is designed as an X-coupled broadband amplifier and differs from the exemplary embodiment shown in FIG. 2 on the one hand in that the resistor R33 is replaced by the primary winding L8 of a negative feedback transformer G and on the other hand, that between the resistor R28 and the inductor L3 is the secondary winding L9 of the negative feedback transformer G.
  • the collector current of the transistor Q1 is fed back to the input, that is to say the emitter, of the transistor Q1 by means of the negative feedback transformer G from the primary winding L8 and the secondary winding L9. This feedback results in an extremely favorable noise figure.
  • FIG. 4 shows a fourth exemplary embodiment of the invention with three receivers.
  • An antenna A is connected to the emitter of a transistor Q28 via a series circuit comprising a resistor R6, an inductor L1 and a capacitor C3. Parallel to the series connection of the inductor L1 and the capacitor C3 is a series connection of an inductor L2 and a capacitor CIO.
  • the collector of the transistor Q28 is connected to the one terminal of a series circuit comprising a resistor R28, the primary winding L13 of a transformer K3, the primary winding L3 of a transformer K1 and the primary winding L6 of a transformer K2.
  • the other connection of the series circuit comprising the resistor R28 and the primary windings L13, L3 and L6 - the free connection of the primary winding L6 - is via a capacitance C18 with the negative pole of a supply voltage source VI and with a connection of the secondary winding L7 of the transformer K2, to which a resistor R18 and a series circuit comprising two oppositely polarized diodes D2 and D4 are connected in parallel.
  • the common connection point of the two diodes D2 and D4 is connected via a capacitance 017 to the first input of a field effect transistor pre-stage M2, which is connected via a resistor R27 and in parallel to it via a capacitance 021 to the negative pole of the supply voltage source VI.
  • the first output of the field effect transistor preamplifier M2 is connected to the input of a receiver FM2 and is connected via a parallel circuit comprising an inductor L16 and a resistor R29 to the positive pole of the supply voltage source VI, which is connected via a series circuit comprising a resistor R32 and a resistor R22 to the second Input of the field effect transistor preamplifier M2 is connected.
  • the second input of the field effect transistor pre-stage M2 is connected via a capacitance 015 to the negative pole of the supply voltage source VI.
  • the second output of the field effect transistor pre-stage M2 is connected to the negative pole of the supply voltage source VI.
  • the first input of the field effect transistor preamplifier M1 is connected via a resistor R26 and in parallel to it via a capacitor C20 at the negative pole of the supply voltage source VI.
  • the first output of the field effect transistor preamplifier M1 is connected to the input of a receiver FM1 and, via a parallel circuit comprising an inductor L15 and a resistor R30, to the positive pole of the supply voltage source VI, which is connected via resistor R32 and in series with resistor R23 to the second Input of the field effect transistor preamplifier Ml is connected.
  • the second input of the field effect transistor preamplifier M1 is connected via a capacitance 014 to the negative pole of the supply voltage source VI.
  • the one connection of the parallel circuit from the secondary winding L4 of the transformer Kl and the Resistor R12 and the second output of the field effect transistor preamplifier M1 are also connected to the negative pole of the supply voltage source VI.
  • Parallel to the secondary winding L5 of the transformer K3 are a resistor R19 and a series connection of two capacitances Ol 1 and C12, their common connection point with the first input of a field effect transistor preamplifier M3 and via a resistor R25 and in parallel therewith via a capacitor 019 with the negative pole of the supply voltage source VI is connected.
  • the first output of the field effect transistor preamplifier M3 is connected to the input of a receiver WB and, via a parallel circuit comprising an inductor L14 and a resistor R31, to the positive pole of the supply voltage source VI.
  • the positive pole of the supply voltage source VI is connected to the negative pole of the supply voltage source VI via a series connection of resistors R3 and R4.
  • the positive pole of the supply voltage source VI is likewise connected to the negative pole of the supply voltage source VI via a series circuit comprising the resistor R32 and a resistor R34.
  • the positive pole of the supply voltage source VI is connected via a series circuit comprising the resistor R32 and a resistor R24 to the second input of the field effect transistor pre-stage M3, which is connected to the negative pole of the supply voltage source VI via a capacitance C13.
  • the second output of the field effect transistor preamplifier M3 is connected to the negative pole of the supply voltage source VI.
  • a first voltage Uabs2 representing the received field strength can be tapped off via a resistor R21, while at the common node of the two diodes D1 and D3 a second voltage Uabsl representing the received field strength can be tapped off via a resistor R20.
  • diodes D2 and D4 and D1 and D3 are tuning diodes which, together with the associated secondary winding L7 and L4, each form an oscillating circuit for tuning.
  • the base of the transistor Q28 is connected via a capacitance C1 to the negative pole of the supply voltage source VI, which serves as a reference potential.
  • the two receivers FM1 and FM2 are the search and the playback receiver of the car radio shown in FIG. As in the exemplary embodiments depicted in FIGS. 2 and 3, the role of the two receivers FM1 and FM2 can be defined. The two receivers can also switch roles as search and playback receivers.
  • the receiver WB is a weather band receiver whose reception band is 155 MHz, while the reception range of the two receivers FM1 and FM2 in the same reception band is 100 MHz.
  • the inductance L1 and the capacitance 03 which are in the form of a bandpass before the emitter of the transistor Q28, filter out the reception band for the two receivers FM1 and FM2.
  • the series connection of inductance L2 and capacitance C10 which is also connected upstream of the emitter of transistor Q28, forms the bandpass for the weather band receiver WB.
  • the parallel connection of the first bandpass, consisting of the inductance L1 and the capacitance 03, and of the second bandpass, made up of the inductance L2 and the capacitance CIO, generates a pole point which is dimensioned in such a way that part of the aeronautical radio area is blocked, so that there is no intermodulation with the signals in the useful bands.
  • FIG. 5 shows the pass curve of the two bandpasses connected in parallel from the inductors L1 and L2 and the capacitors D3 and Cl.
  • FIG. 6 shows the selection curve of the receiver FM1 and the selection curve of the receiver FM2 of the exemplary embodiments shown in FIGS. 1 to 4.
  • the invention is characterized by a number of advantages. Almost complete decoupling is achieved despite low power consumption. No preamplifiers, attenuators or power splitters are required.
  • the search receiver searches the reception band for a better reception frequency and does not cause any audible interference with the audio playback.
  • the input resistance of the invention can be precisely adjusted and adjusted so that standing waves which are no longer disturbing are caused by a mismatch in the resistance.
  • the invention is not limited to two receivers. Rather, any number of receivers can be provided. The advantages of the invention are particularly evident in hard mobile use, for example in a motor vehicle.
  • V preamplifier VI supply voltage source

Landscapes

  • Engineering & Computer Science (AREA)
  • Computer Hardware Design (AREA)
  • Microelectronics & Electronic Packaging (AREA)
  • Computer Networks & Wireless Communication (AREA)
  • Signal Processing (AREA)
  • Input Circuits Of Receivers And Coupling Of Receivers And Audio Equipment (AREA)

Abstract

L'objectif de cette invention est d'injecter un signal d'entrée, p. ex. le signal d'antenne (AS) d'une antenne (A), dans n récepteurs (FM1 à FMn ; WM) au moyen de n transformateurs (K1 à Kn) présentant chacun un enroulement primaire (PW ; L3, L6, L13) et un enroulement secondaire (SW ; L4, L5, L7). A cet effet, un des n récepteurs (FM1 à FMn ; WB) est connecté à chaque enroulement secondaire (SW ; L4, L5, L7) des n transformateurs (K1 à Kn). Le courant d'une source de courant (S ; Q1 ; Q28), régulée par un signal d'entrée (AS), est appliqué aux enroulements primaires montés en série (PW ; L3, L6, L13) des transformateurs (K1 à Kn). De préférence, un transistor en montage à base commune (Q1 ; Q28) sert de source de courant régulable. Le signal d'entrée (AS) est appliqué à l'émetteur du transistor (Q1 ; Q28), dont le courant collecteur est appliqué aux enroulements primaires montés en série (PW ; L3, L6, L13) desdits transformateurs (K1 à Kn).
PCT/EP2003/011904 2002-11-04 2003-10-27 Procede et ensemble circuit permettant d'injecter un signal d'entree dans plusieurs recepteurs WO2004042943A1 (fr)

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
DE10251203.5 2002-11-04
DE2002151203 DE10251203B3 (de) 2002-11-04 2002-11-04 Verfahren und Schaltungsanordnung zum Einspeisen eines Eingangssignales in n Empfänger

Publications (1)

Publication Number Publication Date
WO2004042943A1 true WO2004042943A1 (fr) 2004-05-21

Family

ID=32308469

Family Applications (1)

Application Number Title Priority Date Filing Date
PCT/EP2003/011904 WO2004042943A1 (fr) 2002-11-04 2003-10-27 Procede et ensemble circuit permettant d'injecter un signal d'entree dans plusieurs recepteurs

Country Status (2)

Country Link
DE (1) DE10251203B3 (fr)
WO (1) WO2004042943A1 (fr)

Cited By (2)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
WO2008069785A1 (fr) * 2006-12-05 2008-06-12 Thomson Licensing Appareil d'éclatement actif de signal distribué
EP2230762A3 (fr) * 2006-12-05 2010-12-29 Thomson Licensing Appareil de séparation de signal actif distribué

Citations (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
FR763800A (fr) * 1932-12-14 1934-05-07 Dispositif de montage de plusieurs appareils récepteurs radioélectriques sur une antenne commune
US3832647A (en) * 1973-11-13 1974-08-27 Bell Telephone Labor Inc Signal distribution network
GB2121650A (en) * 1982-04-01 1983-12-21 Clarion Co Ltd Apparatus for receiving broadcast waves

Family Cites Families (6)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US1688036A (en) * 1924-08-05 1928-10-16 Western Electric Co Radiant-energy-transmission system
US1957519A (en) * 1931-12-18 1934-05-08 Bell Telephone Labor Inc Multiple radio receiving system
US2788495A (en) * 1953-07-09 1957-04-09 Du Mont Allen B Lab Inc Coupling circuit
US3094668A (en) * 1959-02-20 1963-06-18 Trak Electronics Company Inc Isolator system providing low attenuation for input signals and extremely high attenuation for signals attempting to pass in the reverse direction
DE2443582C3 (de) * 1974-09-12 1979-04-26 Blaupunkt-Werke Gmbh, 3200 Hildesheim Ankoppelschaltung eines Zweitgerätes an die Antenne eines Autorundfunkempfängers
DE20007619U1 (de) * 2000-04-27 2001-08-30 Krauss Maffei Wegmann Gmbh & C Einrichtung zur Reduktion der Antennenanzahl an einem Kampffahrzeug

Patent Citations (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
FR763800A (fr) * 1932-12-14 1934-05-07 Dispositif de montage de plusieurs appareils récepteurs radioélectriques sur une antenne commune
US3832647A (en) * 1973-11-13 1974-08-27 Bell Telephone Labor Inc Signal distribution network
GB2121650A (en) * 1982-04-01 1983-12-21 Clarion Co Ltd Apparatus for receiving broadcast waves

Cited By (2)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
WO2008069785A1 (fr) * 2006-12-05 2008-06-12 Thomson Licensing Appareil d'éclatement actif de signal distribué
EP2230762A3 (fr) * 2006-12-05 2010-12-29 Thomson Licensing Appareil de séparation de signal actif distribué

Also Published As

Publication number Publication date
DE10251203B3 (de) 2004-08-19

Similar Documents

Publication Publication Date Title
DE3047288A1 (de) Empfangswiedergabesystem
EP1748567A2 (fr) Récepteur radio
DE102008048986B4 (de) Antennenverstärker und Empfangssystem
DE3903262C2 (fr)
DE2428880A1 (de) Fm-am-rundfunkempfaenger
DE2709575A1 (de) Hochfrequenz-sender-empfaenger
EP1405370B1 (fr) Ensemble de raccordement d'antenne, separateur de signaux d'antenne et procede pour reguler une frequence de reception
DE10251203B3 (de) Verfahren und Schaltungsanordnung zum Einspeisen eines Eingangssignales in n Empfänger
DE69832635T2 (de) Antennenschaltung
DE2902616C3 (de) UKW-Empfänger, insbesondere Autoempfänger, mit feldstärkeabhängiger Lautstärkesteuerung
DE2553211C2 (de) Ankoppelschaltung zum Betrieb von zwei Rundfunkempfängern mit einer einzigen Antenne
DE2830047C2 (de) Großsignalfester Autoantennenverstärker
DE4307014B4 (de) Vorrichtung und Verfahren zum Empfang von Rundfunksignalen
DE2142071A1 (de) Sprechfunksystem
EP1110317B1 (fr) Appareil de reception radio
DE3324959A1 (de) Empfangsschaltung fuer ein raumdiversity-verfahren
DE2453354C3 (de) Verkehrsrundfunksystem
DE921334C (de) Abgestimmte Verstaerkerschaltung mit einer Schirmgitterroehre
DE963613C (de) Kombinierter Fernseh- und UKW-Rundfunkempfaenger
DE2907611C2 (de) Empfängerauswahlautomatik für Funkzentralen
DE3017781C2 (fr)
EP1271790B1 (fr) Récepteur radio
DE1766081C3 (de) Verfahren zur exakten Abstimmung eines Überlagerungsempfängers
DE934706C (de) Fernseh- und UKW-Rundfunkempfangsgeraet
DE943654C (de) Funktechnische Empfangseinrichtung, insbesondere fuer Peiler mit Mehrantennensystem

Legal Events

Date Code Title Description
AK Designated states

Kind code of ref document: A1

Designated state(s): JP US

AL Designated countries for regional patents

Kind code of ref document: A1

Designated state(s): AT BE BG CH CY CZ DE DK EE ES FI FR GB GR HU IE IT LU MC NL PT RO SE SI SK TR

121 Ep: the epo has been informed by wipo that ep was designated in this application
122 Ep: pct application non-entry in european phase
NENP Non-entry into the national phase

Ref country code: JP

WWW Wipo information: withdrawn in national office

Country of ref document: JP