WO2003009465A1 - Circuit melangeur - Google Patents
Circuit melangeur Download PDFInfo
- Publication number
- WO2003009465A1 WO2003009465A1 PCT/JP2001/006062 JP0106062W WO03009465A1 WO 2003009465 A1 WO2003009465 A1 WO 2003009465A1 JP 0106062 W JP0106062 W JP 0106062W WO 03009465 A1 WO03009465 A1 WO 03009465A1
- Authority
- WO
- WIPO (PCT)
- Prior art keywords
- transistor
- signal
- input
- electrode
- transistors
- Prior art date
Links
Classifications
-
- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03D—DEMODULATION OR TRANSFERENCE OF MODULATION FROM ONE CARRIER TO ANOTHER
- H03D7/00—Transference of modulation from one carrier to another, e.g. frequency-changing
- H03D7/14—Balanced arrangements
- H03D7/1425—Balanced arrangements with transistors
-
- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03D—DEMODULATION OR TRANSFERENCE OF MODULATION FROM ONE CARRIER TO ANOTHER
- H03D7/00—Transference of modulation from one carrier to another, e.g. frequency-changing
- H03D7/14—Balanced arrangements
- H03D7/1425—Balanced arrangements with transistors
- H03D7/1433—Balanced arrangements with transistors using bipolar transistors
-
- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03D—DEMODULATION OR TRANSFERENCE OF MODULATION FROM ONE CARRIER TO ANOTHER
- H03D7/00—Transference of modulation from one carrier to another, e.g. frequency-changing
- H03D7/14—Balanced arrangements
- H03D7/1425—Balanced arrangements with transistors
- H03D7/1441—Balanced arrangements with transistors using field-effect transistors
-
- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03D—DEMODULATION OR TRANSFERENCE OF MODULATION FROM ONE CARRIER TO ANOTHER
- H03D7/00—Transference of modulation from one carrier to another, e.g. frequency-changing
- H03D7/14—Balanced arrangements
- H03D7/1425—Balanced arrangements with transistors
- H03D7/1458—Double balanced arrangements, i.e. where both input signals are differential
-
- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03D—DEMODULATION OR TRANSFERENCE OF MODULATION FROM ONE CARRIER TO ANOTHER
- H03D2200/00—Indexing scheme relating to details of demodulation or transference of modulation from one carrier to another covered by H03D
- H03D2200/0001—Circuit elements of demodulators
- H03D2200/0025—Gain control circuits
Definitions
- the present invention relates to a mixer circuit, and more particularly, to a direct conversion mixer used for mobile communication.
- FIG. 5 is a circuit diagram showing an example of an even harmonic mixer using a conventional transistor.
- the collectors and emitters of transistors 1 and 2 are connected to each other to form a local frequency doubler.
- a resistor R1 is connected between the collector and the power supply, and a resistor R2 is connected between the emitter and ground.
- a modulated wave signal BB is input to each of the emitters of the transistors 1 and 2, and a signal having a frequency component of a local oscillation wave whose phase is inverted is LO / i LO (i is an inverted signal). Is input.
- twice the local oscillation frequency component is generated in the local frequency multiplication unit, and the desired frequency component can be extracted by multiplying the frequency of the input signal by the local oscillation frequency component.
- the even harmonic mixer shown in FIG. 5 has a small power gain and requires a high local oscillation wave input to operate the local frequency doubling section. Disclosure of the invention
- a main object of the present invention is to provide a mixer circuit suitable for applications requiring a low-frequency current, an IC yield, and a simplified system configuration in the field of high-frequency wireless communication.
- the first and second transistors to which a frequency component signal of a local oscillation wave is input to an input electrode thereof and a second transistor to which a signal having a phase opposite to the local oscillation wave are input are respectively provided.
- a second electrode is configured to be connected to each other, and a local frequency doubler for outputting a modulation signal from the first electrode of each transistor, and a pair for the first and second transistors of the local frequency doubler.
- a third transistor that receives a reference signal at its input electrode and differentially outputs a modulation signal from its first electrode; and a third transistor that outputs the first, second, and third transistors.
- the mixer circuit is formed.
- the modulated wave signal is input to its input electrode, and the first electrode is connected to each of the second electrodes of the first, second, and third transistors.
- the second electrode is the fourth transistor connected to a constant current source
- a local frequency doubler two sets of a local frequency doubler, a third transistor and a fourth transistor for reference are provided, a voltage source is commonly connected to the two sets of local frequency doublers, and a constant current source is provided in two sets. A constant current is commonly supplied to the fourth transistor.
- the constant current source is a variable constant current source.
- variable current source for varying a bias current applied to the input electrode of the third transistor is provided.
- FIG. 1 is a circuit diagram of a mixer circuit according to one embodiment of the present invention.
- FIG. 2 is a circuit diagram of another embodiment of the present invention.
- FIG. 3 is a circuit diagram showing another embodiment of the present invention.
- FIG. 4 is a circuit diagram showing still another embodiment of the present invention.
- FIG. 5 is a circuit diagram showing an example of an even harmonic mixer using a conventional transistor. BEST MODE FOR CARRYING OUT THE INVENTION
- FIG. 1 is a circuit diagram of a mixer circuit according to one embodiment of the present invention.
- the collectors of the transistors 1 and 2 and the emitter are connected to each other, and power is supplied to each collector via the resistor R 3, as in FIG. 5 of the conventional example.
- the component signal LO ⁇ LO is input to the bases of the transistors 1 and 2 to form the local frequency multiplier 10.
- the local frequency multiplying unit 10 generates a frequency twice as high as the local oscillation frequency in the same manner as the even harmonic mixer.
- the emitters of the transistors 1 and 2 are connected to the emitter of the reference transistor 3, and the collector of the reference transistor 3 is connected to the power supply via the resistor R4.
- a bias current (R e f.) Is given to the base of the reference transistor 3.
- the resistors R3 and R4 constitute the load section 6 serving as a voltage source, but other loads may be connected instead of the resistors R3 and R4.
- the emitters of the transistors 1, 2 and 3 are connected to the collector of the modulated wave input transistor 4, and a constant current is supplied from the constant current source 5 to the emitters.
- the modulated wave signal BB is input to the base of the modulated wave input transistor 4.
- the sum of the current flowing through the local frequency multiplier 10 composed of the transistors 1 and 2 and the current flowing through the reference transistor 3 is equal to the current flowing through the modulated wave input transistor 4. equal.
- the current flowing through the transistor 4 is equal to the constant current of the constant current source 5. Therefore, by giving the transistor 4 a gain, a mixer circuit having a gain can be realized.
- the double frequency generated by the local frequency multiplier 10 composed of., 2 fluctuates the current of the local frequency multiplier 10. Since the transistor 4 performs a constant current operation for the local frequency multiplier 10 and the transistor 3, a change in the fluctuated current results in a current of the opposite phase flowing to the transistor 3.
- the transistor 4 has a gain with respect to the modulated wave input, and the amplified signal is frequency-converted in the local frequency multiplier 10.
- the frequency-converted signal is output from the load unit 6 as a differential output signal RF / ⁇ RF.
- the local frequency multiplication unit 10 including the transistors 1 and 2 and the modulated wave input unit including the transistor 4 are provided with the local frequency multiplication unit 10.
- a high-gain mixer circuit can be realized without increasing the input level of the local oscillation wave.
- FIG. 2 is a circuit diagram of another embodiment of the present invention.
- the local frequency doubler 10 and transistors 3 and 4 are configured in the same manner as shown in FIG.
- the local frequency doubler 20 and transistors 9, 1 1 have the same configuration as the mixer circuit shown in FIG. That is, the collector of the transistor 7 and the collector of the transistor 8, the emitter of the transistor 7 and the emitter of the transistor 8 are connected respectively, and the frequency component signals LO and i LO of the local oscillation wave are input to the bases of the transistors 7 and 8, respectively. Is done.
- the emitters of the transistors 7 and 8 are connected to the emitter of the reference transistor 9, and the base of the reference transistor 9 is supplied with a bias current.
- the emitters of the transistors 7, 8 and 9 are connected to the collector of the modulated wave input transistor 11.
- the base of the transistor 11 receives the modulated wave signal BB having a phase opposite to that of the modulated wave signal BB input to the base of the transistor 4.
- Each collector of the local frequency multiplying unit 20 is connected to each collector of the local frequency multiplying unit 10, and each collector is commonly supplied with power via the resistor R 3.
- the collector of the transistor 9 is connected to the collector of the transistor 3, and power is supplied via the respective resistors R4.
- Transistor 1 1 emitter is the same as transistor 4 emitter Are connected to the constant current source 5 in common. That is, the mixer circuit shown in FIG. 2 has a configuration in which the mixer circuit shown in FIG. 1 is made into a Gilbert cell.
- each mixer circuit having the same configuration as that of FIG. 1 has a high gain as described above, and furthermore, by realizing the Gilbert cell configuration, the local oscillator leaking to the output side can be realized.
- a mixer circuit capable of suppressing a frequency component of a wave can be realized.
- FIG. 3 is a circuit diagram showing another embodiment of the present invention. In this embodiment, a variable current source 12 is provided in place of the constant current source 5 shown in FIG. 1, and a variable gain control effect can be obtained.
- FIG. 4 is a circuit diagram showing still another embodiment of the present invention.
- a variable current source 13 is connected to the base of the reference transistor 3 shown in FIG. 1 to vary a bias current, and a variable gain control effect can be obtained.
- the mixer circuit that outputs the modulated wave signal by mixing the frequency component of the local oscillation wave and the modulated wave signal BB has been described, but the radio frequency signal received as the modulated wave signal is input.
- a baseband signal may be output as a modulation signal by mixing with the frequency component of the local oscillation wave.
- a bipolar transistor is used.
- a field effect transistor may be used. .
- a reference transistor is provided and a differential mixer is formed, thereby achieving a high-gain system configuration. Can be easily realized.
- constant current control there is little dependence on variations in semiconductor processes, and it is possible to reduce power supply voltage fluctuations and temperature fluctuations by configuring the constant current flow source with a small bandgap.
- the mixer circuit of the present invention combines the advantages of the conventional mixer circuit and the advantages of the even harmonic mixer, thereby activating the even harmonic mixer and providing a high gain mixer circuit without affecting the carrier component. It can be realized and applicable to mobile communication that modulates directly from baseband signal to radio frequency.
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- Engineering & Computer Science (AREA)
- Power Engineering (AREA)
- Superheterodyne Receivers (AREA)
- Amplitude Modulation (AREA)
Description
Claims
Priority Applications (5)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
JP2002589145A JP4040473B2 (ja) | 2001-07-12 | 2001-07-12 | ミキサ回路 |
CNA018209343A CN1481605A (zh) | 2001-07-12 | 2001-07-12 | 混频电路 |
PCT/JP2001/006062 WO2003009465A1 (fr) | 2001-07-12 | 2001-07-12 | Circuit melangeur |
EP01949963A EP1406380A1 (en) | 2001-07-12 | 2001-07-12 | Mixer circuit |
US10/450,819 US6759887B2 (en) | 2001-07-12 | 2001-07-12 | Mixer circuit |
Applications Claiming Priority (1)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
PCT/JP2001/006062 WO2003009465A1 (fr) | 2001-07-12 | 2001-07-12 | Circuit melangeur |
Publications (1)
Publication Number | Publication Date |
---|---|
WO2003009465A1 true WO2003009465A1 (fr) | 2003-01-30 |
Family
ID=11737541
Family Applications (1)
Application Number | Title | Priority Date | Filing Date |
---|---|---|---|
PCT/JP2001/006062 WO2003009465A1 (fr) | 2001-07-12 | 2001-07-12 | Circuit melangeur |
Country Status (5)
Country | Link |
---|---|
US (1) | US6759887B2 (ja) |
EP (1) | EP1406380A1 (ja) |
JP (1) | JP4040473B2 (ja) |
CN (1) | CN1481605A (ja) |
WO (1) | WO2003009465A1 (ja) |
Cited By (4)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
US7002396B2 (en) | 2002-03-15 | 2006-02-21 | Mitsubishi Denki Kabushiki Kaisha | Frequency converter |
JP2015053583A (ja) * | 2013-09-06 | 2015-03-19 | 株式会社デンソー | 高調波ミキサ |
US9050372B2 (en) | 2000-06-30 | 2015-06-09 | Regents Of The University Of Minnesota | High molecular weight derivatives of vitamin K-dependent polypeptides |
JP2016178414A (ja) * | 2015-03-19 | 2016-10-06 | 三菱電機株式会社 | 高周波ミクサ |
Families Citing this family (9)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
US20020102958A1 (en) * | 2001-01-29 | 2002-08-01 | Buer Kenneth V. | Sub-harmonically pumped k-band mixer utilizing a conventional ku-band mixer IC |
US7358121B2 (en) * | 2002-08-23 | 2008-04-15 | Intel Corporation | Tri-gate devices and methods of fabrication |
US20050176398A1 (en) * | 2002-08-23 | 2005-08-11 | Kenichi Maeda | Mixer circuit |
US7965994B2 (en) * | 2004-10-29 | 2011-06-21 | Broadcom Corporation | Method and system for an analog zero-IF interface for GSM receivers |
US20080094107A1 (en) * | 2006-10-20 | 2008-04-24 | Cortina Systems, Inc. | Signal magnitude comparison apparatus and methods |
US20080284489A1 (en) * | 2007-05-14 | 2008-11-20 | Mediatek Singapore Pte Ltd | Transconductor and mixer with high linearity |
KR101466851B1 (ko) * | 2008-12-30 | 2014-11-28 | 주식회사 동부하이텍 | 3개 입력들을 비교하는 비교 회로 |
CN103117709B (zh) * | 2013-02-05 | 2016-05-25 | 天津大学 | 一种基于对数放大器的混频器 |
US10141930B2 (en) | 2013-06-04 | 2018-11-27 | Nvidia Corporation | Three state latch |
Citations (3)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
JPH02190011A (ja) * | 1989-01-18 | 1990-07-26 | Nec Corp | ダブルバランスミキサ半導体集積回路 |
JPH10224152A (ja) * | 1997-02-05 | 1998-08-21 | Nec Corp | バランス型ミキサのミキシング方法と回路 |
JP2000101353A (ja) * | 1998-06-30 | 2000-04-07 | Toshiba Corp | 周波数変換器 |
Family Cites Families (2)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
US5936466A (en) * | 1997-08-04 | 1999-08-10 | International Business Machines Corporation | Differential operational transconductance amplifier |
US6631257B1 (en) * | 2000-04-20 | 2003-10-07 | Microtune (Texas), L.P. | System and method for a mixer circuit with anti-series transistors |
-
2001
- 2001-07-12 CN CNA018209343A patent/CN1481605A/zh active Pending
- 2001-07-12 EP EP01949963A patent/EP1406380A1/en not_active Withdrawn
- 2001-07-12 US US10/450,819 patent/US6759887B2/en not_active Expired - Fee Related
- 2001-07-12 JP JP2002589145A patent/JP4040473B2/ja not_active Expired - Fee Related
- 2001-07-12 WO PCT/JP2001/006062 patent/WO2003009465A1/ja not_active Application Discontinuation
Patent Citations (3)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
JPH02190011A (ja) * | 1989-01-18 | 1990-07-26 | Nec Corp | ダブルバランスミキサ半導体集積回路 |
JPH10224152A (ja) * | 1997-02-05 | 1998-08-21 | Nec Corp | バランス型ミキサのミキシング方法と回路 |
JP2000101353A (ja) * | 1998-06-30 | 2000-04-07 | Toshiba Corp | 周波数変換器 |
Cited By (4)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
US9050372B2 (en) | 2000-06-30 | 2015-06-09 | Regents Of The University Of Minnesota | High molecular weight derivatives of vitamin K-dependent polypeptides |
US7002396B2 (en) | 2002-03-15 | 2006-02-21 | Mitsubishi Denki Kabushiki Kaisha | Frequency converter |
JP2015053583A (ja) * | 2013-09-06 | 2015-03-19 | 株式会社デンソー | 高調波ミキサ |
JP2016178414A (ja) * | 2015-03-19 | 2016-10-06 | 三菱電機株式会社 | 高周波ミクサ |
Also Published As
Publication number | Publication date |
---|---|
US6759887B2 (en) | 2004-07-06 |
CN1481605A (zh) | 2004-03-10 |
EP1406380A1 (en) | 2004-04-07 |
US20040027187A1 (en) | 2004-02-12 |
EP1406380A8 (en) | 2004-07-21 |
JP4040473B2 (ja) | 2008-01-30 |
JPWO2003009465A1 (ja) | 2004-11-11 |
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